TWI220081B

TWI220081B - Control method and device for discontinuous current mode power factor corrector

Info

Publication number: TWI220081B
Application number: TW92116191A
Authority: TW
Inventors: You-Gang Luo
Original assignee: Univ Nat Taiwan Science Tech
Priority date: 2003-06-13
Filing date: 2003-06-13
Publication date: 2004-08-01
Also published as: TW200428736A

Abstract

The present invention provides a control method for discontinuous current mode power factor corrector, which is applied in an AC/DC conversion for controlling the switching frequency or switching period of a switch to control the power factor corrector for generating a stable output voltage. The method comprises first calculating the absolute value of an input voltage; dividing the absolute value of the input voltage by the output voltage to generate a control signal; then, comparing the output voltage with a reference voltage to generate a differential voltage signal; next, converting the differential voltage signal into a triangular carrier frequency signal; and finally, comparing the differential voltage signal with the triangular carrier frequency signal to generate the switching frequency or the switching period of the switch to achieve the purpose of using the switching frequency or switching period to generate the stable voltage for obtaining the maximum output voltage and the highest input power factor.

Description

1220081 五、發明說明（1) 【發明所屬之技術領域】本發明係為一種不連績電流模式功率因數修正器控制方法及裝置，特別是關於一種切換頻率的控制方法，應用於單開關升壓型整流器之輸出電壓調節或穩壓控制。【先前技術】按，隨著工業的快速發展及能源的日益減少，人們越來越重視電力的品質與使用效率，一般交流對直流 (A C / D C)的電力轉換大都以-一極體橋式整流器等所組成，該二極體橋式整流器雖然具有低成本、架構簡單以及堅固 0 的優點，但由於其輸入電流相對於輸入電壓的正弦波而言，具有相當高的諳波失真，如第一圖所示，係為習知二極體全橋整流的電壓Vs與電流I s波形圖，其中CH1為電壓波形（10V/DIV)，CH2為電流波形（100mA/DIV)，如此畸變的電流波形對於電力系統而言，將會導致功率因數（Power f a c t 〇 r，P F )偏低，而降低整個電力供應系統的電力品質。因此為提高整個電路的功率因數，會在二極體整流之後加裝一具有開關元件之轉換器，一般稱之為單開關升壓型整流器（Single-Switch Boost Rectifier)，如第二圖 _ 所示，係為傳統單開關升壓型整流器之電路圖，利用開關的切換使得電源電流能夠追蹤電源電壓以提高功率因數，降低電流之諧波成分，然而該種升壓型整流器通常只操作在連續傳導模式（Continuous Conduction Mode)，於小功1220081 V. Description of the invention (1) [Technical field to which the invention belongs] The present invention relates to a method and device for controlling non-continuous current mode power factor corrector, in particular to a method for controlling switching frequency, which is applied to single-switch boost Output rectifier or voltage regulation control. [Previous technology] According to the rapid development of industry and the dwindling energy, people pay more and more attention to the quality and efficiency of electricity. Generally, most of the AC to DC (AC / DC) power conversion is based on a -polar bridge. Composed of rectifiers, although this diode bridge rectifier has the advantages of low cost, simple structure, and ruggedness, but its input current has a relatively high chirp distortion compared to the sine wave of the input voltage. The figure shows the voltage Vs and current Is s waveforms of the conventional diode full-bridge rectification, where CH1 is the voltage waveform (10V / DIV) and CH2 is the current waveform (100mA / DIV). Such a distorted current For the power system, the waveform will cause the power factor (PF) to be low, and reduce the power quality of the entire power supply system. Therefore, in order to improve the power factor of the entire circuit, a converter with a switching element is added after the diode rectification, which is generally called a single-switch boost rectifier (Single-Switch Boost Rectifier). This is a circuit diagram of a traditional single-switch boost rectifier. The switching of the switch enables the power supply current to track the power supply voltage to increase the power factor and reduce the harmonic components of the current. However, this type of boost rectifier usually only operates in continuous conduction. Mode (Continuous Conduction Mode)

第5頁 1220081 五、發明說明（2) ^應用場合下才會使用不連續電在不連續傳導模式（DiscorUinu〇us 式右疋細作下，备筮—门 ^nuous Conduction Mode) -★皆波失：ΐ即為傳統不連續電流模式之波形示意圖，其真，…切換頻率倍數附近的低次- 切車'=對該升壓型整流器操作在不連續電流模式下的功率因數修正器（Power Factor correct〇r, pfc)，以下簡稱升壓型PFC，雖然可以將電路的功率因數提高至大於〇. 99的程度，但其電路通常相當地複雜，以致增加了整個電路的體積以及成本’例如使用二個以上的升壓型PFC來組合電路的輸入電流，以提南其功率因數的控制等。職是’本案發明人即為解決上述現有升壓型PFC所具有不便與缺失，乃特潛心研究並配合學理之運用，提出/一種新式之切換頻率控制方法及裝置，可將該升壓型p F ^桑作在不連續傳導模式，以及連續模式之邊界模式，有效提高其功率因數的控制及抑制輸入電流低次諧波量並可調壓’係為一設計合理且有效善上述缺失之發明。【發明内容】本發明係提供以下之技術手段來達成在不連續電流模式下控制功率因數修正器之切換頻率或切換週期，產生穩定之輪出電壓，並得到最大輸出電壓與最高輸入功率因數Page 5 1220081 V. Description of the invention (2) ^ Discontinuous electricity will only be used in the application occasions. In discontinuous conduction mode (DiscorUinu〇us type, right-handed preparation, prepare-gate ^ nuous Conduction Mode)-★ all wave loss : Ϊ́ is the waveform diagram of the traditional discontinuous current mode. It is true that ... the low order near the switching frequency multiple-cut-off '= Power Factor Corrector (Power Factor) operated in the discontinuous current mode for the boost rectifier. correct〇r, pfc), hereinafter referred to as boost PFC, although the power factor of the circuit can be increased to a level greater than 0.99, but its circuit is usually quite complicated, which increases the size and cost of the entire circuit. Two or more boost-type PFCs are used to combine the input current of the circuit to improve the control of its power factor. "The inventor of this case is to solve the inconveniences and defects of the existing booster PFC mentioned above. He has devoted himself to research and cooperated with the application of science to propose / a new type of switching frequency control method and device. F ^ Sang Zuo in the discontinuous conduction mode and the boundary mode of the continuous mode, effectively improve the control of its power factor and suppress the amount of low-order harmonics of the input current and adjust the voltage is a reasonable design and effective invention . [Summary of the Invention] The present invention provides the following technical means to control the switching frequency or switching period of the power factor corrector in the discontinuous current mode, to generate a stable wheel-out voltage, and obtain the maximum output voltage and the maximum input power factor

1220081 五、發明說明（3) 之目的：本發明之主要技術特徵係在於提供一種不連續電流模式功率因數修正器控制方法，係應用於一交/直流電力轉換，藉由控制一切換開關之切換頻率或切換週期，控制該功率因數修正器產生穩定之輸出電壓，該方法首先計算一輸入電壓之絕對值，將該輸入電壓之絕對值除以該輸出電壓產生一控制信號，再比較該輸出電壓及一參考電壓產生一差值電壓信號，接著轉換該差值電壓信號為一三角載波頻率信號，最後比較該差值電壓信號及該三角載波頻率信號，產生該切換開關之切換頻率或切換週期，達成以該切換換頻率或切換週期產生穩定電壓之功效。本發明之次一技術特徵係在於提供一種不連續電流模式功率因數修正器控制裝置，係應用於一交直流電力轉換，藉由控制一切換開關之切換頻率或切換週期，控制該功率因數修正器之產生穩定之輸出電壓，該裝置包括一絕對值運算器，用以將該輸入電壓作一絕對值運算，一類比除法器係將該輸入電壓絕對值除以該輸出電壓，產生一控制信號，一第一比較器比較該輸出電壓及該參考電壓產生一差值電壓信號，一電壓頻率轉換器可藉該差值電壓信號轉換為一三角載波頻率信號，一第二比較器用以比較該控制信號與該三角載波頻率信號，控制該切換開關之切換頻率，以達成產生穩定電壓輸出之功效。【實施方式】1220081 V. Purpose of the invention (3): The main technical feature of the present invention is to provide a discontinuous current mode power factor corrector control method, which is applied to an AC / DC power conversion by controlling the switching of a switch Frequency or switching period to control the power factor corrector to generate a stable output voltage. The method first calculates the absolute value of an input voltage, divides the absolute value of the input voltage by the output voltage to generate a control signal, and then compares the output voltage. And a reference voltage to generate a differential voltage signal, then convert the differential voltage signal into a triangular carrier frequency signal, and finally compare the differential voltage signal and the triangular carrier frequency signal to generate a switching frequency or switching period of the switch, It achieves the effect of generating a stable voltage with the switching frequency or switching period. A second technical feature of the present invention is to provide a discontinuous current mode power factor corrector control device, which is applied to an AC / DC power conversion and controls the power factor corrector by controlling the switching frequency or switching period of a switch. To generate a stable output voltage, the device includes an absolute value calculator for performing an absolute value operation on the input voltage. An analog divider divides the absolute value of the input voltage by the output voltage to generate a control signal. A first comparator compares the output voltage and the reference voltage to generate a difference voltage signal. A voltage-frequency converter can convert the difference voltage signal into a triangular carrier frequency signal. A second comparator is used to compare the control signal. And the triangular carrier frequency signal to control the switching frequency of the switch to achieve the effect of generating a stable voltage output. [Embodiment]

第7頁丄以圓丄Page 7 丄 Yu Yuan 丄

進一步暸解本發明為達成預功效，請參閱以下有關本發發明之目的、特徵與特點，解，然而所附圖式僅提供參明加以限制者。本發明之升壓型PFC電路體（MOSFET)作為該升壓型是藉由該SW1的導通與截蹤輸入電壓的波形，以獲得為了使貴審查委員能更定目的所採取之技術、手段及明之詳細說明與附圖，相^ 當可由此得一深入且具體:瞭考與說明用，並非用來對本發請參閱第四圖所示，係為圖。本發明係利用一場效電晶 PFC電路之切換開關SW1，主= 止，控制輸入電流的波形去追高功率因數。由於輸入電壓v為60Hz之弦波信號，輸入電流丄烽值會隨著輸入電，V之瞬間值而變化，故可將該輸入電流“ 視為許多不連績之三角脈波所組成。而該SW1的切換頻率通常為數十或數百kHz以上’遠大於輸入電源之頻率 6 0Hz，因此在該SW1的每一個切換週期内，其輸入電壓Vs可視為定值’在此切換期間内之升壓型pFc電路可視為一種 DC/DC的直流轉換器。其中當該輸入電壓v為正時，SW1導通，則電感器l上的電壓v l為正值’電感電流i從隨時間直線上升，若s⑺1截止時’則電感益L上的電壓v L為負值，電感電流i從最高點隨時間直線下降至零’當該輸入電壓vS為負時，因前端橋式整流器之整心L作用其電或器L上的電壓v L電流i值相同於正半週。因此使得電感電流i L( = I i si )在每一個切換週期内的最For further understanding of the present invention in order to achieve pre-effects, please refer to the following objects, features, and characteristics of the present invention, but the drawings are only provided for reference and are limited. The step-up PFC circuit body (MOSFET) of the present invention, as the step-up type, uses the turn-on and truncated input voltage waveforms of the SW1 to obtain the technology, means, and The detailed description of the Ming and the drawings can be obtained in depth and specificity: for the purpose of examination and explanation, it is not used to refer to the fourth figure shown in this issue. It is a diagram. The invention uses a switching switch SW1 of the PFC circuit of a field effect transistor to control the waveform of the input current to track the high power factor. Since the input voltage v is a 60Hz sine wave signal, the value of the input current will change with the instantaneous value of the input voltage and V. Therefore, the input current can be regarded as consisting of many non-continuous triangle pulses. The switching frequency of the SW1 is usually tens or hundreds of kHz or more. 'Much greater than the frequency of the input power source 60Hz. Therefore, in each switching cycle of the SW1, its input voltage Vs can be regarded as a fixed value.' During this switching period The step-up pFc circuit can be regarded as a DC / DC converter. When the input voltage v is positive and SW1 is turned on, the voltage vl on the inductor l is positive. The inductor current i rises linearly with time. If s⑺1 is cut off, then the voltage v L on the inductor L is negative, and the inductor current i decreases linearly from zero to zero over time. When the input voltage vS is negative, it is due to the centering effect of the front-end bridge rectifier. The voltage v L current i of the electric OR device L is the same as the positive half cycle. Therefore, the maximum value of the inductor current i L (= I i si) in each switching cycle is

1220081 五、發明說明（5) 高點會追隨輸入電壓絕對值I v si的波形，換言之，輪入電流i缒隨輸入電壓v妁波形，而實現功率因數修正的目的。就實際電路或理論而言，以離散取樣的集合來表示輪入電流的峰值是非常貼切的，故本發明均以離散取樣的^ 入電流峰值為根據。別下本發明之該升壓型PFC電路上，該輸入電壓會隨著時，以正弦波的形式變化，儘管該SW1的導通時間在每一個體^ 1期中皆相同，但是在SW1截止而尚有電流流經二極正比3 Z t J卻非定值。且由於每一個切換週期内的△ J 二周，亦即輸入電壓的瞬間值。因此我們取S 不連續的邊=21趨=連續的區段來推導輪人電流連續與止的時間，即可確此，只要令（△ iTJmax小於該SW1截換§之，輸出電壓為=^ : ί作在不連續的模式 DS1^ ^ &為貝任週期的公式為：其中，D為眚权、田幅。、义期、V〇為輸出電壓、^ V m為輸入電壓振1220081 V. Description of the invention (5) The high point will follow the waveform of the absolute value of the input voltage I v si, in other words, the turn-in current i 缒 follows the waveform of the input voltage v 妁 to achieve the purpose of power factor correction. As far as the actual circuit or theory is concerned, it is very appropriate to use a set of discrete samples to represent the peak value of the in-rush current. Therefore, the present invention is based on the discretely sampled in-rush current peaks. In addition, in the step-up PFC circuit of the present invention, the input voltage will change in the form of a sine wave with time. Although the on-time of the SW1 is the same in each individual ^ 1 period, it is still off when SW1 is turned off. There is a current flowing through the poles which is proportional to 3 Z t J but is not constant. And because △ J in each switching cycle is two weeks, that is, the instantaneous value of the input voltage. Therefore, we take the discontinuous edge of S = 21 trend = continuous section to derive the continuous and stop time of the current of the wheeler, and we can confirm this. As long as (△ iTJmax is less than the SW1 cut, the output voltage is = ^ : The formula for DS1 ^^ in the discontinuous mode is: The formula of the Beren period is: where D is the right and field width., Yi period, V0 is the output voltage, and ^ V m is the input voltage.

因此在弓ISo in Bow I

Mb λα 用上述公—、乂期的輪出電厭式則，必需先求出斟處认#主/、田叫电Μ，再代八 Κ ®對應於該責任週足知作在不連娣ρ上入Α式中，即可得知告日士命玖s不戈 τ ：連績挺式的條件中。而該輪出：，路疋否滿 4叛出電壓Vo之公式如 1220081 五、發明說明（6) ΣMb λα Using the above-mentioned public-and-off-cycle electric exhaustion formula, it is necessary to first find out the office identification # 主 / 、田叫电 Μ, and then replace the eight-k ® corresponding to this responsibility. When ρ is entered into the A formula, we can know that the order of the deceased person's life is not τ: the condition of continuous success. And the turn out: Is the road line full? 4 The formula for the voltage of the defection Vo is 1220081 V. Description of the invention (6) Σ

R 0 n =1^13 …k 2·4R 0 n = 1 ^ 13… k 2 · 4

在上述之公式中，輸出電壓Vo為輸入電壓振幅Vm、責任週期D、切換頻率f s切換週期Ts、輸出負載R以及電感L 的函數，而輸入電流的有效值為：In the above formula, the output voltage Vo is a function of the input voltage amplitude Vm, the duty cycle D, the switching frequency f s the switching cycle Ts, the output load R, and the inductance L, and the effective value of the input current is:

h D^T I =7、一 ——^ rms ° V3 R^L PF-h D ^ T I = 7, one-^ rms ° V3 R ^ L PF-

3L 而輸入端的功率因數為：，DTs， m為其他參數的函數，因此計算出m值，才能算出功率因數 PF。將輸出電壓Vo公式以積分形式展開，經整理後可得： 33L and the input power factor is:, DTs, m is a function of other parameters, so the value of m can be calculated to calculate the power factor PF. The output voltage Vo formula is developed in integral form. After finishing, we can get: 3

R^T 2R ^ T 2

Fl·!9 〇 4L 3 πΐ 由上式可知，當負載電阻R變化時，雖然無法藉由調整責任週期D來穩壓，但是卻可利用改變切換頻率f s (即Ts 的倒數）來達成穩壓的目的。換言之，如果負載電阻R以及切換週期T s的乘積不變，則輸出電壓使能夠維持定值，由此推論出較高的切換頻率應該適合較輕的負載，而較重的負載則需要較低的切換頻率，藉以調節輸出電壓之用。請參閱第五圖所示，係為本發明功率因數修正器之方塊示意圖，而第六圖係為本發明功率因數修正器之控制流Fl ·! 9 〇4L 3 πΐ As can be seen from the above formula, when the load resistance R changes, although the voltage regulation cannot be adjusted by adjusting the duty cycle D, it can be achieved by changing the switching frequency fs (that is, the inverse of Ts). the goal of. In other words, if the product of the load resistance R and the switching period T s is constant, the output voltage can be maintained at a constant value. It is inferred that a higher switching frequency should be suitable for lighter loads, and a heavier load needs to be lower. The switching frequency is used to adjust the output voltage. Please refer to the fifth figure, which is a block diagram of the power factor corrector of the present invention, and the sixth figure is the control flow of the power factor corrector of the present invention.

第10頁 1220081Page 10 1220081

程圖。本發明之功率因數修正器6 〇係藉由上述之公式所導 ^的=括繞對值運算器（ABS)6卜一類比除法器（DI V) 弟比車乂裔（Comp ·) 6 3、一比例積分補償器 (PI)64、一電壓頻率轉換器（VFC)65及一第二比較器 (C 〇 m ρ ·) 6 6戶斤、、且成，其中將該輸入電壓v s經該絕對值管器61運算後得IVS|(100)，再由該類比除法器62將該丨^丨除以輸出電壓V 0即得一控制信號6 7 (J 〇 2 )。卜另外:再由該輸出電壓Vo及一參考電壓Vref之間經該第一比較器6 3之比較回授後，產生一差值電壓信號 68 ( 1 04 ) ’再經過該比例積分補償器64的補償後，送至該電壓頻率轉換恭65，產生出一可調變頻率之三角載波頻率信號6 9 ( 1 0 6 )，最後將該控制信號67與該三角載波頻率信號6 9相比較，輸出控制該8?1的切換週期（1〇8)，藉以改°變系統的切換頻率f s而達到穩壓的目的。請參閱第七圖所示，係為本發明中該電壓頻率轉換器之實施例電路圖。本發明為使該電壓頻率轉換器6 5之輸出頻率隨著該參考電壓Vref改變的同時，其輸出之三角載波 6 9的振幅必須維持不變，因此本發明可利用一 TL494控制 1C’需將内建二角波振盈裔之第5腳位連接一電容哭c至接地端，再將該第β腳位連接一電阻器R丟該比例分補償器64 之輸出端即可，亦即透過所回授的輸出電壓來改變電容器 C沐所相應的電壓，而達到切換週期或頻率隨之改變的效果。 " 請參閱第八圖至第十圖所示，係為本發明之三種不同Process map. The power factor corrector 6 of the present invention is guided by the above formula ^ = bracketed logarithmic arithmetic unit (ABS) 6 analog type divider (DI V) brother car (Comp.) 6 3 , A proportional-integral compensator (PI) 64, a voltage-to-frequency converter (VFC) 65, and a second comparator (C0m ρ ·) 6 6 kg, and it is, wherein the input voltage vs. The absolute value piper 61 calculates IVS | (100), and then the analog divider 62 divides the ^^ 丨 by the output voltage V 0 to obtain a control signal 6 7 (J 〇 2). In addition: a difference voltage signal 68 (1 04) is generated between the output voltage Vo and a reference voltage Vref through the comparison feedback of the first comparator 63 and then passes through the proportional-integral compensator 64 After the compensation, it is sent to the voltage-frequency conversion circuit 65 to generate a triangular carrier frequency signal 6 9 (1 0 6) with adjustable frequency. Finally, the control signal 67 is compared with the triangular carrier frequency signal 69. The output controls the 8? 1 switching cycle (108), thereby changing the switching frequency fs of the system to achieve the purpose of voltage stabilization. Please refer to the seventh figure, which is a circuit diagram of an embodiment of the voltage-frequency converter according to the present invention. In order to make the output frequency of the voltage-to-frequency converter 65 change with the reference voltage Vref, the amplitude of the triangular carrier 609 of the output must be kept constant. Therefore, the present invention can use a TL494 to control the 1C '. The 5th pin of the built-in dihedral wave oscillator is connected to a capacitor c to the ground terminal, and then the β pin is connected to a resistor R to lose the output of the proportional compensator 64, that is, through The feedback output voltage changes the corresponding voltage of the capacitor C to achieve the effect that the switching cycle or frequency changes accordingly. " Please refer to the eighth to tenth diagrams, which are three different types of the present invention.

1220081 —^---------- 五、發明說明（8) 負載狀況實驗下的輸出電壓及電流波形圖。其中第八圖的負載電卩且值為1.077ΚΩ ，而其切換頻率為80kHz，第九圖的負載電阻值為53〇Ω ，而其切換頻率為4〇kHz，第十圖的負載電阻值為3 3 5Ω，而其切換頻率為2β· 67kHz，然該： =載的輸出電壓均能穩壓在mv，且維持相當高的:-率職是’本發明確能藉上然不同於習知者的設計，二揭路之技術，提供一種迥申請前未見於刊物或^開使=提高整體之使用價值，又其件，爰依法提出發明專利申过’誠已符合發明專利之要惟，上述所揭露之圖式二二而已，凡精于此項技藝者當η吨明，僅為本發明之實施例之改良，而這些改變仍 2依據上述之說明作其他種種定之專利範圍中。、、本發明之發明精神及以下所界1220081 — ^ ---------- V. Description of the invention (8) Output voltage and current waveform diagram under load condition experiment. Among them, the load voltage of the eighth figure is 1.077KΩ, and its switching frequency is 80kHz. The load resistance of the ninth figure is 53Ω, and its switching frequency is 40kHz. The load resistance value of the tenth figure is 3 3 5Ω, and its switching frequency is 2β · 67kHz, then: = the output voltage of the load can be stabilized at mv, and maintained quite high:-the rate is' the present invention can indeed borrow from the conventional The author ’s design, the technique of revealing the road, provides a technology that has not been seen in the publication or application before the application = to improve the overall value of use, and other things, according to the law, the application for an invention patent application has been in line with the requirements of the invention patent, The above-disclosed schemes are only two and two. Anyone who is skilled in this art should only make improvements in the embodiments of the present invention, and these changes are still within the scope of other various patents based on the above description. The spirit of the invention and the following boundaries

第12頁 1220081 圖式簡單說明【圖式簡單說明】 (1)圖式說明：第一圖係為習知二極體全橋整流的電壓與電流波形圖 j 第二圖係為傳統單開關升壓型整流器之電路圖；第三圖係為傳統不連續電流模式之波形示意圖；第四圖係為本發明之升壓型PFC電路圖；第五圖係為本發明功率因數修正器之方塊示意圖；第六圖係為本發明功率因數修正器之控制流程圖；第七圖係為本發明中該電壓頻率轉換器之實施例電路圖，第八圖係為本發明之負載電阻值為1 · 0 7 7ΚΩ之輸出電壓及電流波形圖；第九圖係為本發明之負載電阻值為53 0Ω之輸出電壓及電流波形圖；及第十圖係為本發明之負載電阻值為3 3 5Ω之輸出電壓及電流波形圖。 (2 )主要部分之代表符號：功率因數修正器 60 絕對值運算器 61 類比除法器 62 第一比較器 63 比例積分補償器 64Page 12 1220081 Schematic description [Schematic description] (1) Schematic description: The first diagram is the voltage and current waveform diagram of the conventional diode full-bridge rectification j The second diagram is a traditional single switch The circuit diagram of the voltage-type rectifier; the third diagram is a waveform diagram of the traditional discontinuous current mode; the fourth diagram is a boost PFC circuit diagram of the present invention; the fifth diagram is a block diagram of the power factor corrector of the present invention; The sixth diagram is a control flowchart of the power factor corrector of the present invention; the seventh diagram is a circuit diagram of an embodiment of the voltage-frequency converter according to the present invention, and the eighth diagram is a load resistance value of the present invention of 1 · 0 7 7KΩ The output voltage and current waveform diagram; the ninth diagram is an output voltage and current waveform diagram with a load resistance value of 5350 Ω; and the tenth diagram is an output voltage and load impedance value with a load resistance value of 3 35 5 Current waveform diagram. (2) Representative symbols of main parts: Power factor corrector 60 Absolute value calculator 61 Analog divider 62 First comparator 63 Proportional integral compensator 64

第13頁 1220081 圖式簡單說明電壓頻率轉換器 65 第一一比較器 66 控制信號 67 差值電壓信號 68 三角載波頻率信號 69Page 13 1220081 Schematic description of voltage frequency converter 65 First one comparator 66 Control signal 67 Difference voltage signal 68 Triangle carrier frequency signal 69

Claims

1220081 六、申請專利範圍 1. 一種不連續電流模式功率因數修正器控制方法，係應用於一交/直流電力轉換，藉由控制一切換開關之切換頻率或切換週期，控制該功率因數修正器產生穩定之輸出電壓，該方法包括下列步驟：計算一輸入電壓之絕對值；將該輸入電壓之絕對值除以該輸出電壓，產生一控制信號；比較該輸出電壓及一參考電壓，產生一差值電壓信號；轉換該差值電壓信號為一三角載波頻率信號；及比較該控制.信號及該三角載波頻率信號，產生該切換開關之切換頻率或切換週期。 2. —種不連續電流模式功率因數修正器控制裝置，係應用於一交直流電力轉換，藉由控制一切換開關之切換頻率或切換週期，控制該功率因數修正器之產生穩定之輸出電壓，該裝置包括：一絕對值運算器，配置有一輸入端及一輸出端，該輸入端連接至經該橋式整流器後之一輸入電壓端，用以將該輸入電壓作一絕對值運算；一類比除法器，配置有二輸入端及一輸出端，該二輸入端分別連接該絕對值運算器之該輸出端及一輸出電壓端，該輸出端係產生一控制信號；一第一比較器，配置有二输入端及一輸出端，該二輸入端分別連接至該輸出電壓端及一參考電壓端，比較該輸1220081 VI. Application for patent scope 1. A discontinuous current mode power factor corrector control method, which is applied to an AC / DC power conversion, by controlling the switching frequency or switching period of a switch, controlling the power factor corrector to generate The method includes the following steps: calculating the absolute value of an input voltage; dividing the absolute value of the input voltage by the output voltage to generate a control signal; comparing the output voltage with a reference voltage to generate a difference Voltage signal; converting the difference voltage signal into a triangular carrier frequency signal; and comparing the control. Signal and the triangular carrier frequency signal to generate a switching frequency or a switching period of the switch. 2. — A discontinuous current mode power factor corrector control device is applied to an AC / DC power conversion. By controlling the switching frequency or switching period of a switch, the power factor corrector generates a stable output voltage. The device includes: an absolute value calculator configured with an input terminal and an output terminal, the input terminal is connected to an input voltage terminal after the bridge rectifier, and is used for performing an absolute value calculation on the input voltage; an analogy The divider is configured with two input terminals and an output terminal, and the two input terminals are respectively connected to the output terminal and an output voltage terminal of the absolute value calculator, and the output terminal generates a control signal; a first comparator configured There are two input terminals and one output terminal. The two input terminals are respectively connected to the output voltage terminal and a reference voltage terminal.

第15頁 1220081 六、申請專利範圍出電壓及該參考電壓產生一差值電壓信號；一電壓頻率轉換器，配置有一輸入端及一輸出端，該輸入端連接至該第一比較器之輸出端，藉該差值電壓信號轉換為一三角載波頻率信號；及一第二比較器，配置有一第一輸入端、一第二輸入端及一輸出端，該第一輸入端係連接至該類比除法器之輸出端，該第二輸入端係連接至該電壓頻率轉換器之輸出端，該輸出端連接至該控制開關，用以比較該控制信號與該三角載波頻率信號，控制該切換開關之切換頻率而產生穩定電壓輸出者。 3. 如申請專利範圍第2項所述之不連續電流模式功率因數修正器控制裝置，其中該切換開關係為一場效電晶體 (M0SFET)，該第二比較器之輸出端係連接至該場效電晶體之閘極。 4. 如申請專利範圍第2項所述之不連續電流模式功率因數修正器控制裝置，其中該功率因數修正器係由一二極體橋式整流器、一輸入電容器、一電感器、一二極體開關、一輸出電容器、一負載電阻及該切換開關所組成。 5. 如申請專利範圍第2項所述之不連續電流模式功率因數修正器控制裝置，其更包括：一比例積分補償器（P I )，係設於該第一比較器及該電壓頻率轉換器之間，配置有一輸入端及一輸出端，該輸入端連接至該第一比較器之輸出端，該輸出端連接至該電壓頻率轉換器之輸入端。Page 15 1220081 VI. The patent application range generates a difference voltage signal between the output voltage and the reference voltage; a voltage-frequency converter configured with an input terminal and an output terminal, the input terminal is connected to the output terminal of the first comparator To convert the delta voltage signal into a triangular carrier frequency signal; and a second comparator configured with a first input terminal, a second input terminal, and an output terminal, the first input terminal is connected to the analog division The output end of the converter, the second input end is connected to the output end of the voltage-frequency converter, and the output end is connected to the control switch for comparing the control signal with the triangular carrier frequency signal to control the switching of the switch Frequency and produce a stable voltage output. 3. The discontinuous current mode power factor corrector control device according to item 2 of the scope of patent application, wherein the switching on relationship is a field effect transistor (M0SFET), and the output terminal of the second comparator is connected to the field The gate of the effect transistor. 4. The discontinuous current mode power factor corrector control device as described in item 2 of the scope of patent application, wherein the power factor corrector is composed of a diode bridge rectifier, an input capacitor, an inductor, and a two pole It is composed of a body switch, an output capacitor, a load resistor and the switch. 5. The discontinuous current mode power factor corrector control device as described in item 2 of the scope of patent application, further comprising: a proportional-integral compensator (PI), which is provided in the first comparator and the voltage-frequency converter In between, there is an input terminal and an output terminal, the input terminal is connected to the output terminal of the first comparator, and the output terminal is connected to the input terminal of the voltage-frequency converter.

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