TW202220366A - Motor drive circuit and motor module - Google Patents
Motor drive circuit and motor module Download PDFInfo
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- TW202220366A TW202220366A TW110135569A TW110135569A TW202220366A TW 202220366 A TW202220366 A TW 202220366A TW 110135569 A TW110135569 A TW 110135569A TW 110135569 A TW110135569 A TW 110135569A TW 202220366 A TW202220366 A TW 202220366A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
- H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
- H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
- H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
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Abstract
Description
本發明是有關於一種馬達驅動電路及馬達模組。The present invention relates to a motor driving circuit and a motor module.
作為三相馬達的驅動方式,已知有兩相調變方式(例如專利文獻1)。專利文獻1所記載的逆變器裝置包括:控制機構,將三相中保持於接通或斷開的一相以外的兩相的指令值相互與180度相位不同且振幅及頻率相等的兩個三角基波分別進行比較,對與各相對應的切換元件各自的接通、斷開進行脈寬調變(Pulse Width Modulation,PWM)控制。控制機構將與三相中保持於接通或斷開的一相的指令值進行比較的三角基波中的一者,切換為三角基波的另一者。藉此,與將三相中保持於接通或斷開的一相以外的兩相的指令值與相同的三角基波比較並進行PWM控制的情形相比,可減小出入電容器的電流(電容器漣波電流)。
[先前技術文獻][專利文獻]
As a driving method of a three-phase motor, a two-phase modulation method is known (for example, Patent Document 1). The inverter device described in
[專利文獻1]日本專利特開2006-197707號公報[Patent Document 1] Japanese Patent Laid-Open No. 2006-197707
[發明所欲解決之課題][The problem to be solved by the invention]
然而,專利文獻1所記載的逆變器裝置中,PWM訊號的相位的切換限於切換的相保持於接通或斷開的情形。即,各相的PWM波形生成中所用的三角基波在該相進行切換的期間中,固定於180度相位不同的兩個三角基波中的一者,在切換中不進行三角基波的切換。此外,於專利文獻1中給予圖4(b)般的輸出電壓圖案的情形時,由於連接於輸出的馬達為感應性的負荷,故而電流波形相對於電壓波形產生延遲。此時,一部分旋轉角區間中,若以180度相位不同的三角波對切換中的兩個相進行PWM控制,則產生自逆變器向電容器的電流的逆流,減小電容器漣波電流的效果減弱。視情形不同,亦有時與使用同一三角波的情形相比而使總的電容器漣波電流增大。為了抑制該情況,必須於不產生自逆變器向電容器的電流逆流的旋轉角區間中使切換中的兩相的PWM訊號的相位不同,且於產生逆流的旋轉角區間中切換相同的PWM訊號的相位。然而,專利文獻1所記載的逆變器裝置中,於在切換的相保持於接通或斷開時進行PWM訊號的相位的切換的情形時,有可能在PWM訊號相位剛切換後產生長的接通(或斷開)持續時間。However, in the inverter device described in
本發明是鑑於所述課題而成,其目的在於提供一種馬達驅動電路及馬達模組,可抑制於剛切換後產生長的接通(或斷開)持續時間而進行PWM相位的切換。 [解決課題之手段] The present invention has been made in view of the above-mentioned problems, and an object of the present invention is to provide a motor drive circuit and a motor module that can perform switching of PWM phases while suppressing a long ON (or OFF) duration immediately after switching. [Means of Solving Problems]
本發明的例示性的馬達驅動電路以兩相調變方式來控制三相馬達的驅動。所述馬達驅動電路包括第一輸入端子、第二輸入端子、電容器、三個串聯體及訊號生成部。對所述第一輸入端子施加第一電壓。對所述第二輸入端子施加較所述第一電壓更低的第二電壓。所述電容器連接於所述第一輸入端子與所述第二輸入端子之間。所述三個串聯體是將兩個半導體切換元件串聯連接。所述訊號生成部生成對所述三個串聯體各自輸入的PWM訊號。所述PWM訊號包含正相PWM訊號及反相PWM訊號。所述反相PWM訊號的相位與所述正相PWM訊號不同。所述訊號生成部於相位切換時機進行所述PWM訊號的相位的切換。所述PWM訊號於所述正相PWM訊號與所述反相PWM訊號之間且所述相位切換時機的前後,更具有相連脈波組。所述相連脈波組具有相連接通脈波及相連斷開脈波。所述相連接通脈波具有相連接通期間。所述相連斷開脈波具有相連斷開期間。所述相連接通期間較相位切換前或相位切換後的PWM週期的一週期的接通期間更短。The exemplary motor drive circuit of the present invention controls the drive of a three-phase motor in a two-phase modulation manner. The motor drive circuit includes a first input terminal, a second input terminal, a capacitor, three series bodies and a signal generating part. A first voltage is applied to the first input terminal. A second voltage lower than the first voltage is applied to the second input terminal. The capacitor is connected between the first input terminal and the second input terminal. The three series bodies connect two semiconductor switching elements in series. The signal generating unit generates a PWM signal to be input to each of the three series bodies. The PWM signal includes a positive-phase PWM signal and a negative-phase PWM signal. The phase of the inverting PWM signal is different from the phase of the non-inverting PWM signal. The signal generating unit switches the phase of the PWM signal at a phase switching timing. The PWM signal further has a connected pulse group between the positive-phase PWM signal and the negative-phase PWM signal and before and after the phase switching timing. The connected pulse wave group has connected on pulse waves and connected off pulse waves. The connected on pulse waves have a connected on period. The disconnection pulse wave has a disconnection period. The phase-on period is shorter than the on-period of one cycle of the PWM period before or after the phase switching.
本發明的例示性的馬達模組包括所述記載的馬達驅動電路、及三相馬達。所述三相馬達由所述馬達驅動電路驅動。 [發明的效果] An exemplary motor module of the present invention includes the motor drive circuit described above, and a three-phase motor. The three-phase motor is driven by the motor drive circuit. [Effect of invention]
根據例示性的本發明,可抑制於PWM訊號相位剛切換後產生長的接通(或斷開)持續時間而進行PWM相位的切換。According to the exemplary invention, the switching of the PWM phase can be performed while suppressing the generation of a long on (or off) duration immediately after the phase of the PWM signal is switched.
以下,一方面參照圖式一方面對本發明的實施形態加以說明。再者,圖中對相同或相當部分標註相同的參照符號,不重複進行說明。Hereinafter, embodiments of the present invention will be described with reference to the drawings. In addition, the same reference numerals are attached to the same or corresponding parts in the drawings, and the description will not be repeated.
參照圖1及圖2對本發明的實施形態的馬達加以說明。圖1為本發明的實施形態的馬達模組200的區塊圖。圖2為表示逆變器部110的電路圖。A motor according to an embodiment of the present invention will be described with reference to FIGS. 1 and 2 . FIG. 1 is a block diagram of a
如圖1所示,馬達模組200包括馬達驅動電路100及三相馬達M。三相馬達M由馬達驅動電路100驅動。三相馬達M例如為無刷直流(Direct Current,DC)馬達。三相馬達M具有U相、V相及W相。As shown in FIG. 1 , the
馬達驅動電路100以兩相調變方式控制三相馬達M的驅動。馬達驅動電路100包括逆變器部110及訊號生成部120。The
馬達驅動電路100包括三個輸出端子102。三個輸出端子102包含輸出端子102u、輸出端子102v及輸出端子102w。三個輸出端子102向三相馬達M輸出三相的輸出電壓及三相的輸出電流。詳細而言,輸出端子102u向三相馬達M輸出U相的輸出電壓Vu及U相的輸出電流Iu。輸出端子102v向三相馬達M輸出V相的輸出電壓Vv及V相的輸出電流Iv。輸出端子102w向三相馬達M輸出W相的輸出電壓Vw及W相的輸出電流Iw。The
如圖2所示,馬達驅動電路100包括第一輸入端子P、第二輸入端子N、電容器C及三個串聯體112。更具體而言,本實施形態中,馬達驅動電路100包括逆變器部110,逆變器部110包括第一輸入端子P、第二輸入端子N、電容器C及三個串聯體112。逆變器部110更包括直流電壓源B。再者,直流電壓源B亦可位於逆變器部110的外部。As shown in FIG. 2 , the
對第一輸入端子P施加第一電壓V1。第一輸入端子P連接於直流電壓源B。The first voltage V1 is applied to the first input terminal P. As shown in FIG. The first input terminal P is connected to the DC voltage source B.
對第二輸入端子N施加第二電壓V2。第二輸入端子N連接於直流電壓源B。第二電壓V2低於第一電壓V1。The second voltage V2 is applied to the second input terminal N. The second input terminal N is connected to the DC voltage source B. The second voltage V2 is lower than the first voltage V1.
電容器C連接於第一輸入端子P與第二輸入端子N之間。The capacitor C is connected between the first input terminal P and the second input terminal N.
關於三個串聯體112,串聯連接有兩個半導體切換元件。半導體切換元件例如為絕緣閘雙極電晶體(Insulated Gate Bipolar Transistor,IGBT)。再者,半導體切換元件亦可為場效電晶體般的其他電晶體。三個串聯體112包含串聯體112u、串聯體112v及串聯體112w。三個串聯體112相互並聯連接。三個串聯體112各自的一端連接於第一輸入端子P。三個串聯體112各自的另一端連接於第二輸入端子N。對於該些半導體切換元件,分別以第一輸入端子P側(紙面上側)為陰極且以第二輸入端子N側(紙面下側)為陽極而並聯連接有整流元件D。於使用場效電晶體作為半導體切換元件的情形時,亦可使用寄生二極體作為該整流元件。Regarding the three
三個串聯體112各自具有第一半導體切換元件及第二半導體切換元件。詳細而言,串聯體112u具有第一半導體切換元件Up及第二半導體切換元件Un。串聯體112v具有第一半導體切換元件Vp及第二半導體切換元件Vn。串聯體112w具有第一半導體切換元件Wp及第二半導體切換元件Wn。The three
第一半導體切換元件Up、第一半導體切換元件Vp及第一半導體切換元件Wp連接於第一輸入端子P。換言之,第一半導體切換元件Up、第一半導體切換元件Vp及第一半導體切換元件Wp為高電壓側的半導體切換元件。The first semiconductor switching element Up, the first semiconductor switching element Vp, and the first semiconductor switching element Wp are connected to the first input terminal P. As shown in FIG. In other words, the first semiconductor switching element Up, the first semiconductor switching element Vp, and the first semiconductor switching element Wp are semiconductor switching elements on the high voltage side.
第二半導體切換元件Un、第二半導體切換元件Vn及第二半導體切換元件Wn連接於第二輸入端子N。換言之,第二半導體切換元件Un、第二半導體切換元件Vn及第二半導體切換元件Wn為低電壓側的半導體切換元件。The second semiconductor switching element Un, the second semiconductor switching element Vn, and the second semiconductor switching element Wn are connected to the second input terminal N. In other words, the second semiconductor switching element Un, the second semiconductor switching element Vn, and the second semiconductor switching element Wn are semiconductor switching elements on the low voltage side.
第一半導體切換元件與第二半導體切換元件於連接點114連接。詳細而言,第一半導體切換元件Up與第二半導體切換元件Un於連接點114u連接。第一半導體切換元件Vp與第二半導體切換元件Vn於連接點114v連接。第一半導體切換元件Wp與第二半導體切換元件Wn於連接點114w連接。The first semiconductor switching element and the second semiconductor switching element are connected at the
三個串聯體112各自的連接點114連接於三個輸出端子102。詳細而言,串聯體112u的連接點114u連接於輸出端子102u。串聯體112v的連接點114v連接於輸出端子102v。串聯體112w的連接點114w連接於輸出端子102w。The respective connection points 114 of the three
對第一半導體切換元件Up、第一半導體切換元件Vp及第一半導體切換元件Wp輸入PWM訊號。PWM訊號自訊號生成部120輸出。以下,於本說明書中,有時將對第一半導體切換元件Up輸入的PWM訊號記載為「UpPWM訊號」。另外,有時將對第一半導體切換元件Vp輸入的PWM訊號記載為「VpPWM訊號」。有時將對第一半導體切換元件Wp輸入的PWM訊號記載為「WpPWM訊號」。第一半導體切換元件Up、第一半導體切換元件Vp及第一半導體切換元件Wp以既定的PWM週期切換接通與斷開。例如,第一半導體切換元件Up、第一半導體切換元件Vp及第一半導體切換元件Wp分別於UpPWM訊號、VpPWM訊號及WpPWM訊號為高(HIGH)位準的情形時接通。另一方面,第一半導體切換元件Up、第一半導體切換元件Vp及第一半導體切換元件Wp分別於UpPWM訊號、VpPWM訊號及WpPWM訊號為低(LOW)位準的情形時斷開。A PWM signal is input to the first semiconductor switching element Up, the first semiconductor switching element Vp, and the first semiconductor switching element Wp. The PWM signal is output from the
對第二半導體切換元件Un、第二半導體切換元件Vn及第二半導體切換元件Wn輸入PWM訊號。PWM訊號自訊號生成部120輸出。以下,於本說明書中,有時將對第二半導體切換元件Un輸入的PWM訊號記載為「UnPWM訊號」。另外,有時將對第二半導體切換元件Vn輸入的PWM訊號記載為「VnPWM訊號」。有時將對第二半導體切換元件Wn輸入的PWM訊號記載為「WnPWM訊號」。第二半導體切換元件Un、第二半導體切換元件Vn及第二半導體切換元件Wn以既定的PWM週期切換接通與斷開。例如,第二半導體切換元件Un、第二半導體切換元件Vn及第二半導體切換元件Wn分別於UnPWM訊號、VnPWM訊號及WnPWM訊號為高(HIGH)位準的情形時接通。另一方面,第二半導體切換元件Un、第二半導體切換元件Vn及第二半導體切換元件Wn分別於UnPWM訊號、VnPWM訊號及WnPWM訊號為低(LOW)位準的情形時斷開。A PWM signal is input to the second semiconductor switching element Un, the second semiconductor switching element Vn, and the second semiconductor switching element Wn. The PWM signal is output from the
如圖1所示,訊號生成部120具有載波生成部122、電壓指令值生成部124及比較部126。訊號生成部120為硬體電路,包含中央處理單元(Central Processing Unit,CPU)般的處理器及應用特定積體電路(Application Specific Integrated Circuit,ASIC)等。而且,訊號生成部120的處理器藉由執行記憶於記憶裝置的電腦程式,從而作為載波生成部122、電壓指令值生成部124及比較部126發揮功能。As shown in FIG. 1 , the
訊號生成部120控制逆變器部110。具體而言,訊號生成部120藉由生成PWM訊號並輸出PWM訊號,從而控制逆變器部110。更具體而言,訊號生成部120生成對三個串聯體112各自輸入的PWM訊號。The
載波生成部122生成載波訊號。載波訊號例如為三角波。再者,載波訊號亦可為鋸齒波。The
電壓指令值生成部124生成電壓指令值。電壓指令值相當於自馬達驅動電路100輸出的電壓值。即,電壓指令值生成部124生成與輸出電壓Vu、輸出電壓Vv及輸出電壓Vw相應的電壓值作為電壓指令值。The voltage command
比較部126藉由將載波訊號與電壓指令值進行比較從而生成PWM訊號。The
參照圖1~圖3對本發明的實施形態的PWM訊號加以說明。圖3為表示本發明的實施形態的PWM訊號的圖。圖3中,表示三相的PWM訊號中一相的PWM訊號。圖3中,正相PWM期間PT為輸出正相PWM訊號PS的期間。另外,反相PWM期間NT為輸出反相PWM訊號NS的期間。另外,相連脈波組期間AT為輸出相連脈波組AS的期間。關於電流波形,忽視其他相的切換對電流漣波的作用,僅提取該相的切換所致的切換漣波成分來進行圖示。The PWM signal according to the embodiment of the present invention will be described with reference to FIGS. 1 to 3 . FIG. 3 is a diagram showing a PWM signal according to the embodiment of the present invention. In FIG. 3 , the PWM signal of one phase among the three-phase PWM signals is shown. In FIG. 3 , the non-inverting PWM period PT is a period in which the non-inverting PWM signal PS is output. In addition, the inversion PWM period NT is a period in which the inversion PWM signal NS is output. In addition, the continuous pulse wave group period AT is a period during which the continuous pulse wave group AS is output. Regarding the current waveform, the effect of the switching of the other phases on the current ripple is ignored, and only the switching ripple component caused by the switching of the phase is extracted and illustrated.
如圖3所示,PWM訊號包含正相PWM訊號PS及反相PWM訊號NS。反相PWM訊號NS的相位與正相PWM訊號PS不同。本實施形態中,反相PWM訊號NS的相位與正相PWM訊號PS偏移180度。As shown in FIG. 3 , the PWM signal includes a positive-phase PWM signal PS and a negative-phase PWM signal NS. The phase of the inverted PWM signal NS is different from that of the non-inverted PWM signal PS. In this embodiment, the phase of the inversion PWM signal NS and the non-inverting PWM signal PS are shifted by 180 degrees.
訊號生成部120藉由將載波訊號CAS與電壓指令值V進行比較,從而生成PWM訊號。訊號生成部120於相位切換時機tsw進行PWM訊號的相位的切換。此處,訊號生成部120於相位切換時機tsw將PWM訊號的相位由正相切換為反相。即,在相位切換時機tsw之前,PWM訊號的相位為正相。另一方面,在相位切換時機tsw之後,PWM訊號的相位為反相。本實施形態中,相位切換時機tsw為載波訊號CAS的山部的時機。本實施形態中,載波訊號CAS為三角波。The
訊號生成部120於相位切換時機tsw變更電壓指令值V。此處,訊號生成部120將電壓指令值由V變更為1-V。比較部126將電壓指令值與載波訊號CAS進行比較,生成PWM訊號。詳細而言,於PWM訊號的相位為正相的情形時,當載波訊號CAS為電壓指令值以上時,將PWM訊號斷開。另一方面,比較部126將電壓指令值與載波訊號CAS進行比較,當載波訊號CAS小於電壓指令值時,將PWM訊號接通。另一方面,於PWM訊號的相位為反相的情形時,當載波訊號CAS為電壓指令值以上時,將PWM訊號接通。另一方面,比較部126將電壓指令值與載波訊號CAS進行比較,當載波訊號CAS小於電壓指令值時,將PWM訊號斷開。如此,訊號生成部120藉由變更電壓指令值及比較部126的判定處理的方法,從而變更PWM訊號的相位。The
PWM訊號於正相PWM訊號PS與反相PWM訊號NS之間且相位切換時機tsw的前後,更具有相連脈波組AS。相連脈波組AS具有相連接通脈波ASon及相連斷開脈波ASoff。相連接通脈波ASon具有相連接通期間ATon。相連斷開脈波ASoff具有相連斷開期間AToff。相連脈波組AS位於相位切換時機tsw前後的PWM一週期以內的時間範圍。The PWM signal further has a connected pulse group AS between the positive-phase PWM signal PS and the negative-phase PWM signal NS and before and after the phase switching timing tsw. The connected pulse group AS has a connected on-pulse ASon and a connected off-pulse ASoff. The continuous-on pulse wave ASon has a continuous-on period ATon. The disconnection pulse wave ASoff has a disconnection period AToff. The connected pulse wave group AS is located within a time range of one PWM period before and after the phase switching timing tsw.
相連接通期間ATon較相位切換前或相位切換後的PWM週期的一週期的接通期間更短。本實施形態中,相連接通期間ATon較相位切換前的PWM週期的一週期的接通期間Ton更短。詳細而言,相連接通期間ATon為相位切換前的PWM週期的一週期的接通期間Ton的1/2的長度。即,ATon=Ton/2。The continuous on-period ATon is shorter than the on-period of one cycle of the PWM period before or after the phase switching. In the present embodiment, the continuous on-period ATon is shorter than the on-period Ton of one cycle of the PWM cycle before the phase switching. Specifically, the phase-on period ATon is the length of 1/2 of the on-period Ton of one cycle of the PWM cycle before the phase switching. That is, ATon=Ton/2.
PWM訊號於正相PWM訊號PS與反相PWM訊號NS之間且相位切換時機tsw的前後,具有相連脈波組AS。因此,可針對PWM控制中的相中的一者,抑制於PWM訊號相位剛切換後產生長的接通(或斷開)持續時間而進行PWM相位的切換。其結果為,可於PWM訊號相位剛切換後,抑制產生意外的相電流的增減而導致力矩波動或噪音,而且減小電容器漣波電流。The PWM signal has a connected pulse group AS between the positive-phase PWM signal PS and the negative-phase PWM signal NS and before and after the phase switching timing tsw. Therefore, for one of the phases in the PWM control, the switching of the PWM phase can be performed while suppressing a long on (or off) duration immediately after the phase of the PWM signal is switched. As a result, it is possible to suppress the torque fluctuation or noise caused by the unexpected increase or decrease of the phase current immediately after the phase of the PWM signal is switched, and to reduce the ripple current of the capacitor.
另外,相連脈波組AS位於相位切換時機tsw的前後的PWM一週期以內的時間範圍。因此,可於容易產生長的接通(或斷開)持續時間的PWM訊號相位剛切換後,抑制產生長的接通(或斷開)持續時間而進行PWM相位的切換。其結果為,可抑制產生意外的相電流的增減而導致力矩波動或噪音,而且減小電容器漣波電流。In addition, the continuous pulse wave group AS is located within a time range within one PWM cycle before and after the phase switching timing tsw. Therefore, the switching of the PWM phase can be performed while suppressing the generation of a long ON (or OFF) duration immediately after the phase switching of the PWM signal which is likely to generate a long ON (or OFF) duration. As a result, it is possible to suppress a torque ripple or noise due to an unexpected increase or decrease of the phase current, and to reduce the capacitor ripple current.
另外,相連斷開期間AToff較相位切換前或相位切換後的PWM週期的一週期的斷開期間更短。因此,可抑制產生意外的相電流的增減而導致力矩波動或噪音,而且減小電容器漣波電流。本實施形態中,相連斷開期間AToff較相位切換前的PWM週期的一週期的斷開期間Toff更短。詳細而言,相連斷開期間AToff為相位切換前的PWM週期的一週期的斷開期間Toff的1/2的長度。即,AToff=Toff/2。In addition, the connection off period AToff is shorter than the off period of one cycle of the PWM cycle before or after the phase switching. Therefore, it is possible to suppress the occurrence of an unexpected increase or decrease of the phase current, which may cause torque ripple or noise, and to reduce the capacitor ripple current. In the present embodiment, the connection off period AToff is shorter than the off period Toff of one cycle of the PWM cycle before the phase switching. Specifically, the connection-off period AToff is the length of 1/2 of the off-period Toff of one cycle of the PWM cycle before the phase switching. That is, AToff=Toff/2.
另外,相連接通期間ATon與相連斷開期間AToff之比,和相位切換前或相位切換後的PWM週期的一週期的接通期間Ton與斷開期間Toff之比相同。因此,如圖3所示的電流波形般,可抑制相位切換前後的平均電流的變動,可進一步抑制馬達的力矩波動或噪音。再者,相連接通期間ATon與相連斷開期間AToff之比亦可和相位切換前或相位切換後的PWM週期的一週期的接通期間Ton與斷開期間Toff之比稍不同。In addition, the ratio of the connection-on period ATon to the connection-off period AToff is the same as the ratio of the ON period Ton to the OFF period Toff in one cycle of the PWM cycle before or after the phase switching. Therefore, like the current waveform shown in FIG. 3 , the fluctuation of the average current before and after the phase switching can be suppressed, and the torque fluctuation and noise of the motor can be further suppressed. Furthermore, the ratio of the ON period ATon to the OFF period AToff may be slightly different from the ratio of the ON period Ton to the OFF period Toff in one cycle of the PWM cycle before or after the phase switching.
另外,相連斷開期間AToff先於相連接通期間ATon之前,並且斷開期間於相連脈波組AS的期間所佔的比率與相位切換前的斷開期間於PWM週期所佔的比率相同。另外,接通期間於相連脈波組AS的期間所佔的比率與相位切換後的接通期間於PWM週期所佔的比率相同。因此,如圖3所示的電流波形般,相連脈波組AS期間結束時的電流值與相位切換前的電流波峰值幾乎一致。因此,可抑制相位切換前後的平均電流的變動,可進一步抑制馬達的力矩波動或噪音。再者,斷開期間於相連脈波組AS的期間所佔的比率亦可與相位切換前的斷開期間於PWM週期所佔的比率稍不同。另外,接通期間於相連脈波組AS的期間所佔的比率亦可與相位切換後的接通期間於PWM週期所佔的比率稍不同。In addition, the connection-off period AToff precedes the connection-on period ATon, and the ratio of the off period to the period of the connected pulse group AS is the same as the ratio of the off period to the PWM period before the phase switching. In addition, the ratio of the on-period to the period of the connected pulse group AS is the same as the ratio of the on-period after the phase switching to the PWM period. Therefore, like the current waveform shown in FIG. 3 , the current value at the end of the continuous pulse wave group AS period almost matches the current wave peak value before the phase switching. Therefore, the fluctuation of the average current before and after the phase switching can be suppressed, and the torque fluctuation and noise of the motor can be further suppressed. Furthermore, the ratio of the off period to the period of the connected pulse group AS may be slightly different from the ratio of the off period before the phase switching to the PWM period. In addition, the ratio of the on-period to the period of the connected pulse group AS may be slightly different from the ratio of the on-period after the phase switching to the PWM period.
另外,相連脈波組AS的週期為相位切換前或相位切換後的PWM週期的1/2。即,AT=T/2。因此,可抑制相位切換前後的平均電流的變動,可進一步抑制馬達的力矩波動或噪音。In addition, the cycle of the continuous pulse wave group AS is 1/2 of the PWM cycle before the phase switching or after the phase switching. That is, AT=T/2. Therefore, the fluctuation of the average current before and after the phase switching can be suppressed, and the torque fluctuation and noise of the motor can be further suppressed.
再者,相連接通脈波ASon亦可具有多個脈波。即便於相連接通脈波ASon具有多個脈波的情形時,亦可減小電容器漣波電流。Furthermore, the connected on-pulse waves ASon may also have a plurality of pulse waves. The capacitor ripple current can be reduced even when there are multiple pulses connected to the on-pulse ASON.
再者,相連斷開脈波ASoff亦可具有多個脈波。即便於相連斷開脈波ASoff具有多個脈波的情形時,亦可減小電容器漣波電流。Furthermore, the connected and disconnected pulse waves ASoff may have a plurality of pulse waves. The capacitor ripple current can be reduced even when the connected off pulse ASoff has multiple pulses.
根據以上的構成,即便針對切換中的相進行正相PWM與反相PWM的切換,亦可抑制平均電流的變動,可抑制馬達的力矩波動波動或噪音。因此,可進行下述動作,即:在對切換中的兩相中的一者適用反相PWM的情況下更能抑制電容器漣波電流的旋轉角區間中,適用反相PWM,且在若適用反相PWM則反而產生向電容器的逆流電流而使電容器漣波電流劣化的旋轉角區間中,適用正相PWM等,而有效地抑制電容器漣波電流而抑制電容器放熱,實現電容器的小型化及低成本化。與此同時,可抑制伴隨正相PWM與反相PWM的切換的馬達的力矩波動波動或噪音。兩相調變方式中,例如於以電氣旋轉角60度為單位來切換將不切換的相固定於接通的期間與固定於斷開的期間的調變方式的情形時,有時電流波形相對於電壓波形而延遲,導致產生若適用反相PWM則電容器漣波電流劣化的旋轉角區間。因此,藉由僅於此種旋轉角區間,以切換的兩個相的PWM相位成為相同相位的方式,使用本實施形態來進行切換中的相的PWM相位的切換,從而可抑制馬達的力矩波動或噪音並且抑制電容器漣波電流。另外,兩相調變方式中,在將不切換的相僅固定於接通的方式、或僅固定於斷開的方式的情形時,若適用反相PWM則電容器漣波電流減小的旋轉角區間、與若適用反相PWM則電容器漣波電流劣化的旋轉角區間以電氣旋轉角60度為單位而重複。因此,藉由以前者的旋轉角區間中切換的兩個相的PWM相位不同,後者的旋轉角區間中切換的兩個相的PWM相位成為相同相位的方式,使用本實施形態來切換切換中的相的PWM相位,從而可抑制馬達的力矩波動或噪音而抑制電容器漣波電流。正相PWM與反相PWM的切換時機可基於馬達電流的零交叉點。According to the above configuration, even if the switching between the normal-phase PWM and the reverse-phase PWM is performed for the switching phase, the fluctuation of the average current can be suppressed, and the torque ripple and noise of the motor can be suppressed. Therefore, it is possible to perform an operation of applying reverse-phase PWM in the rotation angle section in which the capacitor ripple current can be more suppressed when reverse-phase PWM is applied to one of the two phases being switched, and if applicable Inverse-phase PWM produces a reverse current to the capacitor instead and degrades the capacitor ripple current. In the rotation angle range where the capacitor ripple current is degraded, the application of normal-phase PWM, etc., effectively suppresses the capacitor ripple current and suppresses the capacitor heat generation, and realizes the miniaturization and low power consumption of the capacitor. cost. At the same time, torque ripple and noise of the motor accompanying the switching of the normal-phase PWM and the reverse-phase PWM can be suppressed. In the two-phase modulation method, for example, in the case of switching the modulation method in which the non-switching phase is fixed to the ON period and the OFF period in units of an electrical rotation angle of 60 degrees, the current waveforms may be opposite to each other. The voltage waveform is delayed, resulting in a rotation angle section in which the capacitor ripple current is degraded if the inversion PWM is applied. Therefore, by using this embodiment to switch the PWM phase of the phase being switched so that the PWM phases of the two phases to be switched become the same phase only in such a rotation angle section, the torque ripple of the motor can be suppressed. or noise and suppress capacitor ripple current. In addition, in the two-phase modulation method, when the non-switching phase is fixed only in the on mode or only in the off mode, the rotation angle at which the capacitor ripple current is reduced if the inverse PWM is applied The interval and the rotation angle interval in which the capacitor ripple current is degraded by applying the reverse-phase PWM are repeated in units of an electrical rotation angle of 60 degrees. Therefore, the present embodiment is used to switch the switching phase so that the PWM phases of the two phases switched in the former rotation angle interval are different, and the PWM phases of the two phases switched in the latter rotation angle interval become the same phase. The PWM phase of the phase can be suppressed, thereby suppressing the torque fluctuation or noise of the motor and suppressing the ripple current of the capacitor. The switching timing of the non-inverting PWM and the inverting PWM may be based on the zero-crossing point of the motor current.
繼而,參照圖1、圖2及圖4,對本發明的實施形態的PWM訊號的由反相向正相的切換進行說明。圖4為表示本發明的實施形態的PWM訊號的圖。Next, with reference to FIGS. 1 , 2 and 4 , the switching of the PWM signal from the reverse phase to the normal phase according to the embodiment of the present invention will be described. FIG. 4 is a diagram showing a PWM signal according to the embodiment of the present invention.
如圖4所示,訊號生成部120於相位切換時機tsw將PWM訊號的相位由反相切換為正相。As shown in FIG. 4 , the
與圖3所示的PWM訊號同樣地,PWM訊號於正相PWM訊號PS與反相PWM訊號NS之間且相位切換時機tsw的前後,具有相連脈波組AS。因此,可於容易產生長的接通(或斷開)持續時間的PWM訊號相位剛切換後,抑制產生長的接通(或斷開)持續時間而進行PWM相位的切換。其結果為,可抑制力矩波動或噪音的產生,並且減小電容器漣波電流。Similar to the PWM signal shown in FIG. 3 , the PWM signal has a connected pulse group AS between the positive-phase PWM signal PS and the negative-phase PWM signal NS and before and after the phase switching timing tsw. Therefore, the switching of the PWM phase can be performed while suppressing the generation of a long ON (or OFF) duration immediately after the phase switching of the PWM signal which is likely to generate a long ON (or OFF) duration. As a result, generation of torque ripple and noise can be suppressed, and capacitor ripple current can be reduced.
相連接通期間ATon為相位切換前的PWM週期的一週期的接通期間Ton的1/2的長度。即,ATon=Ton/2。The continuous on-period ATon is the length of 1/2 of the on-period Ton of one cycle of the PWM cycle before the phase switching. That is, ATon=Ton/2.
相連斷開期間AToff為相位切換前的PWM週期的一週期的斷開期間Toff的1/2的長度。即,AToff=Toff/2。The connection-off period AToff is the length of 1/2 of the off-period Toff of one cycle of the PWM cycle before the phase switching. That is, AToff=Toff/2.
另外,相連接通期間ATon先於相連斷開期間AToff之前,並且接通期間於相連脈波組AS的期間所佔的比率與相位切換前的接通期間於PWM週期所佔的比率相同。另外,斷開期間於相連脈波組AS的期間所佔的比率與相位切換後的斷開期間於PWM週期所佔的比率相同。因此,如圖4所示的電流波形般,可抑制相位切換前後的平均電流的變動,可進一步抑制馬達的力矩波動或噪音。再者,接通期間於相連脈波組AS的期間所佔的比率亦可與相位切換前的接通期間於PWM週期所佔的比率稍不同。另外,斷開期間於相連脈波組AS的期間所佔的比率亦可與相位切換後的斷開期間於PWM週期所佔的比率稍不同。In addition, the connection-on period ATon precedes the connection-off period AToff, and the ratio of the on-period to the period of the connected pulse group AS is the same as the ratio of the on-period to the PWM period before the phase switching. In addition, the ratio of the off period to the period of the connected pulse group AS is the same as the ratio of the off period after the phase switching to the PWM cycle. Therefore, like the current waveform shown in FIG. 4 , the fluctuation of the average current before and after the phase switching can be suppressed, and the torque fluctuation and noise of the motor can be further suppressed. Furthermore, the ratio of the on period to the period of the connected pulse group AS may be slightly different from the ratio of the on period before the phase switching to the PWM period. In addition, the ratio of the off period to the period of the connected pulse group AS may be slightly different from the ratio of the off period after the phase switching to the PWM period.
如圖4所示的電流波形般,針對將相位由反相切換為正相的情形,亦可抑制相位切換前後的平均電流的變動,可進一步抑制馬達的力矩波動或噪音。Like the current waveform shown in FIG. 4 , when the phase is switched from the reverse phase to the normal phase, the fluctuation of the average current before and after the phase switching can be suppressed, and the torque fluctuation and noise of the motor can be further suppressed.
再者,參照圖3及圖4所說明的例子中,相位切換時機tsw為載波訊號CAS的山部的時機,但相位切換時機tsw亦可自載波訊號CAS的山部的時機偏移。3 and 4, the phase switching timing tsw is the timing of the peak of the carrier signal CAS, but the phase switching timing tsw may be shifted from the timing of the peak of the carrier signal CAS.
參照圖1、圖2及圖5,對本發明的實施形態的PWM訊號加以說明。圖5為表示本發明的實施形態的PWM訊號的圖。1, 2 and 5, the PWM signal according to the embodiment of the present invention will be described. FIG. 5 is a diagram showing a PWM signal according to the embodiment of the present invention.
如圖5所示,PWM訊號除了正相PWM訊號PS、反相PWM訊號NS及相連脈波組AS,更具有前脈波組BS及後脈波組CS。前脈波組BS位於相連脈波組AS之前。後脈波組CS位於相連脈波組AS之後。As shown in FIG. 5 , in addition to the positive-phase PWM signal PS, the negative-phase PWM signal NS and the connected pulse group AS, the PWM signal also has a front pulse group BS and a back pulse group CS. The previous pulse wave group BS is located before the connected pulse wave group AS. The post pulse wave group CS is located after the connected pulse wave group AS.
前脈波組BS具有前接通脈波BSon及前斷開脈波BSoff。前接通脈波BSon具有前接通期間BTon。前斷開脈波BSoff具有前斷開期間BToff。前脈波組BS的週期與較其更靠前的PWM訊號相同,即,本實施形態中與正相PWM訊號PS相同。The previous pulse wave group BS has a previous on-pulse wave BSon and a previous off-pulse wave BSoff. The pre-on pulse wave BSon has a pre-on period BTon. The previous off pulse wave BSoff has a previous off period BToff. The period of the previous pulse wave group BS is the same as that of the PWM signal that is earlier than it, that is, the same as the normal-phase PWM signal PS in this embodiment.
後脈波組CS具有後接通脈波CSon及後斷開脈波CSoff。後接通脈波CSon具有後接通期間CTon。後斷開脈波CSoff具有後斷開期間CToff。後脈波組CS的週期與較其更靠後的PWM訊號相同,即,本實施形態中與反相PWM訊號NS相同。The post-pulse group CS has post-on pulse waves CSon and post-off pulse waves CSoff. The post-on pulse wave CSon has a post-on period CTon. The post-off pulse wave CSoff has a post-off period CToff. The period of the latter pulse wave group CS is the same as that of the PWM signal further back, that is, the same as the inverted PWM signal NS in this embodiment.
相位切換時機tsw自載波訊號CAS的山部的時機延遲時間t。The phase switching timing tsw is delayed by the time t from the timing of the peak of the carrier signal CAS.
訊號生成部120調整相連脈波組AS、前脈波組BS及後脈波組CS中的至少兩個的脈波長。本實施形態中,訊號生成部120調整相連脈波組AS及後脈波組CS的脈波長。The
本實施形態中,相位切換時機tsw自載波訊號CAS的山部的時機延遲時間t。因此,伴隨切換的開啟(turn on)的時刻延遲時間t。因此,訊號生成部120以補償延遲時間t的方式,調整相連接通期間ATon及後接通期間CTon。詳細而言,訊號生成部120以相連接通期間ATon及後接通期間CTon分別與將電壓指令值設為1-V的情形相比較延長t/2的方式,將使電壓指令值自1-V偏移的值設為電壓指令值。即,訊號生成部120使電壓指令值以換算成脈波長而相當於時間t/2的值偏移。In this embodiment, the phase switching timing tsw is delayed by the time t from the timing of the peak of the carrier signal CAS. Therefore, the timing of turn on accompanying the switching is delayed by the time t. Therefore, the
此時,相連斷開期間AToff由於伴隨切換的開啟時刻延遲時間t,因而成為Toff/2+t。即,AToff=Toff/2+t。At this time, the disconnection period AToff becomes Toff/2+t because the ON timing associated with the switching is delayed by the time t. That is, AToff=Toff/2+t.
另外,相連接通期間ATon的開啟延遲時間t,而且因電壓指令值的偏移而關斷(turn off)亦延遲t/2,故而成為Ton/2-t/2。即,ATon=Ton/2-t/2。In addition, the turn-on delay time t of ATon during the continuous ON period, and the turn-off (turn off) due to the deviation of the voltage command value is also delayed by t/2, so it becomes Ton/2−t/2. That is, ATon=Ton/2−t/2.
另外,後斷開期間CToff因電壓指令值的偏移而縮短時間t,成為Toff-t。即,CToff=Toff-t。In addition, the post-off period CToff is shortened by the time t due to the offset of the voltage command value, and becomes Toff-t. That is, CToff=Toff-t.
另外,後接通期間CTon因電壓指令值的偏移而延遲t/2,成為Ton+t/2。即,CTon=Ton+t/2。In addition, the post-on period CTon is delayed by t/2 due to the deviation of the voltage command value, and becomes Ton+t/2. That is, CTon=Ton+t/2.
訊號生成部120調整相連接通期間ATon、前接通期間BTon及後接通期間CTon中的至少兩個。本實施形態中,訊號生成部120調整相連接通期間ATon及後接通期間CTon。相連接通期間ATon的調整值、前接通期間BTon的調整值及後接通期間CTon的調整值之和為0。本實施形態中,於將相連接通期間ATon的調整值設為t1a、前接通期間BTon的調整值設為t1b、後接通期間CTon的調整值設為t1c的情形時,成為t1a=-t/2、t1b=0、t1c=t/2。因此,成為t1a+t1b+t1c=0。The
訊號生成部120調整相連斷開期間AToff、前斷開期間BToff及後斷開期間CToff中的至少兩個。本實施形態中,訊號生成部120調整相連斷開期間AToff及後斷開期間CToff。相連斷開期間AToff的調整值、前斷開期間BToff的調整值及後斷開期間CToff的調整值之和為0。於將相連斷開期間AToff的調整值設為t2a、前斷開期間BToff的調整值設為t2b、後斷開期間CToff的調整值設為t2c的情形時,成為t2a=t、t2b=0、t2c=-t。因此,成為t2a+t2b+t2c=0。The
如參照圖1、圖2及圖5所說明,訊號生成部120調整相連脈波組AS、前脈波組BS及後脈波組CS中的至少兩個的脈波長。進而,與圖3所示的PWM訊號相比較,接通時間、接通時間各自的合計時間不變化。因此,可抑制伴隨切換動作的平均電流的變動。進而,圖3所示的例子中,在相位切換時機tsw的瞬間,電流振幅成為ΔI/2,相連脈波組AS期間中的電流波形暫時偏向高側,但圖5所示的例子中,電流波形的偏差得到抑制。因此,可進一步抑制伴隨切換動作的平均電流的變動。作為t的值,例如藉由設定為載波訊號CAS的週期的2%~10%,從而可有效地抑制平均電流的變動。As described with reference to FIGS. 1 , 2 and 5 , the
繼而,參照圖1、圖2及圖6,對本發明的實施形態的PWM訊號的由反相向正相的切換進行說明。圖6為表示本發明的實施形態的PWM訊號的圖。Next, with reference to FIG. 1 , FIG. 2 and FIG. 6 , the switching of the PWM signal from the reverse phase to the normal phase according to the embodiment of the present invention will be described. FIG. 6 is a diagram showing a PWM signal according to the embodiment of the present invention.
如圖6所示,訊號生成部120於相位切換時機tsw將PWM訊號的相位由反相切換為正相。與圖5所示的實施形態同樣地,相位切換時機tsw自載波訊號CAS的山部的時機延遲時間t。As shown in FIG. 6 , the
本實施形態中,相位切換時機tsw自載波訊號CAS的山部的時機延遲時間t。因此,伴隨切換的關斷的時刻延遲時間t。因此,訊號生成部120以補償延遲時間t的方式,調整相連斷開期間AToff及後斷開期間CToff。詳細而言,訊號生成部120以相連斷開期間AToff及後斷開期間CToff分別與將電壓指令值設為V的情形相比較延長t/2的方式,將使電壓指令值自V偏移的值設為電壓指令值。In this embodiment, the phase switching timing tsw is delayed by the time t from the timing of the peak of the carrier signal CAS. Therefore, the timing of the turn-off accompanying the switching is delayed by the time t. Therefore, the
此時,相連接通期間ATon由於伴隨切換的關斷的時刻延遲時間t,故而成為Ton/2+t。即,ATon=Ton/2+t。At this time, the connection-on period ATon becomes Ton/2+t due to the delay time t from the timing of the off-time accompanying the switching. That is, ATon=Ton/2+t.
另外,相連斷開期間AToff的關斷延遲時間t,而且因電壓指令值的偏移而開啟亦延遲t/2,故而成為Toff/2-t/2。即,AToff=Toff/2-t/2。In addition, the turn-off delay time t in the connection-off period AToff is delayed by t/2, and the turn-on is also delayed by t/2 due to the deviation of the voltage command value, so it becomes Toff/2−t/2. That is, AToff=Toff/2−t/2.
另外,後接通期間CTon因電壓指令值的偏移而縮短時間t,成為Ton-t。即,CTon=Ton-t。In addition, the post-on period CTon is shortened by the time t due to the deviation of the voltage command value, and becomes Ton−t. That is, CTon=Ton-t.
另外,後斷開期間CToff因電壓指令值的偏移而延遲t/2,成為Toff+t/2。即,CToff=Toff+t/2。In addition, the post-off period CToff is delayed by t/2 due to the deviation of the voltage command value, and becomes Toff+t/2. That is, CToff=Toff+t/2.
訊號生成部120調整相連接通期間ATon、前接通期間BTon及後接通期間CTon中的至少兩個。本實施形態中,訊號生成部120調整相連接通期間ATon及後接通期間CTon。相連接通期間ATon的調整值、前接通期間BTon的調整值及後接通期間CTon的調整值之和為0。本實施形態中,於將相連接通期間ATon的調整值設為t1a、前接通期間BTon的調整值設為t1b、後接通期間CTon的調整值設為t1c的情形時,成為t1a=t、t1b=0、t1c=-t。因此,成為t1a+t1b+t1c=0。The
訊號生成部120調整相連斷開期間AToff、前斷開期間BToff及後斷開期間CToff中的至少兩個。本實施形態中,訊號生成部120調整相連斷開期間AToff及後斷開期間CToff。相連斷開期間AToff的調整值、前斷開期間BToff的調整值及後斷開期間CToff的調整值之和為0。於將相連斷開期間AToff的調整值設為t2a、前斷開期間BToff的調整值設為t2b、後斷開期間CToff的調整值設為t2c的情形時,成為t2a=-t/2、t2b=0、t2c=t/2。因此,成為t2a+t2b+t2c=0。The
如參照圖1、圖2及圖6所說明,訊號生成部120調整相連脈波組AS、前脈波組BS及後脈波組CS中的至少兩個的脈波長。進而,與圖4所示的PWM訊號相比較,接通時間、接通時間各自的合計時間不變化。因此,可抑制伴隨切換動作的平均電流的變動。進而,圖4所示的例子中,於相位切換時機tsw的瞬間,電流振幅成為ΔI/2,相連脈波組AS期間中的電流波形暫時偏向低側,但圖6所示的例子中,電流波形的偏差得到抑制。因此,可進一步抑制伴隨切換動作的平均電流的變動。作為t的值,例如藉由設定為載波訊號CAS的週期的2%~10%,從而可有效地抑制平均電流的變動。As described with reference to FIGS. 1 , 2 and 6 , the
再者,參照圖5所說明的例子中,訊號生成部120使電壓指令值以換算成脈波長而相當於時間t/2的值偏移,但亦可使電壓指令值以換算成脈波長而相當於時間t的值偏移。Furthermore, in the example described with reference to FIG. 5 , the
參照圖1、圖2及圖7,對本發明的實施形態的PWM訊號加以說明。圖7為表示本發明的實施形態的PWM訊號的圖。1, FIG. 2 and FIG. 7, the PWM signal according to the embodiment of the present invention will be described. FIG. 7 is a diagram showing a PWM signal according to the embodiment of the present invention.
本實施形態中,相位切換時機tsw自載波訊號CAS的山部的時機延遲時間t。因此,伴隨切換的開啟的時刻延遲時間t。因此,訊號生成部120以補償延遲時間t的方式,調整相連接通期間ATon及後接通期間CTon。詳細而言,訊號生成部120以相連接通期間ATon及後接通期間CTon分別與將電壓指令值設為1-V的情形相比較延長t的方式,將使電壓指令值自1-V偏移的值設為電壓指令值。即,訊號生成部120使電壓指令值以換算成脈波長而相當於時間t的值偏移。In this embodiment, the phase switching timing tsw is delayed by the time t from the timing of the peak of the carrier signal CAS. Therefore, the timing of turning on accompanying the switching is delayed by the time t. Therefore, the
此時,相連斷開期間AToff由於伴隨切換的開啟的時刻延遲時間t,因而成為Toff/2+t。即,AToff=Toff/2+t。At this time, the disconnection period AToff becomes Toff/2+t due to the delay time t from the ON timing of the switching. That is, AToff=Toff/2+t.
另外,相連接通期間ATon的開啟延遲時間t,而且因電壓指令值的偏移而關斷亦延遲t,故而成為Ton/2。即,ATon=Ton/2。In addition, the turn-on of ATon is delayed by time t during the ON period, and the turn-off of ATon is delayed by t due to the deviation of the voltage command value, so it becomes Ton/2. That is, ATon=Ton/2.
另外,後斷開期間CToff因電壓指令值的偏移而縮短時間t,成為Toff-t。即,CToff=Toff-t。In addition, the post-off period CToff is shortened by the time t due to the deviation of the voltage command value, and becomes Toff-t. That is, CToff=Toff-t.
另外,後接通期間CTon成為Ton。即,CTon=Ton。In addition, CTon becomes Ton in the post-on period. That is, CTon=Ton.
本實施形態中,訊號生成部120不調整相連接通期間ATon、前接通期間BTon及後接通期間CTon。In the present embodiment, the
訊號生成部120調整相連斷開期間AToff、前斷開期間BToff及後斷開期間CToff中的至少兩個。本實施形態中,訊號生成部120調整相連斷開期間AToff及後斷開期間CToff。相連斷開期間AToff的調整值、前斷開期間BToff的調整值及後斷開期間CToff的調整值之和為0。於將相連斷開期間AToff的調整值設為t2a、前斷開期間BToff的調整值設為t2b、後斷開期間CToff的調整值設為t2c的情形時,成為t2a=t、t2b=0、t2c=-t。因此,成為t2a+t2b+t2c=0。The
如參照圖1、圖2及圖7所說明,訊號生成部120調整相連脈波組AS、前脈波組BS及後脈波組CS中的至少兩個的脈波長。進而,與圖4所示的PWM訊號相比較,接通時間、接通時間各自的合計時間不變化。因此,可抑制伴隨切換動作的平均電流的變動。再者,本例中,作為t的值,例如藉由設定載波訊號CAS的週期的5%~20%,從而可有效地抑制平均電流的變動。As described with reference to FIGS. 1 , 2 and 7 , the
再者,參照圖5~圖7所說明的例子中,訊號生成部120以補償延遲時間t的方式,調整相連接通期間ATon及後接通期間CTon,但訊號生成部120亦可以補償延遲時間t的方式來調整前接通期間BTon。Furthermore, in the examples described with reference to FIGS. 5 to 7 , the
參照圖1、圖2及圖8,對本發明的實施形態的PWM訊號加以說明。圖8為表示本發明的實施形態的PWM訊號的圖。1, 2 and 8, the PWM signal according to the embodiment of the present invention will be described. FIG. 8 is a diagram showing a PWM signal according to the embodiment of the present invention.
本實施形態中,相位切換時機tsw自載波訊號CAS的山部的時機延遲時間t。因此,伴隨切換的開啟的時刻延遲時間t。因此,訊號生成部120以事先補償延遲時間t的方式調整前接通期間BTon。詳細而言,訊號生成部120以前接通期間BTon與將電壓指令值設為V的情形相比較延長t的方式,將使電壓指令值自V偏移的值設為電壓指令值。更詳細而言,訊號生成部120以前接通脈波BSon的開啟時間提早t/2,且前接通脈波BSon的關斷時間延遲t/2的方式,將使電壓指令值自V偏移的值設為電壓指令值。即,訊號生成部120使電壓指令值以換算成脈波長而相當於時間t/2的值偏移。In this embodiment, the phase switching timing tsw is delayed by the time t from the timing of the peak of the carrier signal CAS. Therefore, the timing of turning on accompanying the switching is delayed by the time t. Therefore, the
此時,前斷開期間BToff因電壓指令值的偏移而縮短時間t/2,成為Toff-t/2。即,BToff=Toff-t/2。At this time, the pre-off period BToff is shortened by the time t/2 due to the deviation of the voltage command value, and becomes Toff-t/2. That is, BToff=Toff-t/2.
另外,前接通期間BTon因電壓指令值的偏移而開啟提早時間t/2,關斷延遲時間t/2,故而成為Ton+t。即,BTon=Ton+t。In addition, the pre-on period BTon is turned on by an early time t/2 and off by a delay time t/2 due to a shift in the voltage command value, and thus becomes Ton+t. That is, BTon=Ton+t.
另外,相連斷開期間AToff因關斷延遲時間t/2,且伴隨切換的開啟的時刻延遲時間t,故而成為Toff/2+t/2。即,AToff=Toff/2+t/2。In addition, the connection-off period AToff is Toff/2+t/2 because of the off-delay time t/2, and the time-on-time of the switch-on is delayed by the time t. That is, AToff=Toff/2+t/2.
另外,相連接通期間ATon因開啟延遲時間t,故而成為Ton/2-t。即,ATon=Ton/2-t。In addition, the continuous ON period ATon becomes Ton/2−t due to the ON delay time t. That is, ATon=Ton/2-t.
訊號生成部120調整相連接通期間ATon、前接通期間BTon及後接通期間CTon中的至少兩個。本實施形態中,訊號生成部120調整相連接通期間ATon及前接通期間BTon。相連接通期間ATon的調整值、前接通期間BTon的調整值及後接通期間CTon的調整值之和為0。本實施形態中,於將相連接通期間ATon的調整值設為t1a、前接通期間BTon的調整值設為t1b、後接通期間CTon的調整值設為t1c的情形時,成為t1a=-t、t1b=t、t1c=0。因此,成為t1a+t1b+t1c=0。The
訊號生成部120調整相連斷開期間AToff、前斷開期間BToff及後斷開期間CToff中的至少兩個。本實施形態中,訊號生成部120調整相連斷開期間AToff及前斷開期間BToff。相連斷開期間AToff的調整值、前斷開期間BToff的調整值及後斷開期間CToff的調整值之和為0。於將相連斷開期間AToff的調整值設為t2a、前斷開期間BToff的調整值設為t2b、後斷開期間CToff的調整值設為t2c的情形時,成為t2a=t/2、t2b=-t/2、t2c=0。因此,成為t2a+t2b+t2c=0。The
如參照圖1、圖2及圖8所說明,訊號生成部120調整相連脈波組AS、前脈波組BS及後脈波組CS中的至少兩個的脈波長。進而,與圖4所示的PWM訊號相比較,接通時間、接通時間各自的合計時間不變化。因此,可抑制伴隨切換動作的平均電流的變動。As described with reference to FIGS. 1 , 2 and 8 , the
再者,參照圖5~圖8所說明的例子中,相位切換時機tsw自載波訊號CAS的山部的時機延遲,但相位切換時機tsw亦可較載波訊號CAS的山部的時機更早。5 to 8, the phase switching timing tsw is delayed from the timing of the peak of the carrier signal CAS, but the phase switching timing tsw may be earlier than the timing of the peak of the carrier signal CAS.
參照圖1、圖2及圖9,對本發明的實施形態的PWM訊號加以說明。圖9為表示本發明的實施形態的PWM訊號的圖。1, 2 and 9, the PWM signal according to the embodiment of the present invention will be described. FIG. 9 is a diagram showing a PWM signal according to the embodiment of the present invention.
本實施形態中,相位切換時機tsw自載波訊號CAS的山部的時機提早時間t。因此,伴隨切換的開啟的時刻提早時間t。因此,訊號生成部120以調整提早時間t的方式調整前接通期間BTon。詳細而言,訊號生成部120以前接通期間BTon與將電壓指令值設為V的情形相比較而縮短t的方式,將使電壓指令值自V偏移的值設為電壓指令值。更詳細而言,訊號生成部120以前接通脈波BSon的開啟時間延遲t/2,且前接通脈波BSon的關斷時間提早t/2的方式,將使電壓指令值自V偏移的值設為電壓指令值。即,訊號生成部120使電壓指令值以換算為脈波長而相當於時間t/2的值偏移。In this embodiment, the phase switching timing tsw is advanced by the time t from the timing of the peak of the carrier signal CAS. Therefore, the timing of the turn-on accompanying the switching is advanced by the time t. Therefore, the
此時,前斷開期間BToff由於關斷延遲時間t/2,故而成為Toff+t/2。即,BToff=Toff+t/2。At this time, the pre-off period BToff becomes Toff+t/2 due to the off delay time t/2. That is, BToff=Toff+t/2.
另外,前接通期間BTon因電壓指令值的偏移而開啟延遲時間t/2,關斷提早時間t/2,故而成為Ton-t。即,BTon=Ton-t。In addition, the pre-on period BTon is turned on by a delay time t/2 and is turned off early by a time t/2 due to a shift in the voltage command value, and thus becomes Ton−t. That is, BTon=Ton-t.
另外,相連斷開期間AToff由於關斷提早時間t/2,且伴隨切換的開啟的時刻提早時間t,故而成為Toff/2-t/2。即,AToff=Toff/2-t/2。In addition, the connection-off period AToff is Toff/2−t/2 because the turn-off time t/2 is advanced, and the turn-on time accompanying the switching is advanced by the time t. That is, AToff=Toff/2−t/2.
另外,相連接通期間ATon由於開啟提早時間t,故而成為Ton/2+t。即,ATon=Ton/2+t。In addition, the continuous-on period ATon becomes Ton/2+t due to the turn-on advance time t. That is, ATon=Ton/2+t.
訊號生成部120調整相連接通期間ATon、前接通期間BTon及後接通期間CTon中的至少兩個。本實施形態中,訊號生成部120調整相連接通期間ATon及前接通期間BTon。相連接通期間ATon的調整值、前接通期間BTon的調整值及後接通期間CTon的調整值之和為0。本實施形態中,於將相連接通期間ATon的調整值設為t1a、前接通期間BTon的調整值設為t1b、後接通期間CTon的調整值設為t1c的情形時,成為t1a=t、t1b=-t、t1c=0。因此,成為t1a+t1b+t1c=0。The
訊號生成部120調整相連斷開期間AToff、前斷開期間BToff及後斷開期間CToff中的至少兩個。本實施形態中,訊號生成部120調整相連斷開期間AToff及前斷開期間BToff。相連斷開期間AToff的調整值、前斷開期間BToff的調整值及後斷開期間CToff的調整值之和為0。於將相連斷開期間AToff的調整值設為t2a、前斷開期間BToff的調整值設為t2b、後斷開期間CToff的調整值設為t2c的情形時,成為t2a=-t/2、t2b=t/2、t2c=0。因此,成為t2a+t2b+t2c=0。The
如參照圖1、圖2及圖9所說明,訊號生成部120調整相連脈波組AS、前脈波組BS及後脈波組CS中的至少兩個的脈波長。進而,與圖4所示的PWM訊號相比較,接通時間、接通時間各自的合計時間不變化。因此,可抑制伴隨切換動作的平均電流的變動。As described with reference to FIGS. 1 , 2 and 9 , the
再者,參照圖3~圖9所說明的例子中,載波訊號CAS為三角波,但載波訊號CAS亦可為鋸齒。Furthermore, in the examples described with reference to FIGS. 3 to 9 , the carrier signal CAS is a triangular wave, but the carrier signal CAS may also be a sawtooth.
參照圖1、圖2及圖10,對本發明的實施形態的PWM訊號加以說明。圖10為表示本發明的實施形態的PWM訊號的圖。1, 2 and 10, the PWM signal according to the embodiment of the present invention will be described. FIG. 10 is a diagram showing a PWM signal according to the embodiment of the present invention.
如圖10所示,本實施形態中,載波訊號CAS為鋸齒波。此處,訊號生成部120於相位切換時機tsw將PWM訊號的相位由正相切換為反相。As shown in FIG. 10, in this embodiment, the carrier signal CAS is a sawtooth wave. Here, the
PWM訊號具有正相PWM訊號PS、反相PWM訊號NS、相連脈波組AS、前脈波組BS及後脈波組CS。The PWM signal includes a positive-phase PWM signal PS, a negative-phase PWM signal NS, a connected pulse wave group AS, a pre-pulse wave group BS, and a post-pulse wave group CS.
為了抑制伴隨PWM訊號的相位的切換動作的平均電流的變動,較佳為使前接通脈波BSon的開啟時的電流Ia、與後接通脈波CSon的開啟時的電流Ib儘可能一致。即,較佳為以於前接通脈波BSon的關斷至後接通脈波CSon的開啟為止的時間2Toff的期間中,電流降低ΔI的方式,設定相連接通期間ATon。In order to suppress the fluctuation of the average current accompanying the switching operation of the phase of the PWM signal, it is preferable to make the current Ia when the preceding on-pulse wave BSON is turned on and the current Ib when the subsequent on-pulse wave CSon is turned on to match as much as possible. That is, it is preferable to set the continuous on period ATon so that the current decreases by ΔI during the period of time 2Toff from the turning off of the preceding on pulse wave BSon to the turning on of the subsequent on pulse wave CSon.
若以時間Ton接通則電流增加ΔI,若以時間Toff斷開則電流減小ΔI,故而相連接通期間ATon較佳為作為T=Ton+Toff而設定為ATon=Toff×Ton/T。The current increases by ΔI when it is turned on for time Ton, and decreases by ΔI when it is turned off for time Toff. Therefore, ATon is preferably set to ATon=Toff×Ton/T as T=Ton+Toff.
於設定為ATon=Toff×Ton/T的情形時,自前接通脈波BSon至後接通脈波CSon為止之間的斷開期間為2Toff-ATon=Toff×(1+Toff/T)。接通期間的電流上升為ΔI×ATon/Ton=ΔI·Toff/T。斷開期間的電流減小為ΔI×Toff×(1+Toff/T)/Toff=ΔI+ΔI·Toff/T。因此,接通期間的電流上升與斷開期間的電流減小之差量、即自前接通脈波BSon的關斷至後接通脈波CSon的開啟為止的電流減小成為ΔI。因此,可使前接通脈波BSon的開啟時的電流Ia、與後接通脈波CSon的開啟時的電流Ib一致。其結果為,可抑制伴隨PWM訊號的相位的切換動作的平均電流的變動。In the case where ATon=Toff×Ton/T is set, the off period from the pulse wave BSon on the front to the pulse wave CSon on the back is 2Toff−ATon=Toff×(1+Toff/T). The current rise during the ON period is ΔI×ATon/Ton=ΔI·Toff/T. The current during the OFF period is reduced to ΔI×Toff×(1+Toff/T)/Toff=ΔI+ΔI·Toff/T. Therefore, the difference between the current increase in the ON period and the current decrease in the OFF period, that is, the current decrease from the turn-off of the preceding ON pulse wave BSON to the ON of the succeeding ON pulse wave CSon becomes ΔI. Therefore, the current Ia at the time of turning on of the preceding on-pulse wave BSON can be matched with the current Ib at the time of turning on the subsequent on-pulse wave CSon. As a result, the fluctuation of the average current accompanying the switching operation of the phase of the PWM signal can be suppressed.
訊號生成部120於相位切換時機tsw,以相連接通期間ATon成為Toff×Ton/T的方式,將使電壓指令值自1-V偏移的值設為電壓指令值。At the phase switching timing tsw, the
繼而,參照圖1、圖2及圖11,對本發明的實施形態的PWM訊號的由反相向正相的切換進行說明。圖11為表示本發明的實施形態的PWM訊號的圖。Next, with reference to FIGS. 1 , 2 and 11 , the switching of the PWM signal from the reverse phase to the normal phase according to the embodiment of the present invention will be described. FIG. 11 is a diagram showing a PWM signal according to the embodiment of the present invention.
如圖11所示,本實施形態中,載波訊號CAS為鋸齒波。此處,訊號生成部120於相位切換時機tsw將PWM訊號的相位由反相切換為正相。As shown in FIG. 11, in this embodiment, the carrier signal CAS is a sawtooth wave. Here, the
PWM訊號具有正相PWM訊號PS、反相PWM訊號NS、相連脈波組AS、前脈波組BS及後脈波組CS。The PWM signal includes a positive-phase PWM signal PS, a negative-phase PWM signal NS, a connected pulse wave group AS, a pre-pulse wave group BS, and a post-pulse wave group CS.
本實施形態中,相連脈波組AS的相連接通脈波ASon、與後脈波組CS的後接通脈波CSon相連。In the present embodiment, the continuous on-pulse wave ASon of the continuous pulse wave group AS is connected to the subsequent on-pulse wave CSon of the subsequent pulse wave group CS.
為了抑制伴隨PWM訊號的相位的切換動作的平均電流的變動,較佳為使前接通脈波BSon的開啟時的電流Ic、與後接通脈波CSon的開啟時的電流Id儘可能一致。即,較佳為以於自前接通脈波BSon的關斷至後接通脈波CSon的開啟為止的時間T的期間中,電流降低ΔI的方式,設定相連接通期間ATon。In order to suppress the fluctuation of the average current accompanying the switching operation of the phase of the PWM signal, it is preferable to make the current Ic when the preceding on-pulse BSON is turned on and the current Id when the subsequent on-pulse CSon turn on as much as possible. That is, it is preferable to set the continuous-on period ATon so that the current decreases by ΔI during the period from the turn-off of the pre-on pulse wave BSon to the turn-on of the post-on pulse wave CSon.
若以時間Ton接通則電流增加ΔI,若以時間Toff斷開則電流減小ΔI,故而相連接通期間ATon較佳為作為T=Ton+Toff而設定為ATon=Ton-TonToff/T。The current increases by ΔI when it is turned on for time Ton, and decreases by ΔI when it is turned off for time Toff. Therefore, ATon is preferably set to ATon=Ton-TonToff/T as T=Ton+Toff.
於設定為ATon=Ton-TonToff/T的情形時,自前接通脈波BSon至後接通脈波CSon為止之間的斷開期間為Toff+TonToff/T。接通期間的電流上升為ΔI×ATon/Ton=ΔI-ΔI·Toff/T。斷開期間的電流減小為ΔI×(Toff+TonToff/T)/Toff=ΔI+ΔI·Ton/T。因此,接通期間的電流上升與斷開期間的電流減小之差量、即自前接通脈波BSon的關斷至後接通脈波CSon的開啟為止的電流減小成為ΔI。因此,可使前接通脈波BSon的開啟時的電流Ic、與後接通脈波CSon的開啟時的電流Id一致。其結果為,可抑制伴隨PWM訊號的相位的切換動作的平均電流的變動。In the case where ATon=Ton−TonToff/T is set, the off period from when the pulse wave BSon is turned on before and when the pulse wave CSon is turned on after is Toff+TonToff/T. The current rise during the ON period is ΔI×ATon/Ton=ΔI−ΔI·Toff/T. The current during the OFF period is reduced to ΔI×(Toff+TonToff/T)/Toff=ΔI+ΔI·Ton/T. Therefore, the difference between the current increase in the ON period and the current decrease in the OFF period, that is, the current decrease from the turn-off of the preceding ON pulse wave BSON to the ON of the succeeding ON pulse wave CSon becomes ΔI. Therefore, the current Ic when the pre-on pulse wave BSON is turned on can be made to match the current Id when the post-on pulse wave CSon is turned on. As a result, the fluctuation of the average current accompanying the switching operation of the phase of the PWM signal can be suppressed.
訊號生成部120於相位切換時機tsw,以相連接通期間ATon成為Ton-TonToff/T的方式,將使電壓指令值自V偏移的值設為電壓指令值。At the phase switching timing tsw, the
再者,參照圖3~圖11所說明的例子中,變更電壓指令值,但電壓指令值亦可為一定。Furthermore, in the examples described with reference to FIGS. 3 to 11 , the voltage command value is changed, but the voltage command value may be constant.
參照圖1、圖2及圖12,對本發明的實施形態的PWM訊號加以說明。圖12為表示本發明的實施形態的PWM訊號的圖。1, 2 and 12, the PWM signal according to the embodiment of the present invention will be described. FIG. 12 is a diagram showing a PWM signal according to the embodiment of the present invention.
如圖12所示,本實施形態中,電壓指令值為一定。本實施形態中,於相位切換時機tsw,變更載波訊號CAS的相位。詳細而言,於相位切換時機tsw,將載波訊號CAS由山部向谷部切換。因此,訊號生成部120的比較部126的載波訊號CAS與電壓指令值的比較處理亦無須以正相及反相進行切換。例如,可如若載波訊號大於電壓指令值則斷開,若載波訊號大於電壓指令值則接通般,以正相及反相統一處理。因此,於PWM訊號的相位的切換處理時,可簡化運算。As shown in FIG. 12, in this embodiment, the voltage command value is constant. In the present embodiment, the phase of the carrier signal CAS is changed at the phase switching timing tsw. Specifically, at the phase switching timing tsw, the carrier signal CAS is switched from the mountain portion to the valley portion. Therefore, the comparison process of the carrier signal CAS and the voltage command value of the comparing
再者,參照圖12所說明的例子中,亦與參照圖5~圖9所說明的例子同樣地,相位切換時機tsw亦可自載波訊號CAS的山部的時機偏移。Furthermore, in the example described with reference to FIG. 12 , as in the examples described with reference to FIGS. 5 to 9 , the phase switching timing tsw may be shifted from the timing of the peak portion of the carrier signal CAS.
再者,參照圖3~圖9及圖12所說明的例子中,載波訊號CAS為三角波,參照圖10及圖11所說明的例子中,載波訊號CAS為鋸齒,但載波訊號CAS亦可對於三角波與鋸齒,於相位切換時機tsw切換三角波與鋸齒。例如,亦可於正相的情形時載波訊號CAS設為三角波,且反相的情形時載波訊號CAS設為鋸齒波。或者,亦可於正相的情形時載波訊號CAS設為鋸齒波,於反相的情形時載波訊號CAS設為三角波。Furthermore, in the examples described with reference to FIGS. 3 to 9 and FIG. 12 , the carrier signal CAS is a triangular wave. In the examples described with reference to FIGS. 10 and 11 , the carrier signal CAS is a sawtooth, but the carrier signal CAS may also be a triangular wave. With the sawtooth, the triangular wave and the sawtooth are switched at the phase switching timing tsw. For example, the carrier signal CAS can also be set as a triangular wave in the case of normal phase, and the carrier signal CAS can be set as a sawtooth wave in the case of reverse phase. Alternatively, the carrier signal CAS can be set as a sawtooth wave in the case of positive phase, and the carrier signal CAS can be set as a triangular wave in the case of reverse phase.
以上,一方面參照圖式(圖1~圖12)一方面對本發明的實施形態進行了說明。然而,本發明不限於所述實施形態,可於不偏離其主旨的範圍內以各種態樣實施。圖式為了容易理解而主體上示意性地表示各構成要素,但圖示的各構成要素的厚度、長度、個數等為了方便製作圖式而與實際不同。另外,所述實施形態所示的各構成要素的材質或形狀、尺寸等為一例,且並無特別限定,可於實質上不偏離本發明的效果的範圍進行各種變更。The embodiments of the present invention have been described above with reference to the drawings ( FIGS. 1 to 12 ). However, this invention is not limited to the said embodiment, It can implement in various forms in the range which does not deviate from the summary. In the drawings, each component is mainly schematically shown for easy understanding, but the thickness, length, number, etc. of each component shown in the drawings are different from actual ones for the convenience of drawing. In addition, the material, shape, size, etc. of each component shown in the above-described embodiment are examples, and are not particularly limited, and various changes can be made within a range that does not substantially deviate from the effects of the present invention.
100:馬達驅動電路 110:逆變器部 102、102u、102v、102w:輸出端子 112、112u、112v、112w:串聯體 114、114u、114v、114w:連接點 120:訊號生成部 122:載波生成部 124:電壓指令值生成部 126:比較部 200:馬達模組 AS:相連脈波組 ASoff:相連斷開脈波 ASon:相連接通脈波 AT:相連脈波組期間 AToff:相連斷開期間 ATon:相連接通期間 B:直流電壓源 BS:前脈波組 BSoff:前斷開脈波 BSon:前接通脈波 BToff:前斷開期間 BTon:前接通期間 C:電容器 CAS:載波訊號 CS:後脈波組 CSoff:後斷開脈波 CSon:後接通脈波 CToff:後斷開期間 CTon:後接通期間 D:整流元件 Iu、Iv、Iw:輸出電流 M:三相馬達 N:第二輸入端子 NS:反相PWM訊號 NT:反相 PWM期間 P:第一輸入端子 PS:正相PWM訊號 PT:正相PWM期間 T:PWM週期 Toff:斷開期間 Ton:接通期間
Un、Vn、Wn:第二半導體切換元件 Up、Vp、Wp:第一半導體切換元件 V1:第一電壓 V2:第二電壓 t:時間 tsw:相位切換時機
100: Motor drive circuit 110:
圖1為本發明的實施形態的馬達模組的區塊圖。圖2為表示逆變器部的電路圖。圖3為表示本發明的實施形態的PWM訊號的圖。圖4為表示本發明的實施形態的PWM訊號的圖。圖5為表示本發明的實施形態的PWM訊號的圖。圖6為表示本發明的實施形態的PWM訊號的圖。圖7為表示本發明的實施形態的PWM訊號的圖。圖8為表示本發明的實施形態的PWM訊號的圖。圖9為表示本發明的實施形態的PWM訊號的圖。圖10為表示本發明的實施形態的PWM訊號的圖。圖11為表示本發明的實施形態的PWM訊號的圖。 圖12為表示本發明的實施形態的PWM訊號的圖。FIG. 1 is a block diagram of a motor module according to an embodiment of the present invention. FIG. 2 is a circuit diagram showing an inverter unit. FIG. 3 is a diagram showing a PWM signal according to the embodiment of the present invention. FIG. 4 is a diagram showing a PWM signal according to the embodiment of the present invention. FIG. 5 is a diagram showing a PWM signal according to the embodiment of the present invention. FIG. 6 is a diagram showing a PWM signal according to the embodiment of the present invention. FIG. 7 is a diagram showing a PWM signal according to the embodiment of the present invention. FIG. 8 is a diagram showing a PWM signal according to the embodiment of the present invention. FIG. 9 is a diagram showing a PWM signal according to the embodiment of the present invention. FIG. 10 is a diagram showing a PWM signal according to the embodiment of the present invention. FIG. 11 is a diagram showing a PWM signal according to the embodiment of the present invention. FIG. 12 is a diagram showing a PWM signal according to the embodiment of the present invention.
AS:相連脈波組 AS: Linked pulse group
ASoff:相連斷開脈波 ASoff: connected disconnected pulse
ASon:相連接通脈波 ASon: Connected Pulse
AT:相連脈波組期間 AT: During the continuous pulse group
AToff:相連斷開期間 AToff: During disconnection
ATon:相連接通期間 ATon: During the connection
CAS:載波訊號 CAS: carrier signal
NS:反相PWM訊號 NS: Inverted PWM signal
NT:反相PWM期間 NT: Inverted PWM period
PS:正相PWM訊號 PS: positive phase PWM signal
PT:正相PWM期間 PT: Non-inverting PWM period
T:PWM週期 T: PWM period
Toff:斷開期間 Toff: During disconnection
Ton:接通期間 Ton: During the ON period
tsw:相位切換時機 tsw: Phase switching timing
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TWI806784B (en) * | 2022-09-30 | 2023-06-21 | 台達電子工業股份有限公司 | Power conversion circuit for driving motor and control method thereof |
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US8378606B2 (en) * | 2009-10-08 | 2013-02-19 | Microchip Technology Incorporated | Synchronized minimum frequency pulse width modulation drive for sensorless brushless direct current motor |
EP2613106B1 (en) * | 2010-08-30 | 2015-09-23 | Mitsubishi Electric Corporation | Heat pump device, heat pump system and three-phase inverter control method |
JP6331925B2 (en) * | 2014-09-25 | 2018-05-30 | 株式会社安川電機 | Matrix converter, power generation system, and power conversion method |
JP6988172B2 (en) * | 2017-05-30 | 2022-01-05 | 株式会社富士通ゼネラル | Power converter |
JP6732063B1 (en) * | 2019-02-19 | 2020-07-29 | 三菱電機株式会社 | Electric power conversion device, generator motor control device, and electric power steering device |
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TWI806784B (en) * | 2022-09-30 | 2023-06-21 | 台達電子工業股份有限公司 | Power conversion circuit for driving motor and control method thereof |
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WO2022070446A1 (en) | 2022-04-07 |
CN116250173A (en) | 2023-06-09 |
TWI784727B (en) | 2022-11-21 |
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