TW202143667A - 參考信號通道估計 - Google Patents

參考信號通道估計 Download PDF

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TW202143667A
TW202143667A TW110111733A TW110111733A TW202143667A TW 202143667 A TW202143667 A TW 202143667A TW 110111733 A TW110111733 A TW 110111733A TW 110111733 A TW110111733 A TW 110111733A TW 202143667 A TW202143667 A TW 202143667A
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reference signal
frequency domain
processing circuit
domain processing
frequency
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彼得 約翰 布萊克
陳琻滬
蔣靖
塔莫 艾德爾 卡道斯
萬侖 趙
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美商艾斯康實驗室公司
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/022—Channel estimation of frequency response
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/0224—Channel estimation using sounding signals
    • H04L25/0228—Channel estimation using sounding signals with direct estimation from sounding signals
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/0224—Channel estimation using sounding signals
    • H04L25/0228—Channel estimation using sounding signals with direct estimation from sounding signals
    • H04L25/023—Channel estimation using sounding signals with direct estimation from sounding signals with extension to other symbols
    • H04L25/0232—Channel estimation using sounding signals with direct estimation from sounding signals with extension to other symbols by interpolation between sounding signals
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/0212—Channel estimation of impulse response
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03828—Arrangements for spectral shaping; Arrangements for providing signals with specified spectral properties
    • H04L25/03834—Arrangements for spectral shaping; Arrangements for providing signals with specified spectral properties using pulse shaping

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Abstract

本發明之態樣係關於參考信號通道估計。兩個節點之間之一無線通信通道可係基於諸如一探測參考信號之一經接收參考信號來估計。揭示改良參考信號通道估計之效能，並於存在各種損害中之一或多者的情形下，使得通道估計更加穩健的技術。可執行頻域處理及/或時域處理，以減小通道估計中之失真。

Description

參考信號通道估計
本發明之實施例係關於使用一參考信號估計一通信系統中之一通道。
在一無線通信系統中，可期望具有一使用者設備與一基地台之間的一通信通道之一準確估計。某些通信標準包含可用於估計一通信通道之參考信號。此一參考信號可用於估計自一使用者設備至一基地台之一上行鏈路通道。在某些應用中，可基於上行鏈路通道估計自基地台至使用者設備再至基地台之一下行鏈路通道。在真實世界無線通信系統中，一通道估計可由於各種原因而降級。
申請專利範圍中闡述之創新各自具有數個態樣，其中無任一單個態樣能單獨決定其所期望屬性。在不限制申請專利範圍之範疇之情形下，現將簡要闡述本發明之某些顯著特徵。
本發明之一個態樣係一種參考信號通道估計之方法。該方法包括：接收用於通道估計之一參考信號；在一頻域中對該參考信號進行去覆蓋以產生一經去覆蓋參考信號；在該去覆蓋之後，對該經去覆蓋參考信號進行頻域處理以使該經去覆蓋參考信號中之一直流偏移之失真減小；在該頻域處理之後，進行時域處理以使與該經去覆蓋參考信號相關聯之一雜訊底部減小；及基於該頻域處理及該時域處理產生一通道估計，其中該通道估計和一第一節點與一第二節點之間的一通信通道相關聯。
該頻域處理可包括：基於該經去覆蓋頻域參考信號之至少兩個其他頻調產生針對該經去覆蓋頻域參考信號之一頻調之一經估計頻調。該頻域處理可包括：用該經估計頻調替換該頻調以使與該直流偏移相關聯之失真減小。該頻域處理可包括：基於該經估計頻調修改該頻調以使與該直流偏移相關聯之失真減小。
該頻域處理可包括：對該經去覆蓋頻域參考信號進行脈波塑形以使與該直流偏移相關聯之失真減小。
該時域處理可包括：估計對應於通道脈衝回應之間的副載波之時域抽頭之一子集之雜訊功率，並基於該估計對該等時域抽頭之至少一部分執行一每抽頭擴縮。該每抽頭擴縮可涉及最小均方誤差擴縮。該每抽頭擴縮可涉及臨限值化。
該方法可進一步包括：在該去覆蓋之前，對該參考信號進行脈波塑形。
該方法可進一步包括：在該去覆蓋之前，基於一頻率偏移之一指示符旋轉該參考信號。
該時域處理可包括：將一混附雜訊(spur)移動至用於該參考信號之循環移位之時域窗之外。該方法可進一步包括：在該去覆蓋之前，對該參考信號進行脈波塑形。
該參考信號可係一上行鏈路探測參考信號。
該第一節點可係一使用者設備且該第二節點可係一網路節點。該第一節點可係一使用者設備且該第二節點可包含一遠端無線電單元。該第一節點可係一使用者設備且該第二節點可包含與一天線前端整合之一基地台。該第一節點可包含一第一遠端無線電單元且該第二節點可包含一第二遠端無線電單元。該第一節點可係一第一使用者設備且該第二節點可係一第二使用者設備。
本發明之另一態樣係用於通道估計之一系統。該系統包括：一頻域處理電路、一時域處理電路，及通道估計電路。該頻域處理電路經組態以產生一經去覆蓋頻域參考信號，並處理該經去覆蓋頻域參考信號以便使與一直流偏移相關聯之失真減小。該時域處理電路具有耦合至該頻域處理電路之一輸出之一輸入。該時域處理電路經組態以抑制時域通道脈衝回應洩漏。該通道估計電路經組態以基於該時域處理電路之一輸出產生一通道估計，其中該通道估計和一第一節點與一第二節點之間的一無線通信通道相關聯。
該頻域處理電路可經組態以基於該經去覆蓋頻域參考信號之至少兩個其他頻調產生針對該經去覆蓋頻域參考信號之一頻調之一經估計頻調，並用該經估計頻調替換該頻調以使與該直流偏移相關聯之失真減小。
該頻域處理電路可經組態以對該經去覆蓋頻域參考信號執行脈波塑形以使與該直流偏移相關聯之失真減小。
該時域處理電路可包括：一濾波器，其包括複數個抽頭；一雜訊功率估計電路，其經組態以估計對應於通道脈衝回應之間的副載波之該濾波器之該等抽頭之一子集之雜訊功率；及一濾波器抽頭擴縮電路，其經組態以基於該經估計雜訊功率對該濾波器之該等抽頭之至少一部分執行一每抽頭擴縮。
該時域處理電路可經組態以將一混附雜訊移動至用於該參考信號之循環移位之時域窗之外。
該系統可進一步包括一第二時域處理電路，其經組態以對一參考信號進行脈波塑形，該第二時域處理電路具有耦合至該頻域處理電路之一輸入之一輸出。
該系統可進一步包括一第二時域處理電路，其經組態以基於一頻域偏移之一指示符旋轉一參考信號以藉此減小該頻域偏移，其中該第二時域處理電路具有耦合至該頻域處理電路之一輸入之一輸出。
該系統可進一步包括一第二頻域處理電路，其經組態以執行每循環移位頻域處理，其中該第二頻域處理電路耦合於該時域處理電路與該通道估計電路之間。
該第一節點可係一使用者設備且該第二節點可係一網路節點。該第一節點可係一使用者設備且該第二節點可包含一遠端無線電單元。該第一節點可係一使用者設備且該第二節點可包含與一天線前端整合之一基地台。
該經去覆蓋頻域參考信號可係一經去覆蓋上行鏈路探測參考信號。
本發明之另一態樣係用於通道估計之一系統，該系統包括：用於處理一經去覆蓋頻域參考信號以便使與一直流偏移相關聯之失真減小之構件；用於抑制時域通道脈衝回應洩漏之構件，用於抑制之該構件 具有耦合至用於處理之該構件之一輸出之一輸入；及一通道估計電路，其經組態以基於用於抑制之該構件之一輸出產生一通道估計，其中該通道估計和一第一節點與一第二節點之間的一無線通信通道相關聯。
出於概述本發明之目的，本文中已闡述創新之優點及新穎特徵。應理解，未必可根據任何特定實施例來達成所有此等優點。因此，可以達成或最佳化如本文中所教示之一個優點或優點群組而未必達成如本文中可教示或建議之其他優點之一方式來體現或實施創新。
優先權申請案之交叉參考
本申請案主張2020年3月31日提出申請且標題為「REFERENCE SIGNAL CHANNEL ESTIMATION」之美國專利申請案第16/836,668號之優先權的權益，該美國專利申請案之揭示內容係以全文引用的方式且出於所有目的併入本文中。
某些實施例之以下說明呈現特定實施例之各種說明。然而，本文中闡述之創新可以(舉例而言)如申請專利範圍所定義及涵蓋之大量不同方式予以體現。在本說明中，參考其中相似元件符號可指示相同或功能上類似之元件之圖式。將理解，各圖中所圖解說明之元件未必按比例繪製。而且，將理解，某些實施例可包含比一圖式中所圖解說明更多的元件及/或一圖式中所圖解說明之元件之一子集。此外，某些實施例可併入來自兩個或更多個圖式之特徵之任何適合組合。本文中所提供之標題僅為了方便起見，且未必影響申請專利範圍之範疇或意義。
在長程演進(LTE)及新無線電(NR)系統中，一探測參考信號(SRS)可自一使用者設備(UE)傳輸至一節點B，用於估計一上行鏈路通道。更大體而言，一SRS可自一第一節點之一天線傳輸至一第二節點之一天線。對於時分雙工(TDD)系統，可基於通道互易性使用SRS通道估計(CE)來估計一下行鏈路通道品質。在基於碼簿及/或正則化逼零(RZF)預編碼之多輸入多輸出(MIMO)系統中，SRS CE可用於選擇一預編碼矩陣。在此等例項中，尤其在RZF預編碼應用中，期望SRS CE之準確性高。SRS CE可用於校準。
在一真實世界系統中存在可降級SRS CE之效能之各種損害。此等損害包含但不限於以下各項中之一或多者：頻率偏移、時序偏移、時域通道脈衝回應(CIR)洩漏，或相對低頻頻調之失真。此外，邊緣頻調之輸出SRS CE可歸因於頻域中之SRS之一不連續性而係不準確的。在本發明中，提供改良SRS CE之效能之技術以在存在一或多個損害之情形下使得通道估計更加穩健。探測參考訊號
在LTE及第五代(5G) NR中，一SRS之建構通常包含SRS序列產生及至實體資源之映射。可根據一相關通信標準產生SRS。SRS可係本文中所揭示之任何適合實施例中之一上行鏈路SRS。
在LTE及/或NR上行鏈路傳輸中，可存在用於將SRS傳輸至經排程UE之專用正交頻域多工(OFDM)符號。在每一符號中，用於SRS之𝑚𝑆𝑅𝑆資源區塊可由UE之一群組共用。用於SRS之𝑚𝑆𝑅𝑆資源區塊中之所有副載波可劃分成𝐾𝑇𝐶 個正交梳。一正交梳可係在一既定時間分配的在頻域中正交之信號之一群組。每一梳中之資源元素MZC 之數目可根據方程式1，其中MZC 可表示一SRS序列之一長度。
Figure 02_image001
(方程式1)
在方程式1中，
Figure 02_image003
係每一資源區塊中之副載波之數目。舉例而言，
Figure 02_image005
可係12。在每一梳內，𝑀𝑍𝐶 資源元素透過不同循環移位由最多
Figure 02_image007
個SRS共用。傳輸梳數目𝐾𝑇𝐶 由基地台表示且可取值2或4。一個梳可支援之循環移位之最大數目
Figure 02_image009
可係𝐾𝑇𝐶 之一函數，如由方程式2所指示。
Figure 02_image011
(方程式2)
為了使UE經由𝑚𝑆𝑅𝑆資源區塊傳輸一SRS，UE應產生長度為𝑀𝑍𝐶 之一SRS序列。對於UE，第一步可係獲得長度為𝑀𝑍𝐶 之一基本序列𝑟̅𝑢 , (𝑛)，其中n表示經分配頻調之索引。對於一既定長度𝑀𝑍𝐶 ，可存在30或60個基本序列𝑟̅𝑢 , 𝑣 (𝑛)，該等基本序列被劃分成若干個群組，其中𝑢 ∈ {0, 1, ⋯ , 29}係群組數目。一個群組中可存在一個或兩個序列，且一群組內之基本序列索引可分別係𝑣 = {0}或𝑣 = {0, 1}。
對於𝑀𝑍𝐶 ≥ 36，𝑟̅𝑢 ,v (𝑛)可藉由方程式3自一紮德奧夫－朱(Zadoff-Chu (ZC))序列獲得。
Figure 02_image013
(方程式3)
在方程式3中，𝑁𝑍𝐶 可係最大素數使得𝑁𝑍𝐶 ＜ 𝑀𝑍𝐶 ，且xq (𝑚)係自方程式4-1至4-3獲得之長度為𝑁𝑍𝐶 之一ZC序列。
Figure 02_image015
對於𝑀𝑍𝐶 ＜ 36，可根據一第三代夥伴計劃(3GPP)標準產生𝑟̅𝑢 ,v (𝑛)。
可組態用於SRS之群組及序列跳躍。在群組或序列跳躍中，可藉由變化用於每一SRS符號之𝑢及𝑣來選擇一基本序列。在諸多應用中，可停用群組或序列跳躍並簡化𝑢及𝑣之計算，分別如方程式5-1及5-2中所展示。
Figure 02_image017
在方程式5-1中，
Figure 02_image019
由較高層給出。在下文中，假定停用群組或序列跳躍，且因此基本序列表示為𝑟̅(𝑛)，其中下標𝑢及𝑣被省略。
在每一UE中獲得基本序列𝑟̅(𝑛)之後，可藉由根據方程6在頻域中應用一循環移位來產生SRS序列𝑟( 𝑐 ) (𝑛)。
Figure 02_image021
(方程式6)
在方程式6中，𝑐係循環移位索引。接著，將r( 𝑐 ) (𝑛)映射至一經分配梳，該經分配梳透過一逆快速傅立葉變換(IFFT)轉換為時域信號。時域信號可經由具有通道脈衝回應(CIR) ℎ𝑐 (𝑡)，0 ≤ 𝑐 ＜
Figure 02_image023
之通道傳輸至一特定天線。圖1中展示用於SRS模型之一總體方塊圖。
圖1係與一參考信號模型相關聯之一示意性方塊圖。在圖1中，複數個UE 10A、UE 10B、UE 10N經由各別通道12A、12B、12N將具有不同循環移位之SRS無線地傳輸至一節點B 14。不同循環移位可識別哪個裝置及/或天線無線地傳輸一SRS。在一加總點13處，SRS可在參考信號模型中加總。節點B 14可包含一射頻(RF)降頻轉換區塊16及一取樣與循環首碼(CP)移除區塊18。RF降頻轉換區塊16可降頻轉換一經接收RF信號。舉例而言，此降頻轉換可係轉換為基頻。取樣及CP移除區塊18可對經降頻轉換之RF參考信號進行取樣。取樣及CP移除區塊18可移除一循環首碼。節點B 14可自SRS (自UE 10A、UE 10B、UE 10N接收)產生時域接收樣本。節點B 14可係一演進節點B (eNodeB)、一下一代節點B (gNode B)，或者被替換，及/或與任何適合基地台或網路系統一起實施。
在循環移位之最大數目係8之情形下，參考信號模型中可存在8個UE及8個通道。類似地，在循環移位之最大數目係12之情形下，參考信號模型中可存在12個UE及12個通道。任何其他適合數目之最大循環移位及對應通道可根據本文中所揭示之任何適合原則及優點來實施。
儘管在圖1中圖解說明UE，但本文中所揭示之原則及優點可應用於經配置以彼此無線地通信之任何適合節點之間的通道估計。舉例而言，SRS通道估計可用於估計一UE與一網路節點之間的一通道，舉例而言，如圖1中所展示。網路節點可係與一天線前端整合之一基地台。網路節點可包含一遠端無線電單元(RRU)及一基頻單元(BBU)。作為另一實例，SRS通道估計可用於估計兩個網路節點之間(例如，包含RRU之2個節點之間)的一通道。作為又一個實例，SRS通道估計可用於估計兩個UE之間的一通道。根據本文中所揭示之任何適合原則及優點之SRS通道估計可應用於經配置以無線地傳達資訊之任何適合節點之間的通道估計。
儘管出於說明性目的可參考SRS闡述本文中所揭示之實施例，但本文中所揭示之任何適合原則及優點可應用於使用任何適合參考信號及/或任何適合導頻信號進行通道估計。
圖2係經配置以產生一參考信號之圖1之一UE之硬體之一示意性方塊圖。圖1之每一UE 10A至UE 10N皆可包含圖2中所展示之硬體。參考圖2之區塊闡述之功能性可藉由任何適合實體硬體來實施。參考圖2闡述之功能性可在經配置以傳輸一SRS及/或其他參考信號之任何適合節點中實施。
如圖2中所圖解說明，參考信號產生電路系統可包含：一基本序列產生器21、一相位斜坡區塊22、一資源元素映射區塊23、一IFFT區塊24，以及一數位轉類比轉換及RF調變區塊25。基本序列產生器21可產生舉例而言如上文所闡述之一基本序列。作為一個實例，基本序列可使用方程式3來產生。相位斜坡區塊22可將一循環移位應用於由基本序列產生器21產生之基本序列。循環移位可應用於頻域中。每一節點(例如，圖1中之每一UE 10A至UE 10N)皆可具有藉由一各別相位斜坡區塊22應用之一不同循環移位。資源元素映射區塊23可將SRS序列自相位斜坡區塊22映射至一經分配梳。接著，IFFT區塊24可藉由一逆傅立葉變換將經頻域循環移位之信號轉換為時域。一循環首碼可由IFFT區塊24添加。數位轉類比轉換及RF調變區塊25可將IFFT區塊24之輸出轉換為一類比信號，並將該類比信號調變為一射頻。由數位轉類比轉換及RF調變區塊25提供之一RF信號可經由一通信通道無線地傳輸至一節點B及/或其他適合硬體，用於通道估計。參考信號通道估計
處理電路系統可接收諸如一SRS之一參考信號，並基於經接收參考信號產生一通道估計。通道估計可針對一相對寬頻SRS。將參考圖3至圖6E闡述實例信號處理。信號處理電路系統可根據本文中所揭示之任何適合原則及優點執行經改良參考信號通道估計。
圖3係經配置以產生一通道估計之處理電路系統30之一示意性方塊圖。處理電路系統30可接收時域參考信號樣本，並基於參考信號產生一通道估計。舉例而言，時域樣本可自圖1之一取樣及CP移除區塊18接收。如圖3中所圖解說明，處理電路系統30包含一快速傅立葉變換(FFT)區塊31、一第一頻域處理電路32、一逆快速傅立葉變換(IFFT)區塊33、一時域處理電路34、一第二FFT區塊35、一第二頻域處理電路36，以及一通道估計電路37。
經接收參考信號可係一SRS。經接收SRS可由FFT區塊31轉換為頻域。頻域處理電路32具有耦合至FFT區塊31之一輸出之一輸入。第一頻域處理電路32可提取一梳之SRS符號以用於去覆蓋。第一頻域處理電路可使用一基本序列對參考信號進行去覆蓋。經去覆蓋頻域參考信號可含有具有不同相位斜坡之通道頻率回應之一總和。可在對參考信號進行去覆蓋之後藉由第一頻域處理電路32執行額外頻域處理，以改良SRS通道估計效能。第一頻域處理電路32可執行頻域處理以使一直流偏移及/或一低頻偏移之失真減小。下文將論述此處理之實例。
IFFT區塊33可將來自第一頻域處理電路32之經去覆蓋頻域信號轉換為時域。來自IFFT區塊33之一輸出信號可提供至時域處理電路34。時域處理電路34可執行時域處理，以改良SRS通道估計效能。時域處理電路34可執行時域處理以使一雜訊底部減小。下文將論述此處理之實例。時域處理電路34可分離通道脈衝回應。分離通道脈衝回應可根據參考圖6所論述之任何適合原則及優點來執行。
第二FFT區塊35可將來自時域處理電路34之一輸出信號轉換為頻域。第二頻域處理電路36可執行每循環移位頻域處理。第二頻域處理電路36可輸出針對每一循環移位之一通道頻率回應。
通道估計電路37可基於第二頻域處理電路36之一輸出產生一通道估計。通道估計係基於由處理電路系統30接收之參考信號。通道估計和一第一節點與一第二節點之間的一無線通信通道相關聯。作為一個實例，第一節點可係圖1之一UE 10A且第二節點可係圖1之節點B 14。本文中所揭示之處理技術可改良由通道估計電路37產生之通道估計。此在各種應用中可係有利的，諸如用於選擇TDD MIMO系統中之一預編碼矩陣。
在圖4A及圖4B以及對應說明中提供關於處理電路系統30之實施例之更多細節。圖4A係用於產生一通道估計之處理電路系統40之一第一部分之一示意性方塊圖。圖4B係處理電路系統40之一第二部分之一示意性方塊圖。
處理電路系統40接收諸如一SRS之一參考信號。第一FFT區塊31將經接收參考信號轉換為頻域。一參考信號提取電路42可提取一個梳之所有資源元素，用於去覆蓋。此可涉及提取一當前梳之SRS符號。頻域中之經加總SRS可由方程式7表示。在方程式7中，Hc (𝑛) = (ℎ(𝑘𝑇𝑠 ))係循環移位c之通道頻率回應(CFR)，且𝑣(𝑛)表示加成性白高斯雜訊(AWGN)。
Figure 02_image025
(方程式7)
一基本序列產生器43產生用於去覆蓋之一基本序列。基本序列可根據本文中所揭示之任何適合原則及優點來產生。一混合器44或任何其他適合電路可用於使用來自基本序列產生器43之基本序列對參考信號進行去覆蓋。
在藉由基本序列𝑟̅(𝑛)去覆蓋之後，經去覆蓋頻域信號可由方程式8表示。方程式8展示經去覆蓋頻域信號含有具有不同線性相位斜坡之通道頻率回應之一總和。
Figure 02_image027
(方程式8)
一頻域處理電路45可對經去覆蓋信號執行頻域處理，以改良參考信號通道估計效能。
將ℎ(𝑘)表示為長度為𝑁之一時域信號，並藉由將ℎ(𝑘)向右循環移位S來將ℎ(𝑆)(𝑘)定義為序列，亦即，ℎ( 𝑆 ) (𝑘) = ℎ(𝑀𝑂𝐷(𝑘 + 𝑆, 𝑁))，0 ≤ 𝑘 ＜ 𝑁。可藉由IFFT區塊33，透過一IFFT將經去覆蓋信號𝑦'(𝑛)轉換為時域。在時域中，信號變成具有不同循移位之多個通道脈衝回應之一組合，此可由方程式9表示。在方程式9中，𝑁𝐼𝐹𝐹𝑇 表示每梳IFFT大小。
Figure 02_image029
(方程式9)
在IFFT之後，可藉由圖4B之時域處理及通道脈衝回應分離區塊48來執行時域處理，以改良SRS CE效能。假定任何ℎ𝑐 之最大延遲擴展小於
Figure 02_image031
，用於不同循環移位之時域通道可藉由時域處理及通道脈衝回應分離區塊48而相對容易地分離。第二FFT區塊35可包含用以將個別通道脈衝回應變換成頻域之子FFT區塊35A至35N。每循環移位頻域處理電路50A至50N可獲得針對每一循環移位之通道頻率回應。諸如圖3之通道估計電路37之一通道估計電路可基於用於循環移位之通道頻率回應來產生通道估計。
現將論述分離通道脈衝回應。此功能性可(舉例而言)係藉由圖4B之時域處理及通道脈衝回應分離區塊48來執行。為了分離通道脈衝回應，可針對循環移位中之每一者定義一窗。對於一特定循環移位，僅保留落入用於該特定循環移位之窗中的抽頭，且可將所有其他抽頭設定至零。接著，循環移位非零抽頭，且在頻域中，可移除線性相位斜坡。
圖5係圖解說明針對具有8個循環移位之一參考信號之時域通道脈衝回應分離之一圖式。圖5中所展示之實例圖解說明如何將用於一特定移位(亦即，𝑐 = 7)之通道脈衝回應與其他循環移位分離。圖5之最頂部部分展示一時域脈衝回應。存在針對圖5中所展示之8個不同循環移位之時域脈衝回應。存在針對循環移位中之每一者定義的不同窗。可藉由在一特定窗內保留一特定通道脈衝回應(亦即，用於圖5中之循環移位c = 7之通道脈衝回應)並移除其他通道脈衝回應來執行窗化。可移位用於特定通道之脈衝回應以移除循環移位。此可移除頻域中之線性相位斜坡。
現將論述SRS中之ZC序列之性質。若在方程式4-1至4-3中定義之一ZC序列xq (𝑚)藉由自身之一經移位版本來去覆蓋(表示為xq (𝑚 − 𝑠)，𝑠 = 0, ±1, ±2, ±3, …)，則經去覆蓋信號可由方程式10表示。在方程式10中，
Figure 02_image033
可係一恒相位。
Figure 02_image035
(方程式10)
方程式10顯示xq (𝑚) ∙ xq * (𝑚 − 𝑠)係線性相位斜坡之一序列，其中斜率
Figure 02_image037
係s與q之一函數。若停用頻率跳躍及序列跳躍，則𝑞變成取決於小區ID。
xq (𝑚) ∙ xq * (𝑚 − 𝑠)之IFFT表示時域中之一脈衝，且脈衝之延遲與𝑠及𝑞相關。
頻域處理技術可應用於改良參考信號通道估計。此頻域處理可減小直流及/或其他低頻偏移。另一選擇係或另外，頻域處理電路可補償對準確參考信號通道估計之任何其他適合損害。圖3之頻域處理電路32及/或圖4A之頻域處理電路45可實施頻域處理以改良參考信號通道估計。圖6A、圖6B及圖6C圖解說明可由頻域處理電路32及/或頻域處理電路45實施之頻域處理電路之實例方塊圖。圖3之頻域處理電路36及/或圖4A之頻域處理電路50A至50N中之任一者可實施頻域處理以改良參考信號通道估計。圖6D圖解說明可由圖3之頻域處理電路36及/或圖4B之頻域處理電路50A至50N中之任一者實施之一頻域處理電路之實例方塊圖。
圖6A係根據一實施例之一頻域處理電路62之一方塊圖。頻域處理電路62包含經配置以基於一經去覆蓋頻域參考信號之至少兩個其他頻調產生針對該經去覆蓋頻域參考信號之一頻調之一經估計頻調之一頻調估計電路63。頻調估計電路63亦經配置以用該經估計頻調替換該頻調以使與直流偏移相關聯之失真減小。另一選擇係或另外，頻調估計電路63可基於該經估計頻調修改該頻調以使與直流偏移相關聯之失真減小。頻調估計可涉及內插。頻調估計可涉及外插。頻調估計可係基於多相分解。頻調估計可係基於最小平方估計。頻調估計可係基於任何其他適合技術。頻域處理電路62可執行用於通道估計之任何其他適合頻域處理，諸如參考圖3之頻域處理電路32及/或圖4A之頻域處理電路45論述之任何其他適合特徵。
圖6B係根據一實施例之一頻域處理電路64之一方塊圖。頻域處理電路64包含經配置以對一經去覆蓋頻域參考信號進行脈波塑形之一通道頻率回應脈波塑形電路65。脈波塑形可使與一直流偏移相關聯之失真減小。脈波塑形可涉及一升餘弦脈波及/或任何其他適合脈波。頻域處理電路64可執行用於通道估計之任何其他適合頻域處理，諸如參考圖3之頻域處理電路32及/或圖4A之頻域處理電路45論述之任何其他適合特徵。
圖6C係根據一實施例之一頻域處理電路66之一方塊圖。頻域處理電路66包含頻調估計電路63及通道頻率回應脈波塑形電路65。圖6C圖解說明頻調估計可與通道頻率回應脈波塑形一起實施。頻域處理電路65可執行用於通道估計之任何其他適合頻域處理，諸如參考圖3之頻域處理電路32及/或圖4A之頻域處理電路45論述之任何其他適合特徵。
圖6D係根據一實施例之一頻域處理電路67之一方塊圖。頻域處理電路67包含一擴縮電路68。擴縮電路68可與圖6B及/或圖6C之通道頻率回應脈波塑形電路65一起實施。擴縮電路68可擴縮邊緣頻調之通道頻率回應以補償頻域脈波塑形之影響。頻域處理電路67可執行任何其他頻域處理，諸如參考圖3之頻域處理電路36及/或圖4B之頻域處理電路50A至50N中之任一者論述之任何其他適合特徵。
時域處理技術可應用於改良參考信號通道估計。在某些例項中，時域處理可與本文中所揭示之一或多種頻域處理技術一起實施以改良參考信號通道估計。
圖6E係根據一實施例之一時域處理電路69之一方塊圖。時域處理電路69經配置以執行時域處理及通道脈衝回應分離。時域處理電路69包含一通道脈衝回應擴縮電路70。通道脈衝回應擴縮電路70經配置以基於一功率延遲量變曲線擴縮一通道脈衝回應。擴縮可按一濾波器之每抽頭來應用。時域處理電路69可執行任何其他時域處理，諸如參考圖3之時域處理電路34及/或圖4B之時域處理及通道脈衝回應分離區塊48論述之任何其他適合特徵。
在某些實施例中，一時域處理電路可將一混附雜訊移動至用於該參考信號之循環移位之時域窗之外。例如，可將諧波混附雜訊移動至不影響通道估計之未經使用之時域空間。可將混附雜訊移動至用於循環移位之時域窗下方之時域索引及/或移動至用於循環移位之時域窗之間的時域索引。
在某些應用中，可在將一參考信號轉變為頻域之前應用時域脈波塑形。時域脈波塑形可減小頻率偏移及/或時序偏移。
根據某些應用，可在將一參考信號轉變為頻域之前應用頻率旋轉。此可減小頻率偏移。對參考信號通道估計之損害
在一真實世界通信系統中，可存在可影響參考信號通道估計之效能之各種損害。此等損害可包含以下各項中之一或多者：低頻頻調之失真、時域通道脈衝回應洩漏、頻率偏移，或時序偏移。可存在可導致不準確通道估計之各種因素。識別影響參考信號通道估計之效能之損害可係具有挑戰的。透過對SRS通道估計資料之分析來識別本文中所論述之損害。
現將論述低頻頻調之失真。對於具有一零中頻(ZIF)收發器之一RF前端，歸因於本端振盪器(LO)洩漏，直流(DC)偏移可出現於一接收基頻信號中。為了減輕DC偏移分量，在產生用於數位信號處理之基頻樣本之前可將一陷波濾波器應用於一經解調變信號。然而，陷波濾波器可無法完美工作及/或可使DC頻調及一或多個毗鄰頻調失真，尤其在其中上行鏈路符號在時間上不連續之TDD系統中。
若一DC頻調及與該DC頻調毗鄰之頻調失真，則可在頻域中之DC及低頻頻調處之位置引入有色雜訊。有色雜訊頻調可提高時域中之一雜訊底部，並在SRS CE中引入循環間移位干擾。
圖7A係圖解說明來自兩個循環移位的在DC及低頻頻調中具有某些失真之一經去覆蓋探測參考信號之一量值之一圖表。圖7A中之失真頻調位於DC處及其附近。
圖7B係圖解說明一時域中之失真DC及低頻頻調之一圖表。圖7B中繪製樣本功率與時間索引之關係。失真頻調促成圖7B之曲線中之時域中之一駝峰。失真頻調位於對應於不同循環移位(亦即，圖7B中之c = 0及c = 1)之通道脈衝回應之間。此等失真頻調可提高雜訊底部。
現將論述時域通道脈衝回應洩漏。當一頻域通道頻率回應透過一IFFT變換成時域時，通道脈衝回應脈波可具有一顯著旁瓣洩漏，該旁瓣洩漏進入用於一或多個其他循環移位之時域窗中。
圖8A係圖解說明一頻域中之一通道頻率回應之一圖表。在頻域中展示循環移位c = 0之通道頻率回應。在圖8A中，通道在頻域中係相對平坦的。
圖8B係圖解說明與圖8A之通道頻率回應相關聯之一時域中之功率洩漏之一圖表。在執行一1024點IFFT之後，大部分能量集中在循環移位c = 0之一時域窗中，即在圖8B中介於時域索引64與960之間。然而，可存在洩漏至其他窗中之一不可忽略的功率部分。
旁瓣洩漏可使旁瓣洩漏與之相關聯之循環移位之通道頻率回應降級，此可歸因於窗截斷中之信號功率之損失。旁瓣洩漏可藉由引入循環間移位干擾而使一或多個其他循環移位之通道頻率回應效能降級。因此，確保每一循環移位之通道脈衝回應集中在其自身的時域窗中可係重要的。
現將論述頻率偏移。儘管一UE可透過一初始獲取及頻率追蹤環路移除其本端振盪器與一基地台中之一本端振盪器之間的大多數頻率偏移，但仍可存在一殘餘頻率偏移Δ𝑓。有時，殘餘頻率偏移可高達數百赫茲。
與一實體上行鏈路控制通道(PUCCH)及實體上行鏈路共用通道(PUSCH)之解調變(其中可透過一解調變參考信號(DMRS)估計及補償頻率偏移)不同，減輕SRS CE中之頻率偏移可更具通道作用，尤其在考慮到不同UE可具有不同頻率偏移值時。
圖9係圖解說明具有一時序偏移、一頻率偏移及不具有時序或頻率偏移之頻域脈波之一圖表。歸因於非零頻率偏移，頻域中之一sinc脈波可經移位，舉例而言，如圖9中所展示。經移位sinc脈波由sinc(𝑓 − (Δ𝑓/𝐵𝑠𝑐𝑠))表示，其中𝐵𝑠𝑐𝑠係副載波間距。在圖9中，在每一副載波之位置處存在一洩漏抽頭，從而導致載波間干擾(ICI)。對於一既定頻率偏移Δ𝑓，ICI應隨著較大副載波間距值而變得不那麼嚴重。
失真sinc脈波之每一洩漏抽頭皆貢獻於ZC序列之一經加權及經移位版本，此可由方程式11表示。
Figure 02_image039
(方程式11)
在已知上文所論述之ZC序列之性質之情形下，在去覆蓋之後，頻域信號係具有相位斜坡之一經加權通道頻率回應，此可由方程式12表示。
Figure 02_image041
(方程式12)
在時域中，每一洩漏抽頭皆可導致一時域混附雜訊。時域混附雜訊之功率可與抽頭量值|𝐴𝑠|相關。混附雜訊在時域中之位置可自頻域中之相位斜坡之斜率導出。對於第s 諧波混附雜訊，時域位置可藉由方程式13來預測。該位置係方程式13中之小區ID之一函數。
Figure 02_image043
(方程式13)
時域混附雜訊可導致跨越不同循環移位之干擾。時域混附雜訊可使每一UE之SRS CE效能降級。
現將論述時序偏移。一基地台可透過時序提前(TA)來調整一UE之上行鏈路時序。然而，歸因於TA中之抖動，非零時序偏移可仍存於基地台之一符號邊界與來自一UE之經接收信號之一符號邊界之間。
時序偏移可使得可能在一FFT中選擇較少時域樣本。在頻域中，此可導致OFDM之sinc脈波失真。此失真展示於圖9中。若FFT窗中缺失Δ𝑇個樣本，則在頻域中，失真sinc脈波可由函數1表示。函數1暗指在每一副載波之位置處存在一洩漏抽頭。
Figure 02_image045
(函數1)
時序偏移導致之降級可係雙重的。首先，時域中可存在符號間干擾(ISI)。其次，失真sinc脈波可導致頻域中之ICI洩漏。
類似於頻率偏移，時序偏移可在一時域通道脈衝回應中引入諧波混附雜訊。諧波混附雜訊之位置可使用方程式13來預測。改良參考信號通道估計之技術
揭示改良參考信號通道估計之效能之技術。此等技術可使得參考信號通道估計對於一或多個損害更加穩健。經改良參考信號通道估計可補償以下各項中之一或多者：低頻頻調之失真、時域通道脈衝回應洩漏、頻率偏移，或時序偏移。本文中所揭示之改良參考信號通道估計之技術之任何適合組合可彼此一起實施。
參考信號通道估計之一實例方法包含：在一頻域中對一參考信號進行去覆蓋以產生一經去覆蓋參考信號；基於該經去覆蓋參考信號之至少兩個其他頻調估計該經去覆蓋參考信號之一頻調以產生一經估計頻調；及基於該經估計頻調及進一步處理產生一通道估計，其中該通道估計和一第一節點與一第二節點之間的一無線通信通道相關聯。
減小失真之一種技術係頻調估計。頻調估計可涉及內插及/或外插。在某些例項中，估計可係基於多相分解。在某些應用中，估計可係基於最小平方估計。經估計頻調可用於改良參考信號通道估計。頻調估計可舉例而言使用圖6A及/或圖6C之頻調估計電路63來執行。
現將論述基於多相分解之線性內插及外插。方程式8展示，在頻域中，經去覆蓋SRS含有具有不同線性相位斜坡之通道頻率回應之一總和。在下文論述之一實例中，假定
Figure 02_image047
=8。可使用
Figure 02_image049
之任何其他適合值。舉例而言，擴展至
Figure 02_image051
=12係類似的。
在方程式8中
Figure 02_image053
=8之情形下，經去覆蓋SRS可由方程式14表示。
Figure 02_image055
(方程式14)
Figure 02_image057
之值按每8個樣本重複。因此，𝑦’(𝑛)可分解成8個子序列，如方程式15中所展示。
Figure 02_image059
(方程式15)
對於一特定𝑝，假定𝐻𝑐(𝑛)在頻域中緩慢改變，子序列𝑦’(8𝑚+𝑝)應係平滑的。因此，在SRS去覆蓋之後，失真DC頻調及毗鄰頻調可使用𝑦’(𝑛)之多相分解來線性內插。
圖10展示內插之一實例。在圖10中，中心8個經去覆蓋SRS頻調可由8個新頻調替換，該8個新頻調自16個頻調內插，其中每一側上8個頻調。每一經內插頻調可係兩個頻調之平均值，在此實例中，該兩個頻調係來自其各別側之8個頻調，其中
Figure 02_image061
=8。經內插頻調可用於8個經去覆蓋SRS頻調之中心群組。在某些其他應用中，中心8個經去覆蓋SRS頻調可基於8個新的經估計頻調來修改。
圖11展示外插之一實例。類似於內插之處理可延伸至邊緣外插。圖11圖解說明可如何自兩個頻調導出一經外插頻調，該兩個頻調距經外插頻調之距離係
Figure 02_image063
的倍數(亦即，在所圖解說明實例中為8的倍數)。
現將論述基於最小平方估計之內插及外插。在某些應用中，最小平方估計可代替基於多相分解之估計來實施。根據某些應用，一系統可在最小平方估計與基於多相分解之估計之間進行選擇。一本端區域中之可用頻調可一起處理以內插失真低頻頻調及/或外插邊緣頻調。在下文論述之一實例中，假定
Figure 02_image065
=8。可使用
Figure 02_image067
之任何其他適合值。舉例而言，擴展至
Figure 02_image065
=12係類似的。
在一本端頻率區域中，(𝑛)可由一線性多項式表示，如在方程式16中所展示。
Figure 02_image070
(方程式16)
每循環移位可存在2個未知係數。因此，所有循環移位之SRS可藉由方程式17來近似。在方程式17中，𝛺𝑐𝑠表示主動循環移位之集合。
Figure 02_image072
(方程式17)
所有8個循環移位之一係數向量可表示為𝒂 = [ 𝑎0,1 , 𝑎0,0 , 𝑎1,1 , 𝑎1,0 , … … , 𝑎7,1 , 𝑎7,0 ]𝑇 。用於內插之𝐿個頻域樣本之一集合可表示為{(𝑛), 𝑛 ∈ 𝛺𝑌}, 𝛺𝑌 = {𝑛0 , 𝑛1 , … , 𝑛𝐿 −1 }。然後方程式17可表示為方程式18。在方程式18中，⊗表示克羅內克積。
Figure 02_image074
(方程式18)
Figure 02_image076
方程式19提供方程式18之一最小平方解。
Figure 02_image078
(方程式19)
待內插之K 個頻調之索引可表示為一集合𝛺𝐼 = {𝑚0 , 𝑚1 , …, 𝑚𝐾 −1 }。一𝐵矩陣可定義如下。
Figure 02_image080
經內插低頻頻調可由方程式20表示。方程式21之內插矩陣E係為維度K x L且可預計算。
Figure 02_image082
(方程式20)
Figure 02_image084
(方程式21)
假定Hc(𝑛)在頻域中緩慢改變可係無效的。為了使得內插更準確，可藉由方程式22中所展示之一個二次多項式來近似一本端頻率區域中之Hc(𝑛)。
Figure 02_image086
(方程式22)
每循環移位可存在3個未知係數。因此，所有循環移位之SRS可藉由方程式23來近似。在方程式23中，𝛺𝑐𝑠 表示主動循環移位之集合。
Figure 02_image088
(方程式23)
導出方程式20及21中的解之相同程序可再次應用於二次多項式假定，除了係數向量被𝒂=[ 𝑎0,2 , 𝑎0,1 , 𝑎0,0 , 𝑎1,2 ,𝑎1,1 ,𝑎1,0 ,……, 𝑎7,2 ,𝑎7,1 , 𝑎7,0 ]𝑇 替換，且矩陣A及B被以下各項替換之外：
Figure 02_image090
對以上表述之各種修改係可能的。舉例而言，若循環移位未被完全使用，則𝒂及𝐴之維度可減小。作為另一實例，為了近似(𝑛)，不同循環移位可視需要採用不同階之多項式。上文所展示之基於最小平方估計之線性及/或二次內插方法可延伸至邊緣頻調之外插。唯一差異可係𝛺𝑐𝑠、𝛺𝑌 及𝛺𝐼 之定義。
圖12A、圖12B，及圖12C展示關於DC失真、內插及邊緣外插之實例。圖12A展示在使用失真低頻頻調執行一FFT之後之一經接收頻域SRS。圖12B展示將二次內插應用於16個低頻頻調之後之一SRS。與圖12A中之圖表相比，此圖表展示低頻處之經減小失真。圖12C展示在將二次外插應用於每一側上之16個邊緣頻調之後之一SRS。與圖12A中之圖表相比，此圖表亦展示低頻處之經減小失真。
頻域通道頻率回應脈波塑形可減小功率洩漏，此乃因可減小旁瓣及循環間移位干擾。通道頻率回應脈波塑形可(舉例而言)係使用圖6B及/或圖6C之通道頻率回應脈波塑形電路65來執行。
脈波塑形可應用於經頻域去覆蓋符號。可將邊緣頻調乘以在頻域中平滑之一函數。接著在執行一逆FFT之後，每一循環移位之通道脈衝回應應更集中於其自身的時域窗中。因此，歸因於旁瓣之功率洩漏可被減小，且循環間移位干擾可被降低。
脈波之一個實例係一升餘弦函數。升餘弦脈波可應用於頻帶之每一側上之邊緣頻調及經延伸頻調兩者。圖13A展示一矩形脈波及一升餘弦脈波之窗函數。圖13B展示矩形及升餘弦脈波分別相對於一中心抽頭之時域抽頭功率。圖13B展示與使用一矩形脈波相比，藉由升餘弦脈波進行之脈波塑形減小抽頭功率洩漏。
圖14A係在頻域脈波塑形之前具有經外插邊緣頻調之一SRS之一曲線圖。圖14B係一頻域脈波塑形函數之一曲線圖。在圖14B中，一升餘弦函數之跨度自副載波索引-16至56，以及自519至591。圖14C係在應用頻域脈波塑形之後包含經外插邊緣頻調之SRS之一曲線圖。圖14C展示由於頻域脈波塑形之經減小失真。
在時域中分離每一通道脈衝回應之後，可應用一FFT以在頻域中獲得每一循環移位之通道頻率回應。接著可相應地擴縮每一邊緣頻調之通道頻率回應以補償頻域脈波塑形之影響。圖6E之通道脈衝回應擴縮電路70可執行此擴縮。
改良參考信號通道估計之另一技術係基於一功率延遲量變曲線之時域通道脈衝回應擴縮。擴縮可按每抽頭來應用。擴縮可係最小均方誤差(MMSE)擴縮。使用功率延遲量變曲線，可量測每一抽頭上之一平均功率且可估計雜訊功率。接著可應用每抽頭MMSE擴縮來抑制雜訊抽頭。功率延遲量變曲線及MMSE擴縮可包含功率延遲濾波器、雜訊功率估計，及每抽頭擴縮。
圖15係圖解說明在已執行一逆FFT之後針對循環移位之時域通道脈衝回應之一圖式。此圖式係針對8個循環移位。圖15展示用於雜訊功率估計之抽頭可位於用於不同循環移位之窗之間。
圖16係基於一功率延遲量變曲線之時域通道脈衝回應擴縮之一實例方法160之一流程圖。舉例而言，方法160可使用圖6E之通道脈衝回應擴縮電路70來執行。在方塊162處，對一時域抽頭之抽頭功率進行濾波。一無限脈衝回應濾波器可執行該濾波。方程式24可表示濾波，其中n 係一時域索引且α係濾波器之時間常數。
Figure 02_image092
(方程式24)
在方塊164處，估計抽頭之雜訊功率。基於經濾波抽頭功率{
Figure 02_image094
}，藉由取經選擇副載波之平均值來估計雜訊功率。經選擇副載波可係圖15中所指示之用於雜訊功率估計之抽頭。
在方塊166處，應用每抽頭擴縮。該每抽頭擴縮可涉及臨限值化。在臨限值化中，將具有
Figure 02_image094
＞ 𝑎 ∙ 𝑃𝑛𝑜𝑖𝑠𝑒之抽頭選擇為通道抽頭。所有其他抽頭可設定至一值(諸如0之一值)以移除雜訊。每抽頭擴縮可涉及MMSE擴縮。在MMSE擴縮中，第n個抽頭ℎ𝑛 由一因子
Figure 02_image097
擴縮。可應用任何其他適合每抽頭擴縮技術。
圖17係可基於一功率延遲量變曲線執行時域通道脈衝回應擴縮之一時域處理電路之一示意性方塊圖。所圖解說明之時域處理電路包含：具有複數個抽頭之一時域濾波器170、一濾波器172、一雜訊估計電路174，及一抽頭擴縮電路176。濾波器172可係一無限脈衝回應濾波器。濾波器172可對時域抽頭之抽頭功率進行濾波。雜訊功率估計電路174經組態以估計對應於用於通道脈衝回應之時間窗之外的副載波之濾波器之抽頭之一子集之雜訊功率。抽頭擴縮電路176經組態以基於經估計雜訊功率對抽頭之至少一部分執行一每抽頭擴縮。抽頭擴縮電路176可基於臨限值化、MMSE擴縮、任何其他適合擴縮操作，或其任何適合組合執行每抽頭擴縮。
時域脈波塑形可應用於改良參考信號通道估計。為了使SRS CE較少受到頻率偏移及時序偏移之影響，TD脈波塑形可在對頻域符號進行一FFT之前應用於OFDM樣本。
圖18係具有時域脈波塑形之處理電路系統180之一示意性方塊圖。處理電路系統180實施針對經接收參考信號之信號處理之部分，用於產生一通道估計。如所圖解說明，處理電路系統180包含：一時域脈波塑形電路182、快速傅立葉變換區塊41，及參考信號提取電路42。
時域脈波塑形電路182在藉由快速傅立葉變換區塊41將經接收時域樣本轉換為頻域之前應用脈波塑形。此可減小頻率偏移及/或時序偏移。時域脈波塑形電路182可使用本文中所揭示之任何適合處理電路系統來實施。時域脈波塑形電路182之一輸出可耦合至本文中所揭示之快速傅立葉變換區塊中之任一者(諸如圖3之快速傅立葉變換區塊31及/或圖4A之快速傅立葉變換區塊41)之一輸入。FFT區塊41可將歸因於時域脈波塑形電路182之時域脈波塑形而具有一經減小時間偏移及/或頻率偏移之一頻域信號提供至參考信號提取電路42。
在不具有時域脈波塑形電路182之情形下，應用於一快速傅立葉變換區塊之一脈波可係一矩形脈波。時域脈波塑形電路182可舉例而言應用一升餘弦脈波。時域脈波塑形電路182可應用使時間偏移及/或頻率偏移減小之任何其他適合脈波。
圖19A係時域中之一矩形脈波及一升餘弦脈波之一圖表。圖19A之升餘弦脈波具有1之一滾降因子。圖19A之升餘弦脈波係可藉由圖18之脈波塑形電路182產生以減小時序偏移及/或頻率偏移之一脈波之一實例。在一個實例應用中，快速傅立葉變換區塊41可產生一2048點FFT。本文中之教示可類似地應用於其他適合FFT大小。在執行一FFT之後的頻域中之脈波可由方程式25表示，其中𝑓被正規化為副載波間距(SCS)。
Figure 02_image099
(方程式25)
圖19B係頻域中之一sinc脈波及升餘弦脈波之一圖表。與sinc脈波相比，升餘弦脈波之旁瓣之衰減在頻域中明顯更快，如圖19B中所展示。因此，對於升餘弦脈波，ICI洩漏在頻域中可明顯更小。
對於具有滾降因子為1之一升餘弦脈波，旁瓣之衰減在頻域中明顯更快，且除了第一諧波混附雜訊之外，ICI洩漏明顯更小。藉由應用時域脈波塑形，可存在對毗鄰梳之一相對大的洩漏，舉例而言，歸因於頻域中之主瓣之雙倍寬度。因此，在其中沒有SRS或其他參考信號分配至一緊鄰梳中之應用中，應用時域脈波塑形可係有利的。
具有一偏移之頻率旋轉可應用於改良參考信號通道估計。此可減小使用者當中之干擾。
若一基地台維持針對每一UE之頻率偏移之一估計，則估計可來自PUSCH及/或PUCCH解調變。此外，若基地台可最可能自先前SRS CE識別具有主導經接收SRS功率之UE，則在時域中，可以主導UE之頻率偏移來旋轉經接收樣本。應用具有一個偏移之頻率旋轉可藉由方程式26來模型化。
Figure 02_image101
(方程式26)
在某些應用中，可基於所有UE之經估計頻率偏移及SRS功率將一頻率偏移判定為所有循環移位之質心。
圖20係具有頻率旋轉之處理電路系統200之一示意性方塊圖。處理電路系統200實施針對經接收參考信號之信號處理之部分，用於產生一通道估計。如所圖解說明，處理電路系統200包含：一頻率旋轉電路202、快速傅立葉變換區塊41，及參考信號提取電路42。
頻率旋轉電路202可執行頻率旋轉以補償一頻率偏移。頻率偏移可係來自一主導UE。頻率偏移可係來自所有循環移位之一質心。頻率旋轉電路202可減小頻率偏移。頻率旋轉電路202可包含一混合器。頻率旋轉電路202可使用本文中所揭示之任何適合處理電路系統來實施。頻率旋轉電路202之一輸出可耦合至本文中所揭示之快速傅立葉變換區塊中之任一者(諸如圖3之快速傅立葉變換區塊31及/或圖4A之快速傅立葉變換區塊41)之一輸入。圖20中之FFT區塊41可將歸因於頻率旋轉電路202之頻率旋轉而具有一經減小頻率偏移之一頻域信號提供至參考信號提取電路42。
混附雜訊可移動至未經使用之時間空間以改良參考信號通道估計。當偵測到循環移位之通道脈衝回應時，可存在不影響通道估計之未經使用之時域空間。混附雜訊及/或其他雜訊可移動至此未經使用之時域空間以改良通道估計。
圖21係偵測一參考信號之循環移位之一方法210之一流程圖，其中混附雜訊被移動至一未經使用之時間空間中。在方塊212處，可選擇一小區識別符(ID)。當在SRS中停用群組及序列跳躍時，由於諧波混附雜訊之位置可預測為小區ID之一函數，因此可選擇一適當小區ID以使得第一諧波混附雜訊落入未被循環移位中之任一者使用之區域中。
基於在方塊212處選擇之小區ID，在方塊214，將混附雜訊(例如，第一諧波混附雜訊)移動至用於循環移位之時域窗之外的區域中。此技術可有利地與時域脈波塑形一起(例如，與圖18之時域脈波塑形電路182一起)應用，此乃因在應用時域脈波塑形之後第一諧波混附雜訊可係主導的，且在方法210中此等混附雜訊可移動至用於循環移位之時域窗之外。在方塊216處，可偵測循環移位。此循環移位偵測可在不具有位於用於循環移位之時域窗之外而影響通道估計的諧波混附雜訊之情形下執行。可基於經偵測循環移位及進一步處理執行通道估計。
混附雜訊可藉由圖3之時域處理電路34及/或圖4B之時域處理及通道脈衝回應分離電路48移動至未經使用之時間空間。
作為一實例，若一個梳中存在4個SRS循環移位，其中循環移位c = 0、1、2及3，則藉由選擇表示為𝑛𝐶𝐼𝐷之一小區ID使得𝑛𝐶𝐼𝐷𝑚𝑜𝑑 30 = 15，可將時域中之第一諧波混附雜訊移動至用於四個循環移位之截斷窗之外的一區域中。
圖22圖解說明用於四個循環移位之第一諧波混附雜訊之位置。如圖22中所展示，諧波混附雜訊在用於4個循環移位之時域窗之外。在圖22中，混附雜訊移動至用於循環移位之窗之時域索引下方之時域索引中。
作為另一實例，若一個梳中存在8個SRS循環移位，且若用於每一循環移位之時域窗大小設定至64，則小區ID可設定至12或17，使得第一諧波混附雜訊位於用於所有循環移位之時域窗之外。可在具有較多循環移位之情形下存在較小時域窗。在某些例項中，混附雜訊可移動至用於循環移位之窗之間的時域索引。MIMO 環境
圖23係圖解說明其中可執行基於一參考信號之通道估計之一實例多輸入多輸出(MIMO)網路環境230之一圖式。在MIMO網路環境230中，各種UE可與一網路系統無線地通信。此等無線通信可達成高處理量。用於與UE無線地通信之MIMO網路環境230之天線可係分散式的。可基於參考信號估計，使用本文中所揭示之任何適合技術，在MIMO網路環境230中執行針對不同節點之間的通道之通道估計。
各種標準及/或協定可在MIMO網路環境230中實施以在一基地台與一無線通信裝置之間無線地傳達資料。某些無線裝置可使用一正交分頻多工(OFDM)數位調變方案經由一實體層進行通信。用於在環境230中進行無線通信之實例標準及協定可包含：第三代夥伴計劃(3GPP)長程演進(LTE)、高級長程演進(高級LTE)、3GPP新無線電(NR) (亦稱為5G)、全域行動通信系統(GSM)、GSM增強資料速率演進(EDGE)、全球互通微波存取(WiMAX)，及IEEE 802.11標準(可稱為Wi‑Fi)。在某些系統中，一無線電存取網路(RAN)可包含與一或多個演進節點B (亦通常表示為增強節點B、eNodeB或eNB)、gNB，或任何其他適合節點B (xNB)相關聯之一或多個基地台。在某些其他實施例中，無線電網路控制器(RNC)可提供為基地台。一基地台在無線網路與諸如網際網路之一核心網路之間提供一橋接器。基地台可經包含以促進無線網路之無線通信裝置之資料之交換。一基地台可根據本文中所揭示之任何適合原則及優點執行參考信號通道估計。
一無線通信裝置可稱為一使用者設備(UE)。UE可係由一使用者使用之一裝置，諸如一智慧型電話、一膝上型電腦、一平板電腦、蜂巢式電話、一可佩帶計算裝置(諸如智慧型眼鏡或一智慧型手錶或一耳機)、一或多個網路器具(例如，消費者網路器具或工業廠房設備)、具有連接性之一工業機器人，或一運載工具。在某些實施方案中，UE可包含經組態以收集資料並將資料無線地提供至連接至諸如網際網路之一核心網路之一裝置(例如，伺服器)之一感測器或其他網路裝置。此等裝置可稱為物聯網(IoT)裝置。一下行鏈路(DL)傳輸通常稱為自基地收發器(BTS)或eNodeB至一UE之一通信。一上行鏈路(UL)傳輸通常稱為自UE至BTS之一通信。
圖23圖解說明一協同式或雲端無線電存取網路(C-RAN)環境100。在環境230中，eNodeB功能性在一基頻單元(BBU) 240與多個遠端無線電單元(RRU) (例如，RRU 255、RRU 265及RRU 275)之間細分。圖23之網路系統包含BBU 240以及RRU 255、265及275。一RRU可包含多個天線且天線中之一或多者可充當一傳輸接收點(TRP)。RRU及/或一TRP可稱為一服務節點。BBU 240可諸如經由一光纖連接實體地連接至RRU。BBU 240可將操作資訊提供至一RRU以控制來自RRU之信號連同待傳輸之資料及有效負載資料之傳輸及接收。RRU可將自與RRU相關聯之一服務區內之UE接收之資料提供至網路。如圖23中所展示，RRU 255將服務提供至一服務區250內之裝置。RRU 265將服務提供至一服務區260內之裝置。RRU 275將服務提供至一服務區270內之裝置。舉例而言，無線下行鏈路傳輸服務可被提供至服務區270以將資料傳達至服務區270內之一或多個裝置。
在環境230中，一網路系統可經由分散式MIMO與UE無線地通信。舉例而言，UE 283可使用網路系統之天線無線地傳達MIMO資料，該等天線包含RRU 255之至少一個天線、RRU 265之至少一個天線，及RRU 275之至少一個天線。作為另一實例，UE 282可使用包含RRU 255之至少一個天線及RRU 265之至少一個天線之分散式天線無線地傳達MIMO資料。作為又一個實例，UE 288可使用包含RRU 255之至少一個天線及RRU 275之至少一個天線之分散式天線無線地傳達MIMO資料。舉例而言，本文中所揭示之參考信號通道估計之任何適合原則及優點可在此等分散式MIMO應用中實施。
所圖解說明RRU 255、RRU 265，及RRU 275包含多個天線且可提供MIMO通信。舉例而言，一RRU可配備有可用於同時傳輸至諸如一UE之一或多個接收器之各種數目之傳輸天線(例如，2個、4個、8個或更多個)。接收裝置可包含一個以上接收天線(例如，2個、4個等)。接收天線之一陣列可經組態以同時自RRU接收傳輸。包含在一RRU中之每一天線可個別地經組態以根據一特定時間、頻率、功率及方向組態進行傳輸及/或接收。類似地，包含在一UE中之每一天線可個別地經組態以根據一特定時間、頻率、功率及方向組態進行傳輸及/或接收。組態可由BBU 240提供。
圖23中所展示之服務區可將通信服務提供至一不同種類的使用者設備群體。舉例而言，服務區250可包含一UE叢集290，諸如與參加一大型事件之使用者相關聯之裝置之一群組。服務區250亦可包含遠離UE叢集290定位之一額外UE 292。一行動使用者設備294可自服務區260移動至服務區270。一行動使用者設備之另一實例係一運載工具286，該運載工具可包含用於即時導航、板上資料服務(例如，串流視訊或音訊)或其他資料應用之無線通信之一收發器。環境230可包含經組態用於無線通信之半行動或靜止UE，諸如機器人裝置288 (例如，機器人手臂、一自主驅動單元，或其他工業或商業機器人)或一電視284。
一使用者設備282可位於具有重疊服務之一區(例如，服務區250及服務區260)內。環境230中之每一裝置可具有不同效能需求，在某些例項中，該等效能需求可與其他裝置之需求衝突。
網路環境230中之通道估計，諸如根據本文中所揭示之任何適合原則及優點使用參考信號進行的UE與RRU之間的通道之估計，對各種損害中之一或多者可係穩健的。一無線通信通道之一準確估計對於校準及/或預編碼可係有用的。結論
取決於實施例，本文中所闡述之程序或演算法中之任一者之某些動作、事件或功能可以一不同序列執行，可經添加，合併或一起省略(例如，並非所有所闡述操作或事件對於程序或演算法之實踐係必需的)。而且，在某些實施例中，操作或事件可同時執行，例如透過多執行緒處理、中斷處理，或者多個處理器或處理器核心或在其他並行架構上執行，而非依序執行。
本文中所使用之條件語言，尤其諸如「可(can)」、「可(could)」、「可(might)」、「可(may)」、「例如(e.g.)」、「諸如(such as)」等等，除非另外具體陳述或另外在內容脈絡內如所使用而理解，否則通常旨在傳達某些實施例包含而其他實施例不包含某些特徵、元件及/或操作。因此，此條件語言通常不意欲暗示一或多個實施例以任一方式需要此等特徵、元件及/或操作，或一或多個實施例在具有或不具有其他輸入或提示之情形下必然包含用於決定此等特徵、元件及/或步驟是否包含於任一特定實施例中或在任一特定實施例中執行之邏輯。術語「包括(comprising)」、「包含(including)」等等係同義詞，且以一開放方式包含性地使用，且不排除額外元件、特徵、動作、操作等等。另外，當在本申請案中使用時，字詞「本文中(herein)」、「上文(above)」、「下文(below)」及類似含義之字詞應將本申請案視為一整體而非本申請案之任何特定部分。在內容脈絡准許之情形下，在上文實施方式中使用單數或複數之字詞亦可分別包含複數或單數。此外，術語「或(or)」以其包含性意義(而非以其排他性意義)使用，使得當使用時，舉例而言，以連接一元件清單，術語「或(or)」意指清單中之一個元件、某些元件或所有元件。
諸如片語「X、Y、Z中之至少一者」之析取語言，除非另外具體陳述，否則與通常用於呈現一項目、項等可係X、Y或Z，或者其任一組合(例如，X、Y及/或Z)之內容脈絡一起理解。因此，此類析取語言通常不意欲且不應暗示某些實施例需要呈現X中之至少一者、Y中之至少一者，或Z者中之至少一者中的每一者。
除非另外明確陳述或自內容脈絡大體理解，諸如「一(a)」或「一(an)」之冠詞通常應解釋為包含一或多個所闡述項目。因此，諸如「經組態以……之一裝置」之片語意欲包含一或多個所敘述裝置。此一或多個所敘述裝置亦可共同地經組態以執行所陳述敘述。舉例而言，「經組態以執行敘述A、B及C之一處理器」可包含經組態以執行敘述A之一第一處理器，該第一處理器與經組態以執行敘述B及C之一第二處理器一起工作。
如本文中通常所使用，字詞「耦合(coupled)」係指兩個或兩個以上元件可直接彼此耦合，或藉助於一或多個中間元件耦合。同樣，如本文中通常所使用，字詞「經連接(connected)」係指兩個或兩個以上元件可直接連接或藉助於一或多個中間元件連接。連接可經由一空中介面及/或經由導線及/或經由光纖及/或經由任何其他適合連接。
如本文中所使用，術語「判定(determine)」或「判定(determining)」囊括各種各樣之動作。舉例而言，「判定」可包含在不具有使用者干預之情形下經由一硬體元件來計算、運算、處理、導出、產生、獲得、查找(例如，在一表、一資料庫或另一資料結構中查找)、確定等等。此外，「判定(determining)」可包含在不具有使用者干預之情形下經由一硬體元件來接收(例如，接收資訊)、存取(例如，在一記憶體中存取資料)。此外，「判定(determining)」可包含在不具有使用者干預之情形下經由一硬體元件來解析、選擇、抉擇、建立等等。
雖然以上詳細說明已展示、闡述及指出應用於各種實施例之新穎特徵，但可理解，可在不背離本發明之精神之情形下，在所圖解說明之裝置或演算法之形式及細節方面做出各種省略、替換及改變。舉例而言，本文中所闡述之電路區塊及/或方法方塊可經刪除、移動、添加、細分、組合，以一不同次序配置及/或修改。可以各種不同方式實施此等方塊中之每一者。本文中所揭示之方法中之任一者之任何部分可與儲存在由一或多個處理器執行之一非暫時性電腦可讀儲存媒體上之特定指令相關聯地執行。如可認識到，本文中所闡述之某些實施例可體現在不提供本文中所陳述之所有特徵及益處之形式內，此乃因某些特徵可與其他特徵分開使用或實踐。因此，本文中所揭示之某些實施例之範疇係由隨附申請專利範圍而非以上說明來指示。歸屬於申請專利範圍之等效內容之意義及範圍內之所有改變皆將涵蓋於申請專利範圍之範疇內。
10A:使用者設備 10B:使用者設備 10N:使用者設備 12A:通道 12B:通道 12N:通道 13:加總點 14:節點B 16:射頻降頻轉換區塊 18:取樣與循環首碼移除區塊 21:基本序列產生器 22:相位斜坡區塊 23:資源元素映射區塊 24:逆快速傅立葉變換區塊 25:數位轉類比轉換及射頻調變區塊 30:處理電路系統 31:快速傅立葉變換區塊 32:第一頻域處理電路/頻域處理電路 33:逆快速傅立葉變換區塊 34:時域處理電路 35:第二快速傅立葉變換區塊 35A:子快速傅立葉變換區塊 35B:子快速傅立葉變換區塊 35N:子快速傅立葉變換區塊 36:第二頻域處理電路/頻域處理電路 37:通道估計電路 40:處理電路系統 41:快速傅立葉變換區塊 42:參考信號提取電路 43:基本序列產生器 44:混合器 45:頻域處理電路 48:時域處理及通道脈衝回應分離區塊 50A-50N:每循環移位頻域處理電路/頻域處理電路 62:頻域處理電路 63:頻調估計電路 64:頻域處理電路 65:通道頻率回應脈波塑形電路/頻域處理電路 66:頻域處理電路 67:頻域處理電路 68:擴縮電路 69:時域處理電路 70:通道脈衝回應擴縮電路 160:實例方法/方法 162:方塊 164:方塊 166:方塊 170:時域濾波器 172:濾波器 176:抽頭擴縮電路 180:處理電路系統 182:時域脈波塑形電路/脈波塑形電路 202:頻率旋轉電路 210:方法 212:方塊 214:方塊 216:方塊 230:實例多輸入多輸出網路環境/多輸入多輸出網路環境/環境/網路環境 240:基頻單元 250:服務區 255:遠端無線電單元 260:服務區 265:遠端無線電單元 270:服務區 275:遠端無線電單元 282:使用者設備 283:使用者設備 284:電視 288:使用者設備/機器人裝置 290:使用者設備叢集 292:額外使用者設備 294:行動使用者設備
現將參考附圖，藉助於非限制性實例闡述本發明之實施例。
圖1係與一參考信號模型相關聯之一示意性方塊圖。
圖2係經配置以產生一參考信號之圖1之一使用者設備之硬體之一示意性方塊圖。
圖3係經配置以產生一通道估計之處理電路系統之一示意性方塊圖。
圖4A係經配置以產生一通道估計之處理電路系統之一第一部分之一示意性方塊圖。
圖4B係經配置以產生一通道估計之處理電路系統之一第二部分之一示意性方塊圖。
圖5係圖解說明針對具有8個循環移位之一參考信號之時域通道脈衝回應分離之一圖式。
圖6A至圖6E係根據某些實施例可改良通道估計之圖4A至圖4B之處理電路系統之部分之方塊圖。
圖7A係圖解說明來自兩個循環移位的，在直流及低頻頻調中具有某些失真之一經去覆蓋探測參考信號之一量值之一圖表。
圖7B係圖解說明一時域中之失真直流及低頻頻調之一圖表。
圖8A係圖解說明一頻域中之一通道頻率回應之一圖表。
圖8B係圖解說明與圖8A之通道頻率回應相關聯之一時域中之功率洩漏之一圖表。
圖9係圖解說明具有一時序偏移、一頻率偏移及不具有時序或頻率偏移之頻域脈波之一圖表。
圖10展示用於參考信號通道估計之內插之一實例。
圖11展示用於參考信號通道估計之外插之一實例。
圖12A展示在使用失真低頻頻調執行一FFT之後的一經接收頻域SRS。
圖12B展示在將二次內插應用於16個低頻頻調之後的一SRS。
圖12C展示在將二次外插應用於每一側上之16個邊緣頻調之後的一SRS。
圖13A展示一矩形脈波及一升餘弦脈波之窗函數。
圖13B展示矩形及升餘弦脈波分別相對於一中心抽頭之時域抽頭功率。
圖14A係在頻域脈波塑形之前具有經外插邊緣頻調之一SRS之一曲線圖。
圖14B係一頻域脈波塑形函數之一曲線圖。
圖14C係在應用頻域脈波塑形之後包含經外插邊緣頻調之SRS之一曲線圖。
圖15係圖解說明在已執行一逆FFT之後針對循環移位之時域通道脈衝回應之一圖式。
圖16係基於一功率延遲量變曲線進行時域通道脈衝回應擴縮之一實例方法之一流程圖。
圖17係可基於一功率延遲量變曲線執行時域通道脈衝回應擴縮之一時域處理電路之一示意性方塊圖。
圖18係具有時域脈波塑形之處理電路系統之一示意性方塊圖。
圖19A係時域中之一矩形脈波及一升餘弦脈波之一圖表。
圖19B係頻域中之一sinc脈波及一升餘弦脈波之一圖表。
圖20係具有用以補償一頻率偏移之頻率旋轉之處理電路系統之一示意性方塊圖。
圖21係偵測其中混附雜訊被移動至一未經使用之時間空間之一參考信號之循環移位之一方法之一流程圖。
圖22圖解說明用於四個循環移位之第一諧波混附雜訊之位置。
圖23係圖解說明其中可執行基於一參考信號之通道估計之一實例多輸入多輸出(MIMO)網路環境之一圖式。
30:處理電路系統
31:快速傅立葉變換區塊
32:第一頻域處理電路/頻域處理電路
33:逆快速傅立葉變換區塊
34:時域處理電路
35:第二快速傅立葉變換區塊
36:第二頻域處理電路/頻域處理電路
37:通道估計電路

Claims (23)

  1. 一種參考信號通道估計之方法，該方法包括： 接收用於通道估計之一參考信號； 在一頻域中，對該參考信號進行去覆蓋以產生一經去覆蓋參考信號； 在該去覆蓋之後，對該經去覆蓋參考信號進行頻域處理，以使該經去覆蓋參考信號中之一直流偏移的失真減小； 在該頻域處理之後，進行時域處理，以使與該經去覆蓋參考信號相關聯之一雜訊底部減小；及 基於該頻域處理及該時域處理來產生一通道估計，其中該通道估計係和一第一節點與一第二節點之間之一通信通道相關聯。
  2. 如請求項1之方法，其中該頻域處理包括：基於該經去覆蓋頻域參考信號之至少兩個其他頻調來產生針對該經去覆蓋頻域參考信號之一頻調之一經估計頻調。
  3. 如請求項2之方法，其中該頻域處理包括：用該經估計頻調來替換該頻調，以使與該直流偏移相關聯之失真減小。
  4. 如請求項2之方法，其中該頻域處理包括：基於該經估計頻調來修改該頻調，以使與該直流偏移相關聯之失真減小。
  5. 如請求項1之方法，其中該頻域處理包括：對該經去覆蓋頻域參考信號進行脈波塑形，以使與該直流偏移相關聯之失真減小。
  6. 如請求項1之方法，其中該時域處理包括： 估計對應於通道脈衝回應之間之副載波之時域抽頭之一子集的雜訊功率；及 基於該估計，對該等時域抽頭之至少一部分執行一每抽頭擴縮。
  7. 如請求項6之方法，其中該每抽頭擴縮涉及最小均方誤差擴縮或臨限值化中之至少一者。
  8. 如請求項1之方法，進一步包括：在該去覆蓋之前，對該參考信號進行脈波塑形。
  9. 如請求項1之方法，進一步包括：在該去覆蓋之前，基於一頻率偏移之一指示符來旋轉該參考信號。
  10. 如請求項1之方法，其中該時域處理包括：將一混附雜訊移動至用於該參考信號之循環移位的時域窗之外。
  11. 如請求項10之方法，進一步包括：在該去覆蓋之前，對該參考信號進行脈波塑形。
  12. 如請求項1之方法，其中該參考信號係一上行鏈路探測參考信號。
  13. 如請求項1之方法，其中該第一節點係一使用者設備，且該第二節點係一網路節點。
  14. 一種用於通道估計之系統，該系統包括： 一頻域處理電路，其經組態以產生一經去覆蓋頻域參考信號並處理該經去覆蓋頻域參考信號，以便使與一直流偏移相關聯之失真減小；及 一時域處理電路，其具有經耦合至該頻域處理電路之一輸出之一輸入，該時域處理電路經組態以抑制時域通道脈衝回應洩漏；及 一通道估計電路，其經組態以基於該時域處理電路之一輸出來產生一通道估計，其中該通道估計係和一第一節點與一第二節點之間之一無線通信通道相關聯。
  15. 如請求項14之系統，其中該頻域處理電路經組態以基於該經去覆蓋頻域參考信號之至少兩個其他頻調來產生針對該經去覆蓋頻域參考信號之一頻調之一經估計頻調，並用該經估計頻調來替換該頻調，以使與該直流偏移相關聯之失真減小。
  16. 如請求項14之系統，其中該頻域處理電路經組態以對該經去覆蓋頻域參考信號執行脈波塑形，以使與該直流偏移相關聯之失真減小。
  17. 如請求項14之系統，其中該時域處理電路包括： 一濾波器，其包括複數個抽頭； 一雜訊功率估計電路，其經組態以估計對應於通道脈衝回應之間之副載波之該濾波器之該等抽頭之一子集的雜訊功率；及 一濾波器抽頭擴縮電路，其經組態以基於該經估計雜訊功率，對該濾波器之該等抽頭的至少一部分執行一每抽頭擴縮。
  18. 如請求項14之系統，其中該時域處理電路經組態以將一混附雜訊移動至用於該參考信號之循環移位的時域窗之外。
  19. 如請求項14之系統，進一步包括經組態以對一參考信號進行脈波塑形之一第二時域處理電路，該第二時域處理電路具有經耦合至該頻域處理電路之一輸入之一輸出。
  20. 如請求項14之系統，進一步包括經組態以基於一頻域偏移之一指示符來旋轉一參考信號以藉此減小該頻域偏移之一第二時域處理電路，該第二時域處理電路具有經耦合至該頻域處理電路之一輸入之一輸出。
  21. 如請求項14之系統，進一步包括經組態以執行每循環移位頻域處理之一第二頻域處理電路，其中該第二頻域處理電路係耦合於該時域處理電路與該通道估計電路之間。
  22. 如請求項14之系統，其中該第一節點係一使用者設備，且該第二節點係一網路節點。
  23. 一種用於通道估計之系統，該系統包括： 用於處理一經去覆蓋頻域參考信號以便使與一直流偏移相關聯之失真減小的構件； 用於抑制時域通道脈衝回應洩漏的構件，用於抑制之該構件具有經耦合至用於處理之該構件之一輸出之一輸入；及 一通道估計電路，其經組態以基於用於抑制之該構件之一輸出來產生一通道估計，其中該通道估計係和一第一節點與一第二節點之間之一無線通信通道相關聯。
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US11411779B2 (en) 2022-08-09
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US20210328838A1 (en) 2021-10-21
EP4128676A1 (en) 2023-02-08
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US20220345336A1 (en) 2022-10-27

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