TW201820802A

TW201820802A - Transmitting device, transmitting method, receiving device and receiving method

Info

Publication number: TW201820802A
Application number: TW106136505A
Authority: TW
Inventors: 本塚裕幸; 坂本剛憲; 白方亨宗
Original assignee: 美商松下電器（美國）知識產權公司
Priority date: 2016-11-04
Filing date: 2017-10-24
Publication date: 2018-06-01
Also published as: TWI741050B; JP7015136B2; JP2018074573A; WO2018084035A1

Abstract

This transmitting device adopts a configuration provided with: a precoding unit which subjects a first baseband signal and a second baseband signal to a precoding process to generate a first precoded signal and a second precoded signal; an order inverting unit which inverts the order of symbols constituting the second precoded signal to generate a second inverted signal; a phase changing unit which generates a second phase-changed signal obtained by subjecting the second inverted signal to a phase change; and a transmitting unit which transmits the first precoded signal and the second phase-changed signal from respectively different antennas.

Description

發送裝置、發送方法、接收裝置、及接收方法Transmitting device, transmitting method, receiving device, and receiving method

發明領域本揭示是有關於一種進行使用了多天線(multi-antenna)的通訊之發送裝置、發送方法、接收裝置、及接收方法。FIELD OF THE INVENTION The present disclosure relates to a transmitting device, a transmitting method, a receiving device, and a receiving method for performing communication using a multi-antenna.

發明背景無線LAN相關規格的一種、即IEEE802.11ad規格，是有關於利用60GHz頻段的毫米波之無線通訊的規格(非專利文獻1)。在IEEE802.11ad規格中，規定有藉由單載波(Single Carrier)進行的發送。BACKGROUND OF THE INVENTION The IEEE802.11ad standard, which is a type of wireless LAN-related specifications, is a standard for wireless communication using millimeter waves in the 60 GHz band (Non-Patent Document 1). The IEEE 802.11ad standard specifies transmission by a single carrier.

又，關於利用了多天線的通訊技術之1種，有MIMO(多輸入多輸出，Multiple-Input Multiple-Output)(非專利文獻2)。藉由利用MIMO，可提高空間分集(space diversity)效果，且提升接收品質。先前技術文獻非專利文獻Further, as one of communication technologies using multiple antennas, there is MIMO (Multiple-Input Multiple-Output) (Non-Patent Document 2). By using MIMO, the space diversity effect can be improved and the reception quality can be improved. Prior art literature Non-patent literature

非專利文獻1：IEEE802.11ad^TM -2012，2012年12月28日非專利文獻2：“MIMO for DVB-NGH, the next generation mobile TV broadcasting,” IEEE Commun. Mag., vol.57, no.7, pp.130-137，2013年7月非專利文獻3：IEEE802.11-16/0631r0，2016年5月15日非專利文獻4：IEEE802.11-16/0632r0，2016年5月15日Non-Patent Document 1: IEEE802.11ad ^TM -2012, December 28, 2012 Non-Patent Document 2: "MIMO for DVB-NGH, the next generation mobile TV broadcasting," IEEE Commun. Mag., Vol.57, no. 7, pp.130-137, July 2013 Non-Patent Document 3: IEEE802.11-16 / 0631r0, May 15, 2016 Non-Patent Document 4: IEEE802.11-16 / 0632r0, May 15, 2016

發明概要發明欲解決之課題但是，在利用單載波的MIMO通訊中，會有無法充分地得到頻率分集(frequency diversity)效果的情況。SUMMARY OF THE INVENTION Problems to be Solved by the Invention However, in a MIMO communication using a single carrier, a frequency diversity effect may not be sufficiently obtained.

本揭示之非限定的實施例有助於提供一種可提高利用了單載波之MIMO通訊中的頻率分集效果的發送裝置、發送方法、接收裝置、及接收方法。用以解決課題之手段The non-limiting embodiments of the present disclosure help to provide a transmitting device, a transmitting method, a receiving device, and a receiving method that can improve the frequency diversity effect in MIMO communication using a single carrier. Means to solve the problem

本揭示之一態様的發送裝置，具備：預編碼部，對第1基頻訊號與第2基頻訊號施行預編碼處理，以生成第1預編碼訊號與第2預編碼訊號；順序反轉部，使構成前述第2預編碼訊號的符號序列之順序反轉，而生成第2反轉訊號；相位變更部，生成第2相位變更訊號，且該第2相位變更訊號是對前述第2反轉訊號施行了相位變更之訊號；及發送部，分別從不同的天線發送前述第1預編碼訊號與前述第2相位變更訊號。A transmitting device according to one aspect of the present disclosure includes a precoding section that performs precoding processing on the first baseband signal and the second baseband signal to generate a first precoding signal and a second precoding signal; and an order reversing section. , Inverting the order of the symbol sequence constituting the second precoding signal to generate a second inversion signal; the phase changing unit generates a second phase changing signal, and the second phase changing signal is an inverse of the second inversion The signal performs a phase change signal; and the transmitting section transmits the first precoding signal and the second phase change signal from different antennas, respectively.

本揭示之一態様的接收裝置，具備：接收部，以不同的天線來分別接收第1接收訊號及第2接收訊號；及解調部，從前述第1接收訊號及前述第2接收訊號中生成第1基頻訊號及第2基頻訊號，在前述第1接收訊號及前述第2接收訊號中，包含有第1預編碼訊號及第2相位變更訊號，前述第1預編碼訊號，是發送裝置對前述第1基頻訊號及前述第2基頻訊號施行預編碼處理而生成的訊號，前述第2相位變更訊號是下述之訊號：前述發送裝置對前述第1基頻訊號與前述第2基頻訊號施行預編碼處理而生成第2預編碼訊號，且使構成該生成的第2預編碼訊號的符號序列之順序反轉而生成第2反轉訊號，並對該生成的第2反轉訊號施行相位變更而生成的訊號。A receiving device according to one aspect of the present disclosure includes: a receiving section that receives the first receiving signal and the second receiving signal respectively with different antennas; and a demodulating section that generates from the first receiving signal and the second receiving signal The first baseband signal and the second baseband signal include the first precoding signal and the second phase change signal in the first receiving signal and the second receiving signal. The first precoding signal is a transmitting device. The signal generated by performing precoding processing on the first baseband signal and the second baseband signal, and the second phase change signal is the following signal: the transmitting device responds to the first baseband signal and the second baseband signal. The frequency signal is subjected to precoding processing to generate a second precoded signal, and the order of the symbol sequences constituting the generated second precoded signal is reversed to generate a second inverted signal, and the generated second inverted signal is generated. Signal generated by phase change.

再者，這些全面的或具體的態樣可以利用系統、方法、積體電路、電腦程式、或者記錄媒體來實現，亦可藉系統、裝置、方法、積體電路、電腦程式及記錄媒體的任意的組合來實現。發明效果Furthermore, these comprehensive or specific aspects can be realized by using systems, methods, integrated circuits, computer programs, or recording media, or by any of the systems, devices, methods, integrated circuits, computer programs, and recording media. Combination to achieve. Invention effect

根據本揭示的一態樣，可以提高利用了單載波之MIMO通訊中的頻率分集效果。According to one aspect of the present disclosure, the frequency diversity effect in MIMO communication using a single carrier can be improved.

本揭示的一態様中的進一步之優點及效果，從說明書及圖式中可清楚地了解。雖然所述優點及/或效果是藉由一些實施形態以及說明書及圖式所記載之特徵來分別地提供，然而為了得到1個或其以上的相同的特徵，並不一定需要全部都提供。Further advantages and effects in the aspect of the present disclosure can be clearly understood from the description and drawings. Although the advantages and / or effects are provided separately by some embodiments and features described in the description and drawings, it is not necessary to provide all of them in order to obtain one or more of the same features.

用以實施發明之形態以下，參照圖式並詳細地說明本揭示的實施形態。Embodiments for Carrying Out the Invention Embodiments of the present disclosure will be described in detail below with reference to the drawings.

(實施形態1) 圖1為顯示MIMO通訊系統的構成之一例的圖。發送裝置具備複數個發送天線。接收裝置具備複數個接收天線。(Embodiment 1) FIG. 1 is a diagram showing an example of a configuration of a MIMO communication system. The transmitting device includes a plurality of transmitting antennas. The receiving device includes a plurality of receiving antennas.

將各發送天線與各接收天線之間的無線傳遞路徑稱為通道。在圖1中，在第1發送天線與第1接收天線之間、第1發送天線與第2接收天線之間、第2發送天線與第1接收天線之間、及第2發送天線與第2接收天線之間，分別有通道H₁₁ (k)、通道H₁₂ (k)、通道H₂₁ (k)、及通道H₂₂ (k)。在各通道中，可合成例如直接波、反射波、繞射波、及/或散射波。通道H₁₁ (k)、H₁₂ (k)、H₂₁ (k)、及H₂₂ (k)的值為各通道的頻率響應。頻率響應是頻率的指數k中之複數(complex number)。The wireless transmission path between each transmitting antenna and each receiving antenna is called a channel. In FIG. 1, between the first transmitting antenna and the first receiving antenna, between the first transmitting antenna and the second receiving antenna, between the second transmitting antenna and the first receiving antenna, and between the second transmitting antenna and the second receiving antenna Between the receiving antennas, there are a channel H ₁₁ (k), a channel H ₁₂ (k), a channel H ₂₁ (k), and a channel H ₂₂ (k). In each channel, for example, a direct wave, a reflected wave, a diffracted wave, and / or a scattered wave can be synthesized. The values of the channels H ₁₁ (k), H ₁₂ (k), H ₂₁ (k), and H ₂₂ (k) are the frequency response of each channel. The frequency response is the complex number in the exponent k of the frequency.

發送裝置是從各發送天線中將不同的發送資料同時地、亦即在D/A轉換器中以相同的取樣定時(sampling timing)來發送。接收裝置具備複數個接收天線。接收裝置是以各接收天線對接收資料同時地、亦即在A/D轉換器中以相同的取樣定時來進行接收。但是，由於各通道的延遲不同，因此發送裝置已同時發送的發送資料不一定會被接收裝置同時地接收。The transmission device transmits different transmission data from each transmission antenna at the same time, that is, at the same sampling timing in the D / A converter. The receiving device includes a plurality of receiving antennas. The receiving device receives data simultaneously with each receiving antenna, that is, the A / D converter performs reception at the same sampling timing. However, since the delay of each channel is different, the transmission data that the transmitting device has transmitted simultaneously may not necessarily be received by the receiving device at the same time.

圖2是顯示頻率響應之振幅成分的例子之圖。在圖2中，所顯示的是每個通道的頻率響應不同，且通道間的相關較低的狀態之一例。FIG. 2 is a diagram showing an example of an amplitude component of a frequency response. In FIG. 2, an example is shown in which the frequency response of each channel is different and the correlation between channels is low.

接收裝置在接收來自第1發送天線的發送資料x₁ (b,n)之情況下，會進行例如如下的處理。也就是說，接收裝置是對第1接收天線的接收資料與第2接收天線的接收資料乘上複數(complex number)之加權係數，並對資料進行加法運算，以增強來自通道H₁₁ (k)及通道H₁₂ (k)的接收訊號，並抑制來自通道H₂₁ (k)及通道H₂₂ (k)的接收訊號。加權係數是利用例如後述的MMSE(最小均方誤差，Minimum Mean Square Error)而算出。When the receiving device receives the transmission data x ₁ (b, n) from the first transmission antenna, it performs the following processing, for example. That is, the receiving device multiplies the received data of the first receiving antenna and the received data of the second receiving antenna by a complex number weighting coefficient, and adds the data to enhance the data from the channel H ₁₁ (k) And receive signals from channel H ₁₂ (k), and suppress the receive signals from channel H ₂₁ (k) and channel H ₂₂ (k). The weighting coefficient is calculated using, for example, MMSE (Minimum Mean Square Error) described later.

圖3是顯示發送裝置100的構成之一例的圖。在圖3中，發送裝置100具備MAC部101、流(stream)生成部102、編碼部103a、103b、資料調變部104a、104b、預編碼部105、GI(保護間隔(Guard Interval))附加部106a、106b、符號順序反轉部107、資料符號緩衝器108a、108b、相位旋轉部109、發送F/E電路(濾波D/A轉換RF電路)110a、110b、及發送天線111a、111b。FIG. 3 is a diagram showing an example of the configuration of the transmission device 100. In FIG. 3, the transmission device 100 includes a MAC unit 101, a stream generation unit 102, encoding units 103a, 103b, data modulation units 104a, 104b, a precoding unit 105, and a GI (Guard Interval) addition. The units 106a and 106b, the symbol sequence inverting unit 107, the data symbol buffers 108a and 108b, the phase rotation unit 109, the transmission F / E circuits (filtered D / A conversion RF circuits) 110a and 110b, and the transmission antennas 111a and 111b.

發送裝置100是在資料調變部104a、104b中進行π/2-BPSK調變，且從發送天線111a、111b分別發送不同的資料。The transmission device 100 performs π / 2-BPSK modulation in the data modulation sections 104a and 104b, and transmits different data from the transmission antennas 111a and 111b, respectively.

MAC部101是生成發送資料，且將該生成的發送資料輸出至流生成部102。The MAC unit 101 generates transmission data and outputs the generated transmission data to the stream generation unit 102.

流生成部102是將發送資料分割成第1流資料與第2流資料等2個。例如，流生成部102是將發送資料的第奇數個之位元分配至第1流資料，且將發送資料的第偶數個之位元分配至第2流資料。並且，流生成部102會將第1流資料輸出至編碼部103a，且將第2流資料輸出至編碼部103b。流生成部102也可以算出發送資料的CRC(循環冗餘檢查，Cyclic Redundancy Check)，且由將該CRC附加於發送資料的最後來生成流資料。The stream generation unit 102 divides the transmission data into two streams, such as a first stream data and a second stream data. For example, the stream generation unit 102 assigns the odd-numbered bits of the transmission data to the first stream data, and assigns the even-numbered bits of the transmission data to the second stream data. The stream generation unit 102 outputs the first stream data to the encoding unit 103a, and outputs the second stream data to the encoding unit 103b. The stream generation unit 102 may calculate a CRC (Cyclic Redundancy Check) of the transmission data, and generate the stream data by adding the CRC to the end of the transmission data.

將對於從流生成部102輸出的第1流資料的處理，稱為第1發送流處理。第1發送流處理是藉由編碼部103a及資料調變部104a來進行。The processing of the first stream data output from the stream generation unit 102 is referred to as a first transmission stream process. The first transmission stream processing is performed by the encoding unit 103a and the data modulation unit 104a.

將對於從流生成部102輸出的第2流資料的處理，稱為第2發送流處理。第2發送流處理是藉由編碼部103b及資料調變部104b來進行。The processing of the second stream data output from the stream generation unit 102 is referred to as a second transmission stream process. The second transmission stream processing is performed by the encoding unit 103b and the data modulation unit 104b.

編碼部103a、103b會對各流資料進行糾錯編碼處理。編碼部103a、103b亦可將例如LDPC(低密度奇偶檢查，Low Density Parity Check)碼利用於糾錯編碼方式上。The encoding units 103a and 103b perform error correction encoding processing on each stream data. The encoding units 103a and 103b may use, for example, an LDPC (Low Density Parity Check) code for an error correction encoding method.

資料調變部104a、104b是對已藉由編碼部103a、103b進行過糾錯編碼處理的各流資料，施行調變處理。資料調變部104a、104b是將例如π/2-BPSK利用於資料調變方式。The data modulation sections 104a and 104b perform modulation processing on each stream data that has been subjected to error correction coding processing by the coding sections 103a and 103b. The data modulation sections 104a and 104b use, for example, π / 2-BPSK for the data modulation method.

圖4A是顯示符號指數(symbol index)m為奇數的π/2-BPSK(二元相移鍵控，Binary Phase Shift Keying)之星象圖(constellation)的例子。圖4B是顯示符號指數m為偶數的π/2-BPSK之星象圖的例子。將資料調變部104a輸出的資料(也稱為「調變訊號」)表示成調變符號s₁ (m)。又，將資料調變部104b輸出的資料表示成調變符號s₂ (m)。在此，m是表示符號指數，且為正整數。FIG. 4A is an example of a constellation showing π / 2-BPSK (Binary Phase Shift Keying) whose symbol index m is an odd number. FIG. 4B is an example of an astrological chart showing π / 2-BPSK whose sign index m is an even number. The data (also referred to as a "modulation signal") output by the data modulation section 104a is expressed as a modulation symbol s ₁ (m). The data output from the data modulation unit 104b is expressed as a modulation symbol s ₂ (m). Here, m is a sign index and is a positive integer.

在資料調變部104a進行π/2-BPSK調變的情況下，調變符號s₁ (m)、s₂ (m)會成為以下之值。在m為奇數的情況下，s₁ (m)及s₂ (m)是配置在I軸上，且成為+1或-1之任一值。在m為偶數的情況下，s₁ (m)及s₂ (m)是配置在Q軸上，且成為+j或-j之任一值。在此，j為虛數單位。When the data modulation unit 104a performs π / 2-BPSK modulation, the modulation symbols s ₁ (m) and s ₂ (m) have the following values. When m is an odd number, s ₁ (m) and s ₂ (m) are arranged on the I axis and have any value of +1 or -1. When m is an even number, s ₁ (m) and s ₂ (m) are arranged on the Q axis and have any value of + j or -j. Here, j is an imaginary unit.

如算式1所示，預編碼部105是對資料調變部104a、104b的調變符號s₁ (m)、s₂ (m)乘上2行2列的矩陣，而算出預編碼符號x₁ (m)、x₂ (m)。(算式1)As shown in Equation 1, the precoding unit 105 calculates the precoding symbol x ₁ by multiplying the modulation symbols s ₁ (m) and s ₂ (m) of the data modulation units 104a and 104b by a matrix of two rows and two columns. (m), x ₂ (m). (Equation 1)

在算式1中，將被相乘於s₁ (m)、s₂ (m)的2行2列之矩陣，稱為預編碼矩陣(以下表示為「G」)。亦即，預編碼矩陣G是以算式2來表現。(算式2)In Equation 1, a matrix of two rows and two columns multiplied by s ₁ (m) and s ₂ (m) is referred to as a precoding matrix (hereinafter referred to as "G"). That is, the precoding matrix G is expressed by Expression 2. (Equation 2)

但是，算式2的預編碼矩陣僅為一例，也可以將其他矩陣利用於預編碼矩陣G。例如，也可以將其他的么正矩陣(unitary matrix)利用於預編碼矩陣G。在此，所謂的么正矩陣是滿足算式2-1的矩陣。在算式2-1中，G^H 是表示矩陣G的複共軛轉置(complex conjugate transpose)，而I是表示單位矩陣。(算式2-1)However, the precoding matrix of Equation 2 is only an example, and other matrices may be used for the precoding matrix G. For example, another unitary matrix may be used for the precoding matrix G. Here, the so-called positive matrix is a matrix satisfying the expression 2-1. In Equation 2-1, G ^H is a complex conjugate transpose representing the matrix G, and I is an identity matrix. (Equation 2-1)

由於算式2的預編碼矩陣G滿足算式2-1，因此是么正矩陣的一例。Since the precoding matrix G of Equation 2 satisfies Equation 2-1, it is an example of a positive matrix.

利用了算式2的預編碼矩陣G的情況下，x₁ (m)、x₂ (m)會滿足算式2-2的關係。再者，記號「*」是表示複共軛。(算式2-2)When the precoding matrix G of Equation 2 is used, x ₁ (m) and x ₂ (m) satisfy the relationship of Equation 2-2. The symbol "*" indicates complex conjugation. (Equation 2-2)

接著，在算式2-3中表示其他的預編碼矩陣G之例子。(算式2-3)Next, an example of another precoding matrix G is shown in Equation 2-3. (Equation 2-3)

利用了算式2-3的預編碼矩陣G的情況下，x₁ (m)、x₂ (m)會滿足算式2-4的關係。(算式2-4)When the precoding matrix G of Formula 2-3 is used, x ₁ (m) and x ₂ (m) satisfy the relationship of Formula 2-4. (Equation 2-4)

接著，在算式2-5中表示其他的預編碼矩陣G之例子。在算式2-5中, a為實數，b為複數的常數。又，ρ是表示相位位移量的常數。(算式2-5)Next, examples of other precoding matrices G are shown in Equations 2-5. In Equation 2-5, a is a real number and b is a constant of a complex number. In addition, ρ is a constant indicating the amount of phase shift. (Equation 2-5)

利用了算式2-5的預編碼矩陣G的情況下，x₁ (m)、x₂ (m)會滿足算式2-6的關係。(算式2-6)When the precoding matrix G of Formula 2-5 is used, x ₁ (m) and x ₂ (m) satisfy the relationship of Formula 2-6. (Equation 2-6)

在算式2-5中，將a、b都設為1，且將ρ設為-π/4的情況下，算式2-5會變得與算式2相等。In Equation 2-5, when both a and b are set to 1 and ρ is set to -π / 4, Equation 2-5 becomes equal to Equation 2.

圖4C是顯示預編碼部105的輸出資料x₁ (m)、x₂ (m)之星象圖的一例之圖。圖4C與QPSK調變的星象圖是相同的。也就是說，預編碼部105是利用算式1，將以π/2-BPSK調變過的2個調變符號s₁ (m)、s₂ (m)，轉換為相當於QPSK符號的2個預編碼符號x₁ (m)、x₂ (m)。FIG. 4C is a diagram showing an example of an astrological map of the output data x ₁ (m) and x ₂ (m) of the precoding unit 105. Figure 4C is the same as the QPSK modulation horoscope. In other words, the precoding unit 105 converts the two modulation symbols s ₁ (m) and s ₂ (m) modulated by π / 2-BPSK into two equivalent QPSK symbols by using Equation 1. Precoding symbols x ₁ (m), x ₂ (m).

對於從預編碼部105輸出的預編碼符號x₁ (m)的處理，是稱為第1發送RF鏈(chain)處理。第1發送RF鏈(chain)處理是藉由GI附加部106a、資料符號緩衝器108a、發送F/E(前端，Front End)電路110a、及發送天線111a來進行。The process of the precoding symbol x ₁ (m) output from the precoding unit 105 is referred to as a first transmission RF chain process. The first transmission RF chain processing is performed by the GI adding unit 106a, the data symbol buffer 108a, the transmission F / E (Front End) circuit 110a, and the transmission antenna 111a.

對於從預編碼部105輸出的預編碼符號x₂ (m)的處理，是稱為第2發送RF鏈處理。第2發送RF鏈處理是藉由複共軛GI附加部106b、符號順序反轉部107、資料符號緩衝器108b、相位旋轉部109、發送F/E電路110b、及發送天線111b來進行。The process of the precoding symbol x ₂ (m) output from the precoding unit 105 is referred to as a second transmission RF chain process. The second transmission RF chain processing is performed by the complex conjugate GI adding section 106b, the symbol order inversion section 107, the data symbol buffer 108b, the phase rotation section 109, the transmission F / E circuit 110b, and the transmission antenna 111b.

圖5A是顯示GI附加部106a、複共軛GI附加部106b中的GI附加方法的一例之圖。FIG. 5A is a diagram showing an example of a GI adding method in the GI adding section 106a and the complex conjugated GI adding section 106b.

GI附加部106a是將預編碼符號x₁ (m)分割成每個448個符號的資料區塊。例如，將x₁ (m)之最初的448個符號分割成第1資料區塊(x₁ (1,n))，且將其接著的448個符號分割成第2資料區塊(x₁ (2,n))，…，並將第b的448個符號分割成第b資料區塊(x₁ (b,n))。在此，在本實施形態的情況下，n為1以上且448以下的整數，b為正整數。也就是說，x₁ (b,n)是表示第b資料區塊內的第n個預編碼符號。再者，這些符號數僅是一例，本實施形態也可以是這些以外的符號數。The GI appender 106a divides the precoded symbol x ₁ (m) into data blocks of 448 symbols each. For example, the first 448 symbols of x ₁ (m) are divided into the first data block (x ₁ (1, n)), and the following 448 symbols are divided into the second data block (x ₁ ( 2, n)), ..., and divide the 448th symbol of the b into the b-th data block (x ₁ (b, n)). Here, in the case of this embodiment, n is an integer from 1 to 448, and b is a positive integer. That is, x ₁ (b, n) is the n-th precoding symbol in the b-th data block. The number of symbols is only an example, and the number of symbols other than these may be used in the present embodiment.

GI附加部106a是在各資料區塊的前段附加64個符號的GI。GI是對習知的序列進行了π/2-BPSK調變的符號序列。此外，GI附加部106a是在最後的資料區塊之後段附加64個符號的GI。藉此，可生成如圖5A所示的發送符號u1。The GI adding unit 106a is a GI that adds 64 symbols to the top of each data block. GI is a symbol sequence that is π / 2-BPSK modulated on a conventional sequence. The GI adding unit 106a is a GI that adds 64 symbols after the last data block. Thereby, a transmission symbol u1 as shown in FIG. 5A can be generated.

同樣地，複共軛GI附加部106b也是將預編碼符號x₂ (m)分割成每個448個符號的資料區塊，且在各資料區塊的前段附加64個符號的GI，並在最後的資料區塊之後段附加64個符號的GI。但是，複共軛GI附加部106b所附加的GI，是GI附加部106a所附加的GI之複共軛。藉此，可生成如圖5A所示的發送符號u2。Similarly, the complex conjugate GI adding unit 106b also divides the precoded symbol x ₂ (m) into data blocks of 448 symbols each, and adds a GI of 64 symbols to the front of each data block, and finally The 64-symbol GI is appended to the following block of the data block. However, the GI added by the complex conjugated GI adding unit 106b is a complex conjugate of the GI added by the GI adding unit 106a. Thereby, the transmission symbol u2 shown in FIG. 5A can be generated.

在此，將GI附加部106a所附加的GI之第p個符號表示為GI₁ (p)。又，將複共軛GI附加部106b所附加的GI之第p個符號表示為GI₂ (p)。在本實施形態的情況下，p為1以上且64以下的整數。在此情況下，GI₁ (p)與GI₂ (p)存有算式3所示的關係。再者，記號「*」是表示複共軛。(算式3)Here, the p-th symbol of the GI added by the GI adding unit 106a is denoted as GI ₁ (p). The p-th symbol of the GI added by the complex conjugated GI adding unit 106b is denoted as GI ₂ (p). In the case of this embodiment, p is an integer of 1 or more and 64 or less. In this case, GI ₁ (p) and GI ₂ (p) have a relationship shown in Equation 3. The symbol "*" indicates complex conjugation. (Equation 3)

圖5B是顯示對符號區塊(參照圖5A的發送符號u1)進行DFT(Discrete Fourier Transform，離散傅立葉轉換)之後的DFT訊號X₁ (b,k)的例子，其中該符號區塊是在預編碼符號x₁ (b,n)中附加有GI(p)的符號區塊。圖5C是顯示對符號區塊(參照圖5A的發送符號u2)進行DFT之後的DFT訊號X₂ (b,k)的例子，其中該符號區塊是在預編碼符號x₂ (b,n)中附加有GI^* (p)的符號區塊。接著，利用DFT訊號X₁ (b,k)，來說明從GI附加部106a中輸出的訊號之頻率特性。又，利用DFT訊號X₂ (b,k)，來說明從複共軛GI附加部106b中輸出的訊號之頻率特性。FIG. 5B is an example showing a DFT signal X ₁ (b, k) after performing DFT (Discrete Fourier Transform) on a symbol block (refer to the transmission symbol u1 in FIG. 5A), where the symbol block is in a pre- A symbol block of GI (p) is added to the coded symbol x ₁ (b, n). FIG. 5C shows an example of the DFT signal X ₂ (b, k) after DFT of the symbol block (refer to the transmission symbol u2 in FIG. 5A), where the symbol block is the pre-encoded symbol x ₂ (b, n) A symbol block with GI ^* (p) is attached to it. Next, the frequency characteristics of a signal output from the GI adding unit 106a will be described using the DFT signal X ₁ (b, k). The frequency characteristics of the signal output from the complex conjugated GI adding unit 106b will be described using the DFT signal X ₂ (b, k).

在利用了算式2之預編碼矩陣G的情況下，由於x₂ (b,n)及GI^* (p)是x₁ (b,n)及GI(p)的複共軛，因此DFT訊號X₂ (b,k)會成為對DFT訊號X₁ (b,k)的複共軛進行頻率反轉，且在頻率區域施加有相位旋轉的訊號。也就是說，X₂ (b,k)可用算式3-1來表示。(算式3-1)When the precoding matrix G of Equation 2 is used, since x ₂ (b, n) and GI ^* (p) are complex conjugates of x ₁ (b, n) and GI (p), the DFT signal X ₂ (b, k) becomes a signal that frequency-reverses the complex conjugate of the DFT signal X ₁ (b, k), and a phase rotation signal is applied in the frequency region. That is, X ₂ (b, k) can be expressed by Equation 3-1. (Equation 3-1)

再者，如下述內容，將算式3-1中的相位旋轉量(exp(j×2πk/N))表示為W。(算式3-2)The phase rotation amount (exp (j × 2πk / N)) in Equation 3-1 is represented as W as described below. (Equation 3-2)

藉由預編碼處理，可以將2個調變符號s₁ (m)、s₂ (m)混合，並利用2個不同的發送天線來發送。藉此，即可得到空間分集效果。又，藉由預編碼處理，可以將2個調變符號s₁ (m)、s₂ (m)混合，並利用2個不同的頻率指數k、-k來發送。藉此，即可得到頻率分集效果。Through the precoding process, two modulation symbols s ₁ (m) and s ₂ (m) can be mixed and transmitted using two different transmission antennas. In this way, a space diversity effect can be obtained. In addition, by the precoding process, two modulation symbols s ₁ (m) and s ₂ (m) can be mixed and transmitted using two different frequency indices k and -k. Thereby, the frequency diversity effect can be obtained.

再者，在圖5B及圖5C中，在2個不同的頻率指數k、-k之絕對值｜k｜為較小的情況下，由於2個頻率是相接近的，因此會使頻率分集效果減少。在以下，針對抑制像這樣2個頻率相接近，而使頻率分集效果減少的情形之技術進行說明。In addition, in FIG. 5B and FIG. 5C, when the absolute values | k | of two different frequency indices k and -k are small, since the two frequencies are close to each other, the frequency diversity effect is caused. cut back. In the following, a technique for suppressing a situation where the two frequencies are close to each other to reduce the frequency diversity effect will be described.

圖6A是顯示符號順序反轉部107中的符號順序反轉處理的一例。FIG. 6A shows an example of a symbol order inversion process in the symbol order inversion section 107.

如圖6A所示，符號順序反轉部107是針對各符號區塊，而使預編碼符號x₂ (b,n)的順序反轉，並使附加於該預編碼符號x₂ (b,n)的GI(p)之順序反轉。為了使說明更容易理解，是將順序已反轉的預編碼符號x₂ ^{(time reversal)} (b,n)，表示成如算式4。也就是說，以「-n」來表示順序已反轉的符號序列。(算式4)As shown in FIG. 6A, the symbol order reversing unit 107 reverses the order of the precoded symbol x ₂ (b, n) for each symbol block, and adds the precoded symbol x ₂ (b, n) The order of GI (p) is reversed. In order to make the description easier to understand, the precoding symbol x ₂ ^{(time reversal)} (b, n) whose order has been reversed is expressed as Equation 4. In other words, "-n" represents a sequence of symbols whose order has been reversed. (Equation 4)

又，將順序已反轉的GI₂ ^{(time reversal)} (p)，表示成如算式5。也就是說，以「-p」來表示順序已反轉的符號序列。(算式5)In addition, GI ₂ ^{(time reversal)} (p) whose order has been reversed is expressed as Equation 5. In other words, "-p" represents a sequence of symbols whose order has been reversed. (Equation 5)

圖6C是對符號區塊(參照圖5A的發送符號u1)進行DFT之後的DFT訊號X₁ (b,k)的例子，其中該符號區塊是在預編碼符號x₁ (b,n)中附加有GI(p)的符號區塊。圖6C與圖5B是同樣的。又，圖6D是對反轉符號x₂ (-m)進行DFT後的反轉DFT訊號X_2r (b,k)之例子。在此，反轉符號x₂ (-m)包含符號順序反轉後的預編碼符號訊號x₂ (b,-n)、以及對GI的複共軛進行了符號順序反轉的GI^* (p)。接著，利用反轉DFT訊號X_2r (b,k)，來說明從符號順序反轉部107所輸出的訊號之頻率特性。FIG. 6C is an example of a DFT signal X ₁ (b, k) after performing a DFT on a symbol block (refer to the transmission symbol u1 of FIG. 5A), where the symbol block is in a precoded symbol x ₁ (b, n) A symbol block to which GI (p) is attached. 6C is the same as FIG. 5B. 6D is an example of an inverted DFT signal X _2r (b, k) after DFT of the inverted symbol x ₂ (-m). Here, the inversion symbol x ₂ (-m) includes a precoded symbol signal x ₂ (b, -n) after the inversion of the symbol order, and GI ^* (p ). Next, the frequency characteristic of the signal output from the symbol order inversion section 107 will be described using the inverted DFT signal X _2r (b, k).

在利用了算式2之預編碼矩陣G的情況下，由於x₂ (b,-n)及GI^* (-p)是將x₁ (b,n)及GI(p)的順序反轉而成之符號區塊的複共軛，因此X_2r (b,k)是以算式5-2來表示。(算式5-2)When the precoding matrix G of Equation 2 is used, the order of x ₂ (b, -n) and GI ^* (-p) is obtained by reversing the order of x ₁ (b, n) and GI (p). Since the complex conjugate of the symbol block is X _2r (b, k), it is represented by Equation 5-2. (Equation 5-2)

反轉DFT訊號X_2r (b,k)，是對DFT訊號X₁ (b,k)的複共軛施予相位旋轉的訊號。又，在算式5-2中，包含於W的N是DFT尺寸(例如，符號區塊的長度「512」)。The inverted DFT signal X _2r (b, k) is a signal that applies phase rotation to the complex conjugate of the DFT signal X ₁ (b, k). In Equation 5-2, N included in W is a DFT size (for example, the length of a symbol block is "512").

在圖6C、圖6D所示的例子中，與圖5B、圖5C的情況不同，並將第1發送RF鏈處理的DFT訊號X₁ (b,k)、以及第2發送RF鏈處理的反轉DFT訊號X_2r (b,k)＝X₁ ^* (b,k)×W，以相同的頻率指數k來發送。從而，可以得到空間分集效果。In the example shown in FIG. 6C and FIG. 6D, unlike the case of FIG. 5B and FIG. 5C, the DFT signal X ₁ (b, k) processed by the first transmission RF chain and the response of the second transmission RF chain processing The DFT signal X _2r (b, k) = X ₁ ^* (b, k) × W is transmitted with the same frequency index k. Thereby, a space diversity effect can be obtained.

圖6B是顯示符號順序反轉部107中的符號順序反轉處理的另一例。FIG. 6B shows another example of the symbol order inversion processing in the symbol order inversion section 107.

如圖6B所示，符號順序反轉部107是針對各符號區塊，使符號區塊整體的符號序列之順序(符號序列的排列)反轉。此時，符號順序反轉部107為了在符號順序的反轉前之符號區塊、及符號順序的反轉後之符號區塊之間，使GI的位置相等，會移除於最後的資料區塊之後段所附加的GI，並在最初的資料區塊之前附加已使符號順序反轉的GI。再者，如已提出的，符號區塊是例如將64個符號的GI與448個符號的資料區塊合在一起而成的512個符號的區塊。As shown in FIG. 6B, the symbol order reversing unit 107 reverses the order of the symbol sequence (the arrangement of the symbol sequences) of the entire symbol block for each symbol block. At this time, in order to equalize the position of GI between the symbol block before the inversion of the symbol order and the symbol block after the inversion of the symbol order, the symbol order inversion unit 107 removes it from the last data area. The GI appended to the subsequent block of blocks is appended with the GI whose symbol order has been reversed before the first data block. Furthermore, as already proposed, the symbol block is, for example, a 512-symbol block obtained by combining a 64-symbol GI and a 448-symbol data block.

符號順序反轉部107亦可在複共軛GI附加部106b所輸出的發送符號u2當中，依序將448個符號份量的資料符號保存至資料符號緩衝器108b，並且以和保存時不同的順序(相反的順序)來從該資料符號緩衝器108b中讀出資料符號，藉此來實現符號順序的反轉。也就是說，資料符號緩衝器108b亦為相當於LIFO(後進先出，Last In, First Out)緩衝器之緩衝器。再者，資料符號緩衝器108b亦可為記憶體、RAM、或暫存器(register)等。The symbol order reversing unit 107 may also sequentially store data symbols of 448 symbol weights in the data symbol buffer 108b among the transmission symbols u2 output by the complex conjugate GI adding unit 106b, and in a different order from that at the time of saving (Reverse order) The data symbols are read from the data symbol buffer 108b, thereby reversing the order of the symbols. That is, the data symbol buffer 108b is also a buffer equivalent to a LIFO (Last In, First Out) buffer. In addition, the data symbol buffer 108b may be a memory, a RAM, a register, or the like.

由於是在符號順序反轉部107中，進行使發送符號u2的符號順序反轉的處理，因此會產生輸出資料相對於輸入資料的延遲。於是，利用資料符號緩衝器108a，可在GI附加部106a所輸出的發送符號u2當中，對資料符號(例如x₂ (b,n))施予與在符號順序反轉部107所產生的延遲相同的時間之延遲。藉此，GI附加部106a所輸出的發送符號u1與複共軛GI附加部106b所輸出的發送符號u2會以相同的定時(timing)來發送。再者，在以下的說明中，有時將符號順序反轉部107已使發送符號u2反轉而成的符號區塊，表示為反轉符號u2r。Since the symbol sequence inversion unit 107 performs a process of inverting the symbol sequence of the transmission symbol u2, a delay occurs in the output data with respect to the input data. Then, using the data symbol buffer 108a, it is possible to apply a delay to the data symbol (for example, x ₂ (b, n)) among the transmission symbols u2 output by the GI adding unit 106a and the symbol order reversing unit 107. The same time delay. Thereby, the transmission symbol u1 output by the GI adding unit 106a and the transmission symbol u2 output by the complex conjugate GI adding unit 106b are transmitted at the same timing. In the following description, a symbol block obtained by inverting the transmission symbol u2 by the symbol order inversion unit 107 may be referred to as an inverted symbol u2r.

相位旋轉部109在符號順序反轉部107所輸出的反轉符號u2r當中，是按每個符號對資料符號(例如x₂ (b,n))施予不同的相位旋轉。亦即，相位旋轉部109是按每個符號來施行不同的相位變更。相位旋轉部109是利用算式6來對資料符號(例如x₂ (b,n))施予相位旋轉，並利用算式7來對GI(例如GI₂ (p))施予相位旋轉。再者，在算式6、算式7中，θ是表示相位旋轉量。(算式6)(算式7)The phase rotation unit 109 applies a different phase rotation to the data symbol (for example, x ₂ (b, n)) among the inversion symbols u2r output from the symbol order inversion unit 107. That is, the phase rotation unit 109 performs a different phase change for each symbol. The phase rotation unit 109 applies a phase rotation to a data symbol (for example, x ₂ (b, n)) using Equation 6 and a phase rotation to a GI (for example, GI ₂ (p)) using Equation 7. In Equations 6 and 7, θ is the amount of phase rotation. (Equation 6) (Equation 7)

發送裝置100在預編碼部105所輸出的發送符號當中，對x1(b,n)並未施予相位旋轉，而是對x2(b,n)施予相位旋轉。相位旋轉後的發送符號是以算式8來表示。(算式8)Among the transmission symbols output by the precoding unit 105, the transmitting device 100 does not apply phase rotation to x1 (b, n), but instead applies phase rotation to x2 (b, n). The transmission symbol after the phase rotation is represented by Equation 8. (Equation 8)

再者，在圖3中，雖然是將相位旋轉部109配置在第2發送RF鏈處理中，但將相位旋轉部配置在第1發送RF鏈處理及第2發送RF鏈處理之兩者中亦可。在此配置的情況下，可以利用算式9所示的相位旋轉之矩陣。(算式9)In FIG. 3, although the phase rotation unit 109 is disposed in the second transmission RF chain process, the phase rotation unit is disposed in both the first transmission RF chain process and the second transmission RF chain process. can. In the case of this configuration, a matrix of phase rotation shown in Equation 9 can be used. (Equation 9)

再者，在算式8中，n為1以上且448以下的情況也可以視為是有關於資料符號的算式(例如算式6)，而n為449以上且512以下的情況也可以視為是有關於GI的算式(例如，將從算式8的n減去448後的值設為p的情況下之算式7)。在此情況下，算式8是成為n為1以上且512以下，且x₁ (b,n)及x₂ (b,-n)會包含資料符號與GI之雙方。Furthermore, in Equation 8, the case where n is 1 or more and 448 or less can also be regarded as an expression related to the data symbol (for example, Equation 6), and the case where n is 449 or more and 512 or less can also be regarded as an existence An expression for GI (for example, Expression 7 when the value obtained by subtracting 448 from n in Expression 8 is set to p). In this case, Expression 8 is such that n is 1 or more and 512 or less, and x ₁ (b, n) and x ₂ (b, -n) include both the data symbol and the GI.

圖6E是顯示按每個符號區塊對相位旋轉後符號t₁ (b,n)進行了DFT之DFT訊號T₁ (b,k)的圖。圖6F是顯示按每個符號區塊對相位旋轉後符號t₂ (b,n)進行了DFT之DFT訊號T₂ (b,k)的圖。接著，利用T₁ (b,k)、T₂ (b,k)來說明相位旋轉後的訊號之頻率特性。FIG. 6E is a diagram showing a DFT signal T ₁ (b, k) where the symbol t ₁ (b, n) is subjected to DFT for each symbol block. FIG. 6F is a diagram showing a DFT signal T ₂ (b, k) obtained by performing DFT on a symbol t ₂ (b, n) after phase rotation for each symbol block. Next, the frequency characteristics of the signal after the phase rotation will be described using T ₁ (b, k) and T ₂ (b, k).

根據算式8，X₁ (b,k)與T₁ (b,k)是相等的。亦即，圖6C與圖6E除了將記號從X₁ 置換為T₁ 這點之外，其餘是相同的。According to Equation 8, X ₁ (b, k) and T ₁ (b, k) are equal. That is, FIG. 6C and FIG. 6E are the same except that the symbol is replaced from X ₁ to T ₁ .

圖6F所示的T₂ (b,k)是在時間區域中對X_2r (b,k)施予了相位旋轉的訊號。利用算式8而在時間區域中施予了相位旋轉的情況下，在頻率區域中，會使頻率指數以算式9-1所算出的頻格(frequency bin)d之份量而位移。N是DFT尺寸(例如，符號區塊的長度「512」)。(算式9-1)T ₂ (b, k) shown in FIG. 6F is a signal in which a phase rotation is applied to X _2r (b, k) in the time region. When phase rotation is applied in the time region using Equation 8, in the frequency region, the frequency index is shifted by the amount of the frequency bin d calculated by Equation 9-1. N is the DFT size (for example, the length of the symbol block is "512"). (Equation 9-1)

從而，X₁ (b,k)是藉由算式9-2，而在T₁ (b,k)、T₂ (b,k+d)中，利用2個發送天線及2個頻率指數k、k+d來發送。也就是說，可得到空間分集效果及頻率分集效果。(算式9-2)Therefore, X ₁ (b, k) is calculated by Equation 9-2, and in T ₁ (b, k) and T ₂ (b, k + d), two transmission antennas and two frequency indices k, k + d to send. That is, a space diversity effect and a frequency diversity effect can be obtained. (Equation 9-2)

發送裝置100是將相位旋轉量θ設定成接近於π弧度(180度)或-π弧度(-180度)之值，藉此可以提高頻率分集效果，並提高資料流通量(data throughput)。The transmitting device 100 sets the phase rotation amount θ to a value close to π radians (180 degrees) or -π radians (-180 degrees), thereby improving the frequency diversity effect and increasing data throughput.

再者，發送裝置100也可以將相位旋轉量θ設定成與π弧度(180度)不同的值。藉此，使發送天線111a的發送訊號、與發送天線111b的發送訊號之間的訊號分離變容易。又，資料流通量也會變高。The transmission device 100 may set the phase rotation amount θ to a value different from π radian (180 degrees). This makes it easier to separate the transmission signal from the transmission antenna 111a and the transmission signal from the transmission antenna 111b. In addition, the data circulation volume will also increase.

對於OFDM中的發送符號施予和π弧度不同的相位旋轉之方法，已在非專利文獻2中作為PH(跳相，Phase Hopping)技術而揭示。但是，本揭示的發送裝置100與非專利文獻2的情況不同，是利用單載波發送，且在第2發送流處理中進行符號順序反轉。藉此，使2個發送訊號之間的訊號分離變容易。又，可得到比較高的頻率分集效果。A method of applying a phase rotation different from π radians to a transmission symbol in OFDM has been disclosed as a PH (Phase Hopping) technique in Non-Patent Document 2. However, unlike the case of Non-Patent Document 2, the transmission device 100 of the present disclosure uses single carrier transmission and performs symbol order reversal in the second transmission stream processing. This makes it easy to separate the signals between the two transmission signals. In addition, a relatively high frequency diversity effect can be obtained.

發送裝置100也可以將相位旋轉量θ設定成例如，-7π/8弧度(d為-224)、-15π/16弧度(d為240)等之值。The transmitting device 100 may set the phase rotation amount θ to values such as -7π / 8 radians (d is -224), -15π / 16 radians (d is 240), or the like.

發送F/E電路110a、110b包含數位及類比濾波器、D/A轉換器、及RF(無線)電路。發送F/E電路110a會將從資料符號緩衝器108a輸出的發送資料v1(包含圖8所示的GI(p)及t1(b,n)之訊號)轉換成無線訊號，並輸出至發送天線111a。發送F/E電路110b會將從相位旋轉部109所輸出的發送資料v2(包含圖8所示的GI^* (-p)及t2(b,-n)之訊號)轉換成無線訊號，並輸出至發送天線111b。The transmission F / E circuits 110a and 110b include digital and analog filters, D / A converters, and RF (wireless) circuits. The transmitting F / E circuit 110a converts the transmission data v1 (including the signals of GI (p) and t1 (b, n) shown in FIG. 8) output from the data symbol buffer 108a into a wireless signal and outputs it to the transmitting antenna 111a. The transmission F / E circuit 110b converts the transmission data v2 (including the signals of GI ^* (-p) and t2 (b, -n) shown in FIG. 8) output from the phase rotation unit 109 into a wireless signal and outputs it. To the transmitting antenna 111b.

發送天線111a會發送從發送F/E電路110a輸出的無線訊號。發送天線111b會發送從發送F/E電路110b輸出的無線訊號。也就是說，發送天線111a及111b會分別發送不同的無線訊號。The transmitting antenna 111a transmits a wireless signal output from the transmitting F / E circuit 110a. The transmitting antenna 111b transmits a wireless signal output from the transmitting F / E circuit 110b. In other words, the transmitting antennas 111a and 111b transmit different wireless signals, respectively.

像這樣，發送裝置100是在對2個發送流資料施行了預編碼之後，對其中一個發送流資料施行符號順序反轉及相位旋轉。藉此，可以提升空間分集效果與頻率分集效果。又，可以降低資料通訊中的錯誤率，並使資料流通量提升。As described above, the transmission device 100 performs precoding on two transmission stream materials, and then performs symbol order inversion and phase rotation on one of the transmission stream materials. Thereby, the space diversity effect and the frequency diversity effect can be improved. In addition, it can reduce the error rate in data communication and increase the data circulation.

圖7是顯示接收裝置200的構成之圖。FIG. 7 is a diagram showing the configuration of the receiving device 200.

接收天線201a、201b是分別接收無線訊號。將於接收天線201a中對接收訊號的處理，稱為第1接收RF鏈處理。第1接收RF鏈處理是藉由接收F/E電路202a、時間區域同步部203a、及DFT部205a而進行。將於接收天線201b對接收訊號的處理，稱為第2接收RF鏈處理。第2接收RF鏈處理是藉由接收F/E電路202b、時間區域同步部203b、及DFT部205b而進行。The receiving antennas 201a and 201b receive wireless signals respectively. The processing of the received signal in the receiving antenna 201a is referred to as the first receiving RF chain processing. The first reception RF chain processing is performed by the reception F / E circuit 202a, the time zone synchronization unit 203a, and the DFT unit 205a. The processing of the received signal by the receiving antenna 201b is called the second receiving RF chain processing. The second reception RF chain process is performed by the reception F / E circuit 202b, the time zone synchronization unit 203b, and the DFT unit 205b.

接收F/E電路202a、202b包含例如RF電路、A/D轉換器、數位濾波器、類比濾波器、及降低取樣處理部，且將無線訊號轉換成數位基頻訊號。The receiving F / E circuits 202a and 202b include, for example, an RF circuit, an A / D converter, a digital filter, an analog filter, and a downsampling processing unit, and converts a wireless signal into a digital baseband signal.

時間區域同步部203a、203b會進行接收封包的定時同步。再者，時間區域同步部203a與時間區域同步部203b也可以相互地交換定時資訊，而取得第1接收RF鏈處理與第2接收RF鏈處理之間的定時同步。The time zone synchronization units 203a and 203b perform timing synchronization of the received packet. Furthermore, the time zone synchronization unit 203a and the time zone synchronization unit 203b may exchange timing information with each other to obtain timing synchronization between the first reception RF chain process and the second reception RF chain process.

通道估測部204是利用第1接收RF鏈處理的接收訊號、及第2接收RF鏈處理的接收訊號，來算出發送裝置與接收裝置之間的無線通道之頻率響應。亦即，按每個頻率指數k來算出圖1的H₁₁ (k)、H₁₂ (k)、H₂₁ (k)、及H₂₂ (k)。The channel estimation unit 204 calculates the frequency response of the wireless channel between the transmitting device and the receiving device by using the receiving signal processed by the first receiving RF chain and the receiving signal processed by the second receiving RF chain. That is, H ₁₁ (k), H ₁₂ (k), H ₂₁ (k), and H ₂₂ (k) in FIG. 1 are calculated for each frequency index k.

DFT部205a、205b是將接收資料分割成DFT區塊，並進行DFT。DFT區塊例如是512個符號。圖8是顯示在DFT部205a、205b中將接收資料分割成DFT區塊的方法之圖。The DFT sections 205a and 205b divide the received data into DFT blocks and perform DFT. The DFT block is, for example, 512 symbols. FIG. 8 is a diagram showing a method of dividing received data into DFT blocks in the DFT sections 205a and 205b.

將第1接收RF鏈處理的接收資料(對DFT部205a的輸入資料)設為y₁ (n)，且將第2接收RF鏈處理的接收資料(對DFT部205b的輸入資料)設為y₂ (n)。接著，利用圖8來說明y₁ (n)之處理。再者，針對y₂ (n)的處理也是同樣。Set the received data processed by the first receiving RF chain (input data to the DFT unit 205a) to y ₁ (n), and set the received data processed by the second receiving RF chain (input data to the DFT unit 205b) to y ₂ (n). Next, the processing of y ₁ (n) will be described using FIG. 8. The same applies to the processing for y ₂ (n).

如前所述，發送裝置100是利用2個發送天線111a、111b，來發送2個無線訊號(圖8所示的發送資料v1、發送資料v2)。又，2個無線訊號會有下述之情況：分別在通道中產生直接波與複數個延遲波，而到達接收天線201a及201b。As described above, the transmitting device 100 transmits two wireless signals using the two transmitting antennas 111a and 111b (transmission data v1 and transmission data v2 shown in FIG. 8). In addition, the two wireless signals may have the following cases: a direct wave and a plurality of delayed waves are generated in the channel, respectively, and reach the receiving antennas 201a and 201b.

再者，接收訊號除了直接波及延遲波之外，也可以分別包含有例如繞射波及散射波。Moreover, the received signal may include, for example, a diffracted wave and a scattered wave, in addition to the direct wave and the delayed wave.

DFT部205a是將第1之DFT區塊的時間決定成包含發送資料v1的資料區塊t₁ (1,n)、及發送資料v2的資料區塊t₂ (1,n)之直接波及延遲波。將第1之DFT區塊的DFT計算結果表示為Y₁ (1,k)。如已提出的，k是表示頻率指數，為例如1以上且512以下的整數。DFT is the DFT portion 205a of the first block contains the time determined as the data block transmission of information v1 t _{1 (1,} n), and the transmission of information data blocks v2 t ₂ (1, n) of the direct wave and delay wave. The DFT calculation result of the first DFT block is expressed as Y ₁ (1, k). As already mentioned, k is a frequency index, and is, for example, an integer of 1 or more and 512 or less.

同樣地，將DFT部205a、205b中的第b之DFT區塊的DFT計算結果，分別表示為Y₁ (b,k)、Y₂ (b,k)(b為1以上的整數)。Similarly, the DFT calculation results of the b-th DFT block in the DFT units 205a and 205b are expressed as Y ₁ (b, k) and Y ₂ (b, k) (b is an integer of 1 or more).

接收裝置200會利用MMSE權重計算部206、MMSE濾波器部207、逆相位旋轉部208、IDFT(逆DFT)部209a、IDFT及符號順序反轉部209b、及逆預編碼部210，來算出已發送的調變符號s₁ (n)、s₂ (n)的估測值。接著，針對算出已發送的調變符號s₁ (n)、s₂ (n)的估測值之方法進行說明。The receiving device 200 uses the MMSE weight calculation unit 206, the MMSE filter unit 207, the inverse phase rotation unit 208, the IDFT (inverse DFT) unit 209a, the IDFT and sign order inversion unit 209b, and the inverse precoding unit 210 to calculate Estimated values of transmitted modulation symbols s ₁ (n), s ₂ (n). Next, a method of calculating the estimated values of the transmitted modulation symbols s ₁ (n) and s ₂ (n) will be described.

接收裝置200的DFT部205a、205b之輸出訊號Y₁ (b,k)、Y₂ (b,k)，是利用通道之值，並如算式10地表示。(算式10)The output signals Y ₁ (b, k) and Y ₂ (b, k) of the DFT sections 205 a and 205 b of the receiving device 200 are expressed by the formula 10 using the channel values. (Equation 10)

在此，T₁ (b,k)是對發送裝置100的符號區塊(算式8的t₁ (b,n))進行了DFT的訊號。T₂ (b,k)是對發送裝置100的符號區塊(算式8的t₂ (b,n))進行了DFT的訊號。Z₁ (b,k)是對第1之RF鏈部中的雜訊進行了DFT的訊號。Z₂ (b,k)是對第2之RF鏈部中的雜訊進行了DFT的訊號。Here, T ₁ (b, k) is a signal obtained by performing DFT on a symbol block (t ₁ (b, n) of Expression 8) of the transmitting device 100. T ₂ (b, k) is a signal obtained by performing DFT on the symbol block (t ₂ (b, n) of Equation 8) of the transmitting device 100. Z ₁ (b, k) is a DFT signal for the noise in the first RF chain part. Z ₂ (b, k) is a DFT signal for noise in the second RF chain part.

以矩陣來表示算式10的情況下，會成為算式11。(算式11)When Expression 10 is represented by a matrix, Expression 11 is obtained. (Equation 11)

在算式11中，通道矩陣H_2x2 (k)是如算式12地制定。(算式12)In Equation 11, the channel matrix H _2x2 (k) is formulated as in Equation 12. (Equation 12)

MMSE權重計算部206會根據算式12-1來算出權重矩陣W_2x2 (k)。(算式12-1)The MMSE weight calculation unit 206 calculates the weight matrix W _2x2 (k) based on the formula 12-1. (Equation 12-1)

在算式12-1中，H^H 是表示矩陣H的複共軛轉置。又，σ² 是雜訊Z₁ (b,k)、Z₂ (b,k)的分散。又，I₂ _×2 是2行2列的單位矩陣。In Equation 12-1, H ^H is a complex conjugate transpose representing the matrix H. Σ ² is the dispersion of noises Z ₁ (b, k) and Z ₂ (b, k). In addition, I ₂ _{× 2} is an identity matrix of two rows and two columns.

MMSE濾波器部207會利用算式12-2來算出T₁ (b,k)、T₂ (b,k)的估測值T^{^} ₁ (b,k)、T^{^} ₂ (b,k)。再者，將對估測值T^{^} ₁ (b,k)的處理稱為第1接收流處理，且將對T^{^} ₂ (b,k)的處理稱為第2接收流處理。(算式12-2)MMSE filter unit 207 will be calculated by using Equation 12-2 _{T 1 (b, k),} T 2 (b, k) of the estimate of the ^{_{T ^ 1 (b, k)}} , T ^ 2 (b, k). In addition, the processing on the estimated value T ^{^} ₁ (b, k) is referred to as a first reception stream processing, and the processing on T ^{^} ₂ (b, k) is referred to as a second reception stream processing. (Equation 12-2)

將算式12-2的計算稱為MMSE方式。MMSE濾波器部207是根據MMSE方式，而從包含於發送資料v1的t₁ (b,n)、包含於發送資料v2的t₂ (b,n)、及與各自的直接波及延遲波相混合而成的接收資料y1及y2(參照圖8)中，得到相位旋轉後的資料符號t₁ (b,n)、t₂ (b,n)的估測值。但是，MMSE濾波器部207會為了活用通道估測值(通道的頻率響應之估測值)H₁₁ (k)、H₁₂ (k)、H₂₁ (k)、及H₂₂ (k)，並容易進行計算，而如算式12-2所示，對頻率區域訊號進行計算。The calculation of Equation 12-2 is called the MMSE method. MMSE MMSE filter unit according to embodiment 207, comprising from t to the transmission of information v1 ₁ (b, n), it is included in the transmission data t ₂ (b, n) v2 of, and directly affect the respective delayed waves are mixed In the received data y1 and y2 (see FIG. 8) thus obtained, estimated values of data symbols t ₁ (b, n) and t ₂ (b, n) after phase rotation are obtained. However, the MMSE filter unit 207 utilizes the channel estimated values (estimated values of the frequency response of the channels) H ₁₁ (k), H ₁₂ (k), H ₂₁ (k), and H ₂₂ (k) in order to make use of It is easy to perform calculations, and as shown in Equation 12-2, the frequency region signals are calculated.

逆相位旋轉部208是進行和圖3的相位旋轉部109相反的處理。相位旋轉部109的處理是相當於在頻率區域中，如圖6F所示，使頻率指數k、-k位移頻格d的份量之處理。在此，d是藉由算式9-1而算出。於是，逆相位旋轉部208會將從MMSE濾波器部207輸出的第2接收流的頻率區域訊號，位移-d的份量。也就是說，逆相位旋轉部208是在頻率區域中進行算式12-3的處理。(算式12-3)The inverse phase rotation unit 208 performs processing opposite to the phase rotation unit 109 in FIG. 3. The process of the phase rotation unit 109 is equivalent to the process of shifting the frequency indices k and −k by the amount of the frequency division d in the frequency region, as shown in FIG. 6F. Here, d is calculated by Expression 9-1. Then, the inverse phase rotation unit 208 shifts the frequency region signal of the second received stream output from the MMSE filter unit 207 by the amount of -d. That is, the inverse phase rotation unit 208 performs the processing of Expression 12-3 in the frequency region. (Equation 12-3)

再者，接收裝置200亦可將IDFT部209a、IDFT及符號順序反轉部209b、及逆相位旋轉部208對調，而在對來自MMSE濾波器部的輸出進行IDFT之後，施予逆相位旋轉。在此情況下，逆相位旋轉部208是在時間區域中進行算式12-4的處理。(算式12-4)In addition, the receiving device 200 may reverse the IDFT section 209a, the IDFT and sign order inversion section 209b, and the inverse phase rotation section 208, and perform inverse phase rotation after performing IDFT on the output from the MMSE filter section. In this case, the inverse phase rotation unit 208 performs the processing of Expression 12-4 in the time region. (Equation 12-4)

亦即，逆相位旋轉部208雖然是對第2接收流資料施予逆相位旋轉，但由於將符號順序以IDFT及符號順序反轉部209b進行反轉，因此會進行和算式9所制定的矩陣P之乘法運算相同的處理。That is, although the inverse phase rotation unit 208 applies the inverse phase rotation to the second received stream data, since the symbol order is reversed by the IDFT and the symbol order inversion unit 209b, the matrix formed by the sum formula 9 is performed. The multiplication of P is the same.

IDFT部209a會對從逆相位旋轉部208輸出的第1接收流資料進行IDFT。又，IDFT及符號順序反轉部209b會對從逆相位旋轉部208輸出的第2接收流資料進行IDFT,且針對各DFT區塊來反轉符號順序。The IDFT unit 209a performs IDFT on the first received stream data output from the reverse phase rotation unit 208. The IDFT and symbol order inversion unit 209b performs IDFT on the second received stream data output from the inverse phase rotation unit 208, and inverts the symbol order for each DFT block.

逆預編碼部210是對第1接收流資料及第2接收流資料乘上圖3的預編碼部105所利用的預編碼矩陣G之逆矩陣，來算出s1(b,n)、s2(b,n)的估測值。在算式12-5中表示逆預編碼部210的處理。(算式12-5)The inverse precoding unit 210 calculates s1 (b, n) and s2 (b) by multiplying the first received stream data and the second received stream data by the inverse matrix of the precoding matrix G used by the precoding unit 105 in FIG. 3. , n). The processing of the inverse precoding unit 210 is shown in Equation 12-5. (Equation 12-5)

資料解調部211a、211b會對從逆預編碼部210輸出的s1(b,n)、s2(b,n)之估測值進行資料解調，來算出位元資料的估測值。The data demodulation sections 211a and 211b perform data demodulation on the estimated values of s1 (b, n) and s2 (b, n) output from the inverse precoding section 210 to calculate the estimated value of the bit data.

解碼部212a、212b會對位元資料的估測值進行由LDPC碼形成的糾錯處理。The decoding units 212a and 212b perform error correction processing using LDPC codes on the estimated values of the bit data.

流整合部213是整合第1接收流資料與第2接收流資料，且作為接收資料而通知給MAC部215。The stream integration unit 213 integrates the first received stream data and the second received stream data, and notifies the MAC unit 215 as the received data.

標頭資料提取部214是從接收資料中提取出標頭資料，來決定例如MCS(調變與編碼方案，Modulation and Coding Scheme)、圖3的相位旋轉部109所利用的相位旋轉量θ。又，標頭資料提取部214亦可控制：適用於逆預編碼部210的預編碼矩陣G、IDFT及符號順序反轉部209b中的符號反轉處理之有無、及逆相位旋轉部208所利用的相位旋轉量θ。The header data extraction unit 214 extracts header data from the received data to determine, for example, MCS (Modulation and Coding Scheme) and the phase rotation amount θ used by the phase rotation unit 109 in FIG. 3. The header data extraction unit 214 can also control the presence or absence of sign inversion processing in the precoding matrix G, IDFT, and sign order inversion unit 209b applied to the inverse precoding unit 210, and the use by the inverse phase rotation unit 208. Phase rotation amount θ.

在接收裝置200中，由於MMSE濾波器部207是利用將第2發送流資料經頻率位移而成的發送訊號T₁ (b,k)、T₂ (b,k)來進行估測，因此可以得到更高的頻率分集效果。又，可降低接收錯誤率，且提升資料流通量。In the receiving device 200, since the MMSE filter unit 207 estimates the transmission signals T ₁ (b, k) and T ₂ (b, k) obtained by frequency-shifting the second transmission stream data, it can be estimated. Get a higher frequency diversity effect. In addition, it can reduce the reception error rate and increase the data circulation.

＜實施形態1之效果＞在實施形態1中，發送裝置100是對第2預編碼符號附加GI的複共軛，且反轉符號順序，而施予相位旋轉(相位變更)，其中該GI的複共軛是附加於第1預編碼符號之GI的複共軛。<Effects of Embodiment 1> In Embodiment 1, the transmission device 100 adds a complex conjugate of GI to the second precoding symbol, reverses the order of the symbols, and applies phase rotation (phase change). The complex conjugate is a complex conjugate added to the GI of the first precoding symbol.

藉此，在MIMO通道中，可以得到較高的頻率分集效果。又，可以降低通訊資料的錯誤率，並使資料流通量提升。Thereby, in the MIMO channel, a higher frequency diversity effect can be obtained. In addition, the error rate of communication data can be reduced, and the data circulation volume can be increased.

(實施形態2) 在實施形態1中，是針對下述的情況來說明：發送裝置100藉由在資料調變部104a、104b中進行π/2-BPSK調變，而進行MIMO發送。在實施形態2中，是針對下述的情況來說明：發送裝置300(參照圖9)在資料調變部104a、104b中，切換複數個資料調變方式(例如π/2-BPSK調變與π/2-QPSK調變)，而進行MIMO發送。(Embodiment 2) In Embodiment 1, a description will be given of a case where the transmission device 100 performs MIMO / 2 transmission by performing π / 2-BPSK modulation in the data modulation sections 104a and 104b. In the second embodiment, a description is given of a case where the transmitting device 300 (refer to FIG. 9) switches a plurality of data modulation methods (for example, π / 2-BPSK modulation and data modulation) in the data modulation sections 104a and 104b. π / 2-QPSK modulation), and MIMO transmission is performed.

圖9是顯示實施形態2之發送裝置300的構成之圖。再者，對於與圖3相同的構成要素會賦與相同的編號，並省略說明。FIG. 9 is a diagram showing a configuration of a transmitting device 300 according to the second embodiment. In addition, the same components as those in FIG. 3 are assigned the same reference numerals, and descriptions thereof are omitted.

資料調變部104c、104d會對編碼部103a、103b所輸出的編碼資料，進行因應於MAC部101的控制之資料調變。The data modulating units 104c and 104d perform data modulation according to the control of the MAC unit 101 on the encoded data output from the encoding units 103a and 103b.

接著，針對預編碼部105a依據π/2-BPSK調變與π/2-QPSK調變來切換預編碼處理的例子進行說明。Next, an example in which the precoding unit 105a switches precoding processing based on the π / 2-BPSK modulation and the π / 2-QPSK modulation will be described.

圖10A是顯示π/2-QPSK調變的星象圖之一例的圖。從資料調變部104c、104d輸出的調變符號s₁ (m)及s₂ (m)是分別成為+1、-1、+j、-j之任一值。再者，π/2-BPSK調變的星象圖是如圖4A所示。FIG. 10A is a diagram showing an example of an astrological chart of π / 2-QPSK modulation. The modulation symbols s ₁ (m) and s ₂ (m) output from the data modulation units 104 c and 104 d are any one of +1, -1, + j, and -j. Moreover, the astrological chart of π / 2-BPSK modulation is shown in FIG. 4A.

預編碼部105a是因應於在資料調變部104c、104d中所使用的資料調變方式，來變更預編碼矩陣，並進行算式13所示的預編碼處理。(算式13)The precoding unit 105a changes the precoding matrix in accordance with the data modulation method used by the data modulation units 104c and 104d, and performs the precoding processing shown in Equation 13. (Equation 13)

在資料調變部104c、104d中使用π/2-BPSK的情況下，預編碼部105a是利用例如算式2、算式2-3、或算式2-5所示的預編碼矩陣G。When π / 2-BPSK is used in the data modulation units 104c and 104d, the precoding unit 105a uses, for example, the precoding matrix G shown in Equation 2, Equation 2-3, or Equation 2-5.

在資料調變部104c、104d中使用π/2-QPSK的情況下，預編碼部105a是利用例如算式14所示的預編碼矩陣G。(算式14)When π / 2-QPSK is used in the data modulation units 104c and 104d, the precoding unit 105a uses a precoding matrix G shown in Equation 14, for example. (Equation 14)

預編碼部105a在利用算式2來對π/2-BSPK符號進行預編碼的情況下，星象圖是成為與π/2-QPSK相同(參照圖4C)。又，預編碼部105a在利用算式14來對π/2-QSPK符號(參照圖10A)進行預編碼的情況下，星象圖是成為與16QAM相同(參照圖10B)。When the precoding unit 105a precodes the π / 2-BSPK symbol by using Equation 2, the astrological chart becomes the same as π / 2-QPSK (see FIG. 4C). In addition, when the precoding unit 105a precodes the π / 2-QSPK symbol (see FIG. 10A) using Equation 14, the astrological chart becomes the same as that of 16QAM (see FIG. 10B).

π/2-BPSK之符號候補點的數量為2，π/2-QPSK之符號候補點的數量為4，而π/2-16QAM之符號候補點的數量為16。亦即，藉由進行預編碼，星象圖中的符號候補點的數量即會增加。The number of symbol candidate points of π / 2-BPSK is 2, the number of symbol candidate points of π / 2-QPSK is 4, and the number of symbol candidate points of π / 2-16QAM is 16. That is, by performing precoding, the number of symbol candidate points in the astrological map increases.

第2發送RF鏈處理會因調變方式及預編碼矩陣G的種類而不同。在資料調變部104c、104d中使用π/2-BPSK，且在預編碼部105a中使用算式2、算式2-3、或算式2-5所示的預編碼矩陣G的情況下，發送裝置300會與圖3的發送裝置100同樣地，利用複共軛GI附加部106b及符號順序反轉部107，來進行第2發送RF鏈處理。The second transmission RF chain processing differs depending on the modulation method and the type of the precoding matrix G. When π / 2-BPSK is used in the data modulation sections 104c and 104d, and the precoding matrix G shown in Formula 2, Formula 2-3, or Formula 2-5 is used in the precoding section 105a, the transmitting device In the same manner as the transmission device 100 of FIG. 3, 300 performs the second transmission RF chain processing using the complex conjugated GI adding unit 106b and the symbol order reversing unit 107.

複共軛GI附加部106b是對預編碼部105a的輸出x₂ (m)附加GI的複共軛。符號順序反轉部107是對附加有GI的複共軛之輸出x₂ (n)，進行符號順序反轉處理。The complex conjugate GI adding unit 106b is a complex conjugate that adds GI to the output x ₂ (m) of the precoding unit 105a. The sign order inversion unit 107 performs sign order inversion processing on the output x ₂ (n) of the complex conjugate to which the GI is added.

在資料調變部104c、104d中使用π/2-QPSK，且在預編碼部105a中使用算式14所示的預編碼矩陣G的情況下，發送裝置300與圖3的發送裝置100不同，是利用GI附加部106c來進行第2發送RF鏈處理。When π / 2-QPSK is used in the data modulation sections 104c and 104d, and the precoding matrix G shown in Equation 14 is used in the precoding section 105a, the transmitting device 300 is different from the transmitting device 100 in FIG. The GI adding unit 106c performs the second transmission RF chain processing.

GI附加部106c會對預編碼部105a的輸出x₂ (m)附加GI，該GI是與第1之RF鏈處理中GI附加部106a所附加的GI相同。The GI adding unit 106c adds a GI to the output x ₂ (m) of the precoding unit 105a, which is the same as the GI added by the GI adding unit 106a in the first RF chain process.

再者，GI附加部106c亦可附加與GI附加部106a所附加的GI(GI1)不同的GI(GI2)。亦可將相互地正交的序列(互相關(cross correlation)為0)用於GI1與GI2。例如，亦可於GI1中使用規定於11ad規格(參照非專利文獻1)的Ga64序列，且亦可於GI2中使用規定於11ad規格的Gb64序列。The GI adding unit 106c may add a GI (GI2) different from the GI (GI1) added by the GI adding unit 106a. Mutually orthogonal sequences (cross correlation is 0) may be used for GI1 and GI2. For example, a GI64 sequence specified in the 11ad specification (see Non-Patent Document 1) may be used in GI1, and a Gb64 sequence specified in the 11ad specification may be used in GI2.

將π/2-BPSK調變、以及算式2、算式2-3、或算式2-5的預編碼矩陣G之組合，稱為第1預編碼方式類型。將π/2-QPSK調變、以及算式14的預編碼矩陣G的組合，稱為第2預編碼方式類型。再者，針對第1預編碼方式類型與第2預編碼方式類型的判別方法，將於後文描述。The combination of the π / 2-BPSK modulation and the precoding matrix G of Formula 2, Formula 2-3, or Formula 2-5 is referred to as a first precoding method type. The combination of π / 2-QPSK modulation and the precoding matrix G of Equation 14 is referred to as a second precoding method type. In addition, the discrimination method for the first precoding method type and the second precoding method type will be described later.

在第1預編碼方式類型的情況下，選擇部112a是選擇資料符號緩衝器108a的輸出，而選擇部112b是選擇符號順序反轉部107的輸出。In the case of the first precoding method type, the selection section 112 a is an output of the selected data symbol buffer 108 a, and the selection section 112 b is an output of the selected symbol order inversion section 107.

在第2預編碼方式類型的情況下，選擇部112a是選擇GI附加部106a的輸出，而選擇部112b是選擇GI附加部106c的輸出。In the case of the second precoding method type, the selection unit 112a is the output of the selection GI addition unit 106a, and the selection unit 112b is the output of the selection GI addition unit 106c.

再者，選擇部112a也可以配置於GI附加部106a的後段。又，選擇部112b也可以配置於預編碼部105a的後段。In addition, the selection unit 112a may be arranged at the rear stage of the GI adding unit 106a. In addition, the selection unit 112b may be arranged at a later stage of the precoding unit 105a.

接著，針對發送裝置300因應於預編碼方式來變更第2發送RF鏈處理的理由進行說明。Next, the reason why the transmission device 300 changes the second transmission RF chain processing in accordance with the precoding method will be described.

在第1預編碼方式類型中，如算式2-2、算式2-4、或算式2-6所示，x₁ (b,n)與x₂ (b,n)為複共軛的關係，且更進一步地為形成常數因子的關係。從而，如圖5B及圖5C所示，在頻率區域中，第2發送RF鏈處理的訊號是將第1發送RF鏈處理的訊號之頻率反轉而成的訊號，且和第1發送RF鏈處理的訊號為複共軛的關係。In the first type of precoding method, as shown in Equation 2-2, Equation 2-4, or Equation 2-6, x ₁ (b, n) and x ₂ (b, n) are in a complex conjugate relationship. Furthermore, it is a relationship that forms a constant factor. Therefore, as shown in FIG. 5B and FIG. 5C, in the frequency region, the signal processed by the second transmission RF chain is a signal obtained by inverting the frequency of the signal processed by the first transmission RF chain, and is the same as the signal transmitted by the first transmission RF chain. The signal processed is a complex conjugate relationship.

另一方面，在第2預編碼方式類型中，x₁ (b,n)與x₂ (b,n)並不具有複共軛的關係。從而，如圖11A及圖11B所示，在頻率區域中，第1發送RF鏈處理的訊號與第2發送RF鏈處理的訊號，是以相同的頻率來發送。例如，X₁ (b,k)與X₂ (b,k)是以相同的頻率來發送，且X₁ (b,-k)與X₂ (b,-k)是以相同的頻率來發送。On the other hand, in the second precoding scheme type, x ₁ (b, n) and x ₂ (b, n) do not have a complex conjugate relationship. Therefore, as shown in FIGS. 11A and 11B, in the frequency region, the signal processed by the first transmission RF chain and the signal processed by the second transmission RF chain are transmitted at the same frequency. For example, X ₁ (b, k) and X ₂ (b, k) are transmitted at the same frequency, and X ₁ (b, -k) and X ₂ (b, -k) are transmitted at the same frequency .

滿足算式15的複數b存在的情況下，即符合第1預編碼方式類型。(算式15)When a complex number b that satisfies the expression 15 exists, it conforms to the first precoding method type. (Equation 15)

從以上的考察，發送裝置300在第1預編碼方式類型中，是在第2發送RF鏈處理中附加複共軛的GI，並反轉符號順序。亦即，選擇部112b是選擇來自符號順序反轉部107的輸出。另一方面，在第2預編碼方式類型中，是在第2之RF鏈處理中附加和第1之RF鏈處理相同的GI，而不進行符號順序的反轉。亦即，選擇部112b是選擇來自GI編碼部106c的輸出。From the above considerations, in the first precoding method type, the transmitting device 300 adds a complex conjugated GI to the second transmission RF chain processing, and reverses the symbol order. That is, the selection section 112b selects the output from the sign order inversion section 107. On the other hand, in the type of the second precoding method, the same GI as that of the first RF chain is added to the second RF chain processing, without reversing the order of symbols. That is, the selection unit 112b selects the output from the GI encoding unit 106c.

藉此，不論資料調變方式及預編碼矩陣的種類如何，發送裝置300都可以如圖6E、圖6F所示，實現因應於相位旋轉部109所施予的相位旋轉θ(以及由θ利用算式9-1換算而得的d)之頻率分集效果。With this, regardless of the data modulation method and the type of the precoding matrix, as shown in FIG. 6E and FIG. 6F, the transmitting device 300 can realize the phase rotation θ (as well as the θ utilization formula given by the phase rotation unit 109) as shown in FIG. 6E and FIG. 6F. The frequency diversity effect of d) obtained by 9-1 conversion.

在π/2-BPSK中，藉由利用算式2的預編碼矩陣，預編碼後的星象圖會成為和QPSK為同等(參照圖4B)。此情況即符合第1預編碼方式類型。又，在π/2-QPSK中，藉由利用算式14的預編碼矩陣，預編碼後的星象圖會成為和16QAM為同等(參照圖10B)。此情況即符合第2預編碼方式類型。In π / 2-BPSK, by using the precoding matrix of Equation 2, the pre-encoded astrological map becomes equal to QPSK (see FIG. 4B). This case corresponds to the first precoding method type. Furthermore, in π / 2-QPSK, by using the precoding matrix of Equation 14, the precoded astrological map becomes equivalent to 16QAM (see FIG. 10B). This case corresponds to the second precoding type.

再者，選擇部112a、112b亦可在π/2-BPSK調變中，因應於預編碼方式的類型來選擇輸入資料。In addition, the selection units 112a and 112b may select input data according to the type of the precoding method during the π / 2-BPSK modulation.

又，發送裝置300亦可利用與不進行預編碼的發送時之π/2-QPSK及π/2-16QAM為相同的發送參數來發送。發送參數包含例如發送F/E電路110a、110b的RF放大器的後退操作點(Backoff)之設定值。也就是說，發送裝置300亦可因應於調變方式，而利用算式2或算式14之任一個來進行預編碼。藉此，即可以在不變更發送F/E電路110a、110b的構成之情形下進行發送。以下，說明其理由。In addition, the transmitting device 300 may transmit using the same transmission parameters as π / 2-QPSK and π / 2-16QAM when transmitting without precoding. The transmission parameters include, for example, a set value of a backoff operation point (Backoff) of the RF amplifier transmitting the F / E circuits 110a and 110b. In other words, the transmitting device 300 may perform precoding using either of Equation 2 or Equation 14 in accordance with the modulation method. This makes it possible to perform transmission without changing the configuration of the transmission F / E circuits 110a and 110b. The reason will be described below.

在一般的毫米波通訊中，發送F/E電路中的RF放大器的後退操作點之設定值，可因應於發送星象圖配置(圖10A、圖10B等)而適當地設定及變更。例如，在如圖10B的16QAM中，由於相對於平均電力的峰值電力(PAPR)會變大，因此會將RF放大器的後退操作點(Backoff)設得較大，而設定成在RF放大器中不使訊號飽和。又，由於藉由施行預編碼處理而改變發送訊號的星象圖之配置，因此發送F/E電路的設定會被變更。In general millimeter-wave communication, the setting value of the back-off operating point of the RF amplifier in the transmitting F / E circuit can be appropriately set and changed according to the sending astrological map configuration (FIGS. 10A, 10B, etc.). For example, in 16QAM as shown in FIG. 10B, since the peak power (PAPR) relative to the average power becomes larger, the backoff operation point (Backoff) of the RF amplifier is set to be large, and the Saturate the signal. In addition, since the configuration of the astrological map of the transmission signal is changed by performing precoding processing, the setting of the transmission F / E circuit is changed.

相對於此，在本實施形態的發送裝置300中，是藉由利用例如算式2及算式14，來施行預編碼處理，藉此成為與預編碼處理之前的星象圖配置不同，但與習知的調變相同的星象圖配置。也就是說，由於無論預編碼處理的有無，發送訊號都成為習知的星象圖配置，因此變得不需要發送F/E電路的構成及設定之變更，且控制變容易。On the other hand, in the transmitting device 300 of this embodiment, the precoding processing is performed by using, for example, Equation 2 and Equation 14, thereby making it different from the astrological map arrangement before the precoding processing, but it is different from the conventional one. Modulate the same astrological configuration. That is, since the transmission signal becomes a conventional astrological map arrangement regardless of the presence or absence of precoding processing, it is not necessary to change the configuration and setting of the transmission F / E circuit, and control becomes easy.

＜實施形態2之效果＞在實施形態2中，發送裝置300是在第1預編碼符號與第2預編碼符號為複共軛的關係之情況下，對第2預編碼符號附加GI的複共軛，且反轉符號順序，並施予相位旋轉(相位變更)，其中該GI的複共軛是附加於第1預編碼符號的GI的複共軛。<Effects of Embodiment 2> In Embodiment 2, the transmission device 300 adds a GI to the second precoding symbol when the first precoding symbol and the second precoding symbol are in a complex conjugate relationship. Yoke, and reverse the order of the symbols and apply phase rotation (phase change), where the complex conjugate of the GI is a complex conjugate of the GI added to the first precoding symbol.

藉此，可以在MIMO通道中，切換複數個資料調變方式，且可以得到較高的頻率分集效果。又，可以降低通訊資料的錯誤率，並使資料流通量提升。Thereby, in the MIMO channel, a plurality of data modulation modes can be switched, and a higher frequency diversity effect can be obtained. In addition, the error rate of communication data can be reduced, and the data circulation volume can be increased.

(實施形態2的變形例) 在實施形態2中所說明的是，發送裝置300在π/2-BPSK調變的情況下，在符號順序反轉部107中對資料符號及GI的符號進行符號順序反轉之MIMO發送。在實施形態2的變形例中要說明的是，發送裝置400(參照圖12)在GI附加部106d、106e中，按每個流而附加有不同的序列(例如正交的序列)的MIMO發送。(Modification of Embodiment 2) In Embodiment 2, it is explained that when the transmitting device 300 modulates π / 2-BPSK, the symbol sequence inversion unit 107 signs the data symbol and the GI symbol. Order reversed MIMO transmission. In a modification of the second embodiment, the transmission device 400 (see FIG. 12) adds MIMO transmission to the GI adding units 106d and 106e with different sequences (for example, orthogonal sequences) for each stream. .

圖12是顯示實施形態2的變形例之發送裝置400的構成之圖。再者，對於與圖9相同的構成要素會賦與相同的編號，並省略說明。FIG. 12 is a diagram showing a configuration of a transmission device 400 according to a modification of the second embodiment. In addition, the same components as those in FIG. 9 are assigned the same reference numerals, and descriptions thereof are omitted.

GI附加部106d、106e是配置在比選擇部112a、112b及相位旋轉部109更後段。與圖9的發送裝置300不同，無論調變方式如何，發送裝置400都附加按每個流來制定的GI符號亦可。The GI adding sections 106d and 106e are arranged at a later stage than the selecting sections 112a and 112b and the phase rotation section 109. Unlike the transmitting device 300 of FIG. 9, the transmitting device 400 may add a GI symbol specified for each stream regardless of the modulation method.

圖13及圖14是顯示發送裝置400的GI附加部106d、106e的輸出(v3、v4)之發送符號格式的一例之圖。圖13是顯示資料符號的調變為π/2-BPSK調變的情況，而圖14是顯示資料符號的調變為π/2-BPSK調變以外的情況。13 and 14 are diagrams showing an example of a transmission symbol format of the outputs (v3, v4) of the GI adding units 106d and 106e of the transmission device 400. FIG. 13 shows a case where the modulation of the data symbol is changed to π / 2-BPSK modulation, and FIG. 14 shows a case where the modulation of the data symbol is changed to other than π / 2-BPSK modulation.

GI附加部106d是將預編碼符號x₁ (m)分割成每個448個符號的資料區塊，且在各資料區塊的前段附加64個符號的GI(GI₁ (p))。GI是對習知的序列進行了π/2-BPSK調變的符號序列。進而，GI附加部106d是在最後的資料區塊之後段附加64個符號的GI。藉此，可生成如圖13及圖14所示的發送符號v3。再者，這些符號數僅是一例，本實施形態也可以是這些以外的符號數。The GI addition unit 106d divides the precoded symbol x ₁ (m) into data blocks of 448 symbols each, and adds a GI (GI ₁ (p)) of 64 symbols to the top of each data block. GI is a symbol sequence that is π / 2-BPSK modulated on a conventional sequence. Furthermore, the GI adding unit 106d is a GI that adds 64 symbols after the last data block. Thereby, the transmission symbol v3 shown in FIG. 13 and FIG. 14 can be generated. The number of symbols is only an example, and the number of symbols other than these may be used in the present embodiment.

同樣地，GI附加部106e也是將預編碼符號x₂ (m)分割成每個448個符號的資料區塊，且在各資料區塊的前段附加64個符號的GI(GI₂ (p))，並在最後的資料區塊之後段附加64個符號的GI。藉此，可生成如圖13及圖14所示的發送符號v4。GI附加部106e所附加的GI，亦可與GI附加部106d所附加的GI為不同的序列。Similarly, the GI appender 106e divides the precoded symbol x ₂ (m) into data blocks of 448 symbols each, and adds a 64-sign GI (GI ₂ (p)) to the front of each data block. , And a 64-symbol GI is appended to the last data block. Thereby, the transmission symbol v4 shown in FIG. 13 and FIG. 14 can be generated. The GI added by the GI adding unit 106e may be a different sequence from the GI added by the GI adding unit 106d.

接收裝置200亦可在接收了具有圖13及圖14的格式之發送裝置400的發送訊號的情況下，如實施形態1所示，利用算式12-2來進行MMSE等化，並進行接收處理。When the receiving device 200 has received a transmission signal from the transmitting device 400 having the format of FIG. 13 and FIG. 14, as shown in the first embodiment, the MMSE and the like are calculated using Equation 12-2, and reception processing is performed.

接收裝置200亦可比較已進行MMSE等化的GI符號(MMSE濾波器部207的輸出當中與GI相關的部分)、以及習知的GI符號，來檢測通道估測矩陣的誤差，並進行通道估測矩陣的補正。可在GI₁ (p)與GI₂ (p)為正交序列的情況下，算出藉由MMSE等化而估測的GI₁ (p)、及習知的GI₁ (p)之相關性。在此算出中，可減輕MMSE等化的殘餘誤差，並且可高精度地算出例如相位偏移之值。因此，可以高精度地補正通道估測矩陣，並改善接收性能。The receiving device 200 may also compare the GI symbols that have been MMSE equalized (the GI-related part of the output of the MMSE filter section 207) and the conventional GI symbols to detect the error of the channel estimation matrix and perform channel estimation. Correction of measurement matrix. When GI ₁ (p) and GI ₂ (p) are orthogonal sequences, the correlation between GI ₁ (p) estimated by MMSE equalization and the conventional GI ₁ (p) can be calculated. In this calculation, it is possible to reduce the residual error of MMSE equalization and to calculate, for example, the value of the phase shift with high accuracy. Therefore, it is possible to correct the channel estimation matrix with high accuracy and improve the reception performance.

接著，針對接收裝置200的MMSE濾波器部207接收具有圖13及圖14的格式之發送裝置400的發送訊號之其他方法進行說明。Next, another method in which the MMSE filter unit 207 of the receiving device 200 receives a transmission signal from the transmitting device 400 having the format of FIGS. 13 and 14 will be described.

接收裝置200會藉由算式16來生成GI₁ (p)及GI₂ (p)的副本訊號(replica signal)。在此，所謂副本訊號是指，在發送了習知型樣(pattern)(例如GI₁ (p)及GI₂ (p))的情況下，以接收天線接收的訊號之估測值，且是藉由在習知型樣上乘上通道矩陣(參照算式12)而算出。(算式16)The receiving device 200 generates a replica signal of GI ₁ (p) and GI ₂ (p) by using Equation 16. Here, the so-called copy signal refers to an estimated value of a signal received by a receiving antenna when a conventional pattern (such as GI ₁ (p) and GI ₂ (p)) is transmitted, and is It is calculated by multiplying the conventional pattern by the channel matrix (see Equation 12). (Equation 16)

在算式16中，X_G1 (k)及X_G2 (k)是對GI時間區域訊號(符號)GI₁ (p)及GI₂ (p)進行了DFT的訊號(GI的頻率區域訊號)。又，Y_G1 (k)及Y_G2 (k)是接收裝置200接收了GI₁ (p)及GI₂ (p)時的頻率區域訊號。藉由對Y_G1 (k)及Y_G2 (k)賦與記號「^」，以顯示其為估測值。In Equation 16, X _G1 (k) and X _G2 (k) are DFT signals (GI frequency region signals) obtained by GI time region signals (symbols) GI ₁ (p) and GI ₂ (p). Y _G1 (k) and Y _G2 (k) are frequency region signals when the receiving device 200 receives GI ₁ (p) and GI ₂ (p). By assigning the symbol "^" to Y _G1 (k) and Y _G2 (k), they are displayed as estimated values.

接收裝置200是藉由算式17，而從接收訊號Y₁ (b,k)減去Y^_G1 (k)來估測包含於接收訊號的資料訊號成分Y^_D1 (k)，且從Y₂ (b,k)減去Y^_G2 (k)來估測資料訊號成分Y^_D2 (k)。(算式17)The receiving device 200 estimates the data signal component Y ^ _D1 (k) included in the received signal by subtracting Y ^ _G1 (k) from the received signal Y ₁ (b, k) by using Equation 17, and from Y ₂ (b, k) subtract Y ^ _G2 (k) to estimate the data signal component Y ^ _D2 (k). (Equation 17)

接收裝置200會將已估測的資料訊號成分Y^_D1 (k)及Y^_D2 (k)設為輸入並進行MMSE等化，藉此算出發送資料符號的估測值T^_D1 (k)及T^_D2 (k)。(算式18)The receiving device 200 sets the estimated data signal components Y ^ _D1 (k) and Y ^ _D2 (k) as inputs and performs MMSE equalization, thereby calculating the estimated value T ^ _D1 (k) of the transmitted data symbol. And T ^ _D2 (k). (Equation 18)

雖然在算式18中進行的計算處理與算式12-2是同樣的，但是下述之點不同：相對於算式12-2的輸入Y₁ (b,k)及Y₂ (b,k)包含資料及GI的訊號成分之情形，算式18的輸入Y^_D1 (k)及Y^_D2 (k)是包含有減去了GI的訊號成分之資料的訊號成分。Although the calculation processing performed in Equation 18 is the same as that in Equation 12-2, the following points are different: The inputs Y ₁ (b, k) and Y ₂ (b, k) contain the data for Equation 12-2 In the case of the signal component of GI, the inputs Y ^ _D1 (k) and Y ^ _D2 (k) in Equation 18 are signal components including data minus the signal component of GI.

由於MMSE濾波器部207在接收發送裝置400的發送訊號之情況下，每個流的GI並不是複共軛及時間順序反轉的關係，因此在GI的符號之解調中，要得到與實施形態1同樣的頻率分集效果是困難的。據此，會有下述情況：從GI的符號到資料符號的符號間干涉於MMSE等化後殘留，而使接收性能降低。When the MMSE filter unit 207 receives a transmission signal from the transmitting device 400, the GI of each stream is not a relationship of complex conjugation and time sequence inversion. Therefore, it is necessary to obtain and implement the GI symbol demodulation. It is difficult to achieve the same frequency diversity effect in the first form. According to this, there may be a case where inter-symbol interference from a GI symbol to a data symbol remains after MMSE equalization, and the reception performance is degraded.

在此，MMSE濾波器部207是在接收發送裝置400的發送訊號之情況下，利用算式16、算式17、及算式18而從接收訊號中減去GI的符號副本(symbol replica)，並進行MMSE等化。也就是說，減輕GI的影響來進行資料符號的MMSE等化。Here, when the MMSE filter unit 207 receives a transmission signal from the transmission device 400, it uses Equation 16, 17, and 18 to subtract the symbol replica of the GI from the received signal, and performs MMSE Equalization. That is, the MMSE of data symbols is reduced by reducing the influence of GI.

接收裝置200是對於MMSE濾波器部207利用算式18所生成的發送資料符號之估測值T^_D1 (k)及T^_D2 (k)，進行包含逆相位旋轉及逆預編碼之與實施形態1及實施形態2同樣的接收處理。The receiving device 200 performs an implementation including inverse phase rotation and inverse precoding on the estimated values T ^ _D1 (k) and T ^ _D2 (k) of the transmitted data symbols generated by the MMSE filter unit 207 using Equation 18. The receiving process is the same as in Embodiment 1 and Embodiment 2.

＜實施形態2的變形例之效果＞在實施形態2的變形例中，發送裝置400是在第1預編碼符號與第2預編碼符號為複共軛的關係之情況下，對第2預編碼符號來反轉符號順序，並施予相位旋轉(相位變更)。又，在第1預編碼符號與第2預編碼符號***不同的GI。<Effect of Modification of Embodiment 2> In a modification of Embodiment 2, the transmission device 400 performs the second precoding when the first precoding symbol and the second precoding symbol are in a complex conjugate relationship. Signs are used to reverse the order of the signs, and phase rotation (phase change) is applied. In addition, different GIs are inserted between the first precoding symbol and the second precoding symbol.

＜實施形態的總結＞本揭示之第1態様的發送裝置，具備：預編碼部，對第1基頻訊號與第2基頻訊號施行預編碼處理，以生成第1預編碼訊號與第2預編碼訊號；順序反轉部，使構成前述第2預編碼訊號的符號序列之順序反轉，而生成第2反轉訊號；相位變更部，生成第2相位變更訊號，且該第2相位變更訊號是對前述第2反轉訊號施行了相位變更之訊號；及發送部，分別從不同的天線發送前述第1預編碼訊號與前述第2相位變更訊號。<Summary of Embodiment> The transmitting device of the first aspect of the present disclosure includes a precoding unit that performs precoding processing on the first baseband signal and the second baseband signal to generate a first precoding signal and a second precoding signal. A coding signal; an order reversing unit that reverses the order of the symbol sequence constituting the second precoding signal to generate a second reversing signal; a phase changing unit that generates a second phase changing signal and the second phase changing signal It is a signal in which a phase change is performed on the second inversion signal; and a transmitting unit transmits the first precoding signal and the second phase change signal from different antennas, respectively.

本揭示之第2態様的發送裝置，是在第1態様的發送裝置中，具備：第1附加部，在前述第1預編碼訊號中附加第1習知訊號；及第2附加部，在前述第2預編碼訊號中附加與前述第1習知訊號為複共軛的關係的第2習知訊號。The transmission device of the second aspect of the present disclosure is the transmission device of the first aspect, and includes: a first adding unit that adds a first known signal to the first precoding signal; and a second adding unit that is described above The second precoding signal is added with a second conventional signal having a relationship of complex conjugation with the first conventional signal.

本揭示之第3態様的發送裝置，是在第2態様的發送裝置中，前述順序反轉部是使構成前述第2習知訊號的符號序列之順序反轉，且在已反轉的第2習知訊號上連結已反轉的第2預編碼訊號，來生成前述第2反轉訊號。The transmitting device of the third state of the present disclosure is the transmitting device of the second state of the present invention. The order reversing unit reverses the order of the sequence of symbols constituting the second known signal, and reverts the second inverted signal sequence. The conventional signal is connected with the inverted second precoding signal to generate the aforementioned second inverted signal.

本揭示之第4態様的發送裝置，是在第2態様的發送裝置中，前述順序反轉部是讓已使前述第2習知訊號連結於前述第2預編碼訊號的符號序列的順序反轉，而生成前述第2反轉訊號。The transmitting device of the fourth state of the present disclosure is the transmitting device of the second state of the present invention. The order reversing unit reverses the order of the symbol sequence in which the second conventional signal is connected to the second precoding signal. To generate the aforementioned second inversion signal.

本揭示之第5態様的發送裝置，是在第2至第4態様的任一態様之發送裝置中，具備：第3附加部，在前述第2預編碼訊號中附加第3習知訊號；及選擇部，根據前述第1基頻訊號與前述第2基頻訊號是否為複共軛的關係，來選擇是否使前述第2反轉訊號、及已附加有前述第3習知訊號的前述第2預編碼訊號的任一個輸入至前述相位變更部。The transmission device of the fifth aspect of the present disclosure is a transmission device of any of the second to fourth aspects, and includes: a third appending unit that adds a third known signal to the second precoding signal; and The selection unit selects whether to make the second inversion signal and the second signal to which the third conventional signal is added according to whether the first fundamental signal and the second fundamental signal are complex conjugate. Any one of the precoding signals is input to the phase changing section.

本揭示之第6態様的發送方法，是對第1基頻訊號與第2基頻訊號施行預編碼處理，以生成第1預編碼訊號與第2預編碼訊號，且使構成前述第2預編碼訊號的符號序列之順序反轉，而生成第2反轉訊號，並生成對前述第2反轉訊號施行了相位變更的第2相位變更訊號，且分別從不同的天線發送前述第1預編碼訊號與前述第2相位變更訊號。The transmission method of the sixth state of the present disclosure is to perform precoding processing on the first baseband signal and the second baseband signal to generate a first precoding signal and a second precoding signal, and make up the aforementioned second precoding. The sequence of the symbol sequence of the signals is reversed to generate a second inverted signal, and a second phase change signal that has undergone a phase change to the aforementioned second inverted signal is generated, and the aforementioned first precoded signals are transmitted from different antennas, respectively. And the second phase change signal.

本揭示之第7態様的接收裝置，具備：接收部，分別以不同的天線來接收第1接收訊號及第2接收訊號；及解調部，從前述第1接收訊號及前述第2接收訊號中生成第1基頻訊號及第2基頻訊號，在前述第1接收訊號及前述第2接收訊號中，包含有第1預編碼訊號及第2相位變更訊號，前述第1預編碼訊號，是發送裝置對前述第1基頻訊號及前述第2基頻訊號施行預編碼處理而生成的訊號，前述第2相位變更訊號是下述之訊號：前述發送裝置對前述第1基頻訊號與前述第2基頻訊號施行預編碼處理而生成第2預編碼訊號，且使構成該生成的第2預編碼訊號的符號序列之順序反轉而生成第2反轉訊號，並對該生成的第2反轉訊號施行相位變更而生成的訊號。The receiving device of the seventh aspect of the present disclosure includes a receiving section that receives the first receiving signal and the second receiving signal with different antennas, respectively; and a demodulating section that receives from the first receiving signal and the second receiving signal. Generate a first baseband signal and a second baseband signal. The first reception signal and the second reception signal include a first precoding signal and a second phase change signal. The first precoding signal is transmitted. The signal generated by the device by performing precoding processing on the first baseband signal and the second baseband signal. The second phase change signal is the following signal: the sending device decodes the first baseband signal and the second baseband signal. The baseband signal is subjected to a precoding process to generate a second precoded signal, and the order of the symbol sequences constituting the generated second precoded signal is reversed to generate a second inverted signal, and the generated second inverted The signal is generated by changing the phase of the signal.

本揭示之第8態様的接收方法，是分別以不同的天線來接收第1接收訊號及第2接收訊號，且從前述第1接收訊號及前述第2接收訊號中生成第1基頻訊號及第2基頻訊號，在前述第1接收訊號及前述第2接收訊號中，包含有第1預編碼訊號及第2相位變更訊號，前述第1預編碼訊號，是發送裝置對前述第1基頻訊號及前述第2基頻訊號施行預編碼處理而生成的訊號，前述第2相位變更訊號是下述之訊號：前述發送裝置對前述第1基頻訊號與前述第2基頻訊號施行預編碼處理而生成第2預編碼訊號，且使構成該生成的第2預編碼訊號的符號序列之順序反轉而生成第2反轉訊號，並對該生成的第2反轉訊號施行相位變更而生成的訊號。The receiving method of the eighth state of the present disclosure is to receive the first receiving signal and the second receiving signal with different antennas, respectively, and to generate the first baseband signal and the first receiving signal from the first receiving signal and the second receiving signal. The 2 baseband signal includes the first precoding signal and the second phase changing signal in the first receiving signal and the second receiving signal. The first precoding signal is the first baseband signal sent by the transmitting device to the first baseband signal. And a signal generated by performing precoding processing on the second baseband signal, the second phase change signal is a signal in which the transmitting device performs precoding processing on the first baseband signal and the second baseband signal, and A signal generated by generating a second precoding signal, reversing the order of the symbol sequences constituting the generated second precoding signal, generating a second inverted signal, and performing a phase change on the generated second inverted signal. .

以上，雖然參照著圖式對各種實施形態作了說明，但是本揭示當然並不限定於所述例子。顯然地，只要是本發明所屬技術領域中具有通常知識者，應可以在專利申請範圍中所記載的範疇内想到各種變更例或修正例，且理應了解的是，關於該等亦當屬於本揭示的技術性範圍。又，在不脫離本揭示之要旨的範圍內，亦可將上述實施形態中的各構成要素任意組合。Although various embodiments have been described above with reference to the drawings, it is needless to say that the present disclosure is not limited to the examples. Obviously, as long as those who have ordinary knowledge in the technical field to which the present invention belongs, they should be able to think of various alterations or amendments within the scope described in the scope of patent applications, and it should be understood that these should also belong to this disclosure Technical scope. In addition, the respective constituent elements in the above embodiments may be arbitrarily combined without departing from the gist of the present disclosure.

在上述各實施形態中，雖然本揭示是舉利用硬體而構成的例子來作説明，但本揭示亦可在與硬體的協同合作下以軟體來實現。In each of the above-mentioned embodiments, although the present disclosure is described by taking an example configured using hardware, the present disclosure may also be implemented in software in cooperation with hardware.

又，於上述各實施形態的説明中所用到的各個功能方塊，典型上是作為具有輸入端子及輸出端子的積體電路之LSI而實現。這些可以個別地集成為1個晶片，亦可以藉包含一部分或全部的方式來集成1個晶片。在此，雖然是做成LSI，但按照集成度的差異，也會有稱為IC、System LSI(系統LSI)、Super LSI(特大型LSI)與Ultra LSI(超大型LSI)之情形。In addition, each functional block used in the description of each of the embodiments described above is typically implemented as an LSI having an integrated circuit including an input terminal and an output terminal. These can be integrated into one chip individually, or one chip can be integrated by including a part or all of them. Here, although it is made as an LSI, it may be called IC, System LSI, Super LSI, and Ultra LSI depending on the degree of integration.

又，積體電路化的手法並不限於LSI，亦可利用專用電路或通用處理器來實現。亦可在LSI製造後，利用可程式設計的FPGA(現場可程式閘陣列，Field Programmable Gate Array)、可再構成LSI內部之電路電池的連接或設定之可重組態處理器(Reconfigurable Processor)。In addition, the technique of integrated circuit is not limited to LSI, and it can be realized by a dedicated circuit or a general-purpose processor. After the LSI is manufactured, a programmable FPGA (Field Programmable Gate Array) can be used, and a reconfigurable processor (Reconfigurable Processor) can be used to reconnect or set the circuit battery inside the LSI.

此外，若是因為半導体技術之進歩或藉由其衍生之其他技術而有可替換LSI之積體電路化的技術出現，當然亦可使用該技術來進行功能方塊的集成化。本發明可具有生物技術之應用等的可能性。産業上之可利用性In addition, if integrated circuit technology that replaces LSI appears due to advances in semiconductor technology or other technologies derived from it, of course, this technology can also be used to integrate functional blocks. The invention may have the possibility of application of biotechnology and the like. Industrial availability

本揭示可以廣泛地應用於從複數個天線發送調變訊號的通訊系統中。The present disclosure can be widely applied to a communication system that transmits modulation signals from a plurality of antennas.

100、300、400‧‧‧發送裝置100, 300, 400‧‧‧ sending devices

101、215‧‧‧MAC部101, 215‧‧‧MAC Department

102‧‧‧流生成部102‧‧‧Stream generation department

103a、103b‧‧‧編碼部103a, 103b‧‧‧Coding Department

104a、104b、104c、104d‧‧‧資料調變部104a, 104b, 104c, 104d‧‧‧ Data Modulation Department

105、105a‧‧‧預編碼部105, 105a‧‧‧ precoding department

106a、106c、106d、106e‧‧‧GI附加部106a, 106c, 106d, 106e‧‧‧GI additional department

106b‧‧‧複共軛GI附加部106b‧‧‧ Complex Conjugate GI Additional Section

107‧‧‧符號順序反轉部107‧‧‧Symbol order reversal section

108a、108b‧‧‧資料符號緩衝器108a, 108b‧‧‧ Data Symbol Buffer

109‧‧‧相位旋轉部109‧‧‧phase rotation section

110a、110b‧‧‧發送F/E電路110a, 110b‧‧‧ Send F / E circuit

111a、111b‧‧‧發送天線111a, 111b‧‧‧ transmitting antenna

112a、112b‧‧‧選擇部112a, 112b‧‧‧Selection Department

200‧‧‧接收裝置200‧‧‧ receiving device

201a、201b‧‧‧接收天線201a, 201b‧‧‧Receiving antenna

202a、202b‧‧‧接收F/E電路202a, 202b‧‧‧Receive F / E circuit

203a、203b‧‧‧時間區域同步部203a, 203b‧‧‧‧Time zone synchronization department

204‧‧‧通道估測部204‧‧‧Channel estimation department

205a、205b‧‧‧DFT部205a, 205b ‧‧‧ DFT

206‧‧‧MMSE權重計算部206‧‧‧MMSE weight calculation department

207‧‧‧MMSE濾波部207‧‧‧MMSE Filtering Department

208‧‧‧逆相位旋轉部208‧‧‧Reverse phase rotation section

209a‧‧‧IDFT部209a‧‧‧IDFT

209b‧‧‧IDFT及符號順序反轉部209b‧‧‧IDFT and Symbol Order Reversal Department

210‧‧‧逆預編碼部210‧‧‧ Inverse Precoding Department

211a、211b‧‧‧資料解調部211a, 211b‧‧‧ Data Demodulation Department

212a、212b‧‧‧解碼部212a, 212b‧‧‧Decoding Department

213‧‧‧流整合部213‧‧‧Stream Integration Department

214‧‧‧標頭資料提取部214‧‧‧Header Data Extraction Department

H11(k)、H12(k)、H21(k)、H22(k)‧‧‧通道H11 (k), H12 (k), H21 (k), H22 (k) ‧‧‧ channels

圖1是顯示實施形態1之MIMO通訊系統的構成之一例的圖。圖2是顯示頻率響應之振幅成分的例子之圖。圖3是顯示實施形態1之發送裝置的構成之一例的圖。圖4A是顯示符號指數(symbol index)為奇數的π/2-BPSK(二元相移鍵控，Binary Phase Shift Keying)之星象圖(constellation)的例子之圖。圖4B是顯示符號指數(symbol index)為偶數的π/2-BPSK之星象圖的例子之圖。圖4C是顯示預編碼部的輸出資料之星象圖的例子之圖。圖5A是顯示GI附加方法的一例之圖。圖5B是顯示對預編碼的符號中附加有GI的符號區塊進行了DFT之DFT訊號的例子之圖。圖5C是顯示對預編碼的符號中附加有GI^＊的符號區塊進行了DFT時的DFT訊號的例子之圖。圖6A是顯示符號順序反轉部中的符號順序反轉處理的一例之圖。圖6B是顯示符號順序反轉部中的符號順序反轉處理的另一例之圖。圖6C是顯示對預編碼的符號中附加有GI的符號區塊進行了DFT時的DFT訊號的例子之圖。圖6D是顯示對反轉符號進行了DFT時的反轉DFT訊號的例子之圖。圖6E是顯示按每個符號區塊對相位旋轉後符號進行了DFT的DFT訊號之圖。圖6F是顯示按每個符號區塊對相位旋轉後符號進行了DFT的DFT訊號之圖。圖7是顯示接收裝置的構成之一例的圖。圖8是顯示在DFT部中將接收資料分割成DFT區塊的方法之圖。圖9是顯示實施形態2之發送裝置的構成之圖。圖10A是顯示π/2-QPSK調變的星象圖之一例的圖。圖10B是顯示16QAM調變的星象圖之一例的圖。圖11A是顯示第1發送RF鏈(chain)處理之DFT訊號的例子之圖。圖11B是顯示第2發送RF鏈(chain)處理之DFT訊號的例子之圖。圖12是顯示實施形態2之變形例的發送裝置的構成之圖。圖13是顯示實施形態2之變形例的GI附加方法之一例的圖。圖14是顯示實施形態2之變形例的GI附加方法之另一例的圖。FIG. 1 is a diagram showing an example of a configuration of a MIMO communication system according to the first embodiment. FIG. 2 is a diagram showing an example of an amplitude component of a frequency response. FIG. 3 is a diagram showing an example of a configuration of a transmission device according to the first embodiment. FIG. 4A is a diagram showing an example of an constellation of π / 2-BPSK (Binary Phase Shift Keying) whose symbol index is odd. FIG. 4B is a diagram showing an example of an astrological chart of π / 2-BPSK whose symbol index is an even number. 4C is a diagram showing an example of an astrological chart of output data of a precoding section. FIG. 5A is a diagram showing an example of a GI addition method. FIG. 5B is a diagram showing an example of a DFT signal in which DFT is performed on a symbol block to which GI is added in a precoded symbol. 5C is a diagram showing an example of a DFT signal when DFT is performed on a symbol block to which GI ^* is added to a precoded symbol. 6A is a diagram showing an example of a symbol order inversion process in a symbol order inversion section. FIG. 6B is a diagram showing another example of the symbol order inversion processing in the symbol order inversion section. 6C is a diagram showing an example of a DFT signal when DFT is performed on a symbol block to which a GI is added to a precoded symbol. 6D is a diagram showing an example of an inverted DFT signal when DFT is performed on an inverted symbol. FIG. 6E is a diagram showing a DFT signal obtained by performing DFT on a symbol after phase rotation for each symbol block. FIG. 6F is a diagram showing a DFT signal obtained by performing DFT on a symbol after phase rotation for each symbol block. FIG. 7 is a diagram showing an example of a configuration of a receiving device. FIG. 8 is a diagram showing a method of dividing received data into DFT blocks in the DFT section. Fig. 9 is a diagram showing a configuration of a transmission device according to a second embodiment. FIG. 10A is a diagram showing an example of an astrological chart of π / 2-QPSK modulation. FIG. 10B is a diagram showing an example of an astrological chart of 16QAM modulation. FIG. 11A is a diagram showing an example of a DFT signal processed by a first transmission RF chain. FIG. 11B is a diagram showing an example of the DFT signal processed by the second transmission RF chain. FIG. 12 is a diagram showing a configuration of a transmission device according to a modification of the second embodiment. 13 is a diagram showing an example of a GI addition method according to a modification of the second embodiment. 14 is a diagram showing another example of a GI addition method according to a modification of the second embodiment.

Claims

一種發送裝置，具備：預編碼部，對第1基頻訊號與第2基頻訊號施行預編碼處理，以生成第1預編碼訊號與第2預編碼訊號；順序反轉部，使構成前述第2預編碼訊號的符號序列之順序反轉，而生成第2反轉訊號；相位變更部，生成第2相位變更訊號，且該第2相位變更訊號是對前述第2反轉訊號施行了相位變更的訊號；及發送部，分別從不同的天線發送前述第1預編碼訊號與前述第2相位變更訊號。A transmitting device includes: a precoding unit that performs precoding processing on a first baseband signal and a second baseband signal to generate a first precoding signal and a second precoding signal; and a sequence reversing unit configured to constitute the first 2 The sequence of the symbol sequence of the precoded signal is reversed to generate a second inverted signal; the phase changing unit generates a second phase changed signal, and the second phase changed signal is a phase change of the second inverted signal And a transmitting unit that respectively transmits the first precoding signal and the second phase change signal from different antennas.

如請求項1之發送裝置，其更具備：第1附加部，在前述第1預編碼訊號中附加第1習知訊號；及第2附加部，在前述第2預編碼訊號中附加是與前述第1習知訊號為複共軛的關係的第2習知訊號。For example, the transmitting device of claim 1 further includes: a first appending section that adds a first known signal to the first precoding signal; and a second appending section that adds the second precoding signal with the foregoing precoding signal. The first learned signal is a second learned signal in a complex conjugate relationship.

如請求項2之發送裝置，其中，前述順序反轉部是使構成前述第2習知訊號的符號序列之順序反轉，且在已反轉的第2習知訊號上連結已反轉的第2預編碼訊號，來生成前述第2反轉訊號。For example, the transmitting device of claim 2, wherein the order reversing unit reverses the order of the symbol sequences constituting the second conventional signal, and links the reversed second conventional signal to the reversed second conventional signal. 2 pre-encode the signal to generate the aforementioned second inversion signal.

如請求項2之發送裝置，其中，前述順序反轉部是讓已使前述第2習知訊號連結於前述第2預編碼訊號的符號序列的順序反轉，而生成前述第2反轉訊號。For example, the transmission device of claim 2, wherein the sequence inversion unit reverses the sequence of the symbol sequence in which the second conventional signal is linked to the second precoding signal, and generates the second inversion signal.

如請求項2至4中任一項之發送裝置，其更具備：第3附加部，在前述第2預編碼訊號中附加第3習知訊號；及選擇部，根據前述第1基頻訊號與前述第2基頻訊號是否為複共軛的關係，來選擇是否使前述第2反轉訊號、及已附加有前述第3習知訊號的前述第2預編碼訊號的任一個輸入至前述相位變更部。If the transmitting device of any one of claims 2 to 4, further includes: a third appending section, which adds a third learning signal to the aforementioned second precoding signal; and a selecting section, which is based on the aforementioned first baseband signal and Whether or not the second baseband signal is a complex conjugate is to select whether to input any of the second inverted signal and the second precoded signal to which the third conventional signal is added to the phase change. unit.

一種發送方法，其為：對第1基頻訊號與第2基頻訊號施行預編碼處理，以生成第1預編碼訊號與第2預編碼訊號；使構成前述第2預編碼訊號的符號序列之順序反轉，而生成第2反轉訊號；生成對前述第2反轉訊號施行了相位變更的第2相位變更訊號；及分別從不同的天線發送前述第1預編碼訊號與前述第2相位變更訊號。A transmission method includes: performing precoding processing on a first baseband signal and a second baseband signal to generate a first precoded signal and a second precoded signal; Generates a second inversion signal by inverting the sequence; generates a second phase change signal in which a phase change is performed on the second inversion signal; and sends the first precoding signal and the second phase change from different antennas, respectively Signal.

一種接收裝置，具備：接收部，分別以不同的天線來接收第1接收訊號及第2接收訊號；及解調部，從前述第1接收訊號及前述第2接收訊號中生成第1基頻訊號及第2基頻訊號，在前述第1接收訊號及前述第2接收訊號中，包含有第1預編碼訊號及第2相位變更訊號，前述第1預編碼訊號，是發送裝置對前述第1基頻訊號與前述第2基頻訊號施行預編碼處理而生成的訊號，前述第2相位變更訊號是下述之訊號：前述發送裝置對前述第1基頻訊號與前述第2基頻訊號施行預編碼處理而生成第2預編碼訊號，且使構成該生成的第2預編碼訊號的符號序列之順序反轉而生成第2反轉訊號，並對該生成的第2反轉訊號施行相位變更而生成的訊號。A receiving device includes: a receiving section for receiving a first reception signal and a second reception signal with different antennas; and a demodulation section for generating a first baseband signal from the first reception signal and the second reception signal. And the second baseband signal, the first reception signal and the second reception signal include a first precoding signal and a second phase change signal, and the first precoding signal is a transmission device for the first baseband signal. The frequency signal and the second baseband signal are generated by performing precoding processing. The second phase change signal is a signal that the transmitting device performs precoding on the first baseband signal and the second baseband signal. Processing to generate a second precoding signal, and inverting the sequence of the symbol sequences constituting the generated second precoding signal to generate a second inverting signal, and generating a phase change to the generated second inverting signal to generate Signal.

一種接收方法，其為：分別以不同的天線來接收第1接收訊號及第2接收訊號；及從前述第1接收訊號及前述第2接收訊號中生成第1基頻訊號及第2基頻訊號，在前述第1接收訊號及前述第2接收訊號中，包含有第1預編碼訊號及第2相位變更訊號，前述第1預編碼訊號，是發送裝置對前述第1基頻訊號與前述第2基頻訊號施行預編碼處理而生成的訊號，前述第2相位變更訊號是下述之訊號：前述發送裝置對前述第1基頻訊號與前述第2基頻訊號施行預編碼處理而生成第2預編碼訊號，且使構成該生成的第2預編碼訊號的符號序列之順序反轉而生成第2反轉訊號，並對該生成的第2反轉訊號施行相位變更而生成的訊號。A receiving method includes: receiving a first receiving signal and a second receiving signal with different antennas; and generating a first baseband signal and a second baseband signal from the first receiving signal and the second receiving signal, respectively. The first receiving signal and the second receiving signal include a first precoding signal and a second phase changing signal, and the first precoding signal is the first baseband signal and the second The baseband signal is a signal generated by performing precoding processing. The second phase change signal is a signal in which the transmitting device performs precoding processing on the first baseband signal and the second baseband signal to generate a second precoding signal. The signal is encoded, and the sequence of the symbol sequence constituting the generated second precoded signal is reversed to generate a second inverted signal, and the generated second inverted signal is subjected to a phase change.