TW201810902A - Isolated high-step-up DC-DC converter - Google Patents

Isolated high-step-up DC-DC converter Download PDF

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TW201810902A
TW201810902A TW105101501A TW105101501A TW201810902A TW 201810902 A TW201810902 A TW 201810902A TW 105101501 A TW105101501 A TW 105101501A TW 105101501 A TW105101501 A TW 105101501A TW 201810902 A TW201810902 A TW 201810902A
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capacitor
switching element
voltage
inductor
input
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TWI565207B (en
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胡國英
江文莊
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國立臺北科技大學
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Abstract

An isolated high-step-up DC-DC converter is presented, which possesses a high voltage gain, continuous input current and galvanic isolation. This converter is constructed by a boost convertion circuit, a forward convertion circuit and the double voltage circuit. The isolated high-step-up DC-DC converter use an coupled inductor and two switches. One switch transfers the energy to the coupled inductor's secondary side as the other switch is turned off. In addition, the double voltage circuit is added to the secondary side to further upgrade the voltage gain.

Description

隔離型高升壓直流-直流轉換器Isolated high-boost DC-DC converter

本發明是有關於一種高升壓直流-直流轉換器，特別是指一種隔離型高升壓直流-直流轉換器。The present invention relates to a high-boost DC-DC converter, and more particularly to an isolated high-boost DC-DC converter.

近年來，隨著材料的進步，熱電產生器(Thermoelectric Generator, TEG)的應用場合逐漸增加。此熱電模組(Thermoelectric Module)近年來熱電模組除了效率可提升到20%左右，且成本也逐漸降低，未來將可廣泛應用於汽車廢熱、工業廢熱、船舶廢熱、穿戴式科技等場合。In recent years, with the advancement of materials, the application of Thermoelectric Generator (TEG) has gradually increased. In recent years, the thermoelectric module has been improved in efficiency by about 20%, and the cost is gradually reduced. In the future, it can be widely used in automobile waste heat, industrial waste heat, ship waste heat, wearable technology and the like.

熱電產生器係將廢熱的能量轉換成電能之後，可以直接連接負載使用，若此負載之等效電阻不等於熱電模組之等效內阻，將無法得到最大功率輸出，故需研製一具有最大功率追蹤之電源轉換器(Maximum Power Point Tracking, MPPT)。The thermoelectric generator converts the energy of waste heat into electrical energy, and can be directly connected to the load. If the equivalent resistance of the load is not equal to the equivalent internal resistance of the thermoelectric module, the maximum power output cannot be obtained, so it is necessary to develop a maximum Power Power Tracking (MPPT).

目前熱電轉換系統分為獨立型熱電轉換系統、單級熱電轉換系統、雙級熱電轉換系統、多重能源輸入轉換系統，而前述熱電轉換系統都各自有其優點與缺點。At present, the thermoelectric conversion system is divided into a stand-alone thermoelectric conversion system, a single-stage thermoelectric conversion system, a two-stage thermoelectric conversion system, and a multi-energy input conversion system, and each of the aforementioned thermoelectric conversion systems has its own advantages and disadvantages.

另外，已知熱電模組之輸出電壓低且輸出電能不穩定，因此需要採用一具寬廣輸入電壓之高升壓轉換器來滿足負載的需求。再者，就傳統升壓型轉換器(Boost Converter)而言，由於受到寄生元件影響，升壓比最多只能升至四倍左右。又，在實際應用上須採用隔離型轉換器以符合安全的要求。In addition, it is known that the output voltage of the thermoelectric module is low and the output power is unstable, so a high boost converter with a wide input voltage is required to meet the load demand. Furthermore, in the case of a conventional boost converter, the boost ratio can only be increased by up to four times due to the influence of parasitic elements. In addition, isolated converters must be used in practical applications to meet safety requirements.

因此，本發明之其中一目的，即在提供一種解決先前技術缺失的隔離型高升壓直流-直流轉換器。Accordingly, it is an object of the present invention to provide an isolated high step-up DC-DC converter that addresses the prior art deficiencies.

本發明隔離型高升壓直流-直流轉換器在一些實施態樣中電性連接一負載，用以對一輸入電壓進行升壓並提供該負載，包含一升壓轉換電路、一順向式轉換電路及一倍壓電路。In some embodiments, the isolated high-boost DC-DC converter is electrically connected to a load for boosting an input voltage and providing the load, including a boost conversion circuit and a forward conversion. Circuit and double voltage circuit.

該升壓轉換電路具有一第一順向導通元件、一第一電容、一輸入電容、一輸入電感及一第一開關元件，該輸入電容的一端與該輸入電感之一端耦接該輸入電壓，該第一順向導通元件之一端與該輸入電感之另一端耦接該第一開關元件的一第一端，該第一電容之另一端接地。The boost converter circuit has a first forward conducting component, a first capacitor, an input capacitor, an input inductor, and a first switching component, and one end of the input capacitor is coupled to the input voltage at one end of the input inductor, One end of the first forward conducting component and the other end of the input inductor are coupled to a first end of the first switching component, and the other end of the first capacitor is grounded.

該順向式轉換電路具有一耦合電感及一第二開關元件，該耦合電感具有一初級側繞組及一次級側繞組，該初級側繞組的打點端耦接該第一順向導通元件之另一端與該第一電容之一端，該初級側繞組的非打點端耦接該第一開關元件的一第二端及第二開關元件的一第一端，該第二開關元件的一第二端接地。The forward conversion circuit has a coupled inductor and a second switching element, the coupled inductor has a primary side winding and a primary side winding, and the dot end of the primary side winding is coupled to the other end of the first forward conducting component The first end of the first side of the first switching element is coupled to a second end of the first switching element and a first end of the second switching element, and a second end of the second switching element is grounded .

該倍壓電路具有一第二電容、一第二順向導通元件及一第三順向導通元件，該第二電容的一端耦接該第二順向導通元件的一端，該第二電容的另一端耦接該次級側繞組的打點端，該第二順向導通元件的另一端耦接該次級側繞組的非打點端，該第二電容之另一端接地。The voltage doubling circuit has a second capacitor, a second forward conducting component and a third forward conducting component, and one end of the second capacitor is coupled to one end of the second forward conducting component, the second capacitor The other end is coupled to the striking end of the secondary side winding, the other end of the second forward conducting element is coupled to the non-tapping end of the secondary side winding, and the other end of the second capacitor is grounded.

藉此，當該第一開關元件與該第二開關元件導通時，該第三順向導通元件導通，該第一順向導通元件及該第二順向導通元件截止，該輸入電感兩端之跨壓為該輸入電壓，該輸入電感進行激磁，該第一電容對該輸入電感的一激磁電感放電，使得該激磁電感兩端之跨壓為該第一電容之跨壓，故激磁電感進行激磁並傳遞電流對該第二電容放電並將能量送至該負載；當該第一開關元件與該第二開關元件截止時，該第三順向導通元件截止，該第一順向導通元件及該第二順向導通元件導通，該輸入電感兩端之跨壓為該輸入電壓減去該第一電容之跨壓，該輸入電感進行去磁並對該第一電容充電，該激磁電感兩端之跨壓為該第二電容之跨壓傳遞到該初級側繞組使得該激磁電感進行去磁，並將去磁之能量經由該次級側繞組傳送至該第二電容使該第二電容進行充電以提供該負載所需之能量。Thereby, when the first switching element and the second switching element are turned on, the third forward conducting component is turned on, and the first forward conducting component and the second forward conducting component are turned off, and the input inductor is both ends The input voltage is excited by the input voltage, and the first capacitor discharges a magnetizing inductance of the input inductor, so that the voltage across the magnetizing inductor is the voltage across the first capacitor, so the magnetizing inductance is excited. And transmitting a current to discharge the second capacitor and sending energy to the load; when the first switching element and the second switching element are turned off, the third forward conducting component is turned off, the first forward conducting component and the The second forward conducting component is turned on. The voltage across the input inductor is the input voltage minus the voltage across the first capacitor. The input inductor is demagnetized and charges the first capacitor. Transmitting a voltage across the second capacitor to the primary side winding causes the magnetizing inductance to demagnetize, and transferring demagnetized energy to the second capacitor via the secondary side winding to charge the second capacitor mention The energy required for the load.

在一些實施態樣中，該第一順向導通元件及該第二順向導通元件皆為二極體。In some implementations, the first forward conducting component and the second forward conducting component are both diodes.

在一些實施態樣中，該第一開關元件及該第二開關元件皆為N型金氧半場效電晶體，該第一開關元件及該第二開關元件之閘極則受控制以決定導通與否，該第一開關元件及該第二開關元件之第一端皆為源極，該第一開關元件及該第二開關元件之第二端皆為汲極。In some implementations, the first switching element and the second switching element are all N-type MOS field-effect transistors, and the gates of the first switching element and the second switching element are controlled to determine conduction and No, the first ends of the first switching element and the second switching element are all sources, and the second ends of the first switching element and the second switching element are both drains.

在一些實施態樣中，該第一開關元件的第一端與第二端之間及該第二開關元件的第一端與第二端之間皆反向連接一二極體。In some implementations, a diode is reversely connected between the first end and the second end of the first switching element and between the first end and the second end of the second switching element.

在一些實施態樣中，所述隔離型高升壓直流-直流轉換器係電性連接一熱電產生器以接收該熱電產生器將熱能轉換為電能所產生的該輸入電壓。In some implementations, the isolated high-boost DC-DC converter is electrically coupled to a thermoelectric generator to receive the input voltage generated by the thermoelectric generator to convert thermal energy into electrical energy.

在一些實施態樣中，所述隔離型高升壓直流-直流轉換器電性連接的該負載係一發光二極體模組。In some implementations, the load electrically connected to the isolated high-boost DC-DC converter is a light-emitting diode module.

本發明至少具有以下功效：此系統之成本較雙級熱電轉換系統低，效率較雙級熱電轉換系統來的高，當熱電轉換器提供能量時，直流轉換器可透過控制器的最大功率追蹤技術來使得蓄電池能在獲得最大功率下進行充電。The invention has at least the following effects: the cost of the system is lower than that of the two-stage thermoelectric conversion system, and the efficiency is higher than that of the two-stage thermoelectric conversion system. When the thermoelectric converter provides energy, the DC converter can pass the maximum power tracking technology of the controller. This allows the battery to be charged at maximum power.

參閱圖1，本發明之實施例的其中一種應用，單級熱電轉換系統5包括一隔離型高升壓直流-直流轉換器100、一控制器50、熱電產生模組51及一蓄電池52，控制器50具有最大功率追蹤功能，隔離型高升壓直流-直流轉換器100之輸出連接至蓄電池52以進行充電。Referring to FIG. 1, in one application of an embodiment of the present invention, a single-stage thermoelectric conversion system 5 includes an isolated high-boost DC-DC converter 100, a controller 50, a thermoelectric generation module 51, and a battery 52. The device 50 has a maximum power tracking function, and the output of the isolated high-boost DC-DC converter 100 is connected to the battery 52 for charging.

參閱圖2，本發明之實施例的另一種應用，單級熱電轉換系統6包括一隔離型高升壓直流-直流轉換器100、一熱電產生器61及一發光二極體模組62。熱電產生器61包含一熱板(Hot Plate)611、一熱面(Hot side)612、一冷面(Cold side)613及一冷板(Cold plate)614，藉由熱板611、熱面612、冷面613及冷板614的熱電效應，由溫差產生電壓轉換，當溫差產生時會產生輸入電壓Vi 。Referring to FIG. 2, another application of the embodiment of the present invention, the single-stage thermoelectric conversion system 6 includes an isolated high-boost DC-DC converter 100, a thermoelectric generator 61, and a light-emitting diode module 62. The thermoelectric generator 61 includes a hot plate 611, a hot side 612, a cold side 613, and a cold plate 614, and the hot plate 611 and the hot surface 612. The thermoelectric effect of the cold surface 613 and the cold plate 614 generates a voltage conversion by the temperature difference, and an input voltage V i is generated when the temperature difference is generated.

參閱圖3及圖4，隔離型高升壓直流-直流轉換器100電性連接一負載R o ，且對輸入電壓Vi 進行升壓並提供負載R o 。隔離型高升壓直流-直流轉換器100包含一升壓轉換電路1、一順向式轉換電路2及一倍壓電路3。Referring to FIG. 3 and FIG. 4, the isolated high-boost DC-DC converter 100 is electrically connected to a load R o and boosts the input voltage V i and provides a load R o . The isolated high-boost DC-DC converter 100 includes a boost converter circuit 1, a forward converter circuit 2, and a voltage doubler circuit 3.

升壓轉換電路1具有一第一順向導通元件D 1 、一第一電容C 1 、一輸入電容D 0 、一輸入電感L i 及一第一開關元件S 1 ，輸入電容C 1 的一端與輸入電感L i 之一端耦接輸入電壓Vi ，第一順向導通元件D 1 之一端與輸入電感L i 之另一端耦接第一開關元件S 1 的一第一端，第一電容C 1 之一端接地。The boost converter circuit 1 has a first forward conducting component D 1 , a first capacitor C 1 , an input capacitor D 0 , an input inductor L i and a first switching component S 1 , and one end of the input capacitor C 1 One end of the input inductor L i is coupled to the input voltage V i , and one end of the first forward conducting component D 1 and the other end of the input inductor L i are coupled to a first end of the first switching component S 1 , and the first capacitor C 1 One end is grounded.

順向式轉換電路2具有一耦合電感21及一第二開關元件S 2 ，耦合電感21具有一初級側繞組211及一次級側繞組212，初級側繞組211的打點端耦接第一順向導通元件D 1 之另一端與第一電容C 1 之另一端，初級側繞組211的非打點端耦接第一開關元件S 1 的一第二端及第二開關元件S 2 的一第一端，第二開關元件S 2 的一第二端接地。The forward conversion circuit 2 has a coupled inductor 21 and a second switching element S 2 . The coupled inductor 21 has a primary side winding 211 and a primary side winding 212. The dot end of the primary side winding 211 is coupled to the first forward conduction. D 1 and the other end of the element to the other end of the first capacitor C 1, the non-dot end of the primary winding 211 is coupled to a second end and a first terminal of a first switching element a second switching element S 2 of S, A second end of the second switching element S 2 is grounded.

倍壓電路3具有一第二電容C 2 、一第二順向導通元件D 2 、一第三順向導通元件D o 及一輸出電容C o ，第二電容C 2 的一端耦接第二順向導通元件D 2 的一端，第二電容C 2 的另一端耦接次級側繞組212的打點端，第二順向導通元件D 2 的另一端耦接次級側繞組212的非打點端，第二電容C 2 之另一端接地。The voltage doubler circuit 3 has a second capacitor C 2 , a second forward conducting component D 2 , a third forward conducting component D o and an output capacitor C o , and one end of the second capacitor C 2 is coupled to the second D forward conducting member 2 at one end, the other end of the second capacitor C 2 is coupled to the secondary winding of the striking end 212, the other end of the second forward conducting element D 2 is coupled to the non-dot end of the secondary winding 212 The other end of the second capacitor C 2 is grounded.

隔離型高升壓轉換器之動作原理分析如下。The principle of operation of the isolated high boost converter is analyzed as follows.

於進行電路動作原理分析之前，先就其相關的符號定義及其所需之假設做一簡單的說明：Vi 為輸入電壓、Vo 為輸出電壓。Ii 為輸入電流、Io 為輸出電流。能量傳遞電容C 1 、C 2 之容值足夠大，使其跨壓為某一定值。vgs 1 為開關S 1 之驅動訊號、vds 1 為開關S 1 之跨壓、vgs 2 為開關S 2 之驅動訊號、vds 2 為開關S 2 之跨壓、vLi 為輸入電感之跨壓、vLm 為激磁電感之跨壓、vN 1 為線圈N 1 之跨壓、vN 2 為線圈N 2 之跨壓、vD 1 為第一順向導通元件D 1 之跨壓、vD 2 為第二順向導通元件D 2 之跨壓、vDo 為第三順向導通元件Do 之跨壓。Ii 為輸入電流、Io 為輸出電流、iLi 為流經輸入電感Li 之電流、iLm 為流經激磁電感Lm 之電流、iN 1 為流經理想變壓器一次側之電流、iN 2 為流經理想變壓器二次側之電流、ix 為流經激磁電感Lm 之電流iLm 與流經理想變壓器一次側之電流iN 1 之總和、ic 1 為流經能量傳遞電容C 1 之電流、ic 2 為流經能量傳遞電容C 2 之電流。Ts 為切換週期。變壓器耦合係數為一，即不考慮漏感。各元件均視為理想元件。電感與電容均不考慮其寄生電阻。輸入電感及激磁電感在半載以上時皆操作於連續導通模式(Continous Condution Mode, CCM)。於穩態時進行所有電路動作原理之分析。Before performing the circuit action principle analysis, a brief description of its associated symbol definition and its required assumptions is made: V i is the input voltage and V o is the output voltage. I i is the input current and I o is the output current. The capacitances of the energy transfer capacitors C 1 and C 2 are sufficiently large to make their voltage across a certain value. v gs 1 is the driving signal of the switch S 1 , v ds 1 is the voltage across the switch S 1 , v gs 2 is the driving signal of the switch S 2 , v ds 2 is the voltage across the switch S 2 , and v Li is the input inductance The voltage across the voltage, v Lm is the voltage across the magnetizing inductance, v N 1 is the voltage across the coil N 1 , v N 2 is the voltage across the coil N 2 , v D 1 is the voltage across the first forward conducting element D 1 , v D 2 is the cross-pressure of the second forward conducting element D 2 , and v Do is the cross-pressure of the third forward conducting element D o . I i is the input current, I o is the output current, i Li is the current flowing through the input inductor L i , i Lm is the current flowing through the exciting inductance L m , i N 1 is the current flowing through the primary side of the ideal transformer, i N 2 is the current flowing through the secondary side of the ideal transformer, i x is the sum of the current i Lm flowing through the exciting inductance L m and the current i N 1 flowing through the primary side of the ideal transformer, and i c 1 is the energy transfer capacitance flowing through The current of C 1 , i c 2 is the current flowing through the energy transfer capacitor C 2 . T s is the switching period. The transformer coupling coefficient is one, that is, the leakage inductance is not considered. Each component is considered an ideal component. Both the inductor and the capacitor do not consider their parasitic resistance. The input inductor and the magnetizing inductor operate in the Continous Condution Mode (CCM) for more than half a load. Analyze the principle of all circuit operations at steady state.

參閱圖5，本發明所提之隔離型高升壓轉換器的波形時序圖，各元件相關動作原理分析如下。Referring to FIG. 5, the waveform timing diagram of the isolated high boost converter of the present invention is analyzed as follows.

狀態一：[]State one: [ ]

參閱圖6，當第一開關元件S 1 與第二開關元件S 2 導通時，第三順向導通元件Do 導通，第一順向導通元件D 1 及第二順向導通元件D 2 截止，輸入電感Li 兩端之跨壓為輸入電壓Vi ，輸入電感Li 進行激磁，第一電容C 1 對輸入電感Li 的一激磁電感Lm 放電，使得激磁電感Lm 兩端之跨壓為第一電容C 1 之跨壓VC 1 ，故激磁電感Lm 進行激磁，傳遞電流iN 2 對第二電容C 2 放電並將能量送至負載。其相關方程式如公式(1)。(1)Referring to Figure 6, when the first switching element S 1 and S 2 of the second switching element is turned on, the third forward conducting element D o is turned on, a first forward conducting element D 1 and second D 2 cis conducting element is turned off, The voltage across the input inductor L i is the input voltage V i , the input inductor L i is excited, and the first capacitor C 1 discharges a magnetizing inductance L m of the input inductor L i such that the voltage across the magnetizing inductor L m is across. energizing the first voltage V C across the capacitor C of 11, so that the magnetizing inductance L m, i N 2 is transmitted to the load current of the second capacitor C 2 and the discharge energy. Its related equation is as in formula (1). (1)

狀態二：[]State 2: [ ]

參閱圖7，當第一開關元件S 1 與第二開關元件S 2 截止時，第三順向導通元件Do 截止，第一順向導通元件D 1 及第二順向導通元件D 2 導通，輸入電感Li 兩端之跨壓為輸入電壓Vi 減去第一電容C 1 之跨壓VC 1 ，輸入電感Li 進行去磁，並對第一電容C 1 充電，激磁電感Lm 兩端之跨壓為第二電容C 2 之跨壓VC 2 傳遞到初級側繞組211，使得激磁電感Lm 進行去磁，並將去磁之能量經由次級側繞組212傳送至第二電容C 2 ，使第二電容C 2 進行充電以提供負載所需之能量。其相關方程式如公式(2)。(2)Referring to FIG. 7, when the first switching element S 1 and the second switching element S 2 are turned off, the third forward conducting element D o is turned off, and the first forward conducting element D 1 and the second forward conducting element D 2 are turned on. L i of the input voltage across both ends of the inductor 1, the input inductor is demagnetized L i V i is the input voltage minus the first voltage V C across the capacitor C of 1, and a first charge capacitor C 1, two magnetizing inductance L m The voltage across the terminal is transmitted to the primary side winding 211 across the voltage V C 2 of the second capacitor C 2 such that the magnetizing inductance L m is demagnetized and the demagnetized energy is transmitted to the second capacitor C via the secondary side winding 212 2, the second capacitor C 2 is charged to provide the energy required for the load. Its related equation is as in formula (2). (2)

C. 電壓轉換比推導C. Voltage conversion ratio derivation

本電路設計於於半載以上時操作於連續導通模式，在進行電壓轉換比推導前，在此定義理想變壓器匝數比如公式(3)。(3)This circuit is designed to operate in continuous conduction mode above half load. Before the voltage conversion ratio is derived, the ideal transformer turns are defined here as equation (3). (3)

首先，輸入電感Li 於一週期內須符合伏秒平衡(Voltage-Second Balance)，故可得其相關方程式如公式(4)。(4)First, the input inductor L i must meet in one cycle volt-second balance (Voltage-Second Balance), so obtaining the correlation equation may be as shown in equation (4). (4)

經由整理後可得其相關方程式如公式(5)。(5)After sorting, the relevant equations are obtained as in equation (5). (5)

此外，激磁電感Lm 於一週期內亦須符合根據伏秒平衡，故可得其相關方程式如公式(6)。(6)In addition, the magnetizing inductance L m must also be in accordance with the volt-second balance over a period of time, so the relevant equation can be obtained as equation (6). (6)

此時將公式(7)代入公式(6)，並可獲得其相關方程式如公式(8)。(7)(8)At this time, the formula (7) is substituted into the formula (6), and the relevant equation is obtained as the formula (8). (7) (8)

接著，根據克希荷夫電壓定律(Kirchhoff’s Voltage Law, KVL），輸出電壓Vo 於狀態ㄧ時如公式(9)。(9)Then, according to Kirchhoff's Voltage Law (KVL), the output voltage V o is in the state ㄧ as in the formula (9). (9)

其中，狀態ㄧ時之二次側跨壓vN 2 如公式(10)。(10)Wherein, the secondary side crossing pressure v N 2 in the state ㄧ is as in the formula (10). (10)

最後，將公式(8)與(10)式代入公式(9)中，可得所提電路之電壓轉換比如公式(11)。(11)Finally, substituting equations (8) and (10) into equation (9), the voltage conversion of the proposed circuit is obtained, for example, equation (11). (11)

參閱圖8，可知本發明所提出之隔離型高升壓轉換器之電壓轉換比較傳統反馳式轉換器之電壓轉換比來的高，且與文獻１～４之升壓型轉換器相比，在同樣的匝數下，電壓轉換比亦較高。本發明之架構與文獻１、文獻２、文獻３及文獻４之轉換器皆操作於連續導通模式下且匝數比n = 4。文獻１為R. W. Erickson and D. Maksimovic,Fundamentals of Power Electronics , 2nd ed., Norwell: Kluwer Academic Publishers, 2001；文獻２為Tsorng-Juu Liang, Jian-Hsieng Lee, Shih-Ming Chen, Jiann-Fuh Chen and Lung-Sheng Yang, “Novel isolated high-step-up DC-DC converter with voltage lift,”IEEE Transactions on Power Electronics , vol. 60, no. 4, pp. 1483-1491, 2013；文獻３為Sang-Uk Seo, Kui-Jun Lee, Rae-Young Kim and Dong-Seok Hyun, “Aggregated modeling and control of integrated boost-flyback high step-up converter,”IEEE IECON’11 , pp. 1191-1196, 2011；文獻４為Shuai Jiang, Dong Cao, Yuan Li, Member and Fang Zheng Peng, “Grid-connected boost-half-bridge photovoltaic microinverter system using repetitive current control and maximum power point tracking,”IEEE Transactions on Power Electronics , vol. 27, no. 11, pp. 4711-4722, 2012。Referring to FIG. 8, it can be seen that the voltage conversion of the isolated high-boost converter proposed by the present invention is higher than that of the conventional fly-back converter, and compared with the boost converters of documents 1 to 4. At the same number of turns, the voltage conversion ratio is also higher. The architecture of the present invention and the converters of documents 1, 2, 3 and 4 operate in continuous conduction mode with a turns ratio n = 4. Document 1 is RW Erickson and D. Maksimovic, Fundamentals of Power Electronics , 2nd ed., Norwell: Kluwer Academic Publishers, 2001; Document 2 is Tsorng-Juu Liang, Jian-Hsieng Lee, Shih-Ming Chen, Jiann-Fuh Chen and Lung-Sheng Yang, "Novel isolated high-step-up DC-DC converter with voltage lift," IEEE Transactions on Power Electronics , vol. 60, no. 4, pp. 1483-1491, 2013; Document 3 is Sang-Uk Seo, Kui-Jun Lee, Rae-Young Kim and Dong-Seok Hyun, "Aggregated modeling and control of integrated boost-flyback high step-up converter," IEEE IECON'11 , pp. 1191-1196, 2011; Shuai Jiang, Dong Cao, Yuan Li, Member and Fang Zheng Peng, "Grid-connected boost-half-bridge photovoltaic microinverter system using repetitive current control and maximum power point tracking," IEEE Transactions on Power Electronics , vol. 27, no. 11, pp. 4711-4722, 2012.

參閱圖9，隔離型高升壓轉換器應用之系統架構，其包含一主功率級與回授電路，其具有一分壓電路(Voltage Divider)71、一類比數位轉換器(Analog-to-Digital Converter, ADC)72、一運算單元73及二閘極驅動器(Gate Driver)741、742，分壓電路71用以取得輸出電壓的類比訊號，再經由類比數位轉換器72轉成數位訊號後傳送至運算單元73以得到相對之控制力，最後再將此控制力藉由閘極驅動器741、742來調控第一開關元件S 1 及第二開關元件S 2 。Referring to Figure 9, the system architecture of the isolated high boost converter application includes a main power stage and feedback circuit having a voltage divider 71 and an analog-to-digital converter (Analog-to- Digital Converter (ADC) 72, an arithmetic unit 73 and two gate drivers 741 and 742. The voltage dividing circuit 71 is used to obtain an analog signal of the output voltage, and then converted into a digital signal by the analog digital converter 72. It is sent to the arithmetic unit 73 to obtain a relative control force, and finally the control force is used to regulate the first switching element S 1 and the second switching element S 2 by the gate drivers 741 and 742.

隔離型高升壓轉換器之系統操作模式如表1以及系統規格如表2所示。由於此規格必須搭配熱電模組，並加入最大功率追蹤控制以獲得熱電模組之最大功率。當熱電模組輸出為35W時，此時之熱電模組之輸出電壓為7V；而在熱電模組輸出為17.5W時，此時之熱電模組之輸出電壓為5V。根據上述所言，故將轉換器之輸入電壓設定在某一範圍內，故即。 表1 The system operation mode of the isolated high-boost converter is shown in Table 1 and the system specifications are shown in Table 2. Since this specification must be matched with a thermoelectric module, maximum power tracking control is added to obtain the maximum power of the thermoelectric module. When the output of the thermoelectric module is 35W, the output voltage of the thermoelectric module at this time is 7V; and when the output of the thermoelectric module is 17.5W, the output voltage of the thermoelectric module at this time is 5V. According to the above, the input voltage of the converter is set within a certain range, so . Table 1

隔離型高升壓轉換器之實作波形說明如下。The implementation waveform of the isolated high boost converter is described below.

參閱圖10，可得知當開關S 1 、S 2 截止時，輸入電感之跨壓vLi 產生電壓突波，這是由於耦合電感21T 上的漏感、開關S 1 之背接電容、開關S 2 之背接電容發生共振。Referring to FIG. 10, it can be seen that when the switches S 1 and S 2 are turned off, the voltage across the input inductor v Li generates a voltage spurt due to the leakage inductance on the coupled inductor 21 T , the back-connection capacitance of the switch S 1 , and the switch. The backing capacitor of S 2 resonates.

參閱圖11，可得知當開關S 1 、S 2 截止時，開關S 1 、S 2 之跨壓產生電壓突波，這是由於耦合電感21T 上的漏感、開關S 1 之背接電容、開關S 2 之背接電容發生共振。Referring to FIG. 11, it can be seen that when the switches S 1 and S 2 are turned off, the voltage across the switches S 1 and S 2 generates a voltage spurt due to the leakage inductance on the coupled inductor 21 T and the back-connection capacitance of the switch S 1 . The backing capacitor of switch S 2 resonates.

參閱圖12，可得知當開關S 1 、S 2 截止時，電流ix 上之振鈴現象乃是因為耦合電感21T 上的漏感與開關S 1 、S 2 之背接電容發生共振，這是由於耦合電感21T 上的漏感、開關S 1 之背接電容、開關S 2 之背接電容發生共振，此共振也造成二次側之電流iN 2 產生電流突波。此外，當導通S 1 、S 2 導通時，電流ix 上之電流突波是由於順向導通元件D 2 於截止時產生逆向回復電流，此電流反射至一次側，故造成此現象。Referring to FIG. 12, it can be seen that when the switches S 1 and S 2 are turned off, the ringing phenomenon on the current i x is because the leakage inductance on the coupled inductor 21 T resonates with the back-connection capacitance of the switches S 1 and S 2 . This is because the leakage inductance on the coupled inductor 21 T , the back-connection capacitance of the switch S 1 , and the back-connection capacitance of the switch S 2 resonate, and this resonance also causes the secondary side current i N 2 to generate a current surge. Further, when the conductions S 1 and S 2 are turned on, the current surge on the current i x is caused by the reverse return current generated when the forward conduction element D 2 is turned off, and this current is reflected to the primary side, thus causing this phenomenon.

參閱圖13，可得知當開關S 1 、S 2 截止時，耦合電感21一次側線圈之跨壓上有振鈴現象，這是由於耦合電感21T 的漏感、開關S 1 之背接電容、開關S 2 之背接電容共振所造成的；而當開關S 1 、S 2 導通時，耦合電感21一次側線圈之跨壓上有振鈴現象，這是由於漏感與順向導通元件D 1 上之寄生電容共振。Referring to FIG. 13, it can be seen that when the switches S 1 and S 2 are turned off, there is a ringing phenomenon on the voltage across the primary side coil of the coupled inductor 21 due to the leakage inductance of the coupled inductor 21 T and the back-connection capacitance of the switch S 1 . The backing of the switch S 2 is caused by the resonance of the capacitor; and when the switches S 1 and S 2 are turned on, the crossover of the primary side coil of the coupled inductor 21 has a ringing phenomenon, which is due to the leakage inductance and the forward conduction element D 1 . The parasitic capacitance resonates.

參閱圖14，可得知能量傳輸電容C 1 、能量傳輸電容C 2 之跨壓VC 1 、VC 2 於任何負載下皆約穩定處於一定值。Referring to FIG. 14, it can be seen that the voltage transfer capacitor C 1 and the voltage transfer capacitors C 2 across the voltages V C 1 and V C 2 are stable at a certain value under any load.

參閱圖15，可得知當開關S 1 、S 2 導通時，順向導通元件之跨壓vD 1 上產生電壓突波，這是由於漏感與順向導通元件D 1 上之接面電容發生共振所產生的；當開關截止時，順向導通元件D 1 即將導通，順向導通元件之跨壓vD 1 上產生負電壓突波，這是由於耦合電感21T 上的漏感、開關S 1 之背接電容、開關S 2 之背接電容、順向導通元件D 1 上之接面電容發生共振。Referring to FIG. 15, it can be seen that when the switches S 1 and S 2 are turned on, a voltage surge is generated across the voltage across the voltage component V D 1 due to the leakage inductance and the junction capacitance on the forward-conducting element D 1 . When resonance occurs, when the switch is turned off, the forward conduction element D 1 is turned on, and the voltage across the voltage across the voltage V D 1 generates a negative voltage surge. This is due to the leakage inductance and switching on the coupled inductor 21 T . the S 1 back to the capacitor, the switch S 2 back to the capacitor, the forward conducting surface of the capacitor element D 1 resonance.

參閱圖16，可得知輸出電壓漣波Δvo 皆小於100mV。Referring to Figure 16, it can be seen that the output voltage ripple Δ v o is less than 100 mV.

綜上所述，本發明裝置，故確實能達成本發明之目的。In summary, the apparatus of the present invention can indeed achieve the object of the present invention.

惟以上所述者，僅為本發明之實施例而已，當不能以此限定本發明實施之範圍，凡是依本發明申請專利範圍及專利說明書內容所作之簡單的等效變化與修飾，皆仍屬本發明專利涵蓋之範圍內。However, the above is only the embodiment of the present invention, and the scope of the invention is not limited thereto, and all the equivalent equivalent changes and modifications according to the scope of the patent application and the patent specification of the present invention are still The scope of the invention is covered.

1‧‧‧升壓轉換電路
100‧‧‧隔離型高升壓直流-直流轉換器
2‧‧‧順向式轉換電路
21‧‧‧耦合電感
211‧‧‧初級側繞組
212‧‧‧次級側繞組
3‧‧‧倍壓電路
5、6‧‧‧單級熱電轉換系統
50‧‧‧控制器
51‧‧‧熱電產生模組
52‧‧‧蓄電池
61‧‧‧熱電產生器
62‧‧‧發光二極體模組
71‧‧‧分壓電路
72‧‧‧類比數位轉換器
73‧‧‧運算單元
741、742‧‧‧閘極驅動器
S 1‧‧‧第一開關元件
S 2‧‧‧第二開關元件
D 1‧‧‧第一順向導通元件
D 2‧‧‧第二順向導通元件
Do ‧‧‧第三順向導通元件
Li ‧‧‧輸入電感
Vi ‧‧‧輸入電壓
Li ‧‧‧輸入電感
C 1‧‧‧第一電容
Lm ‧‧‧激磁電感1‧‧‧Boost conversion circuit
100‧‧‧Isolated high-boost DC-DC converter
2‧‧‧ Forward conversion circuit
21‧‧‧coupled inductor
211‧‧‧Primary side winding
212‧‧‧Secondary side winding
3‧‧‧ double voltage circuit
5, 6‧‧‧ single-stage thermoelectric conversion system
50‧‧‧ Controller
51‧‧‧Thermal generation module
52‧‧‧Battery
61‧‧‧Thermal generator
62‧‧‧Lighting diode module
71‧‧‧voltage circuit
72‧‧‧ analog digital converter
73‧‧‧ arithmetic unit
741, 742‧‧ ‧ gate driver
S 1 ‧‧‧first switching element
S 2 ‧‧‧Second switching element
D 1 ‧‧‧First forward conduction component
D 2 ‧‧‧second forward conduction component
D o ‧‧‧third forward conduction component
L i ‧‧‧inductor
V i ‧‧‧ input voltage
L i ‧‧‧inductor
C 1 ‧‧‧first capacitor
L m ‧‧‧Magnetic inductance

本發明之其他的特徵及功效，將於參照圖式的實施方式中清楚地呈現，其中： 圖1是本發明隔離型高升壓直流-直流轉換器之實施例的其中一種應用的一示意圖； 圖2是本發明隔離型高升壓直流-直流轉換器之實施例的另一種應用的一示意圖； 圖3是本發明隔離型高升壓直流-直流轉換器之實施例的電路圖； 圖4是該實施例標示電流及電壓符號的電路圖； 圖5 是該實施例的波形時序圖； 圖6 是該實施例處於狀態一之電路動作示意圖； 圖7是該實施例處於狀態二之電路動作示意圖； 圖8 是本發明與文獻１～４之電壓轉換比Vo /Vi對責任週期D之關係示意圖； 圖9是該實施例之系統架構示意圖； 圖10至圖16 是於100%額定負載且Vi = 6伏之相關量測波形圖。Other features and advantages of the present invention will be apparent from the embodiments of the present invention, wherein: FIG. 1 is a schematic diagram showing one of the applications of the embodiment of the isolated high-boost DC-DC converter of the present invention; 2 is a schematic diagram showing another application of the embodiment of the isolated high-boost DC-DC converter of the present invention; FIG. 3 is a circuit diagram of an embodiment of the isolated high-boost DC-DC converter of the present invention; FIG. 5 is a circuit diagram of the waveform of the embodiment; FIG. 6 is a schematic diagram of the circuit operation of the embodiment in the state 1; FIG. 7 is a schematic diagram of the circuit operation of the embodiment in the state 2; Figure 8 is a schematic diagram showing the relationship between the voltage conversion ratio Vo /Vi of the present invention and the documents 1 to 4 for the duty cycle D; Figure 9 is a schematic diagram of the system architecture of the embodiment; Figure 10 to Figure 16 are at 100% rated load and Vi = Corresponding measurement waveform of 6 volts.

Claims (6)

一種隔離型高升壓直流-直流轉換器，電性連接一負載，用以對一輸入電壓進行升壓並提供該負載，包含： 一升壓轉換電路，具有一第一順向導通元件、一第一電容、一輸入電容、一輸入電感及一第一開關元件，該輸入電容的一端與該輸入電感之一端耦接該輸入電壓，該第一順向導通元件之一端與該輸入電感之另一端耦接該第一開關元件的一第一端，該第一電容之一端接地； 一順向式轉換電路，具有一耦合電感及一第二開關元件，該耦合電感具有一初級側繞組及一次級側繞組，該初級側繞組的打點端耦接該第一順向導通元件之另一端與該第一電容之另一端，該初級側繞組的非打點端耦接該第一開關元件的一第二端及第二開關元件的一第一端，該第二開關元件的一第二端接地；及 一倍壓電路，具有一第二電容、一第二順向導通元件及一第三順向導通元件，該第二電容的一端耦接該第二順向導通元件的一端，該第二電容的另一端耦接該次級側繞組的打點端，該第二順向導通元件的另一端耦接該該次級側繞組的非打點端，該第二電容之另一端接地； 藉此，當該第一開關元件與該第二開關元件導通時，該第三順向導通元件導通，該第一順向導通元件及該第二順向導通元件截止，該輸入電感Li 兩端之跨壓為該輸入電壓，該輸入電感進行激磁，該第一電容對該輸入電感的一激磁電感放電，使得該激磁電感兩端之跨壓為該第一電容之跨壓，故激磁電感進行激磁並傳遞電流對該第二電容放電並將能量送至該負載；當該第一開關元件與該第二開關元件截止時，該第三順向導通元件截止，該第一順向導通元件及該第二順向導通元件導通，該輸入電感兩端之跨壓為該輸入電壓減去該第一電容之跨壓，該輸入電感進行去磁並對該第一電容充電，該激磁電感兩端之跨壓為該第二電容之跨壓傳遞到該初級側繞組使得該激磁電感進行去磁，並將去磁之能量經由該次級側繞組傳送至該第二電容使該第二電容進行充電以提供該負載所需之能量。An isolated high-boost DC-DC converter electrically connected to a load for boosting an input voltage and providing the load comprises: a boost conversion circuit having a first forward conducting component, a first capacitor, an input capacitor, an input inductor, and a first switching component, wherein one end of the input capacitor is coupled to the input voltage, and one end of the first forward conducting component and the input inductor are One end is coupled to a first end of the first switching element, one end of the first capacitor is grounded; a forward converting circuit has a coupled inductor and a second switching element, the coupled inductor has a primary side winding and once a step-side winding, the other end of the first forward-passing component is coupled to the other end of the first capacitor, and the non-injecting end of the primary-side winding is coupled to the first of the first switching component a first end of the second end and the second switching element, a second end of the second switching element is grounded; and a voltage doubling circuit having a second capacitor, a second forward conducting component, and a third cis Guide pass One end of the second capacitor is coupled to one end of the second forward conducting component, the other end of the second capacitor is coupled to the striking end of the secondary side winding, and the other end of the second forward conducting component is coupled The non-tapping end of the secondary side winding, the other end of the second capacitor is grounded; thereby, when the first switching element and the second switching element are turned on, the third forward conducting element is turned on, the first The forward conduction component and the second forward conduction component are turned off, the voltage across the input inductor L i is the input voltage, and the input inductor is excited, and the first capacitor discharges a magnetizing inductance of the input inductor, so that The voltage across the magnetizing inductor is the voltage across the first capacitor, so the magnetizing inductor excites and transmits a current to discharge the second capacitor and deliver energy to the load; when the first switching element and the second switch When the component is turned off, the third forward conducting component is turned off, the first forward conducting component and the second forward conducting component are turned on, and the voltage across the input inductor is the input voltage minus the cross of the first capacitor Voltage, the input inductor Demagnetizing and charging the first capacitor, the voltage across the magnetizing inductor is transmitted to the primary side winding by the voltage across the second capacitor, so that the magnetizing inductance is demagnetized, and the demagnetizing energy is passed through the The stage side windings are delivered to the second capacitor to charge the second capacitor to provide the energy required for the load. 如請求項1所述隔離型高升壓直流-直流轉換器，其中，該第一順向導通元件及該第二順向導通元件皆為二極體。The isolated high-boost DC-DC converter of claim 1, wherein the first forward conducting component and the second forward conducting component are both diodes. 如請求項1所述隔離型高升壓直流-直流轉換器，其中，該第一開關元件及該第二開關元件皆為N型金氧半場效電晶體，該第一開關元件及該第二開關元件之閘極則受控制以決定導通與否，該第一開關元件及該第二開關元件之第一端皆為源極，該第一開關元件及該第二開關元件之第二端皆為汲極。The isolated high-boost DC-DC converter of claim 1, wherein the first switching element and the second switching element are N-type MOS half-effect transistors, the first switching element and the second The gate of the switching element is controlled to determine whether the first or both ends of the first switching element and the second switching element are the source, and the second end of the first switching element and the second switching element are both It is bungee jumping. 如請求項3所述隔離型高升壓直流-直流轉換器，其中，該第一開關元件的第一端與第二端之間及該第二開關元件的第一端與第二端之間皆反向連接一二極體。The isolated high-boost DC-DC converter of claim 3, wherein between the first end and the second end of the first switching element and between the first end and the second end of the second switching element Both are connected in reverse to a diode. 如請求項1至4其中任一請求項所述隔離型高升壓直流-直流轉換器，其係電性連接一熱電產生器以接收該熱電產生器將熱能轉換為電能所產生的該輸入電壓。The isolated high-boost DC-DC converter according to any one of claims 1 to 4, which is electrically connected to a thermoelectric generator to receive the input voltage generated by the thermoelectric generator converting thermal energy into electrical energy. . 如請求項1至4其中任一請求項所述隔離型高升壓直流-直流轉換器，其電性連接的該負載係一發光二極體模組。The isolated high-boost DC-DC converter according to any one of claims 1 to 4, wherein the load is electrically connected to a light-emitting diode module.
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TWI748347B (en) * 2020-02-15 2021-12-01 國立清華大學 Control method for single-phase inverter and device thereof
TWI750016B (en) * 2020-12-02 2021-12-11 大陸商艾科微電子（深圳）有限公司 Flyback converter and control method thereof

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TWI358188B (en) * 2008-09-17 2012-02-11 Delta Electronics Inc Forward-flyback converter with active-clamp circui
WO2012109783A1 (en) * 2011-02-14 2012-08-23 Intersil Americas Inc. Isolated boost dc/dc converter
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TWI748347B (en) * 2020-02-15 2021-12-01 國立清華大學 Control method for single-phase inverter and device thereof
TWI750016B (en) * 2020-12-02 2021-12-11 大陸商艾科微電子（深圳）有限公司 Flyback converter and control method thereof
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