201208242 六、發明說明： 【發明所屬之技術領域】 本發明涉及積體電路。更具體地，本發明提供了用於初級側感測和調 整的系統和方法。僅僅作為示例，本發明已應用於反激式電源變換器 (flyback P〇wer converter)。但是將認識到，本發明具有較寬廣範圍的應用。 【先前技術】 初級側感測和調整被廣泛用在針對諸如充電器之類的小型電源應用的 反激式電源變糾中。反激式電源變換包括初級繞組以及與變換器 =輸出電麵關聯的次級敝。對於初級规測和調整，通常藉由檢測緊 密耗合到次級繞組關雜組的電壓來細輸丨電壓。由於輔助繞組的電 ，反映了與次級繞組相關聯的輸出電壓，因此，在輔助繞組中感測到的電 壓可用來調整次級側輸出電塵。 ，1 _是顯不具有初級側感測和調整的傳統開關模式反激式電源變換系 ，的簡化=圖。該反激式電源變換系統刚包括變壓器n〇、電源開關⑶、 測電阻If 13G、表示輸出魏的等效電闕魏電㈣14()、採樣保持元 ^ M0、誤差放大器182、迴路補償網路184、pwM/pFM信號產生 ，輯控制το件188以及f雜動器19Gt>另外，變壓胃nG包括初級繞^2、 ^組114和輔助繞組116。此外’該反激式電源變換系統1〇〇包括電阻 ^嶽^ Μ、二極體160和168、以及電容器1%和198。例如，迴路補 请油84也稱為補償網路。在另一示例中，迴路補償網路184包括迴路 雷厭示’電源變換系統则在輸出端子處產生輸出龍M2，輸出 ^輸出電壓接收。為了在所希望的範_調整輸出電廢142, 負載⑼有關的f訊需要被提取以用於控制目的。 ，的貪Λ可在非連續導電模式（DCM)下利用輔助繞组出來提取。 嗜ΐΐ地’备電源開關120為接通時’能量被儲存在變壓器110中。缺 3丄斷開時’所儲存的能量被遞送給輸出端子，並且Ϊ ⑽和輸出==下助來映射輸罐142。例如，輔權 3 201208242201208242 VI. Description of the Invention: [Technical Field of the Invention] The present invention relates to an integrated circuit. More specifically, the present invention provides systems and methods for primary side sensing and adjustment. Merely by way of example, the invention has been applied to flyback P〇wer converters. However, it will be appreciated that the invention has a wide range of applications. [Prior Art] Primary side sensing and adjustment are widely used in flyback power supply correction for small power applications such as chargers. The flyback power conversion includes a primary winding and a secondary turn associated with the converter = output face. For primary measurement and adjustment, the 丨 voltage is typically measured by detecting the voltage that is tightly coupled to the secondary winding group. Since the electrical power of the auxiliary winding reflects the output voltage associated with the secondary winding, the sensed voltage in the auxiliary winding can be used to adjust the secondary side output dust. , 1 _ is a simplified = map of the traditional switch mode flyback power conversion system with no primary side sensing and adjustment. The flyback power conversion system just includes a transformer n〇, a power switch (3), a measuring resistor If 13G, an equivalent electric power indicating the output Wei (four) 14 (), a sample and hold element ^ M0, an error amplifier 182, a loop compensation network 184. The pwM/pFM signal is generated, and the control device 188 and the f-gitter 19Gt are further included. The transformer stomach nG includes a primary winding ^2, a group 114, and an auxiliary winding 116. Further, the flyback power conversion system 1 includes resistors, diodes 160 and 168, and capacitors 1% and 198. For example, circuit replenishment oil 84 is also referred to as a compensation network. In another example, the loop compensation network 184 includes a loop radar. The power conversion system produces an output dragon M2 at the output terminal and an output ^ output voltage reception. In order to adjust the output electrical waste 142 in the desired mode, the load (9) related information needs to be extracted for control purposes. Greedy can be extracted using the auxiliary winding in discontinuous conduction mode (DCM). The energy is stored in the transformer 110 when the standby power switch 120 is turned "on". The stored energy is delivered to the output terminal when 缺3丄 is disconnected, and Ϊ(10) and output==down assist map the transfer tank 142. For example, auxiliary rights 3 201208242
Kux=nx(v〇+yF +j〇 xReJ 其中Vaux表示輔助電壓118 ’ V。表示輸出電壓142，並且％表示二 。另外，IQ表示與輸出電壓142械應的輸出電; 出^机也稱為負載電流。此外表示輸出魏電阻器140的電阻。而且， ^表:辅助繞組116與次級繞組114之間的阻數比，並且n等於Nau氣。 Naux表不輔助繞組116的阻數，並且Nsee表示次級繞組ιΐ4的匝數。 ^如圖1所示，輔助電壓118由包括電阻器170和172的分壓器接收， 該分壓器將輔助電壓118變換為回饋電壓174。 ° V^=kxKuX=kxnx(V0+VF+I0xReq) (等式 2-1) k = +R2) (等式2-2) 其中’ Vfb表示回饋電壓174,並且k表示回饋係數。另外，凡和私 7刀別表示電阻器17〇和172的電阻。 圖2是示出回饋電壓174以及流經次級繞组114之次級電流的傳統波 形的簡化示圖。如圖2所示，Vfb^U別表示回饋輕174和次級電流。 ，外’ ‘表不電源開關12G為接通時的時間段，並且w表示電源開關12〇 為關閉時的時間段。此外，tDemag表示退磁過程的時間段。 參考圖1和圖2，回饋電壓Vfb由採樣和保持元件18〇接收。在接近退 磁過程的結尾處，流經次級繞組114的次級電流變得接近於零。此時，回 饋電麼VFB例如在圖2㈣點a處被採樣。_樣的電壓％隨後由元件 180保持直到下一採樣為止。 經採樣電壓VA由誤差放大器182接收，誤差放大器182將經採樣的電 壓vA與參考電壓V』比較，並且還放A Va與Vrcf之間的差值。誤差放大 器182與補偵網路184 —起將一個或多個輸出信號185發送給 產生器186。例如，補償網路184包括電容器。在另一示例中，pwM/pFM =號產生器186還從感測電阻器13〇接收感測電壓132，感測電阻器13〇將 流經初級繞組112的初級電流變換為感測電壓。作為回應，pwM/pFM信號 產生器186將調變信號187輸出給邏輯控制元件188，邏輯控制元件188將 控制信號189發送給閘驅動器19〇。作為回應，閘驅動胃19〇將驅動信號 192發送給電源開關12〇。 因此，如圖1所示，輸出信號185用來控制驅動信號192的脈衝寬度 201208242 或切麵率，並且因此控制輸出電壓142。例如，輸 電壓V_p相賴。在另-示例中，圖3是利作為輪㈣ 摇^員 載電流）的函數的補償電壓Vcomp的簡化示目。 u也稱為負 具體地，負反饋迴路用來藉由調整所採樣的電 V。，以使得vA變為等於參考電壓Vref。因此，、而調整輸出電壓 (等式3)Kux=nx(v〇+yF +j〇xReJ where Vaux represents the auxiliary voltage 118 'V. It represents the output voltage 142, and % represents 2. In addition, IQ represents the output power with the output voltage 142; It is the load current. It also indicates the resistance of the output Wei resistor 140. Moreover, the table shows the resistance ratio between the auxiliary winding 116 and the secondary winding 114, and n is equal to Nau gas. Naux indicates the resistance of the auxiliary winding 116, And Nsee represents the number of turns of the secondary winding ι4. ^ As shown in Figure 1, the auxiliary voltage 118 is received by a voltage divider comprising resistors 170 and 172 which convert the auxiliary voltage 118 to a feedback voltage 174. ° V ^=kxKuX=kxnx(V0+VF+I0xReq) (Equation 2-1) k = +R2) (Equation 2-2) where 'Vfb denotes a feedback voltage 174, and k denotes a feedback coefficient. In addition, the resistance of the resistors 17〇 and 172 is indicated by the private and the other. 2 is a simplified diagram showing a conventional waveform of the feedback voltage 174 and the secondary current flowing through the secondary winding 114. As shown in Figure 2, Vfb^U indicates the feedback light 174 and the secondary current. , outside ' ‘ indicates the time period when the power switch 12G is on, and w indicates the time period when the power switch 12 〇 is off. In addition, tDemag represents the time period of the demagnetization process. Referring to Figures 1 and 2, the feedback voltage Vfb is received by the sample and hold element 18A. At the end of the near demagnetization process, the secondary current flowing through the secondary winding 114 becomes close to zero. At this time, the feedback VFB is sampled, for example, at point a of Fig. 2 (4). The _-like voltage % is then held by component 180 until the next sample. The sampled voltage VA is received by an error amplifier 182 which compares the sampled voltage vA with a reference voltage V" and also places the difference between A Va and Vrcf. Error amplifier 182, in conjunction with patch network 184, transmits one or more output signals 185 to generator 186. For example, compensation network 184 includes a capacitor. In another example, the pwM/pFM = number generator 186 also receives a sense voltage 132 from the sense resistor 13A, which transforms the primary current flowing through the primary winding 112 into a sense voltage. In response, the pwM/pFM signal generator 186 outputs the modulated signal 187 to the logic control element 188, which sends the control signal 189 to the gate driver 19A. In response, the gate drives the stomach 19 to send a drive signal 192 to the power switch 12A. Thus, as shown in FIG. 1, the output signal 185 is used to control the pulse width 201208242 or the facet ratio of the drive signal 192, and thus the output voltage 142. For example, the input voltage V_p depends. In another example, Figure 3 is a simplified representation of the compensation voltage Vcomp as a function of the wheel (four). Also referred to as negative, specifically, a negative feedback loop is used to adjust the sampled electrical V. So that vA becomes equal to the reference voltage Vref. Therefore, adjust the output voltage (Equation 3)
Vref=kynx(v〇+VF+I〇XRj 因此， (等式4) 由於輸出電壓V。由負反饋迴路調整，因此使得迴路對所有負 在所有輸入電壓處保持穩定通常是很重要的。此外，回盈 現出良好的峰心 ㈣而要表 如圖1所示，對於電源變換系統1〇〇，回饋迴路至少包括控制級和電源 例如’控制級至少包括誤差放大器182、迴路補償網路184和 L號產生器186中的-部分。在另一示例令，電源級至少包括邏輯控制元 = ==、匕閘驅動器19〇以及閘驅動器190與用於輸出電壓V。的輸出端子之 —前向路徑的整體傳輸函數由控制級的傳輸函數和電源級的傳輸函數來 確定°對於電源變換系統则，電源級的傳輸函數為：Vref=kynx(v〇+VF+I〇XRj Therefore, (Equation 4) Since the output voltage V is adjusted by the negative feedback loop, it is usually important that the loop remains stable for all negative input voltages. A good peak (4) is shown in Fig. 1. For the power conversion system, the feedback loop includes at least a control stage and a power supply. For example, the 'control stage includes at least an error amplifier 182 and a loop compensation network 184. And a portion of the L-number generator 186. In another example, the power stage includes at least a logic control element ===, a gate driver 19A, and a gate driver 190 and an output terminal for outputting a voltage V. The overall transfer function to the path is determined by the transfer function of the control stage and the transfer function of the power stage. For a power conversion system, the transfer function of the power stage is:
ZpowcXS)^^-X ^+ResrXC0XS D l + ^-xs 2 (等式5) 其中，R。表示輸出電阻，C。表示輸出電容，並且心紅表示與輸出電容 聯的電阻。料’ s等於j®，並且ω是角頻率，通常簡稱為頻率。此外， D表示調變信號187的工作週期。 基於等式5，電源級在頻域中的極點位置為： .、 2 pi (等式6) 因此，對於給定的c。，極點位置的頻率隨著輸出電阻而改變。另外， 電源級在頻域中的零點位置為： 201208242 w ° (等式7) 通常ReSr非常小，因此ωζ1通常比ωρ1大得多。 圖4和圖5各自顯示反激式電源變換系統100的電源級的簡化傳統波 德圖。 如上面討論，電源級和控制級是回饋迴路的前向路徑的部分。回饋迴 路可由穩定性和動態性來表徵，這兩者對於反激式電源變換系統的初級側 感測和調整通常是很重要的。 因此極希望改進初級側感測和調整的技術。 【發明内容】 本發明涉及積體電路。更具體地，本發明提供了用於初級側感測和調 整的系統和方法。僅僅作為示例，本發明已應用於反激式電源變換器。但 是將認識到，本發明具有較寬廣範圍的應用。 根據一個實施例，一種用於調整電源變換系統的輸出電壓的系統包括 耦合到電容器的誤差放大器。該誤差放大器配置以接收參考電壓、第一電 壓和調節電流並且與電容器一起產生補償電壓。該第一電壓與回饋電壓相 關聯。另外’該系統包括··電流產生器，配置以接㈣償電壓並且產生調 節=流和第-電流；以及餓產生器，配置以接收第—電流和第二電流。 該信號產生ϋϋ配置以減翻電壓並產生觀信號。此外，鮮〜統包括： 閉驅動器’ Ί亥間驅動器直接4間接軸合到信號產&器並且酉己置以至少基 於與調變親相Μ的資訊產生鶴親；以及開關，配置以接收驅動$ j並且影料經與她繞組她合的初級繞_她電m級繞^ ^源變換⑽的輸出龍和輸出電流相_，並且該獅變⑽統至 曰Γ級和次級繞組。該回饋電屢至少取決於輸出鎌和輸出電流，並 還於初級電流。該誤差放大器至少由-跨導來表徵並且 菩雷基翻㈣流相__f訊纽變該跨導，並且該跨導隨 系統的輸㈣減㈣小，如，爾_電源變換ZpowcXS)^^-X ^+ResrXC0XS D l + ^-xs 2 (Equation 5) where R is. Indicates the output resistance, C. Indicates the output capacitor and the red heart indicates the resistance associated with the output capacitor. The material 's is equal to j®, and ω is the angular frequency, often referred to simply as frequency. Further, D represents the duty cycle of the modulation signal 187. Based on Equation 5, the pole position of the power stage in the frequency domain is: ., 2 pi (Equation 6) Therefore, for a given c. The frequency of the pole position changes with the output resistance. In addition, the zero position of the power stage in the frequency domain is: 201208242 w ° (Equation 7) Usually ReSr is very small, so ωζ1 is usually much larger than ωρ1. 4 and 5 each show a simplified conventional Bode diagram of the power stage of the flyback power conversion system 100. As discussed above, the power stage and control stage are part of the forward path of the feedback loop. The feedback loop can be characterized by stability and dynamics, both of which are often important for primary side sensing and adjustment of the flyback power conversion system. It is therefore highly desirable to improve the techniques of primary side sensing and adjustment. SUMMARY OF THE INVENTION The present invention relates to an integrated circuit. More specifically, the present invention provides systems and methods for primary side sensing and adjustment. Merely by way of example, the invention has been applied to flyback power converters. However, it will be appreciated that the invention has a wide range of applications. According to one embodiment, a system for adjusting an output voltage of a power conversion system includes an error amplifier coupled to a capacitor. The error amplifier is configured to receive a reference voltage, a first voltage, and a regulated current and to generate a compensation voltage with the capacitor. The first voltage is associated with the feedback voltage. Further, the system includes a current generator configured to recharge (4) the voltage and generate a regulation = current and a first current; and a hungry generator configured to receive the first current and the second current. This signal produces a chirp configuration to reduce the voltage and generate a viewing signal. In addition, the fresh ~ system includes: Closed drive ' Ί 间 drive directly 4 indirectly coupled to the signal production & and has been set to generate at least based on information related to the modulation of the relatives; and switches, configured to receive Drive $ j and the shadow is passed through the primary winding with her windings. She outputs the output dragon and the output current phase _, and the lion becomes (10) to the 曰Γ and secondary windings. This feedback depends on at least the output 镰 and output current, and also on the primary current. The error amplifier is characterized by at least a transconductance and the Boolean (four) flow phase __f signal changes the transconductance, and the transconductance is small (four) minus (four) with the system, such as, _ power conversion
括:=放J 201208242 饋電壓相關聯。另外，該方法包括：處理與參考電壓、第一電壓和調節電 流相關聯的資訊；由耦合到電容器的誤差放大器產生補償電壓；接收補償 電壓；以及至少基於與補償電壓相關聯的資訊來產生調節電流和第一電 流。此外，該方法包括：接收第一電流、第二電流和感測電壓；至少基於 與第一電流、第二電流和感測電壓相關聯的資訊來產生調變信號；處理與 調變信號相關聯的資訊；以及至少基於與調變信號相關聯的資訊來產生驅 動信號。該方法還包括接收驅動信號並且至少基於與驅動信號相關聯的資 訊來影響初級電流。該初級電流流經與次級繞組相搞合的初級繞組。該次 級繞組與電源變換系統的輸出電壓和輸出電流相關聯。該回饋電壓至少取 決於輸出電壓和輸出電流，並且該感測電壓至少取決於初級電流。該誤差 放大器至少由一跨導來表徵。用於處理與參考電壓、第一電壓和調節電流 相關聯的資訊的步驟包括：至少基於與調節電流相關聯的資訊來改變該跨 導。該跨導隨著電源變換系統的輸出電流的減小而減小。例如，該跨導還 隨著電源變換系統的輸出電流的增大而增大。 根據又-實侧，-刻於機電麵換彡_輸出霞的系統包括 通過第-開Μ接地麵合到電容器的誤差放大器。該誤差放Α||配置以接 收參考電壓和第-電壓，並且如果第__接通則與電容器產生補 電壓。該第-電壓與回饋電壓相關聯。另外，該系統包括：第—開關，至 =^到誤差放大器和電容n ;以及信號產生器，配置以接收補償電壓和 一電流。該信號產生器還配置以接收感測電壓並產 =還包括:邏輯控制元件，配置以接收調變信號並且至上=變 4相關聯的賴緑生㈣健；，配置以接 酉少基於與控制信號侧聯的f訊產生驅動信號；以及且 丈置=收驅動信號並且影響流經與次級繞組_合的初級繞組的初二 =^級繞組與電源變換系統的輸出電壓和輸出電流相_，並且該電 少==次級繞組。該回饋觀少取心 換頻率來表徵。該第一開關配置以受控制信號控制i夕卜 低準位，===’㈣―開嶋，ω糊信號為邏輯 根據又-實施例，-種用於調整電源變換系統的輸出電壓的方法包括 201208242 由誤差放大器接收參考電壓和第—電壓。該第—電壓與回饋電壓相關聯， 並且誤差放大器通過第一開關間接地耦合到電容器。另外，該方法勺 處理與參考電壓和第—《相_的資訊；如果第-聊接通，則=誤差 放大器與電容[起產生補償電壓；接收補償電壓、第—電流和感測麼. ^及至少基於與補償電壓、第—電流和感測電壓相_的資訊來產生調變 «。此外’該方法包括：處理與調變信號相關聯的資訊；至少基於 變信號相關聯的資訊來產生控制信號；處理與控制信號相關聯的資訊;、至 =基於與控繼肋關聯的f訊來產生驅動信號；以及至少基於與驅動作 说相關聯的資絲影響她電流。該初級電献_次魏_輕合的; 。該次級繞组與電源變齡統的輸出電壓和輪出電流相關聯。該回 =壓=取決於輸出電壓和輸出較，並且該_電壓至少取決於初級 =。該㈣信號至少由脈誠度和切換解來表徵。驗處理與控制作 號相關聯的賴的步驟包括：如果控繼號為邏輯高準位，則接 ^ 關，並且如果控制信號為邏輯低準位，則斷開第一開關。 开 =又-實施例…·於調整電源變齡統的輸出電壓的系統包括 地耗合到電容器的誤差放大器。該誤差放大器配置以接 償電壓。該第一電壓與回饋糖目關聯。另外!統=器=補 峨大器和電容器;以及信號產生器，配置以接【補=壓 = 信號產^還配置以接收感測電壓並產生調變信號。此外， 電源統至少包括初峨組和次級触。該回饋電壓至 口輸出電流’並且該感測籠至少取決於初級電流。該 脈衝寬度和第—切換頻率來表徵。該單擊信號至少由 Ϊ二切換ΐ率來表徵。該第二脈衝寬度是由單擊產生器確 並且a亥第一切換鮮等於第一切換頻率。該第一開關配置以受 201208242 單擊fs號控制。如果單擊信號為邏輯高準位，則第一開關接通，並且如果 單擊信號為邏輯低準位，則第一開關斷開。 根據又-實施例種用於調整電源變齡統的輸出電壓的方法包括 由誤差放大器接收參考電壓和第—電[該第—電壓與回饋電壓相關聯， 並且誤差放大器通過第一開關間接地耦合到電容器。另外，該方法包括： 處理與參考電壓和第—電壓相_的資訊；如果第—剩接通，則由誤差 放大器與電容H-起產生補償電壓；接收補償電壓H流和感測電星； 以及至少基於與爾賴、第―電流和制霞蝴_資減生調變信 號。此外’該方法包括：處理與調變信號相關聯的資訊；至少基於與調^ 信號相Μ的資訊產生控娜號；處理與控制錢侧聯的魏；以及至 =、基於與控制信號相關聯的資訊產生單擊信號和藤動信號。此外，該方法 ^ :基於與單擊信號相關聯㈣訊調節第—觸；以及至少基於與驅動 的資絲辟她錢，該她紐赫與纽繞組她合的 ΓΪΪί。触級繞轉魏變換纽的輸4龍和輸出電油關聯。該 』^至>取決於輸出電壓和輸出電流，並且該細電壓至少取決於初 罝控制信號至少由第"'脈衝寬度和第—_頻率來表徵，並且該 由ίΐίί 寬度和第二切換頻率來表徵。該第二脈衝寬度是 ±斋確疋的常數’並且該第二切換頻率等於第一切換頻率 第一開關。 幵哥並且如果單擊信號為邏輯低準位，則斷開 與傳統技術相比通過本發明獲得了許多 供:具有跨導的誤差放大器，該跨導 二提 :;小並且隨著電源變換系統的輸出電流的增電 點位置在頻率上低於電源級制級=源=控制級的零 的組合的增益曲線在增益‘等於0 C1B的位置處具有 1 dB/d=^電Γ 一示例中，該電源變換系統在⑼的解°在又 裕’從而確保了從滿負載條件到：載口:置足夠的相位餘 的-些實施例在所有負載條载^牛^回饋迴路的穩定性。本發明 性。 、^镇〈路k供了良好的動態性和穩定 9 201208242 取決於實施例，可以獲得這些益處中的一個或多個。參考下面的詳細 描述和附圖可以全面地理解本發明的這些益處以及各個另外的目的、特徵 和優點。 【實施方式】 本發明涉及積體電路。更具體地，本發明提供了用於初級側感測和調 整的系統和方法。僅僅作為示例，本發明已應用於反激式電源變換器。但 是將認識到，本發明具有寬得多的應用範圍。 、圖6是顯示根據本發明實施例之用於開關模式反激式電源變換系統的 初級側感測和調鶴統賴化賴。該示圖僅僅是示例，其不應當不當地 限制U利範圍的範_。熟知該項技術領域之人將認識到許彡變體 換和修改。 根據—個實施例’用於初級側感測和調整的祕_包括至少具有電 ，級65G的回饋迴路。例如’電源級㈣具有如等式5所述的傳輸函數 j〇wer(s)。在另一示例中，電源級65〇具有頻域中的極點位置％和頻域中的 零點位置ωζ ’如分別由等式6和等式7所描述。 杜2據另一實施例，系，统_至少還包括控制級，該控制級包括跨導元 :=、622和624，電容元件63〇以及加法元件 如 ===統_的誤差放大器— Ζ control (s): :3:Include: = put J 201208242 feed voltage associated. Additionally, the method includes: processing information associated with a reference voltage, a first voltage, and a regulated current; generating a compensation voltage by an error amplifier coupled to the capacitor; receiving a compensation voltage; and generating an adjustment based on at least information associated with the compensation voltage Current and first current. Moreover, the method includes receiving a first current, a second current, and a sensing voltage; generating a modulated signal based on at least information associated with the first current, the second current, and the sensing voltage; processing is associated with the modulated signal Information; and generating a drive signal based at least on information associated with the modulated signal. The method also includes receiving a drive signal and affecting the primary current based at least on the information associated with the drive signal. The primary current flows through a primary winding that engages the secondary winding. The secondary winding is associated with the output voltage and output current of the power conversion system. The feedback voltage depends at least on the output voltage and the output current, and the sense voltage is at least dependent on the primary current. The error amplifier is characterized by at least a transconductance. The step of processing information associated with the reference voltage, the first voltage, and the regulated current includes altering the transconductance based at least on information associated with the regulated current. The transconductance decreases as the output current of the power conversion system decreases. For example, the transconductance also increases as the output current of the power conversion system increases. According to the yet-solid side, the system engraved on the electromechanical surface _ output Xia includes an error amplifier that is coupled to the capacitor through the first-opening ground plane. The error is set to || receive to receive the reference voltage and the first voltage, and if the __ is turned on, a complementary voltage is generated with the capacitor. The first voltage is associated with the feedback voltage. Additionally, the system includes a first switch, to =^ to the error amplifier and capacitor n, and a signal generator configured to receive the compensation voltage and a current. The signal generator is further configured to receive the sensed voltage and further include: a logic control element configured to receive the modulated signal and to the upper = change 4 associated with the green (four) health; configured to interface with less control The signal side of the signal generates a drive signal; and the set = receive drive signal and affects the output voltage and output current phase of the primary and secondary windings of the primary winding flowing through the secondary winding and the power conversion system And the less electricity == secondary winding. This feedback is characterized by a small change in frequency. The first switch is configured to be controlled by the control signal, and the ω paste signal is a logic according to another embodiment, and the method for adjusting the output voltage of the power conversion system Including 201208242 The reference voltage and the first voltage are received by the error amplifier. The first voltage is associated with the feedback voltage and the error amplifier is indirectly coupled to the capacitor through the first switch. In addition, the method spoon handles the information with the reference voltage and the first - "phase_; if the first-talk is connected, then = error amplifier and capacitor [from generating the compensation voltage; receiving the compensation voltage, the first current and the sensing. ^ And generating a modulation « based on at least information related to the compensation voltage, the first current, and the sense voltage. In addition, the method includes: processing information associated with the modulated signal; generating a control signal based on at least information associated with the variable signal; processing information associated with the control signal; and = being based on the associated information Generating a drive signal; and affecting her current based at least on the wire associated with the drive. The primary electricity contribution _ times Wei _ light combined; The secondary winding is associated with the output voltage and the wheel current of the power supply age. The return = voltage = depends on the output voltage and the output comparison, and the _ voltage depends at least on the primary =. The (iv) signal is characterized by at least the pulse integrity and the switching solution. The steps associated with the control process are as follows: if the control number is a logic high level, then the switch is turned off, and if the control signal is at a logic low level, the first switch is turned off. On = again - embodiment... The system for adjusting the output voltage of the power supply age includes an error amplifier that is grounded to the capacitor. The error amplifier is configured to compensate for the voltage. The first voltage is associated with a feedback sugar. In addition, the system=compensation amplifier and capacitor; and the signal generator are configured to receive [compensation = voltage = signal generation) and are also configured to receive the sensing voltage and generate a modulation signal. In addition, the power system includes at least a primary group and a secondary touch. The feedback voltage to the port output current 'and the sense cage depends at least on the primary current. The pulse width and the first-switching frequency are characterized. The click signal is characterized by at least a second switching rate. The second pulse width is determined by the click generator and the first switch is equal to the first switching frequency. The first switch configuration is controlled by 201208242 by clicking the fs number. If the click signal is at a logic high level, the first switch is turned "on" and if the click signal is at a logic low level, the first switch is turned off. According to yet another embodiment, a method for adjusting an output voltage of a power supply age includes receiving a reference voltage and a first voltage by an error amplifier [the first voltage is associated with a feedback voltage, and the error amplifier is indirectly coupled through the first switch To the capacitor. In addition, the method includes: processing information related to the reference voltage and the first voltage phase; if the first-remaining is turned on, generating a compensation voltage by the error amplifier and the capacitor H-; receiving the compensation voltage H current and sensing the electric star; And at least based on the relationship between Erlai, the first current and the xiaxia. In addition, the method includes: processing information associated with the modulated signal; generating a control number based on at least information related to the modulated signal; processing and controlling the money side of the Wei; and up to, based on the associated control signal The information generates a click signal and a vine motion signal. In addition, the method ^: is based on the association with the click signal (four) to adjust the first touch; and at least based on the money with the driver, she is the same as the new one. The touch-level turns around the Wei-transform New Zealand's 4 dragons and outputs electric oil. The 』^至> depends on the output voltage and the output current, and the fine voltage is at least dependent on the initial control signal being characterized by at least the "pulse width and the -_ frequency, and the width is switched by ίΐίί and the second Frequency to characterize. The second pulse width is a constant of ± 疋 疋 and the second switching frequency is equal to the first switching frequency of the first switch.幵哥 and if the click signal is at a logic low level, the disconnection is obtained by the present invention compared to conventional techniques: an error amplifier with transconductance, which is small and follows the power conversion system The gain point of the output current is lower than the power stage level = source = control level of the zero gain curve at the gain 'equal to 0 C1B where there is 1 dB / d = ^ power Γ in the example The power conversion system in (9) solves the problem in the sufficiency of ''and thus ensures the stability from the full load condition to: the carrier: set enough phase residuals - some embodiments in all load strips. The present invention. , ^ town < road k for good dynamics and stability 9 201208242 Depending on the embodiment, one or more of these benefits can be obtained. These and other additional objects, features and advantages of the present invention will be fully understood from the description and appended claims appended claims. [Embodiment] The present invention relates to an integrated circuit. More specifically, the present invention provides systems and methods for primary side sensing and adjustment. Merely by way of example, the invention has been applied to flyback power converters. However, it will be appreciated that the invention has a much broader range of applications. Figure 6 is a diagram showing the primary side sensing and the modulating system of the switch mode flyback power conversion system according to an embodiment of the present invention. This diagram is merely an example and should not unduly limit the scope of the U-scope. Those skilled in the art will recognize and modify the modifications. The secret for primary side sensing and adjustment according to an embodiment includes a feedback loop having at least an electrical, stage 65G. For example, the power stage (4) has a transfer function j〇wer(s) as described in Equation 5. In another example, the power stage 65A has a pole position % in the frequency domain and a zero position ω ζ ' in the frequency domain as described by Equation 6 and Equation 7, respectively. According to another embodiment, the system further includes at least a control stage including transconductance elements: =, 622, and 624, a capacitive element 63 〇, and an adder element such as an error amplifier of === _ Control (s): :3:
sxC (等式8) 因此，傳輸級在頻域中的零點位置為： 和控顯示在刪載條件下具有常數g』電源級 輸出電^。、中等輸出電流和大輪出電流！。表示。在另-示 201208242 例中，組合傳輸函數等於電源級的傳輸函數乘以控制級的傳輸函數。 如圖7(c)所示’對於重負載，在頻率上極點位置ωρΐ高於零點位置ω^。 此外，增益曲線710在點A1處與水平軸相交，在〇犯處具有_2〇 dB/dec 的斜率。點A1與相位曲線712上的點J1相對應❶因此，點π具有離_18〇。 大於90°的相位。因此，回饋迴路是穩定的。 如圖7 (b)所示，對於中等負載，在頻率上極點位置ωρΐ低於零點位 置〇)z2。此外，增益曲線720在點Β1處與水平軸相交，在〇 dB處具有-40 dB/dec的斜率。點B1與相位曲線722上的點K1相對應。因此，點K1具 有離-180°小於90°的相位。因此，回鎖迴路不穩定。 類似的，如圖7 (a)所示，對於輕負載，在頻率上極點位置ωρΐ低於 零點位置①^。此外，增益曲線730在點m處與水平軸相交，在〇犯處具 有-40 dB/dec的斜率。點E1與相位曲線732上的點L1相對應。因此，點 L1具有離-180。小於90。的相位。因此，回鑛迴路不穩定。 根據一個實施例，提高回饋迴路穩定性的一種方式是增大補償電容C。 因此，增益曲線710、720和730在〇 dB時例如在非常低的頻率處與水平 軸相交，這使得所有負載條件保持離_18〇。的足夠相位餘裕。但是大的補償 電容C可能導致低的迴路頻寬，並且因此導致差的動態性。 根據另一實施例，為了使回饋迴路穩定，零點位置的頻率ωζ2應當隨負 載條件改變，因為根據等式6，極點位置的頻率ωρ1隨著負載條件改變。例 如，如等式9所述，藉由隨著降低負載而減小gmi來減小零點位置ωζ2的頻 率。在另一示例中，在所有負載條件下，極點位置ωρΐ的頻率保持高於零點 位置0½。根據又一實施例，增益也隨著降低gmi而減小。 圖8 (a)、（b)和（c)是顯示根據本發明實施例之具有隨著負載的減 小而減小的gml的電源級和控制級的組合傳輸函數的簡化波德圖。具體地， 圖8 (a)、（b)和（c)分別對應於輕負載、中等負載和重負載。例如，輕 負載、中等負載和重負載分別由小輸出電流I。、中等輸出電流j。和大輸出 電流I。表示。在另一示例中，組合傳輸函數等於電源級的傳輸函數乘以控 制級的傳輸函數。 如圖8( c )所示’對於重負載’在頻率上極點位置％〗高於零點位置ωώ。 此外’增益曲線810在點Α2處與水平轴相交，例如在〇犯處具有_2〇 dB/dec 的斜率。點A2與相位曲線812上的點J2相對應。根據一個實施例，點J2 201208242 具有離180大於90。的相位。因此，例如，回饋迴路對於重負載是穩定的。 似地’如圖8 (b)所示’對於中等負載，在頻率上極點位置ωρ1也 向於零點錄。增益鱗82G在點m触水平_交，例如在議處 ，有40 dB/dec的斜率。點Β2與相位曲線822上的點κ2相對應。根據另 實施例‘點Κ2具有離_18〇。大於9〇。的相位。因此，例如，回饋迴路對於 中等負載是穩定的。 類似地’如圖8 (a)所示’對於輕負載，在頻率上獅位置ωρ1也高 於零點位置啦。増益曲線83G在點Ε2處與水平軸相交例如在祕處具 有-40 dB/dec的斜率。點Ε2與相位曲線832上的點L2相對應。根據另一個 實施例’點L2具有離_18〇。大於9〇。的相位。因此，例如，回鑛迴路對於輕 負載是穩定的。 圖9是顯不根據本發明另一實施例之用於開關模式反激式電源變換系 ^的初級側，測和調録制簡化稍。齡圖健是賴，其不應當不 當地限制申請專利範圍的範.。熟知該項技術領域之人將認識到許 體、替換和修改。 。。在-個實施例中’反激式電源變換系統·包括電源開關92()、感測電 阻，930、採樣保持元件980、誤差放大器982、pWM/pFM信號產生器986、 邏，控制元件988、閘驅動器990、電容器954、電流|生器952以及前向 饋达（feedforward)元件962。例如，電源開關920、感測電阻器93〇、採 樣保持元件980、邏輯控制元件988以及閉驅動器_分別與電源開關12〇、 感測電阻If 13G、採樣保持元件18〇、邏輯控制元件188以及閘驅動器19〇 相同。在另一示例中，PWM/PFM信號產生器986與pwM/pFM信號產生 β 186相同。 在另一實施例中，反激式電源變換系統9〇〇還包括變壓器丨1〇、電镜電 2器140、電阻器170和172、二極體160和168、電容器196和198，其 皆於圖1中示出。例如，變愿器11〇包括初級繞組112、次級繞組114和輔 助繞組116。 如圖6和圖9所示，根據一個實施例，誤差放大器982包括減法元件 610和跨導元件62〇。在另一實施例令，前向馈送元件962對應於跨導元件 622。在又一實施例中，電容器954對應於電容元件63〇，並且電流產生器 952對應於跨導元件624。在又一實施例令，用於相加電流&和h的節點96^ 12 201208242 與加法元件640相對應。 在一個實施例中，回饋電壓VFB由採樣保持元件980接收。例如，在 接近退磁過程的結尾處當次級電流變得接近零時，回饋電壓Vi?b被採樣， 並且經採樣的電壓VA隨後由元件980保持直到下一採樣為止。在另一示例 中，經採樣的電壓VA由誤差放大器982接收，誤差放大器982將經採樣的 電壓VA與參考電壓Vref相比較，並且還放大\^與Vref之間的差值。 在另一實施例中，誤差放大器982與電容器954 —起將補償電壓984 發送給電流產生器952。作為回應，電流產生器952產生電流1^和1丨。例 如，電流Iea流入或流出誤差放大器982。在另一示例中，電流I〗流入節點 964並被加到電流I2中，並且這兩個電流之和流入pw^ypFM信號產生器 986。 。 在又一實施例中’電流I2由前向饋送元件962產生，前向饋送元件962 接收並處理經採樣的電壓VA和參考電壓Vref。例如，電流^和12具有不同 相位。在又一示例中，PWM/PF1V[信號產生器986還從感測電阻器93〇接 收感測電壓932，感測電阻器930將流經初級繞組112的初級電流變換為感 測電壓。 如圖9所示，根據一個實施例，響應於電流Iea，誤差放大器982改變 其跨導gml。例如，補償電壓反映負載條件，如圖3所示。在另一示例中， 補償電壓用來經由電流IEA控制誤差放大器982的跨導gml。 根據一個實施例，藉由隨著降低的負載而減小gml從而在頻率上減小系 統900的零點位置ωζ2，如等式9所述。例如，增益也隨著gmi的降低而減 小。在另一示例中，極點位置ωρ1在所有負載條件下之頻率上保持高於零點 位置0½。 如圖9所示，PWM/PFM信號產生器986將調變信號987輸出給邏輯 控制元件988，邏輯控制元件988將控制信號989發送給閘驅動器99〇。根 據一個實施例，作為回應，閘驅動器990將驅動信號992發送給電源開關 920。 圖10(a)是顯示根據本發明一個實施例之用於開關模式反激式電源變 換系統900的誤差放大器982、電容器954和電流產生器952的簡化示圖。 該示圖僅僅是示例，其不應當不當地限制申請專利範圍的範疇。熟知該項 技術領域之人將認識到許多變體、替換和修改。 13 201208242 如圖10 (a)所示’誤差放大器982與電容器954 —起將補償電壓984 發送給電流產生器952。根據一個實施例，作為回應，電流產生器952產生 電流Iea和1〗。例如，電流Iea流出誤差放大器982。在另一示例中，電流 Ιι流出誤差放大器982。 ~ 根據一個實施例’ Ιι隨著VCMnp的增大而減小，並且ι]隨著乂⑶师的減 小而增大。根據另一實施例’誤差放大器982改變其跨導gml以響應電流 Iea。例如，補償電壓984隨著輸出電流I。的減小而減小。在另一示例中， 電流Iea隨著補償電壓984的減小而增大。在又一示例中，如圖1〇 (心所 示， (等式10)sxC (Equation 8) Therefore, the zero position of the transmission stage in the frequency domain is: and the control display has a constant g" power stage output power ^ under the condition of deletion. Medium output current and large wheel current! . Said. In the other example, 201208242, the combined transfer function is equal to the transfer function of the power stage multiplied by the transfer function of the control stage. As shown in Fig. 7(c), for a heavy load, the pole position ωρΐ is higher than the zero position ω^ on the frequency. In addition, the gain curve 710 intersects the horizontal axis at point A1 and has a slope of _2 〇 dB/dec at the smuggling. Point A1 corresponds to point J1 on phase curve 712. Therefore, point π has a distance of _18 〇. A phase greater than 90°. Therefore, the feedback loop is stable. As shown in Fig. 7(b), for a medium load, the pole position ωρΐ is lower than the zero position 〇)z2 at the frequency. In addition, gain curve 720 intersects the horizontal axis at point ,1 with a slope of -40 dB/dec at 〇 dB. Point B1 corresponds to point K1 on phase curve 722. Therefore, the point K1 has a phase of -180° less than 90°. Therefore, the lockback loop is unstable. Similarly, as shown in Fig. 7(a), for a light load, the pole position ωρΐ is lower than the zero position 1^ on the frequency. In addition, the gain curve 730 intersects the horizontal axis at point m and has a slope of -40 dB/dec at the sin. Point E1 corresponds to point L1 on phase curve 732. Therefore, the point L1 has an off-180. Less than 90. The phase. Therefore, the return loop is unstable. According to one embodiment, one way to increase the stability of the feedback loop is to increase the compensation capacitance C. Thus, gain curves 710, 720, and 730 intersect the horizontal axis at 〇 dB, such as at very low frequencies, which keeps all load conditions away from _18 〇. Sufficient phase margin. However, a large compensation capacitor C may result in a low loop bandwidth and thus a poor dynamics. According to another embodiment, in order to stabilize the feedback loop, the frequency ω ζ 2 of the zero position should be changed with the load condition because the frequency ωρ1 of the pole position changes according to the load condition according to Equation 6. For example, as described in Equation 9, the frequency of the zero position ω ζ 2 is reduced by decreasing gmi as the load is reduced. In another example, the frequency of the pole position ωρΐ remains above the zero position 01⁄2 under all load conditions. According to yet another embodiment, the gain also decreases as the gmi is lowered. 8(a), (b) and (c) are simplified Bode diagrams showing a combined transfer function of a power supply stage and a control stage having a gml which decreases as the load decreases, in accordance with an embodiment of the present invention. Specifically, Figures 8(a), (b), and (c) correspond to light load, medium load, and heavy load, respectively. For example, light load, medium load, and heavy load are respectively output current I by small. Medium output current j. And large output current I. Said. In another example, the combined transfer function is equal to the transfer function of the power stage multiplied by the transfer function of the control stage. As shown in Fig. 8(c), 'for heavy loads', the pole position % is higher than the zero position ω 在 at the frequency. Furthermore, the 'gain curve 810 intersects the horizontal axis at point , 2, for example with a slope of _2 〇 dB/dec at the smuggler. Point A2 corresponds to point J2 on phase curve 812. According to one embodiment, point J2 201208242 has a distance greater than 90 from 180. The phase. Thus, for example, the feedback loop is stable to heavy loads. Similarly, as shown in Fig. 8(b), for a medium load, the pole position ωρ1 is also recorded at the zero point on the frequency. The gain scale 82G touches the horizontal _ intersection at point m, for example at the conference, with a slope of 40 dB/dec. Point 2 corresponds to point κ2 on phase curve 822. According to another embodiment, the point 2 has a distance of _18 。. More than 9 inches. The phase. Thus, for example, the feedback loop is stable to moderate loads. Similarly, as shown in Fig. 8(a), for a light load, the lion position ωρ1 is also higher than the zero position at the frequency. The gain curve 83G intersects the horizontal axis at point 例如 2, for example, at a secret point with a slope of -40 dB/dec. Point 2 corresponds to point L2 on phase curve 832. According to another embodiment, point L2 has a distance of _18 〇. More than 9 inches. The phase. Thus, for example, the return mine loop is stable to light loads. Fig. 9 is a view showing a simplified side of a switching mode flyback power conversion system according to another embodiment of the present invention. The age chart is a Lai, and it should not unduly restrict the scope of the patent application. Those skilled in the art will recognize the modifications, substitutions, and modifications. . . In one embodiment, a 'flyback power conversion system includes a power switch 92 (), a sense resistor, 930, a sample and hold element 980, an error amplifier 982, a pWM/pFM signal generator 986, a logic, a control element 988, Gate driver 990, capacitor 954, current | generator 952, and feedforward element 962. For example, the power switch 920, the sense resistor 93A, the sample and hold element 980, the logic control element 988, and the shutdown driver _ are respectively connected to the power switch 12A, the sense resistor If 13G, the sample and hold element 18, the logic control element 188, and The gate driver 19 is the same. In another example, PWM/PFM signal generator 986 is identical to pwM/pFM signal generation β 186. In another embodiment, the flyback power conversion system 9A further includes a transformer 〇1〇, an electron microscope heater 140, resistors 170 and 172, diodes 160 and 168, capacitors 196 and 198, both of which are This is shown in Figure 1. For example, the torque converter 11A includes a primary winding 112, a secondary winding 114, and an auxiliary winding 116. As shown in Figures 6 and 9, error amplifier 982 includes subtraction element 610 and transconductance element 62, according to one embodiment. In another embodiment, the forward feed element 962 corresponds to the transconductance element 622. In yet another embodiment, capacitor 954 corresponds to capacitive element 63A and current generator 952 corresponds to transconductance element 624. In still another embodiment, the node 96^12 201208242 for summing current & and h corresponds to the summing element 640. In one embodiment, the feedback voltage VFB is received by the sample and hold element 980. For example, when the secondary current becomes near zero at the end of the near demagnetization process, the feedback voltage Vi?b is sampled and the sampled voltage VA is then held by element 980 until the next sample. In another example, the sampled voltage VA is received by an error amplifier 982 that compares the sampled voltage VA to a reference voltage Vref and also amplifies the difference between <RTIgt; In another embodiment, error amplifier 982, along with capacitor 954, sends a compensation voltage 984 to current generator 952. In response, current generator 952 produces currents 1^ and 1丨. For example, current Iea flows into or out of error amplifier 982. In another example, current I is flowing into node 964 and added to current I2, and the sum of the two currents flows into pw^ypFM signal generator 986. . In yet another embodiment, current I2 is generated by forward feed element 962, which receives and processes sampled voltage VA and reference voltage Vref. For example, currents ^ and 12 have different phases. In yet another example, PWM/PF1V [Signal Generator 986 also receives sense voltage 932 from sense resistor 93, which converts the primary current flowing through primary winding 112 into a sense voltage. As shown in Figure 9, in accordance with one embodiment, error amplifier 982 changes its transconductance gml in response to current Iea. For example, the compensation voltage reflects the load conditions, as shown in Figure 3. In another example, the compensation voltage is used to control the transconductance gml of the error amplifier 982 via the current IEA. According to one embodiment, the zero position ω ζ 2 of the system 900 is reduced in frequency by decreasing gml with reduced load, as described in Equation 9. For example, the gain also decreases as the gmi decreases. In another example, the pole position ωp1 remains above the zero position 01⁄2 at all frequencies under load conditions. As shown in Figure 9, PWM/PFM signal generator 986 outputs modulated signal 987 to logic control component 988, which sends control signal 989 to gate driver 99A. In response, gate driver 990 transmits drive signal 992 to power switch 920, in response. Figure 10 (a) is a simplified diagram showing an error amplifier 982, capacitor 954 and current generator 952 for a switched mode flyback power conversion system 900, in accordance with one embodiment of the present invention. This illustration is only an example and should not unduly limit the scope of the claimed patent. Those skilled in the art will recognize many variations, substitutions and modifications. 13 201208242 As shown in FIG. 10(a), the error amplifier 982 transmits the compensation voltage 984 to the current generator 952 together with the capacitor 954. In response, in response, current generator 952 produces currents Iea and 1'. For example, current Iea flows out of error amplifier 982. In another example, current Ι flows out of error amplifier 982. ~ According to one embodiment, Ιι decreases as VCMnp increases, and ι] increases as the 乂(3) division decreases. According to another embodiment, the error amplifier 982 changes its transconductance gml in response to the current Iea. For example, the compensation voltage 984 follows the output current I. The decrease is reduced. In another example, current Iea increases as compensation voltage 984 decreases. In yet another example, as shown in Figure 1 (indicated by the heart, (Equation 10)
Smx α bias-Iea 其中，1細8表示由電流源產生的恒定電流，並且〜是由誤差放大器982 的某些元件的特性確定的常數。根據本發明一個實施例，基於等式10，誤 差放大器982的gm]隨著電流IEA的增大並且因此隨著輸出電流I。（也稱為 負載電流）的減小而減小。例如，電流IEA隨著輸出電流的減小而增大並且 隨著輸出電流的增大而減小，因此，誤差放大器982的gml隨著輸出負载條 件改變，從而在所有負載條件下使得零點位置ωχ2保持低於極點位置。 圖10(b)是顯示根據本發明另一實施例之用於開關模式反激式電源變 換系統900的誤差放大器982、電容器954和電流產生器952的簡化示圖。 該示圖僅僅是賴’其福當;ί；當地限射請專職圍的齡。熟知該項 技術領域之人將認識到許多變體、替換和修改。 如圖10 (b)所示’誤差放大器982與電容器954 一起將補償電壓984 發送給電流產生器952。根據一個實施例，作為回應，電流產生器952產生 電流IEA和1】。例如’電流1^流入誤差放大器982。在又一示例中，電流 Ιι流出誤差放大器982。 ” 根據一個實施例，I!隨著Ve()mp的增大而減小，並且l隨著VeQmp的減 J、而增大。根據另一實施例，補償電壓984隨著輸出電流I。的減小而減小。 例如，電流IEA隨著補償電磨984的減小而增大。在另一示例中，如圖 (b)所示， (等式11) 其中，1恤3表示由電流源產生的恒定電流，並且恥是由誤差放大器982 201208242 的某些元件的特性確定的常數。根據本發明另一實施例，基於等式u，誤 差放大器982的gml隨著電流Iea的增大並且因此隨著輸出電流1。（也稱為 負，電流）的減小而減小。例如，電流Iea隨著輸出電流的減小而增大並且 隨著輸出電流的增大而減小，因此，誤差放大器982的gmi隨著輸出負載條 件改變，從而在所有負載條件下使得零點位置ωζ2保持低於極點位置叫丨。 圖10(c)是顯示根據本發明又一實施例之用於開關模式反激式電源變 換系統900的誤差放大器982、電容器954和電流產生器952的簡化示圖。 該示圖僅僅是示例，其不應當不當地限制申請專利範圍的範疇。熟知該項 技術領域之人將g忍識到許多變體、替換和修改。 如圖10 (c)所示，誤差放大器982與電容器954 一起將補償電壓984 發送給電流產生器952。根據一個實施例，作為回應，電流產生器952產生 電流IEA和I]。例如，電流Iea流入誤差放大器982。在又一示例中，電流 Ιι流出誤差放大器982。 & 根據-個實施例，I!隨著％。呵的增大而減小，並且⑽著v_p的減 小而增大。根據另一實施例’補償電壓984隨著輸出電流j。的減小而減小。 例如，電流IEA隨著補償電壓984的減小而減小。在另一示例中，如圖1〇 (c)所示，Smx α bias-Iea where 1 is 8 represents a constant current generated by a current source, and ~ is a constant determined by characteristics of certain elements of the error amplifier 982. According to an embodiment of the invention, based on Equation 10, the gm] of the error amplifier 982 increases with the current IEA and thus with the output current I. The reduction (also referred to as load current) decreases. For example, the current IEA increases as the output current decreases and decreases as the output current increases, so the gml of the error amplifier 982 changes with the output load condition, thereby causing the zero position ωχ2 under all load conditions. Keep below the pole position. Figure 10 (b) is a simplified diagram showing an error amplifier 982, a capacitor 954, and a current generator 952 for a switch mode flyback power conversion system 900 in accordance with another embodiment of the present invention. The map is only Lai's Fudang; ί; local limited shots, please be full-time. Those skilled in the art will recognize many variations, substitutions and modifications. As shown in FIG. 10(b), the error amplifier 982, together with the capacitor 954, sends a compensation voltage 984 to the current generator 952. In response, in response, current generator 952 produces currents IEA and 1]. For example, 'current 1^ flows into error amplifier 982. In yet another example, current Ι flows out of error amplifier 982. According to one embodiment, I! decreases as Ve() mp increases, and l increases as VeQmp decreases by J. According to another embodiment, compensation voltage 984 follows output current I. For example, the current IEA increases as the compensation electric grinder 984 decreases. In another example, as shown in (b), (Equation 11) where 1 shirt 3 represents current The constant current produced by the source, and shame is a constant determined by the characteristics of certain elements of error amplifier 982 201208242. According to another embodiment of the invention, based on equation u, the gml of error amplifier 982 increases with current Iea and Therefore, it decreases as the output current 1 (also referred to as negative, current) decreases. For example, the current Iea increases as the output current decreases and decreases as the output current increases, thus, The gmi of the error amplifier 982 changes with the output load condition, so that the zero position ω ζ 2 is kept below the pole position under all load conditions. Figure 10 (c) is a diagram showing the switch mode reverse according to still another embodiment of the present invention. The error amplifier 982 of the excitation power conversion system 900, A simplified illustration of a container 954 and a current generator 952. This illustration is merely an example and should not unduly limit the scope of the claimed scope. Those skilled in the art will recognize many variations, substitutions, and modifications. As shown in Figure 10(c), error amplifier 982, along with capacitor 954, sends a compensation voltage 984 to current generator 952. In response, in accordance with one embodiment, current generator 952 produces currents IEA and I]. For example, current Iea flows into error amplifier 982. In yet another example, current 流出 flows out of error amplifier 982. & According to one embodiment, I! decreases with increasing %, and (10) decreases with decreasing v_p According to another embodiment, the compensation voltage 984 decreases as the output current j. decreases. For example, the current IEA decreases as the compensation voltage 984 decreases. In another example, as shown in FIG. (c),
gn,l^^c^hi〇s+IEA (等式12) 其中，Ibias表示由電流源產生的恒定電流，並且〜是由誤差放大器982 的某些元件的特性確定的常數。根據本發明又一實施例，基於等式12，誤 差放大器982的gml隨著電流1以的減小並且因此隨著輸出電流i。（也稱為 負載電流）的減小喊小。例如，電流Iea隨著輸出電流的減小而減小並且 隨著輸出電流的增大而增大，因此，誤差放大器982的^隨著輸出負載條 件改變’從而在所有負載條件下使得零點位i啦保持低於極點位置％。 圖1〇⑷趟示根據本發明又一實施例之用於_模式反激式電源變 換系統900的誤差放大器982、電容器州和電流產生器松的簡化示圖。 該示圖僅僅是示例’其不應當不當地限制巾請專利範_範4。熟知該項 技術領域之人將認識到許多變體、替換和修改。 如圖10 (d)所示，誤差放大器982與電容器954 —起將補償電壓984 發送給電流產生器952。根據一個實施例，作為回應，電流產生器952產生 電流IEA和I!。例如，電流1从流出誤差放大器982。在又一示例中，電流 15 201208242Gn, l^^c^hi〇s+IEA (Equation 12) where Ibias represents a constant current generated by a current source, and ~ is a constant determined by the characteristics of certain elements of the error amplifier 982. In accordance with yet another embodiment of the present invention, based on Equation 12, the gml of the error amplifier 982 decreases with current 1 and thus with the output current i. The reduction in (also known as load current) is small. For example, the current Iea decreases as the output current decreases and increases as the output current increases, so the error amplifier 982 changes with the output load condition to make the zero point i under all load conditions. Keep it below the pole position %. 1(4) shows a simplified diagram of an error amplifier 982, a capacitor state, and a current generator loose for a _ mode flyback power conversion system 900 in accordance with yet another embodiment of the present invention. This diagram is merely an example 'it should not unreasonably limit the scope of the patent. Those skilled in the art will recognize many variations, substitutions and modifications. As shown in FIG. 10(d), error amplifier 982, along with capacitor 954, sends a compensation voltage 984 to current generator 952. In response, in response, current generator 952 produces currents IEA and I!. For example, current 1 flows from error amplifier 982. In yet another example, the current 15 201208242
IdA出誤差放大器982。 根據一個實施例，I!隨著 V comp 的增大而減小’並且I!隨著vec)mp的減 小而增大。根據另一實施例，補償電壓984隨著輸出電流I。的減小而減小。 例如’電流Iea隨著補償電壓984的減小而減小。在另一示例中，如圖 (d)所示， (等式13) 其中’ Ibias表示由電流源產生的恒定電流，並且仏是由誤差放大器982 的某些元件的特性確定的常數。根據本發明又一實施例，基於等式13，誤 差放大器982的gml隨著電流IEA的減小並且因此隨著輸出電流1。（也稱為 負載電流）的減小而減小。例如，電流Iea隨著輸出電流的減小而減小並且 隨著輸出電流的增大而增大’因此’誤差放大器982的gml隨著輸出負載條 件改變，從而在所有負載條件下使得零點位置ωζ2保持低於極點位置ωρΐ。' 圖11是顯示根據本發明又一實施例之用於開關模式反激式電源變換系 統900的誤差放大器982、電容器954和電流產生器952的簡化示圖。該示 圖僅僅是示例，其不應當不當地限制申請專利範圍的範疇。熟知該項技術 領域之人將認識到許多變體、替換和修改。 如圖11所示，誤差放大器982與電容器954 —起將補償電壓984發送 給電流產生器952。根據一個實施例，作為回應，電流產生器952產生電流 ΙΕΑ和I!。例如，電流1以流出誤差放大器982。在又一示例中，電流h流出 誤差放大器982。在又一示例中，誤差放大器982包括一個或多個 電晶體。 根據一個實施例，隨著VcOTnp的增大而減小，並且&隨著^。师的減 小而增大。根據另一實施例，補償電壓984隨著輸出電流j。的減小而減小。 例如，誤差放大器982的gml隨著補償電壓984的減小而減小。在另一示例 中’ gml隨輸出電流I。（也稱為負載電流）的減小而減小。 圖12是顯示根據本發明另一實施例之用於開關模式反激式電源變換系 統的初級側感測和調整系朗簡化示圖。該示圖僅僅是賴，其不應當不 當地限制_料利範gj的料。熟知翻技術領域之人將認識 體、替換和修改。 在-個實施例中’反激式電源變換系統U⑻包括電源開關122()、感測 電阻器1230、採樣保持耕128()、誤差放大器1282、pw]着fm信號產生 16 201208242 器1286、邏輯控制元件1288、閘驅動器1290、電容器1254、前向饋送元 件1262和開關1264。例如，電源開關1220、感測電阻器1230、採樣保持 元件1280、邏輯控制元件1288和閘驅動器1290分別與電源開關120、感 測電阻器130、採樣保持元件180、邏輯控制元件188以及閘驅動器190相 同。在另一示例中，PWM/PFM信號產生器1286基本上與PWM/PFM信號 產生器186相同。在又一示例中，誤差放大器1282與誤差放大器182相同。 在另一實施例中，反激式電源變換系統1200還包括變壓器110、電纜 電阻器140、電阻器170和172、二極體160和168、電容器196和198， 它們都在圖1中示出。例如’變壓器11〇包括初級繞組112、次級繞组114 和輔助繞組116。 根據一個實施例’回饋電壓VFB由採樣保持元件128〇接收。例如，在 接近退磁過程的結尾處當次級電流變得接近零時，回饋電壓Vfb被採樣， 並且經採樣的電壓VA隨後由元件1280保持直到下一採樣為止。在另一示 例中’經採樣的電壓VA由誤差放大1282接收，誤差放大器1282將經採樣 的電壓VA與參考電壓vref相比較，並且還放大vA與vref之間的差值。 根據另一實施例，如果開關1264接通，則誤差放大器1282與電容器 1254 —起將補償電壓1284發送給pWM/pFM信號產生器1286。例如， PWM/PFM信號產生器薦還接收由前向饋送元件㈣產生的電流^。在 另一不例中，前向饋送元件1262接收並處理經採樣的電壓Va與參考電壓 vref。在又一示例中，補償電壓1284和電流l2具有不同的相位。、 根據又-實施例，PWM/PFM信號產生器1286還從感測電阻器123〇 接收感測電壓1232 ’感測電阻器㈣將流經初級繞組112的初級電流變換 為感測電壓n PWM/PFM將猶電壓1284變換為貞細償電流並且 將該補償電流添加到電流l2中。 ，圖12所示’PWM/PFM信號產生器1286將調變信號㈣輸出給邏 讀1288 ’邏輯控制播1288將控制信號簡發送給開關1264和 動器1290㊉者。根據一個實酬，作為回應，閘驅動器129〇將驅動 5 。根制—實補，_264在控制信號 聊為雜騎位時接通，並且在㈣信號1289為邏輯低準位時斷開。 备控制信號1289的切換頻率隨著PFM模式中的負載而改變，輕 負载產生低的切換頻率，而大負載產生高的頻率。在另—示例中，控制信 17 201208242 =289的脈衝寬度隨著pWM模式中的負載而改變，輕負載產生窄的脈衝 大負載產生寬的脈衝寬度。因此，根據—個實施例，誤差放大器 1282的有效跨導隨著負載條件而改變。 根據另一實施例， gm、eff=gmlxr0”x 九 (等式14) e ’gmLe0^不誤差放大器1282的有效跨導，並且gml表示誤差放大 β的固有跨導。另外，Ton表示控制信號1289的脈衝寬度，k表示控 制信號1289的切換頻率。 例如’有效跨導隨著輸出負載條件而改變，由此使得在頻域中零點位 置保持低於極齡置。在另_示例巾，誤差放大器1282的有效跨導隨著負 載，變輕（例如，隨著輸出電流1〇的變小）而變小。在又一示例中，通過 隨著負載的減小而減小gml eff從而使得系統12〇〇的零點位置啦的頻率減 小。在一個實施例中，增益也隨著gmi eff的減小而減小。在另一示例中，極 點位置(Opf財貞載條件下之頻率上保持高於零點位置啦。 圖13是顯示根據本發明另一實施例之用於開關模式反激式電源變換系 =的初級側感測和調㈣統的簡化示圖。該示圖僅僅是示例，其不應當不 當地限制_料利範圍的範十熟知制技術領域之人將認識到許多變 體、替換和修改。 ，一個實施例中，反激式電源變換系統13〇〇包括電源開關132〇、感測 ，阻器1330、採樣保持元件138〇、誤差放大器1382、pwM/pFM信號產生 器1386、邏輯控制元件1388、閘驅動器139〇、電容器1354、前向饋送元 =1362、開關1364和單擊產生器1352。例如，電源開關1320、感測電阻 器1330、採樣保持元件138〇、邏輯控制元件1388和閘驅動器139〇分別與 電源開關120、感測電阻器130、採樣保持元件18〇、邏輯控制元件188以 及閘驅動器190相同。在另一示例中，pwM/pFM信號產生器1386基本上 與PWM/PFM信號產生器186相同。在又一示例中，誤差放大器1382與誤 差放大器182相同。 在另一實施例中，反激式電源變換系統1300還包括變壓器110、電纜 電阻器140、電阻器no和172、二極體160和168、電容器196和198， 它們都在圖1中示出。例如，變壓器110包括初級繞組1]2、次級繞組114 和輔助繞組116。 201208242 根據一個實施例’回饋電壓VFB由採樣保持元件1380接收。例如，在 接近退磁過程的結尾處當次級電流變得接近零時’回饋電壓vfb被採樣， 並且經採樣的電壓VA隨後由元件1380保持直到下一採樣為止。在另一示 例中，經採樣的電壓VA由誤差放大器1382接收，誤差放大器1382將經採 樣的電壓vA與參考電壓vref相比較，並且還放大％與Vref之間的差值。 根據另一實施例，如果開關1364接通，則誤差放大器1382與電容器 1354 —起將補償電壓1384發送給PWM/PFM信號產生器1386。例如， PWM/PFM信號產生器1386還接收由前向饋送元件1362產生的電流l2。在 另一不例中，前向饋送元件1362接收並處理經採樣的電壓Va與參考電壓 vref。在又一示例中，補償電壓1384和電流l2具有不同的相位。 根據又一實施例，PWM/PFM信號產生器1386還從感測電阻器133〇 接收感測電壓1332 ’感測電阻器1330將流經初級繞組112的初級電流變換 為感測電壓。例如，PWM/PFM將補償電壓1384變換為補償電流並且將該 補償電流添加到電流12中。IdA outputs error amplifier 982. According to one embodiment, I! decreases as Vcomp increases and I increases with the decrease in vec)mp. According to another embodiment, the compensation voltage 984 follows the output current I. The decrease is reduced. For example, the current Iea decreases as the compensation voltage 984 decreases. In another example, as shown in (d), (Equation 13) where 'Ibias represents a constant current generated by a current source, and 仏 is a constant determined by the characteristics of certain elements of error amplifier 982. According to a further embodiment of the invention, based on Equation 13, the gml of the error amplifier 982 decreases with current IEA and thus with the output current 1. The reduction (also referred to as load current) decreases. For example, the current Iea decreases as the output current decreases and increases as the output current increases. Therefore, the gml of the error amplifier 982 changes with the output load condition, thereby making the zero position ω ζ 2 under all load conditions. Keep below the pole position ωρΐ. Figure 11 is a simplified diagram showing an error amplifier 982, a capacitor 954 and a current generator 952 for a switched mode flyback power conversion system 900 in accordance with yet another embodiment of the present invention. This illustration is only an example and should not unduly limit the scope of the patent application. Those skilled in the art will recognize many variations, substitutions, and modifications. As shown in FIG. 11, error amplifier 982, in conjunction with capacitor 954, transmits a compensation voltage 984 to current generator 952. In response, in accordance with an embodiment, current generator 952 produces currents I and I!. For example, current 1 flows out of error amplifier 982. In yet another example, current h flows out of error amplifier 982. In yet another example, error amplifier 982 includes one or more transistors. According to one embodiment, it decreases as VcOTnp increases, and & The division's reduction increases. According to another embodiment, the compensation voltage 984 follows the output current j. The decrease is reduced. For example, gml of error amplifier 982 decreases as compensation voltage 984 decreases. In another example, 'gml follows the output current I. The reduction (also referred to as load current) decreases. Figure 12 is a simplified diagram showing the primary side sensing and adjustment system for a switch mode flyback power conversion system in accordance with another embodiment of the present invention. The diagram is only Lai, which should not unduly limit the material. Those who are familiar with the field of technology will recognize, replace and modify. In one embodiment, the flyback power conversion system U (8) includes a power switch 122 (), a sense resistor 1230, a sample and hold 128 (), an error amplifier 1282, a pw, an fm signal generation 16 201208242, 1286, logic Control element 1288, gate driver 1290, capacitor 1254, forward feed element 1262, and switch 1264. For example, power switch 1220, sense resistor 1230, sample and hold element 1280, logic control element 1288, and gate driver 1290, respectively, and power switch 120, sense resistor 130, sample and hold element 180, logic control element 188, and gate driver 190 the same. In another example, PWM/PFM signal generator 1286 is substantially identical to PWM/PFM signal generator 186. In yet another example, error amplifier 1282 is the same as error amplifier 182. In another embodiment, flyback power conversion system 1200 also includes transformer 110, cable resistor 140, resistors 170 and 172, diodes 160 and 168, capacitors 196 and 198, all of which are shown in FIG. . For example, the 'transformer 11' includes a primary winding 112, a secondary winding 114, and an auxiliary winding 116. According to one embodiment, the feedback voltage VFB is received by the sample and hold element 128A. For example, when the secondary current becomes near zero at the end of the near demagnetization process, the feedback voltage Vfb is sampled and the sampled voltage VA is then held by element 1280 until the next sample. In another example, the sampled voltage VA is received by error amplification 1282, which compares the sampled voltage VA with a reference voltage vref and also amplifies the difference between vA and vref. According to another embodiment, if switch 1264 is turned "on", error amplifier 1282, along with capacitor 1254, sends compensation voltage 1284 to pWM/pFM signal generator 1286. For example, the PWM/PFM signal generator recommends receiving the current generated by the forward feed element (4). In another example, forward feed element 1262 receives and processes sampled voltage Va and reference voltage vref. In yet another example, the compensation voltage 1284 and current 12 have different phases. According to yet another embodiment, the PWM/PFM signal generator 1286 also receives the sense voltage 1232 from the sense resistor 1232'. The sense resistor (4) converts the primary current flowing through the primary winding 112 into a sense voltage nPWM/ The PFM converts the heave voltage 1284 into a fine current and adds the compensation current to the current l2. The 'PWM/PFM signal generator 1286 shown in Fig. 12 outputs the modulated signal (4) to the logic 1288' logic control broadcast 1288 to send the control signal to the switch 1264 and the slave 1290. According to a remuneration, in response, the gate driver 129 will drive 5 . Root - Real complement, _264 turns "on" when the control signal talks for a mixed ride, and turns off when the (4) signal 1289 is at a logic low level. The switching frequency of the standby control signal 1289 changes with the load in the PFM mode, the light load produces a low switching frequency, and the large load produces a high frequency. In another example, the pulse width of the control signal 17 201208242 = 289 changes with the load in the pWM mode, the light load produces a narrow pulse and the large load produces a wide pulse width. Thus, according to one embodiment, the effective transconductance of error amplifier 1282 changes with load conditions. According to another embodiment, gm, eff = gmlxr0"x IX (Equation 14) e 'gmLe0^ does not have an effective transconductance of the error amplifier 1282, and gml represents the inherent transconductance of the error amplification β. In addition, Ton represents the control signal 1289 The pulse width, k, represents the switching frequency of the control signal 1289. For example, 'the effective transconductance changes with the output load condition, thereby keeping the zero position in the frequency domain below the extreme age. In another example, the error amplifier The effective transconductance of 1282 becomes lighter with the load (eg, as the output current becomes smaller). In yet another example, system 12 is caused by decreasing gml eff as the load decreases. The frequency of the zero position of 〇〇 is reduced. In one embodiment, the gain also decreases as the gmi eff decreases. In another example, the pole position (the frequency remains high under the Opf condition) Figure 13 is a simplified diagram showing a primary side sensing and tuning system for a switch mode flyback power conversion system = in accordance with another embodiment of the present invention. Should not be unreasonably restricted Those skilled in the art of the art will recognize many variations, substitutions, and modifications. In one embodiment, the flyback power conversion system 13 includes a power switch 132, sensing, a resistor 1330, sampling Holding element 138, error amplifier 1382, pwM/pFM signal generator 1386, logic control element 1388, gate driver 139, capacitor 1354, forward feed element = 1362, switch 1364, and click generator 1352. For example, power switch 1320, sense resistor 1330, sample and hold element 138, logic control element 1388, and gate driver 139 are the same as power switch 120, sense resistor 130, sample and hold element 18, logic control element 188, and gate driver 190, respectively. In another example, the pwM/pFM signal generator 1386 is substantially identical to the PWM/PFM signal generator 186. In yet another example, the error amplifier 1382 is identical to the error amplifier 182. In another embodiment, the flyback The power conversion system 1300 further includes a transformer 110, a cable resistor 140, resistors no and 172, diodes 160 and 168, capacitors 196 and 198, all of which are shown in FIG. For example, transformer 110 includes a primary winding 1]2, a secondary winding 114, and an auxiliary winding 116. 201208242 According to one embodiment, the feedback voltage VFB is received by the sample and hold element 1380. For example, at the end of the demagnetization process, the secondary current The feedback voltage vfb is sampled as it becomes near zero, and the sampled voltage VA is then held by the component 1380 until the next sample. In another example, the sampled voltage VA is received by the error amplifier 1382, which will be the error amplifier 1382 The sampled voltage vA is compared to the reference voltage vref and also amplifies the difference between % and Vref. According to another embodiment, if switch 1364 is turned "on", error amplifier 1382, along with capacitor 1354, sends a compensation voltage 1384 to PWM/PFM signal generator 1386. For example, the PWM/PFM signal generator 1386 also receives the current l2 generated by the forward feed element 1362. In another example, forward feed element 1362 receives and processes sampled voltage Va and reference voltage vref. In yet another example, the compensation voltage 1384 and the current l2 have different phases. According to yet another embodiment, the PWM/PFM signal generator 1386 also receives the sense voltage 1332' from the sense resistor 133'. The sense resistor 1330 converts the primary current flowing through the primary winding 112 into a sense voltage. For example, the PWM/PFM converts the compensation voltage 1384 into a compensation current and adds the compensation current to the current 12.
如圖13所示，PWM/PFM信號產生器1386將調變信號1387輸出給邏 輯控制讀1388 ’邏輯控制元件1388將控制信號1389發送給單擊產生器 1352和閘驅動器兩者。根據—個實施例，作為喊 將驅動信號1392發送給電源開關·。 ] _ U ，據另—實施例，單擊產生器1352產生作為信號㈣一部分之具有 二二a ΐ的脈衝以響應控制仏號1389的脈衝。根據又一實施例，開關1364 ίΪΓΐ號1389為邏輯高準位時接通’並且在㈣錢I389為邏輯低準 位時斷開。 信號，的切換頻率隨著負載而改變，輕負載產生低的切 的右纷路道陡：載產生兩的頻率。因此，根據一個實施例，誤差放大器1382 的有效跨導隨著負載條件而改變。 根據另一實施例， 苴 （等式15) ，、中’ gml_eff表示誤差放大器1382的有效跨莫 器1382 _有跨導。Μ，τ 啊效跨導，並且gml表不誤差放大 示控制俨轳ηβ〇 ^另卜Tcm-C(>nst表不信號丨353的恒定脈衝寬度，。表 的切換^補 頻率。例如，控制信號1389的切換鮮與信號1353 201208242 在另一示例中，有效跨導隨著輸出負載條件而改變，由此使得在頻域 置保持低於極雌置。在又—示财，誤差放大器1382的有效跨 :隨者、負載，輕(例如’隨著輸出電流I。的變小）而變小。在又-示例 通過隨著貞載的減小而減小從而使得彡、統IMG的零點位置％ 的^率減小。在—個實施例中’增益也隨著gml_eff的減小而減^在另-示 例中，極點位置ωρ1在所有負載條件下之頻率上保持高於零點位置啦。 —實施例，—種麟調整電源變換系統的輸出電壓的系統包括 揭0到，容器的誤差放大器。賴差放大ϋ配置以接收參考電壓、第一電 壓和調節電流纽與電容器-缝生補彳m該第 另外’該系統包括：電流產生器，配置以接收補償電壓並且 第—電流；以及信號產生器，配置以接收第—電流和第二電流。 ^還配置以接收感測電壓並產生調變信號。此外，該系統包括： g i該閉驅動器直接或間接地搞合到信號產生器並^•配置以至少基 妹廿调，城相_的資訊產生鶴信號；以及關，配置以接收驅動信 雷、、/5 t料城次級繞組她合的初級敝的初級電流。触級繞組與 ”、’衫統的輸iljf：壓和輸出電流㈣聯，並且該電源變齡統至少包 繞組和她敝。該_«至少取決於輸*電壓和輸出電流，並 /曰W電壓至》取決於初級電流。該誤差放大器至少藉由一跨導來表徵 莫配置以至少基於與調節電流相關聯的資訊來改變該跨導，並且該跨 她金著電源變換系統的輸丨電流的減小而減小。例如，跨導還隨著電源變 、、^的輸出電流的增大而增大。在另一示例令，該系統是根據圖6、圖9、 a、，1〇 (b)、圖1〇 (c)、圖1〇 (d)和/或圖u來實現。 補巾’料闕包括前向饋送元件’該前峨送元件配置以 因沾*電壓和第"'電壓並且產生第二電流。該第二電流和第—電流與不 ς^立相關聯。在又一示例中，該系統還包括採樣保持元件，該採樣保 66 =厭配置以接㈣饋電壓’在預定時間處對_電祕樣，保持經採樣 ^1，並且將所保持的電壓輸出作為第—電壓。在又—示例中，該系統 輯控制70件，魏輯控制元_合到信號產生器和閘驅動器。該 發件配置以接收調變信號並且至少基於與調變信號相關聯的資訊 J j域給難絲。在又—示财，該誤差放大^包括恒流電源， 以生怪定電流，調節電流流入或流出誤差放大器，並且誤差放大器 201208242 蚀至少取決於怪疋電流和調節電流。在又一示例中’電源變換系統包 =貝祕，該回饋迴路至少包括控制級和電源級。電源級至少包括閘驅 二，乂，在閘驅動器與用於輸出電壓和輸出電流的輸出端子之間的-個或 多個70件’並且控制級至少包括誤差放大器和信號產生器中的-部分。在 ί一m控制級至少由在頻域中至少具有零點位置的第—傳輸函數來表 ^ ’並電祕至少由在頻財至少具有_位置的第二傳輸函數來表 回貝迴路至;^由第-傳輸函數和第三傳輸函數的組合來表徵。在又一 示^中二不論輸出電流如何，零點位置在頻率上低於極點位置。在又一示 =够第-傳輸函數與第二傳輸函數的組合與作為第—頻率函數的增益和 數的相位相關聯。在又一示例中，不論輸出電流如何，如 果增a等於0 dB，則第-頻率函數具有2〇 _ec的斜率。在又一示例中， 不論輸出電流如何，如果增益等於〇dB，則相位為離·18〇。至少9〇。。 括· 實施例，—種胁調整電源變換系統的輸出電壓的方法包 Ϊ1放大减收參考電壓、第一電壓和調節電流。該第-電壓與回 另2，該方法包括：處理與參考《、第-«和調節電 ; 容器的誤差放大器產生補齡接收補償 基於與補償電壓相關聯的資訊來產生調節電流和第-電 r楚ίΐ 括：接收第—電流、第二電流和感測電壓；至少基於 流和感測電壓相關聯的資訊來產生調變信號;處理與 ===訊’·以及至少基於與調變信號相關聯的資訊來產生驅 收驅動信號並且至少基於與驅動信號相關聯的資 讯^響减H減電献纟績她繞組她合的她触 變換系統的輸出賴和輸出電流相關聯。該回饋麵至作 出電壓和輸出電流，並且該感測電屋至少取決於初級電流。咳誤差 放大器至少由-跨縣表徵。祕處理與參 /電 :::跨導隨著電源變換系統的輸出電流的減小而減 = 隨者電源變換緖的輸出電_增大，大。在另—稍巾， :6在圖9、圖二(a)、圖10㈦、圖10 (c)、圖1〇⑷和心 現在又—讀中，财法還包括··由麵魏元件触參考電 = 電塵’以及至少基於與參考鍾和第―麵蝴聯㈣絲產 21 201208242 流。該第一電流和第二電流至少具有不同的相位。 、根據又-實齡彳，—細於調整電_⑽、_輸出電壓的系統包括 通過第-開Μ接地编合到電容n的誤差放大i該誤差放大置以接 收參考，壓和第-電壓，並壯果第—開關接賴與電容卜起產生補償 電整4第-電壓與回饋電壓相關聯。另外，該系統包括：第一開關，至 =搞合職差2大ϋ和電容^ ;以及信缝生器，配置以接收補償電壓和 ▲ -電流。該城產生轉配置以接收感啦壓並產生調變鐵。此外， =系統還包括：邏輯控制元件’配置以接收調變信號並且至少基於與調變 減相關聯的資訊來纽控制健；閘驅動器，配置以接收控制信號並且 配置以至少基於與控制信號相關聯的資訊產生驅動信號；以及第二開關， 酉己置以接收驅動錢並且影響流經與次級繞纟 1_合_級敝的初級 繞組與電源變換祕的輸出賴和輸㈣流相_，並且該電 系統至少包括贿繞組和次級繞組。翻饋電壓至少取決於輸出電 f和輸出電流’並且該感測電壓至少取決於 =寬度和切換頻率來表徵。第—開關配置以受控制信號控制。 二邏輯低 配收回饋電壓’在預定時間處對回饋電壓採樣，保持經採樣 差放大器與第-開_組合至少由有效跨導 = 輸出^的減=而減小並且隨著電源變換系統的輸出電流的增大而增大的 ，據又-實補，—__錢觀齡統 由誤差放大器接收參考《和第—龍。該第—電顯回括 處理斑來老她3 J 鶴合到電容器。另外，該方法包括： 差細相，的資訊:如果苐-開關為接通，則由誤 差放大态”電奋Is-起產生補償電壓；接收 壓’·以及至少基於與補償電壓、第—電流和感測電壓相關聯的;訊 22 201208242 調變信號。此外，該方法包括：處理與調變信號相關聯的資訊；至少基於 與調變信號相關聯的資訊來產生控制信號；處理與控制信號相關聯的資 訊；至少基於與控制信號相關聯的資訊來產生驅動信號；以及至少基於與 驅動信號相關聯的資訊來影響初級電流。該初級電流流經與次級繞組相耗 合的初級繞組。該次級繞組與電源變換系統的輸出電壓和輸出電流相關 聯。該回饋電壓至少取決於輸出電壓和輸出電流，並且該制電壓至少取 決於初級電流。該控制信號至少由脈衝寬度和切換頻率來表徵。用於處理 與控制信號相__資訊的步驟包括：如果控制信號為邏輯高準位，則接 通第-開關’並且如果控制信號為邏輯低準位，則斷開第—開關。例如， 根據圖12來實現。在另—示例中’該方法包括：由前向舰元件接 邻U 和第""電壓，以及至少基於與參考電壓和第—電壓相關聯的資 3來產生第-電流。該第_電流和補償電壓至少具有不同的相位。 、s、Ϊ據又—實關，-_於調整電源變換系統的輸出電壓的系統包括 間接地麵合到電容器的誤差放大器。該誤差放大器配置以接 和第"~電壓’並且如果第—開關接通則與電容起產生補償 2。第-電，回饋電壓相關聯。另外，該系統包括：第—開關，3 -;ϊ誤ίίϊ::容器;以及信號產生器’配置以接收補償電壓和第 統接收感測電壓並產生調變信號。此外，該系 聯:資訊生置以接收調變信號並且至少基於與調變信號相關 開關發送單擊信號；閘驅動器，配置以接收控制S H 基於與控制信號相訊; =且影響流經與次級繞_合的初級繞二： 第-脈：和取^流。該控制信號至少由 =切換頻率來表徵。該====== 違第二切換頻率等於第 平料生糾疋的常數，並且 如果單擊信號為邏輯高準位，'難° =:_置以受單擊信號控制。 低準位，娜—開_^\ _触’並且如科悔號為賴 斷開。例如，該系統根據圖13來實現。 23 201208242 Γ例中，该系統還包括前向錯送元件’該前向饋送元件配置以 的相位相_和^—電壓並且產生第—電流。第—電流和補償電壓與不同 置=:示例中，該系統還包括採樣保持元件，該採樣保持 雷愿-#請:饋霞，翻定時間處朗饋電麟樣，絲經採樣的 電屋。並且將所保持的電壓輸出作為第—電壓。在又—示例中，至少 ㈣組合至少由有效跨縣表徵。有效跨導至少取決於第 :’、又一不例中，有效跨導隨著電源變換系統的輸出電流的減 小而減小’並且隨著電源變齡統的輸出電流的增大而增大。 實施例’ 一種用於調整電源變換系統的輸出電壓的方法包括 技且收參考電壓和第—電壓。該第—龍與回饋電翻關聯， ΐπϊίϋϊ通過第-開關間接_合到電容器。另外，該方法包括： 第—電壓相關聯的資訊；如果第—開關接通，則由誤差 s I二二' 一起產生補償電壓；接收補償電壓、第一電流和感測電壓； t基於，、補償電壓、第_電流和感測電壓相關聯的資訊產生調變信號。 相隱·處理與調變信號相關聯的資訊；至少基於與調變信號 相關聯的㈣產生控制信號；處理與控制信號相關聯的資訊：以及至少基 ^與控制信肋»㈣訊產生單雜餘爾錢。此外，财法包括： 襲㈣糊節第―關；以及至少基於與驅動信號相 Β的資蘇4减電流，初級電流流經與次級繞組她合的初級繞 。該次級繞減f源變齡_輸出輕和輸出電流侧I該回饋電 ，至广取決於輸出電壓和輸出電流，並且該感測電壓至少取決於初級電 ^。雜制信號至少由第-脈衝寬度和第—_頻率來表徵，並且該單擊 1由第二脈衝寬度和第二切換頻率來表徵。該第二脈衝寬度是由單 n器f疋的常數，並且該第二切換頻料於第-切換頻率。用於基於 j擊信號相關聯的資訊調節第—開關的步驟包括：如果單擊信號為邏輯 =準位，則接通第H並且如果單擊信號為邏輯低準位，則斷開第一 ，關。例如，該方法根_ 13來實現。在另—補中，該方法包括：由前 ，饋送元件接收參考電壓和第—電壓，以及至少基於與參考電壓和第一電 ㈣關聯的資訊產生m該第—電流和補償電壓至少具有不同的相 位。 雖然已描述了本發明的特定實施例，_熟知該項技術領域之人將明 24 201208242 μ存t與所述實施例等同的其它實施例。因此，將明白，本發明不局限 、不出的特定實施例，而是僅由申請專利範圍的範《#來限定。 【圖式簡單說明】 &朗具有減側細和調整的傳統開隨式反激式電源變換系 所*的間化示圖； ㈣L2是說明回饋電壓174以及流經次級繞組114的次級電流的傳統波 形的簡化示圖； 几_ f 3疋說明作為輸出電流（也稱為負載電流）的函數的補償電1的簡 化不圖； =4和圓5各自說明反激式電源變齡統之電源級的簡化傳統波德圖； 圖6 I說明娜本發明實施例之用於開關模式反激式電源變換系統的 初級側感測和調整系統的簡化示圖； 圖7 (a)、（b)和⑷是說明在不同負載條件下具有常數的電源級 和控制級的組合傳輸函數的簡化波德圖； 圖8 (a)、（b)和（c)是說明根據本發明實施例之具有隨著負載的減 小而減小的gm]的電源級和控制級的組合傳輸函數的簡化波德圖； 圖9是說明根據本發明另一實施例之用於開關模式反激式電源變換系 統的初級側感測和調整系統的簡化示圖； 圖10 (a)、（b)、（c)和（d)是說明根據本發明一個實施例之用於開 關模式反激式電源變齡制誤差放大^ '電容器和電流產生器的簡化示 圆， 圖11是說明根據本發日m施例之用於_模式反激式電源變換系 統的誤差放大器'電容器和電流產生器的簡化示圖； 圖12是說明根據本發明另—實施例之祕開關模式反激式電源變換系 統的初級側感測和調整系統的簡化示圖；以及 圖13是說明根據本發明另一實施例之用於開關模式反激式電源變換系 統的初級側感測和調整系統的簡化示圖。 【主要元件符號說明】 100 反激式電源變換系統 25 201208242 110 變壓器 112 初級繞組 114 次級繞組 116 輔助繞組 118 輔助電壓 120 電源開關 130 感測電阻器 132 感測電壓 140 電纜電阻器 142 輸出電壓 150 輸出負載 160、 168二極體 170、 172電阻器 174 回饋電壓 180 採樣保持元件 182 誤差放大器 184 迴路補償網路 185 輸出信號 186 PWM/PFM信號產生器 187 調變信號 188 邏輯控制元件 190 閘驅動器 192 驅動信號 196、 198電容器 600 系統 610 減法元件 620、 622、624跨導元件 630 電容元件 640 加法元件 650 電源級 26 201208242 710、720、730增益曲線 712、722、732相位曲線 810、820、830增益曲線 812、822、832相位曲線 900 反激式電源變換系統 920 電源開關 930 感測電阻器 932 感測電壓 952 電流產生器 954 電容器 962 前向饋送元件 964 節點 980 採樣保持元件 982 誤差放大器 984 補償電壓 986 PWM/PFM信號產生器 987 調變信號 988 邏輯控制元件 989 控制信號 990 閘驅動器 992 驅動信號 1200 反激式電源變換系統 1220 電源開關 1230 感測電阻器 1232 感測電壓 1254 電容器 1262 前向饋送元件 1264 開關 1280 採樣保持元件 1282 誤差放大器 27 201208242 1284 補償電壓 1286 PWM/PFM信號產生器 1287 調變信號 1288 邏輯控制元件 1289 控制信號 1290 閘驅動器 1292 驅動信號 1300 反激式電源變換系統 1320 電源開關 1330 感測電阻器 1332 感測電壓 1352 單擊產生器 1353 信號 1354 電容器 1362 前向饋送元件 1364 開關 1380 採樣保持元件 1382 誤差放大器 1384 補償電壓 1386 PWM/PFM信號產生器 1387 調變信號 1388 邏輯控制元件 1389 控制信號 1390 閘驅動器 1392 驅動信號 28As shown in Figure 13, PWM/PFM signal generator 1386 outputs modulated signal 1387 to logic control read 1388' logic control element 1388 to send control signal 1389 to both click generator 1352 and the gate driver. According to an embodiment, the drive signal 1392 is sent to the power switch as a shout. ] _ U , according to another embodiment, the click generator 1352 generates a pulse having a 22 a ΐ as part of the signal (4) in response to the pulse of the control code 1389. According to yet another embodiment, switch 1364 ί 1 1389 is turned "on" when it is at a logic high level and is turned "off" when (4) money I389 is at a logic low level. The switching frequency of the signal changes with the load, and the light load produces a low cut right channel steep: the load produces two frequencies. Thus, according to one embodiment, the effective transconductance of error amplifier 1382 changes with load conditions. According to another embodiment, 苴 (Equation 15), where 'gml_eff' represents the effective transponder 1382_ of the error amplifier 1382 has a transconductance. Μ, τ 效 effect transconductance, and gml table error-free amplification control 俨轳ββ 〇 ^ Other Tcm-C (> nst table does not signal 丨 353 constant pulse width, the table switching ^ complement frequency. For example, Switching the control signal 1389 to the signal 1353 201208242 In another example, the effective transconductance changes with output load conditions, thereby causing the frequency domain to remain below the extreme female. In addition, the error amplifier 1382 The effective span: the follower, the load, and the light (for example, 'as the output current I. becomes smaller) becomes smaller. In the again - the example is reduced by the decrease of the load, so that the zero point of the IMG The rate of position % is reduced. In one embodiment, the 'gain is also reduced as gml_eff decreases. In the other example, the pole position ωρ1 remains above the zero position at all frequencies under load conditions. - Embodiment, - the system for adjusting the output voltage of the power conversion system includes a fault amplifier of the container. The differential amplification is configured to receive the reference voltage, the first voltage, and the adjustment current and the capacitor - the stitching compensation m the other 'the system includes: a flow generator configured to receive the compensation voltage and a first current; and a signal generator configured to receive the first current and the second current. ^ is further configured to receive the sensing voltage and generate a modulated signal. Additionally, the system includes: Gi the closed drive directly or indirectly fits into the signal generator and ^• configuration to at least the base sister tone, the city phase _ information to generate the crane signal; and off, configured to receive the drive letter mine, /5 t material city The primary winding of the primary winding of the secondary winding. The contact winding is connected with the "," the iljf: the voltage and the output current (four), and the power supply age is at least wrapped in the winding and her 敝. The _« depends at least The input voltage and the output current, and / / W voltage to "depend on the primary current. The error amplifier at least by a transconductance to characterize the configuration to change the transconductance based at least on information associated with the regulated current, and The trans-conductance is reduced as the output current of the galvanic power conversion system decreases. For example, the transconductance also increases as the power supply changes, and the output current increases. In another example, the system is According to Figure 6, 9, a, 1 〇 (b), Figure 1 〇 (c), Figure 1 〇 (d) and / or Figure u to achieve. The patch 'material 阙 includes the forward feed element 'the front feed element configuration to The second current is generated by the voltage and the " voltage. The second current and the first current are associated with each other. In yet another example, the system further includes a sample and hold element, the sample protection 66 = 配置 configuration to connect (four) feed voltage 'at a predetermined time to _ electrical secret sample, keep sampled ^1, and the maintained voltage output as the first voltage. In the example - the system controls 70 pieces, The control unit is coupled to the signal generator and the gate driver. The sender is configured to receive the modulated signal and to provide a hardwire based on at least the information Jj associated with the modulated signal. In the case of - fortune, the error amplification ^ includes a constant current source to regulate the current, adjust the current into or out of the error amplifier, and the error amplifier 201208242 etch depends at least on the quirk current and the regulation current. In yet another example, the power conversion system package = the secret, the feedback loop includes at least a control stage and a power stage. The power stage includes at least a gate drive 2, 乂, one or more 70 pieces between the gate driver and an output terminal for output voltage and output current and the control stage includes at least an error amplifier and a signal generator . The control level of the 一m is at least represented by a first transfer function having at least a zero position in the frequency domain, and the timbre is at least represented by a second transfer function having at least a _ position in the frequency; Characterized by a combination of a first transfer function and a third transfer function. In still another example, regardless of the output current, the zero position is lower in frequency than the pole position. In still another indication = the combination of the first-transfer function and the second transfer function is associated with the phase of the gain and number as a function of the first frequency. In yet another example, regardless of the output current, if a is increased by equal to 0 dB, the first-frequency function has a slope of 2 〇 _ec. In yet another example, regardless of the output current, if the gain is equal to 〇 dB, the phase is off 18 〇. At least 9 weeks old. . In the embodiment, the method of adjusting the output voltage of the power conversion system includes expanding and reducing the reference voltage, the first voltage, and the regulation current. The first voltage and the second voltage, the method includes: processing and reference ", - - and adjusting the power; the error amplifier of the container generates compensation for the compensation of the age based on the information associated with the compensation voltage to generate the regulated current and the first r楚ίΐ include: receiving a first current, a second current, and a sensing voltage; generating a modulated signal based on at least information associated with the flow and the sensed voltage; processing and ===signaling, and at least The associated information is generated to generate a drive drive signal and based at least on the information associated with the drive signal, the output of the hermetic conversion system is associated with the output current. The feedback surface is responsive to the voltage and output current, and the sense house is dependent at least on the primary current. The cough error amplifier is characterized by at least - cross-county. The secret processing and the parameter / electric ::: transconductance decrease with the decrease of the output current of the power conversion system = the output power of the power conversion converter increases and increases. In the other - a little towel, : 6 in Figure 9, Figure 2 (a), Figure 10 (seven), Figure 10 (c), Figure 1 (4) and the heart is now - read, the financial law also includes · by the surface of the Wei element touch Reference electricity = electric dust 'and at least based on the flow with the reference clock and the first side of the butterfly (four) silk production 21 201208242. The first current and the second current have at least different phases. According to the same-real age, the system that is finer than adjusting the electric_(10), _ output voltage includes the error amplification by the first-opening grounding to the capacitor n. The error is amplified to receive the reference, the voltage and the first voltage. And the strong fruit - the switch depends on the capacitor and the capacitor to generate the compensation. The fourth voltage is associated with the feedback voltage. In addition, the system includes: a first switch, to = 2 joints and capacitors; and a letter breaker, configured to receive the compensation voltage and ▲ - current. The city produces a turn configuration to receive the sense pressure and produce a modulated iron. Additionally, the = system further includes: the logic control element 'configured to receive the modulated signal and control the health based at least on information associated with the modulation reduction; the gate driver configured to receive the control signal and configured to be based at least on the control signal The associated information generates a drive signal; and the second switch, which is set to receive the drive money and affects the output and the output (four) flow phase of the primary winding and the power conversion secret flowing through the secondary winding 1_he And the electrical system includes at least a brittle winding and a secondary winding. The feed voltage is dependent at least on the output power f and the output current & and the sense voltage is characterized at least by the = width and the switching frequency. The first switch configuration is controlled by a control signal. The second logic low with the retraction feed voltage 'samples the feedback voltage at a predetermined time, keeping the sampled difference amplifier and the first-on_ combination reduced by at least the effective transconductance = output ^ minus = and with the output of the power conversion system The increase in current increases, according to the -real complement, -__ Qian Guanling system receives the reference "and the dragon" by the error amplifier. The first - electric display included the treatment of the spot to bring her 3 J crane into the capacitor. In addition, the method includes: differential fine phase, information: if the 苐-switch is turned on, the compensation voltage is generated by the error amplification state "Electronics Is-; the receiving voltage'· and at least based on the compensation voltage, the first current And the sensing voltage is associated with the sensing voltage; in addition, the method includes: processing information associated with the modulated signal; generating a control signal based on at least information associated with the modulated signal; processing and control signals Associated information; generating a drive signal based at least on information associated with the control signal; and affecting the primary current based at least on information associated with the drive signal. The primary current flows through a primary winding that is consuming the secondary winding. The secondary winding is associated with an output voltage and an output current of the power conversion system. The feedback voltage depends at least on the output voltage and the output current, and the voltage is dependent at least on the primary current. The control signal is at least a pulse width and a switching frequency. Characterization. The steps for processing the __ information with the control signal include: if the control signal is at a logic high level, then Turning on the -switch' and if the control signal is at a logic low level, the first switch is turned off. For example, according to Figure 12. In another example, the method includes: connecting the forward ship element to the U and a "" voltage, and at least based on a resource 3 associated with the reference voltage and the first voltage to generate a first current. The _ current and the compensation voltage have at least different phases. s, Ϊ, and _ The system for adjusting the output voltage of the power conversion system includes an error amplifier that is indirectly grounded to the capacitor. The error amplifier is configured to connect the "~voltage' and if the first switch is turned on, the capacitor is compensated 2 The first-electric, feedback voltage is associated. In addition, the system includes: a first switch, a 3 -; a fault ίίϊ:: a container; and a signal generator 'configured to receive the compensation voltage and the first receive sense voltage and generate a tone In addition, the system is configured to receive a modulated signal and transmit a click signal based at least on a switch associated with the modulated signal; the gate driver is configured to receive the control SH based on the control signal ; = and affect the flow through the secondary winding - the primary winding two: first - pulse: and take the flow. The control signal is characterized by at least = switching frequency. The ====== violation of the second switching frequency is equal to The first level is a constant constant, and if the click signal is at a logic high level, 'difficulty =:_ is set to be controlled by the click signal. Low level, Na-open _^\ _ touch' and The repentance is broken. For example, the system is implemented according to Figure 13. 23 201208242 In the example, the system further includes a forward misfeed element 'the forward feed element is configured with phase phase _ and ^ - voltage and is generated The first-current. The first-current and the compensation voltage are different. In the example, the system also includes a sample-and-hold component. The sample is kept by Ray-#Please: Feeding the cloud, the time is at the time of the feeding, the wire is passed. Sampling electric house. And the held voltage output is taken as the first voltage. In yet another example, at least (four) combinations are characterized by at least an effective cross-county. The effective transconductance depends at least on the first: ', in another example, the effective transconductance decreases as the output current of the power conversion system decreases' and increases as the output current of the power supply age increases. . Embodiments A method for adjusting an output voltage of a power conversion system includes techniques and receiving a reference voltage and a first voltage. The first dragon is associated with the feedback, and the ΐπϊίϋϊ is indirectly coupled to the capacitor through the first switch. In addition, the method includes: a first voltage-related information; if the first switch is turned on, the compensation voltage is generated by the error s I and II'; receiving the compensation voltage, the first current, and the sensing voltage; The information associated with the compensation voltage, the _th current, and the sense voltage produces a modulated signal. Concealing and processing information associated with the modulated signal; at least based on (4) generating a control signal associated with the modulated signal; processing information associated with the control signal: and at least the base and the control signal » (4) generating a single miscellaneous Yuer money. In addition, the financial method includes: attack (four) paste section - off; and based at least on the driving signal, the primary current flows through the primary winding with the secondary winding. The secondary winding reduces the source age _ output light and the output current side I the feedback, up to the output voltage and output current, and the sense voltage depends at least on the primary power. The hash signal is characterized by at least a first pulse width and a first frequency, and the click 1 is characterized by a second pulse width and a second switching frequency. The second pulse width is a constant from the unit n, and the second switching frequency is at the first switching frequency. The step of adjusting the first switch based on the information associated with the j-click signal includes: turning on the H if the click signal is logic=level, and disconnecting the first if the click signal is at a logic low level, turn off. For example, the method root _ 13 is implemented. In another method, the method includes: receiving, by the feed element, a reference voltage and a first voltage, and at least based on the information associated with the reference voltage and the first electrical (four), the first current and the compensation voltage are at least different Phase. Although specific embodiments of the invention have been described, other embodiments of the invention will be apparent to those skilled in the art. Therefore, it will be understood that the invention is not limited to the specific embodiments, and is only limited by the scope of the patent application. [Simple diagram of the diagram] & Lang has an internalized diagram of the conventional open-back flyback power conversion system with reduced side and fine adjustment; (4) L2 is a description of the feedback voltage 174 and the secondary flowing through the secondary winding 114 A simplified diagram of the conventional waveform of the current; a few _f 3 疋 illustrates a simplified diagram of the compensation 1 as a function of the output current (also referred to as the load current); =4 and 5 respectively illustrate the flyback power supply age A simplified conventional Bode diagram of the power stage; Figure 6I illustrates a simplified diagram of a primary side sensing and adjustment system for a switch mode flyback power conversion system in accordance with an embodiment of the invention; Figure 7 (a), ( b) and (4) are simplified Bode diagrams illustrating a combined transfer function of a power supply stage and a control stage having constants under different load conditions; Figures 8(a), (b) and (c) are diagrams illustrating an embodiment in accordance with the present invention. A simplified Bode diagram of a combined transfer function of a power stage and a control stage having a reduced gm] as the load decreases; FIG. 9 is a diagram illustrating a switch mode flyback power conversion in accordance with another embodiment of the present invention. A simplified diagram of the primary side sensing and adjustment system of the system; 10(a), (b), (c) and (d) are diagrams illustrating a simplified representation of a switch mode flyback power supply aging error amplification capacitor and current generator in accordance with one embodiment of the present invention. Figure 11 is a simplified diagram illustrating an error amplifier 'capacitor and current generator for a _ mode flyback power conversion system according to the present embodiment. Figure 12 is a diagram illustrating another embodiment of the present invention. A simplified diagram of a primary side sensing and conditioning system of a switch mode flyback power conversion system; and FIG. 13 is a diagram illustrating primary side sensing and for a switched mode flyback power conversion system in accordance with another embodiment of the present invention. A simplified diagram of the adjustment system. [Main component symbol description] 100 flyback power conversion system 25 201208242 110 Transformer 112 primary winding 114 secondary winding 116 auxiliary winding 118 auxiliary voltage 120 power switch 130 sensing resistor 132 sensing voltage 140 cable resistor 142 output voltage 150 Output Load 160, 168 Diode 170, 172 Resistor 174 Feedback Voltage 180 Sample Hold Element 182 Error Amplifier 184 Loop Compensation Network 185 Output Signal 186 PWM/PFM Signal Generator 187 Modulation Signal 188 Logic Control Element 190 Gate Driver 192 Drive signal 196, 198 capacitor 600 system 610 subtraction element 620, 622, 624 transconductance element 630 capacitive element 640 addition element 650 power stage 26 201208242 710, 720, 730 gain curve 712, 722, 732 phase curve 810, 820, 830 gain Curves 812, 822, 832 Phase Curve 900 Flyback Power Conversion System 920 Power Switch 930 Sense Resistor 932 Sense Voltage 952 Current Generator 954 Capacitor 962 Forward Feed Element 964 Node 980 Sample and Hold Element 982 Error Amplifier 984 Compensation Voltage986 PWM/PFM signal generator 987 Modulation signal 988 Logic control element 989 Control signal 990 Gate driver 992 Drive signal 1200 Flyback power conversion system 1220 Power switch 1230 Sense resistor 1232 Sense voltage 1254 Capacitor 1262 Forward feed element 1264 Switch 1280 Sample and Hold Element 1282 Error Amplifier 27 201208242 1284 Compensation Voltage 1286 PWM/PFM Signal Generator 1287 Modulation Signal 1288 Logic Control Element 1289 Control Signal 1290 Gate Driver 1292 Drive Signal 1300 Flyback Power Conversion System 1320 Power Switch 1330 Sense Measure Resistor 1332 Sense Voltage 1352 Click Generator 1353 Signal 1354 Capacitor 1362 Forward Feed Element 1364 Switch 1380 Sample Hold Element 1382 Error Amplifier 1384 Compensation Voltage 1386 PWM/PFM Signal Generator 1387 Modulation Signal 1388 Logic Control Element 1389 Control Signal 1390 gate driver 1392 drive signal 28