200812208 七、 指定代表圖： (一） 本案指定代表圖為：第六圖。 (二） 本代表圖之元件符號簡單說明：無。 八、 本案若有化學式時，讀揭示最能顯示發明特徵 的化學式： 九、 發明說明： •【發明所屬之技術領域】 本案係指一種交錯式雙管正激轉換器之控制方 法·，特別是指應用於電源供應器的交錯式雙管正激轉 換器。 【先前技術】 隨著電源技術的迅速發展，市場對於伺服器電源 和通訊電源的效率（包括滿載和輕載時的效率）、可靠 ⑩ 度、以及功率密度等性能皆提出了更高的需求。在形 式眾多的轉換器當中，交錯式雙管正激轉換器由於所 具有的諸多優點而得到了廣泛的應用;諸如：變壓器 一次侧不存在橋式電路的直通問題使得可靠度變高、 開關管在一半的輸入電壓下進行開關使得開關損耗較 小、對稱式的架構使得其電磁干擾(EMI)雜訊較小、變 壓器二次侧的等效频率是一次侧的兩倍而能夠減小其 二次侧所連接之濾波電感的體積等等。 請參閱第一圖，其為習用之交錯式雙管正激轉換 4 200812208 器的電路圖。其中，交錯式雙管正激轉換器ίο主要係 由四個開關S1〜S4、四個一次側二極體⑴〜仏二: 艾，益工1，、二:欠侧的二個整流二極體^^〜沉和― =，二極體D7、以及輸出端的濾波電感L及遽波電 谷（一者形成一濾波電路)所構成。此輸 其-般係為前-級轉換器 係由功率半導體元件所構成，圖中係以 乳效電晶體(^40卯£乃來表示；至於變壓器τ卜乃 的一、二次側線圈匝數比則均為Ν: 1。 久=二圖係為針對第一圖之交錯式雙管正激轉換哭 :各=1關進行控制時的時序圖，其中横軸為； &，軸為各電晶體開關的導通（〇Ν)/關斷(〇ff)狀 二圖則為在配合第二圖之控制方法的情形下、 圖之父錯式雙管正激轉換器中各變 側各二極體之電屢波形圖。要注意的是勹 各時刻點W系完全對應於第三圖中的各時；：中 以下同時參考第二圖與第三圖說 式雙管正轉換H的運作肋。α兄以圖之父錯 敕法在t0時刻’電晶體開關S1*S2導通，二次側的 正概一極體D5導通，輪入雷厭、@ ' 头 向輪出端㈣)物^糾Vmsti§_T〗 的敕ί ’開關S1和S2同時關斷’此時二次側 的正/瓜—極體D5承受反向帝厭、义 止，於是二次侧的病、ώ 包、叙生反向恢復後截 的高I料二同時，一次侧 篮川和02導通，變屢器在〜心電 200812208 壓的作用下復位。此時，流經整流二極體D5的電流便 轉移到續流二極體D7，而當激磁電流減小至零時，二 極體D1和D2電流便自然過零而截止。 在t2時刻，另一路轉換器的電晶體開關S3和S4 導通，整流二極體D6導通，二次侧的續流二極體D7 承受反向電壓、發生反向恢復後截止，流經續流二極 體D7的電流轉到整流二極體D6。此時，整流二極體 D5所承受的最高反向電壓為2Vin/N+Vspike;其中 鲁 Vspike為續流二極體D7反向恢復所產生的電壓峰值。 在上述針對第二圖所示之傳統控制模式所進行之 交錯式雙管正激轉換器的工作原理分析之中，可以看 出：當電晶體開關SI、S2關斷時，負載電流由整流二 極體D5轉移到續流二極體D7，而在電晶體開關S3、 S4導通時，負载電流則由續流二極體D7轉移到整流 二極體D6。由此可知，在一個完整的工作週期内，二 次侧二極體一共發生了四次的反向恢復，其中兩次由 φ 整流二極體D5和D6產生，另外兩次則由讀流二極體 D7產生。 是故，在第一圖的交錯式雙管正激轉換器中使用 第二圖之控制方法，會在變壓器二次侧的二極體上因 為反向恢復而產生較大的開關損耗，使得轉換器10整 體的效率降低。 請參閱第四圖，其為日本特開平10-4680號案件 所揭露之另一種交錯式雙管正激轉換器的電路圖，與 第一圖相比，交錯式雙管正激轉換器40中省去了續流 6 200812208 後面將會敘述其原因。第五圖則為針對第 制管正激轉換器的各電晶體瞻 雙管正激轉換器的運作原理。 口心又錯式 "it:圖:控模式不同之處在於:在 電曰曰體是將其導通與關斷的時刻分別控制於 電曰曰體開關S2和S4導通與關斷的之前和之後，如第 五圓所示。 示 在to時刻之前，電晶體開關S1處於狀能，+ (負導通— S1仍在缺t導:刻’；晶體開關S2關斷，但電晶體開關 一 V通，一次侧的續流二極體D1導通，折算到 ❿ 壓：二的負載電流與激磁電流沿著電晶體開關S卜變 二:體^咖續流，而負载電流仍然流經整流 二t2時刻，電晶體開關％導通，到了飞時 壓的^用下^的電壓變為下正上負；在這個反向電 體D6—極體D5的負载電流轉到整流二極 _ :々丨L、""一極體D5的電流減小到零時二極體D5 經變°同時折算到—次侧的負載電流流 、、T2、—次側續流二極體W以及電晶體開關 7 200812208 。 S3 〇 在時刻’電晶體開關S4導通’一次侧的績流二 極體D3承受了 Vin的反向電壓，使得二極體D3在發 生反向恢復後截止；輸入電壓源Vin經變壓器T2向二 次侧傳輸能量。 透過上述對於第四圖及第五圖所示的交錯式雙管 正激轉換器之工作原理的分析，可以看出:透過改變 了第二圖之傳統的控制模式，不再同時導通與關斷電 修 晶體開關SI、S2(S3、S4)，而是按照第五圓所示的時 序進行開關的切換，使得負載電流由二極體D5直揍轉 到二極體D6(或是由二極體D6直接轉到二極體D5)， 而不再經過續流二極體D7;此為前述之二次侧續流二 極體D7可以省略的原因所在。其他的優點是，在一個 週期之内，避免了兩次讀流二極體的反向恢復，減小 了反向恢復的開關損耗。 然而，第五圖之控制方法的缺點在於，一次侧的 _ 續流二極體Dl、D3在流過負載電流之時，其在Vin 的反向電壓作用下會截止而產生較強的反向恢復，而 帶來了附加的反向恢復損耗。 職是之故，申請人鑑於前述二種習知技術之缺 失，乃經悉心試驗與研究，並一本鍥而不捨之精神， 終構思出本案，以下為本案之簡要說明。 【發明内容】 本案一方面提出一種交錯式雙管正激轉換器之控 8 200812208 制方法’交錯式雙管正激轉換器之控制方法，該轉換 器包括.· 弟一功率半導體開關及一第一二極體 .—叹 孩罘 功率半導體開_-端連接於該第—二極體的陰極而 構成一輪入電源高壓端； 一第二功率半導體開關及一第二二極 該第 /丨，——^朋：7砀乐一 功率半導體開_ —端連接於該第—二極體的陽極，200812208 VII. Designation of representative representatives: (1) The representative representative of the case is as follows: Figure 6. (2) A brief description of the symbol of the representative figure: None. 8. If there is a chemical formula in this case, the reading reveals the chemical formula that best shows the characteristics of the invention: IX. Description of the invention: • [Technical field to which the invention belongs] This case refers to a method of controlling an interleaved double-tube forward converter, especially Refers to the interleaved two-switch forward converter applied to the power supply. [Prior Art] With the rapid development of power supply technology, the market has put forward higher demands on the efficiency of server power supply and communication power supply (including efficiency at full load and light load), reliability of 10 degrees, and power density. Among the many types of converters, the interleaved two-switch forward converter has been widely used due to its many advantages; for example, the straight-through problem of no bridge circuit on the primary side of the transformer makes the reliability higher, the switch tube Switching at half the input voltage results in a small switching loss. The symmetrical architecture makes the electromagnetic interference (EMI) noise smaller, and the equivalent frequency of the secondary side of the transformer is twice that of the primary side. The volume of the filter inductor connected to the secondary side, and so on. Please refer to the first figure, which is a circuit diagram of the conventional interleaved two-switch forward conversion 4 200812208. Among them, the interleaved double-tube forward converter ίο mainly consists of four switches S1~S4, four primary side diodes (1)~仏2: Ai, Yigong 1, and two: two rectifying diodes on the underside The body ^^~ sink and ―=, the diode D7, and the output filter inductance L and the chopper electric valley (one forming a filter circuit). The first-stage converter is composed of power semiconductor components, and the figure is represented by a milk-effect transistor (^40卯£; as for the first and second side coils of the transformer τBai) The ratio is Ν: 1. The long = two diagram is the interleaved double-tube forward conversion for the first graph: the timing diagram when each = 1 is controlled, where the horizontal axis is; & The two diagrams of the conduction (〇Ν)/off (〇ff) of each transistor switch are in the case of the control method of the second figure, and the different sides of the father-type double-tube forward converter of the figure are respectively The electric waveform of the diode is repeated. It should be noted that the W system at each moment corresponds to the time in the third diagram; the operation of the second and third diagrams simultaneously refers to the operation of the double-tube positive conversion H. The rib. The α brother uses the father of the figure to correct the method at the time t0 'the transistor switch S1*S2 is turned on, the second side of the positive one pole D5 is turned on, the wheel is into the thunder, @ 'head to the wheel end (four)) ^纠Vmsti§_T〗 敕ί 'Switch S1 and S2 are simultaneously turned off' At this time, the secondary side of the positive / melon - polar body D5 is subject to reverse emperor, righteous, so the secondary side of the disease, ώ After the reverse recovery Syrian raw material two high I cut simultaneously, and the primary-side basket 02 River turned repeatedly becomes reset at ~ 200 812 208 Pressure in ECG. At this time, the current flowing through the rectifying diode D5 is transferred to the freewheeling diode D7, and when the exciting current is reduced to zero, the currents of the diodes D1 and D2 are naturally zero-crossed and turned off. At time t2, the transistor switches S3 and S4 of the other converter are turned on, the rectifying diode D6 is turned on, and the freewheeling diode D7 on the secondary side is subjected to the reverse voltage, and the reverse recovery is performed, and the freewheeling is performed. The current of the diode D7 goes to the rectifying diode D6. At this time, the highest reverse voltage of the rectifying diode D5 is 2Vin/N+Vspike; wherein Lu Vspike is the voltage peak generated by the reverse recovery of the freewheeling diode D7. In the above analysis of the working principle of the interleaved two-switch forward converter for the conventional control mode shown in the second figure, it can be seen that when the transistor switches SI, S2 are turned off, the load current is rectified by two. The pole body D5 is transferred to the freewheeling diode D7, and when the transistor switches S3, S4 are turned on, the load current is transferred from the freewheeling diode D7 to the rectifying diode D6. It can be seen that in a complete working cycle, the secondary side diodes have a total of four reverse recovery, two of which are generated by the φ rectifying diodes D5 and D6, and the other two by the reading two. The polar body D7 is produced. Therefore, in the interleaved two-switch forward converter of the first figure, the control method of the second figure is used, which causes a large switching loss due to reverse recovery on the diode on the secondary side of the transformer, so that the conversion is performed. The overall efficiency of the device 10 is reduced. Please refer to the fourth figure, which is a circuit diagram of another interleaved two-switch forward converter disclosed in the case of Japanese Patent Laid-Open No. 10-4680. Compared with the first figure, the interleaved double-tube forward converter 40 is omitted. Going to the continuation of the stream 6 200812208 will be described later. The fifth diagram shows the operation of each transistor for the first tube forward converter. The mouth and the wrong type "it: diagram: the control mode is different: in the electric body is to turn it on and off the time is controlled before the electric body switch S2 and S4 are turned on and off respectively and After that, as shown in the fifth circle. Before the time of to, the transistor switch S1 is in the shape energy, + (negative conduction - S1 is still missing t guide: engraved); crystal switch S2 is turned off, but the transistor switch is V-pass, the free-wheeling dipole on the primary side Body D1 is turned on, converted to ❿ pressure: two load current and excitation current along the transistor switch S Bu two: body ^ coffee freewheeling, and the load current still flows through the rectification two t2 moment, the transistor switch % conduction, arrived The voltage of the flying voltage is changed to be lower positive and negative; in this reverse electric body D6 - the load current of the polar body D5 is turned to the rectifying diode _: 々丨L, """ When the current is reduced to zero, the diode D5 is converted to the load current flow of the secondary side, T2, the secondary side freewheeling diode W, and the transistor switch 7 200812208. S3 〇 at the moment 'electricity The crystal switch S4 is turned on. The primary side diode D3 of the primary side is subjected to the reverse voltage of Vin, so that the diode D3 is turned off after the reverse recovery occurs; the input voltage source Vin transmits energy to the secondary side via the transformer T2. The working principle of the interleaved two-switch forward converter shown in the fourth and fifth figures above The analysis shows that by changing the traditional control mode of the second figure, the crystal switches SI, S2 (S3, S4) are not turned on and off at the same time, but according to the timing shown by the fifth circle. The switch is switched so that the load current is diverted from the diode D5 to the diode D6 (or directly from the diode D6 to the diode D5), and no longer passes through the freewheeling diode D7; this is The foregoing secondary side freewheeling diode D7 can be omitted. Other advantages are that reverse recovery of the two read current diodes is avoided within one cycle, and the reverse recovery switch is reduced. However, the disadvantage of the control method of the fifth figure is that the primary side _ freewheeling diodes D1, D3 will be cut off under the reverse voltage of Vin when the load current flows, resulting in a strong Reverse recovery, which brings additional reverse recovery loss. For the sake of the job, the applicant, in view of the lack of the above two conventional techniques, was carefully tested and researched, and the spirit of perseverance was finally conceived. The following is a brief description of the case. [Summary of the Invention] The invention provides an control method for an interleaved double-switch forward converter. The method for controlling the interleaved double-switch forward converter is as follows: the converter includes a power semiconductor switch and a first diode. The sigh power semiconductor open _- terminal is connected to the cathode of the first diode to form a high voltage end of the wheeled power supply; a second power semiconductor switch and a second diode are the first / 丨, - ^ friends: 7 a power semiconductor is connected to the anode of the first diode,
極連接於該第—功率半導體開關的 另端，且该第二二極體的陽極連接於該第二功率半 ‘體開關的另一端而構成一輸入電源低麗端； 一第三功率半導體開關及一第三二極體，該第三 功率半導體開_—端連接於該第三二極體的陰極並 且連接至該輸入電源高壓端； 一第四功率半導體開關及一第四二極體，該第四 功士半導體開關的-端連接於該第三二極體的陽極， 該第四二極體的陰極連接於該第三功率半導體開關的 另一端’且該第四二極體的陽極連接於該第四功率半 導體開_另—端並且連接至該輸人電源低壓端； -第-變壓器，其一次側線圈之第一端連接於該 第-功率半導體_與該第二二極體之連接節點，並 -次侧_之第二端連接於功率半導體開關盘 該第一二極體之連接節點； 、 一第一整流開關，其第一端連接於該第一變壓哭 之二次侧線圈的第一端； " -第二變壓器，其一次側線圈之第一端連接於該 200812208 第三功率半導體開關與該第四二極體之連接節點，宜 -次側關H連接於_四功率铸體開關ς 該第三二極體之連接節點，其二次側線圈之第二端連 接至該第一變壓器之二次侧線圈的第二端.及 一第二整流開關，：a：第一端丄車垃兮’外 J /、罘知連接於該第二變壓哭 之二次側線_第-端，其第二端連接於該: 開關的第二端；. 正桃 该控制方法包括步驟如下： ⑻在一控制週期之内，於t。時刻關斷該第一功率 +導體開關，並保持該第二功率半導體開關導通； 關 (b)於時刻同時導通該第三與第四功率半導體 並於t2時刻關斷該第二功率半導體_.、汗 ⑷於t3__該第三功率半導體開關； 關；WM時刻同時導通該第—與第二功率半導體開 忘舌(:)於t5時刻關斷該第四功率半導體開關，之後依 序重覆上述步驟以進行下一控制週期； 其中，to〈h〈t2〈t3〈t4〈t5。’ 驟如=者，該轉換器更包括—第二控制方法， 半導=二控制週期之内，於t。時刻開通該第二； ^關’並保持㈣—功率半導體開關導通； 於tl Ν'刻關Wf該第二功率半導體開關； t2時刻開通該第三功率半導體開關% )於t3時刻關斷該第一功率半導體開關； 10 200812208 (6)於（4軸開通四功率半導體關； (f)於t5時刻關斷該第四功率半導體開關; ⑻於㈣刻開通該第—功率半導體開關； 時刻關斷該第三功率半導體 後 依序重覆上述步驟以進行下一控制週期;傻 其中， 方沐當態情況下’該轉換器採用該第—控制 制方法。呆持時間的狀態下，該轉換器採用該第二控 較佳者，其中該第一變壓器之一次側線 一 數比與該第二變壓器之-次侧線圈相; ――人側線圈之匝數比相等。 了 較佳者，其中該#整流開關係為二極體。 流開ίΐ佳^其中該等變麼器之二次側更㈣妾於一續 接二：，：：：=連接於該第一與第二整流開關之連 的Μ，，、、广弟一端連接於該第一變壓器之二次側線圈 更連中該第一與第二整流開關之連接節點 —據波電^電路’該滤波電路包括一遽波電感及 控制=另::=種交錯式雙管正— 一第一主轉換電路，包括： 一第一開關及一第五開關，該第—開關 11 200812208 的弟連接於该弟五開關的第_端而構成一輸入電 源高壓端； ^ 一第二開關及一第六開關，該第二開關 ，第端連接於該第五開關的第二端，該第六開關的 =連接於該第一開關的第二端，且該第六開關的 第連接於該第—開關的第二端而構成—入 低壓端; y 、 一第一變壓器，其一次侧線圈之第一端 連接於該第一開關與該第六開關之連接節點，其一次 圈之第—端連接於該第五開關與該第二開關之連 接卽點；及 一緣芦^ 第―整流開關，其第—端連接於該第 夂i态之—次侧線倒的第一端；及 mi 一第ΐ主轉換電路’由第三、第四、第七、第八 :L:弟严器以及一第二整流開關所構成，其 連接!1係刀別與該第-主開關電路之内的第一、第 第六開關、該第一變壓器以及該第-整η 二:::/且該第二主轉換電路並編於:； 该控制方法包括步驟如下： 別（1^制週期之内，力t〇時刻關斷一 關，並保持該第二開關導通·， 弟開 ⑻於t]時刻同時導通該第三與第四 k刻關斷該第二開關; 1關亚於b (c)於時刻關斷該第三開關·， 12 200812208 ^於％時刻同時導通該第一與第二開關； 牛骤以^ /5吩刻關斷該第四開關，之後依序重覆上述 步驟=進行下—控制週期； 二中 t〇〈，〈 k〈 t3〈 t4〈 t5。 控制方=再:::=:種交錯式雙管正激轉換器之 轉換電路U固彼此並聯的主轉換電路(跑3)，每一主 第-控制開關的第流開關’該 端而構成-輪入電源ΐ:於㈣-糊關的第- 第二控制開關第，續流開關’該 端，1 m n 運接於该弟一績流開關的第二 的第二端端連接於該第—控制開關 控制開關的第二端：:：開：的第二端連接於該第二 =而構成一輪入電源低壓端； —弟一變壓哭，甘 u ，、上 連接於該第一抑制其一次侧線圈之第一端 點，i二？開關與該第二續流開關之連接節 點，其一次側線圈之 从 m心迓按即 該第二控制開關之連接^連^於該第一續流開關與 壓器之二次側:以關端其及第 該控制方法包括步驟如 在一控制週期之内，· ⑻於tp時刻針對第ρ個主轉換電路關斷其第-控 13 200812208 制顧㈣其帛二㈣咖絲導it狀態； >(b)於tp+1枯刻針對第p+1個主轉換電路同時導通 其第一、第二控制開關； (C)於tp+2時刻針對第卩個主轉換電路關斷該第二 控制開關； (d)在之後的各個時刻依序針對第P+i個，第p+i+1 個主轉換電路重覆上述步驟⑻〜(c);及 一並於針對第一個主轉換電路同時導通其第一與第 控制開關之後才關斷第M個主轉換電路的該第二個 其中，i=0，nim.，M。 ’俾得更深入之 本案得藉由下列圖式及詳細說明 了解·· 【實施方式】 一圖或第四圖之交 由於轉換器10或 完整敘述，因此此 本案之控制方法可以應用於第 錯式雙管正激轉換器10或40中， 40之電路結構已於前述發明内容中 處不加以贅述。 對第六圖，其為制本案所提出之控制方, 體二：或弟四圖之交錯式雙管正激轉換器的各電, 圖可4日體開闕的導通_/關斷(OFF)狀態。由第ί :不同^之=與：二_用的控制方: 处在於開關S1和S2係同時導通，但不同挺 14 200812208 Γπ^ ^ 在開關si導通後，開關S4才闕斷。 以第六圖的時序圖來看，在一控制週期之内，係 ，時刻關斷開關S1 ’開關S2仍保持導通狀能。輪 斷開關S2m3時刻，關斷關83，於14時刻同時導 :=S1、S2。最後.，於t5時刻關斷㈣ 後的t刻依序重覆上述步驟以進行下-控制週期， 且於同時導通開關S1 # 82之後才關斷開關S4。 這種控制方法的特點在於，既可以減小二次的 反向恢復損耗，X可叫免—讀之 向恢復。 從筱的反 篦：：笛則為在配合第六圖之控制方法的情形下、 ^-，(或弟四圖)之交錯式雙管正激轉換器中各變壓 态與〃一次侧各二極體之電壓波形圖。要注棄β， 第七圖中的各時刻點tQ〜t5係完全對應於 時刻點。 口甲的各 以下同時參考第六圖與第七圖說明本案之气 雙管正激轉換器的控制方法。值得—提的是，盘^ 相同’圖中的功率半導體開關皆係以金氧半場效带曰 體ΐ表Γ ’ D1〜D 4則是選用耐壓等級較高的二極i日，曰 ^變壓器ΤΙ、T2的一、二次侧線圈匝數比則均為N: ， 在10時刻之前’電晶體開關S1和S2同時導通 200812208 輸入電壓源Vin經開關SI、S2、變壓器T1向二次侧 傳輸能量，負載電流流經整流二極體D5。 在t〇時刻，開關S1關斷，但開關S2仍然保持導 通，一次侧的續流二極體D2導通，折算到一次側的負 載電流和激磁電流沿著變壓器T1、開關S2 —次側以 及續流二極體D2進行續流，變壓器T1兩端電壓為零。 在t!時刻，電晶體83和84導通，輸入電壓源¥出 加在變壓器T2上，此時變壓器T2兩端的電壓為上正 φ 下負，流經整流二極體D5的電流在這個反向電壓的作 用下轉移到整流二極體D6，二極體D5的電流減小到 零發生反向恢復後截止。流過變壓器T1二次側的負載 電流轉移到變壓器T2，此時，只剩下激磁電流在變壓 器T1的一次侧沿著變壓器T1、開關S2和二極體D2 進行續流。 在t2 B寺刻，開關S2關斷，一次侧的續流二極體 D1導通，變壓器一次侧的電壓變為一Vin，此時，整 φ 流二極體D5所承受的最大反向電壓為2Vin/N。變壓 器T1在一 Vin的作用下復位，激磁電流減小。而當激 磁電流減小至零時，一次侧的續流二極體D1和D2自 然過零截止，變壓器T1的激磁電感開始與電晶體開關 S1和S2的寄生電容諧振。 在t3時刻，電晶體開關S3關斷，一次侧的續流二 .極體D4導通，變壓器T2兩端電壓從Vin變為零，並 在下一個時刻之前最終將變壓器T1的兩端鉗位至 零，同時使得開關S1和S2上的電壓變為Vin/2,等待 16 200812208 下一個週期開通。 t4時刻時’電晶體開關S1、S2導通，電流從二極體 D6轉移至二極體D5;輸入電壓Vin經開關SI、S2,變 壓器T1向二次側傳輸能量。 至t5時刻，電晶體開關S4關斷，一次侧的續流二 極體D3導通，變壓器T2在一Vin的作用下復位，激 磁電流減小。此時，整流二極體D6所承受的最大反向 電壓為2Vin/N 〇 透過上述對第六圖所示的控制模式下交錯式雙管 正激轉換器工作原理的分析，可以看出：流過整流二 極體D5的負載電流，在開關S1關斷之後仍然流過開 關D5續流。直到開關S3、S4導通之後，負載電流從 整流二極體D5直接轉移到整流二極體D6，而不再經 過續流二極體D7，因此，續流二級體D7可以省略。 由此可知，本案所提第六圖之控制方法可以同時應用 在第一圖及第四圖所示的電路架構中。在一個完整的 週期内，二次侧二極體一共只發生兩次的反向恢復… 分別是整流二極體D5和D6。因此，在第六圖所示的 控制模式下，兩次由續流二極體D7產生的反向恢復便 可以被避免，相應二次侧二極體的反向恢復損耗亦可 以減小。同時，因為避免了續流二極體的反向恢復， 因此不存在因為續流二極體反向恢復所產生的電壓尖 峰。相對於第二圖所示的習用之控制模式，利用本案 的控制方法進行控制的轉換器之整流二極體可承受的 最大反向截止電壓係由2Vin/N+Vspike減小到2 Vin/N， 17 200812208 如果便可以選取耐壓等級相對較低的整流二極體，其 正向導通壓降(VF)更小，減小了通態損耗，亦進一步 提升了效率。 相對於第五ffl所示的第二種習用之交錯式雙管正 激轉換器的控制模式，在第六圖所示的控制方法下， 其一次侧的續流二極體D1、D2(D3、D4)均在電流過 零時自然截止，避免了在第五圖所示的控制模式下， 一次侧績流二極體流過負載電流時、在Vin的反向電 壓作用下截止而產生較強之反向恢復的情形，也避免 了因一次侧續流二極體的反向恢復所帶來的附加損耗 和電壓尖峰。 請參閱第八圖，其為第四圖之交錯式雙管正激轉 換器的第一種變化型電路，其中轉換器80僅係將第四 圖之交錯式雙管正激轉換器的二次侧整流二極體更換 為金氧半場效電晶體S5、S6，其同樣可以使用本案之 控制方法。 請參閱第九圖，其為第四圖之交錯式雙管正激轉 換器的第二種變化型電路，其中轉換器90僅係將第四 圖之交錯式雙管正激轉換器的一次侧續流二極體更換 為金氧半場效電晶體S5〜S8，其同樣可以使用本案之 控制方法。 請參閱第十圖，其為第四圖之交錯式雙管正激轉 換器的第三種變化型電路，若將電路方塊1001視為一 主轉換電路，則轉換器100係由Μ個主轉換電路彼此 並聯所構成，其中Μ-3，其同樣可以使用本案之控制 18 200812208 请參閱第十一圖，其為使用本案所 夕 第十圖之摩，路交錯式雙管正激轉換 電晶體開關進行控制時的時序圖。 、广、 以第十-圖的時序圖來看，在一控制週期之内， 於to時刻針對第一個主轉換電路 門 ，保持導通；接著於tl時刻，針對第二個The pole is connected to the other end of the first power semiconductor switch, and the anode of the second diode is connected to the other end of the second power half-body switch to form an input power supply low end; a third power semiconductor switch And a third diode, the third power semiconductor is connected to the cathode of the third diode and connected to the high voltage end of the input power; a fourth power semiconductor switch and a fourth diode, The end of the fourth power semiconductor switch is connected to the anode of the third diode, the cathode of the fourth diode is connected to the other end of the third power semiconductor switch and the anode of the fourth diode is connected The fourth power semiconductor is turned on and connected to the low voltage end of the input power source; a first transformer having a first end of the primary side coil connected to the first power semiconductor and the second diode Connecting the node, and the second end of the secondary side is connected to the connection node of the first diode of the power semiconductor switch panel; and a first rectifier switch, the first end of which is connected to the first transformer The first end of the side coil; " a second transformer having a first end of the primary side coil connected to the connection node of the 200812208 third power semiconductor switch and the fourth diode, and a secondary side switch H connected to the _four power cast switch ς a connecting node of the triode body, the second end of the secondary side coil is connected to the second end of the secondary side coil of the first transformer. And a second rectifying switch, a: the first end brakes 'External J /, knowingly connected to the second side line _ first end of the second variable pressure crying, the second end of which is connected to the second end of the switch; the peach control method comprises the following steps: (8) Within a control cycle, at t. Turning off the first power + conductor switch and keeping the second power semiconductor switch turned on; turning off (b) turning on the third and fourth power semiconductors at the same time and turning off the second power semiconductor at time t2. , sweat (4) at t3__ the third power semiconductor switch; off; WM simultaneously turns on the first and second power semiconductor open tongue (:) at time t5 to turn off the fourth power semiconductor switch, then repeat in sequence The above steps are performed for the next control cycle; wherein, to <h<t2<t3<t4<t5. For example, the converter further includes a second control method, semi-conductance = two control cycles, at t. Turning on the second at any time; ^OFF' and keeping (4) - the power semiconductor switch is turned on; tw Ν 'cutting Wf the second power semiconductor switch; t2 turning on the third power semiconductor switch %) turns off the first at t3 A power semiconductor switch; 10 200812208 (6) in (4 axis turn-on four power semiconductor off; (f) turn off the fourth power semiconductor switch at time t5; (8) turn on the first power semiconductor switch in (4); After the third power semiconductor, the above steps are repeated in sequence to perform the next control cycle; in the case of the square, the converter adopts the first control method. In the state of staying time, the converter The second control is preferred, wherein the first side line ratio of the first transformer is equal to the second side coil of the second transformer; the turns ratio of the human side coil is equal. Preferably, wherein #Rectification open relationship is a diode. Flow open ίΐ佳 ^ The secondary side of the device is more (4) 一 Continuation 2:,:::= is connected to the first and second rectifier switch The end of the Μ,,,,,, The secondary side coil of a transformer is further connected to the connection node of the first and second rectifying switches - according to the wave circuit ^ the filter circuit comprises a chopper inductor and control = another:: = interlaced double tube positive - one The first main conversion circuit includes: a first switch and a fifth switch, wherein the first switch 11200812208 is connected to the _th end of the fifth switch to form an input power supply high voltage terminal; ^ a second switch and a sixth switch, the second switch, the first end is connected to the second end of the fifth switch, the second switch is connected to the second end of the first switch, and the sixth switch is connected to the second switch The second end of the first switch constitutes a low voltage end; y, a first transformer, the first end of the primary side coil is connected to the connection node of the first switch and the sixth switch, and the first one of the cycles The end is connected to the connection point of the fifth switch and the second switch; and the first edge of the first rectification switch, the first end of which is connected to the first end of the second side line of the 夂i state; Mi a ΐ main conversion circuit 'by the third, fourth, seventh, eighth: L: And a second rectifier switch, which is connected to the first and sixth switches in the first-main switch circuit, the first transformer, and the first-n-n two::: And the second main conversion circuit is programmed in:; the control method includes the following steps: (In the 1^ system cycle, the force t〇 moments off a level, and keeps the second switch turned on, and the brother opens (8) Turning the third switch on the third and fourth k moments simultaneously at time t]; 1 turning off the third switch at time b (c), 12 200812208 ^ turning on the first at the time of % And the second switch; the cow suddenly turns off the fourth switch by ^ /5, and then repeats the above steps in sequence to perform the next-control cycle; two in t〇<, <k<t3<t4<t5. Control side = re:::=: the conversion circuit of the interleaved double-tube forward converter U is connected to the main conversion circuit (running 3) in parallel with each other, and the first-stage switch of each main-control switch constitutes the end - Turning in the power supply ΐ: in the (four) - paste off the second - second control switch, the freewheeling switch 'the end, 1 mn is connected to the second end of the second stream of the diver switch is connected to the first - control the second end of the switch control switch::: open: the second end is connected to the second = and constitutes a low-voltage end of the wheeled power supply; - the younger one presses the crying, the Gan, and the upper is connected to the first suppression The first end of its primary side coil, i? a connection node of the switch and the second freewheeling switch, wherein the connection of the primary side coil from the m-cardary ring, that is, the connection of the second control switch is connected to the secondary side of the first freewheeling switch and the pressure device: And the first control method includes the steps of, for example, within a control period, (8) turning off the first control for the ρ main conversion circuit at time tp, and the second (four) coffee guide state; > (b) simultaneously turning on the first and second control switches for the p+1th main conversion circuit at tp+1; (C) turning off the first main conversion circuit at time tp+2 The second control switch; (d) sequentially repeats the above steps (8) to (c) for the P+ith, p+i+1 main conversion circuits at each subsequent time; and together with the first main The second circuit of the Mth main conversion circuit, i=0, nim., M, is turned off after the conversion circuit turns on its first and second control switches. 'The case of getting deeper and deeper can be understood by the following figures and detailed explanations. · Embodiments The intersection of a picture or a fourth figure is due to the converter 10 or a complete description. Therefore, the control method of this case can be applied to the first error. In the double-switch forward converter 10 or 40, the circuit structure of 40 has not been described in the foregoing summary. For the sixth figure, it is the control party proposed in this case. The second power of the two-tube forward converter of the second or the fourth figure is shown as the conduction of the 4th body opening _/OFF (OFF) )status. By the ί: different ^ = and: _ used control: The switch S1 and S2 are simultaneously turned on, but different 14 200812208 Γ π ^ ^ After the switch si is turned on, the switch S4 is cut off. In the timing diagram of the sixth figure, within a control period, the switch S1 is turned off and the switch S2 remains on. At the time of turning off the switch S2m3, the off 83 is turned off, and at the same time at 14 o'clock: =S1, S2. Finally, at step t5, after (4) is turned off (4), the above steps are repeated in order to perform the down-control cycle, and the switch S4 is turned off after the switch S1 #82 is turned on at the same time. This control method is characterized in that it can reduce the secondary reverse recovery loss, and X can be called the read-to-read recovery. From the 篦 篦:: flute is in the case of the control method of the sixth figure, ^-, (or four pictures) of the staggered double-tube forward converter in each of the variable pressure state and the first side of each The voltage waveform of the diode. To discard β, each time point tQ~t5 in the seventh figure corresponds completely to the time point. The following is a description of the control method of the gas double-tube forward converter in this case with reference to the sixth and seventh figures. It is worth mentioning that the power semiconductor switches in the same figure are all in the form of a gold-oxygen half-field effect Γ body Γ ' D1~D 4 is a two-pole i-day with a high withstand voltage rating, 曰^ The turns ratio of the primary and secondary coils of the transformer ΤΙ and T2 are both N: , before 10 o'clock, the transistor switches S1 and S2 are simultaneously turned on. The input voltage source Vin is switched to the secondary side via the switches SI, S2 and T1. The energy is transmitted, and the load current flows through the rectifying diode D5. At time t〇, switch S1 is turned off, but switch S2 remains on, the free-wheeling diode D2 on the primary side is turned on, and the load current and excitation current converted to the primary side are along the transformer T1, switch S2 - secondary side and continued The current diode D2 performs freewheeling, and the voltage across the transformer T1 is zero. At time t!, the transistors 83 and 84 are turned on, and the input voltage source is applied to the transformer T2. At this time, the voltage across the transformer T2 is upper positive φ lower, and the current flowing through the rectifying diode D5 is reversed. Under the action of the voltage, it is transferred to the rectifying diode D6, and the current of the diode D5 is reduced to zero, and the reverse recovery is performed. The load current flowing through the secondary side of the transformer T1 is transferred to the transformer T2. At this time, only the exciting current remains on the primary side of the transformer T1 along the transformer T1, the switch S2, and the diode D2. At the t2 B temple, the switch S2 is turned off, the free-wheeling diode D1 on the primary side is turned on, and the voltage on the primary side of the transformer becomes a Vin. At this time, the maximum reverse voltage that the entire φ-current diode D5 is subjected to is 2Vin/N. The transformer T1 is reset by a Vin and the exciting current is reduced. When the exciting current is reduced to zero, the free-wheeling diodes D1 and D2 on the primary side are naturally zero-crossed, and the magnetizing inductance of the transformer T1 starts to resonate with the parasitic capacitance of the transistor switches S1 and S2. At time t3, the transistor switch S3 is turned off, the freewheeling on the primary side is two. The pole body D4 is turned on, the voltage across the transformer T2 is changed from Vin to zero, and the two ends of the transformer T1 are finally clamped to zero before the next moment. At the same time, the voltage on the switches S1 and S2 is changed to Vin/2, waiting for the next cycle of 16 200812208 to be turned on. At time t4, the transistor switches S1 and S2 are turned on, and the current is transferred from the diode D6 to the diode D5; the input voltage Vin is passed through the switches SI and S2, and the transformer T1 transmits energy to the secondary side. At time t5, the transistor switch S4 is turned off, the free-wheeling diode D3 on the primary side is turned on, and the transformer T2 is reset by a Vin, and the exciting current is reduced. At this time, the maximum reverse voltage of the rectifying diode D6 is 2Vin/N. Through the above analysis of the working principle of the interleaved two-switch forward converter in the control mode shown in the sixth figure, it can be seen that the flow The load current across the rectifying diode D5 continues to flow through the switch D5 after the switch S1 is turned off. Until the switches S3, S4 are turned on, the load current is directly transferred from the rectifying diode D5 to the rectifying diode D6, and no longer passes through the free current diode D7. Therefore, the freewheeling diode D7 can be omitted. It can be seen that the control method of the sixth figure in the present case can be simultaneously applied to the circuit architectures shown in the first figure and the fourth figure. In a complete cycle, the secondary side diodes only have two reverse recoveryes in total... Resonant diodes D5 and D6, respectively. Therefore, in the control mode shown in Fig. 6, the reverse recovery by the freewheeling diode D7 can be avoided twice, and the reverse recovery loss of the corresponding secondary diode can be reduced. At the same time, since the reverse recovery of the freewheeling diode is avoided, there is no voltage spike due to the reverse recovery of the freewheeling diode. Compared with the conventional control mode shown in the second figure, the maximum reverse cutoff voltage that the rectifier diode of the converter controlled by the control method of the present invention can withstand is reduced from 2Vin/N+Vspike to 2 Vin/N. , 17 200812208 If you can select a rectifying diode with a relatively low withstand voltage rating, its forward voltage drop (VF) is smaller, which reduces the on-state loss and further improves the efficiency. Compared with the control mode of the second conventional interleaved two-switch forward converter shown in the fifth ffl, in the control method shown in FIG. 6, the free-wheeling diodes D1 and D2 on the primary side (D3) D4) is naturally cut off when the current crosses zero. It avoids the control mode shown in the fifth figure. When the primary side flow diode flows through the load current, it is cut off under the reverse voltage of Vin. In the case of strong reverse recovery, additional losses and voltage spikes due to reverse recovery of the primary side freewheeling diode are also avoided. Please refer to the eighth figure, which is a first variation of the interleaved two-switch forward converter of the fourth figure, wherein the converter 80 is only the second of the interleaved two-switch forward converter of the fourth figure. The side rectifying diodes are replaced with gold oxide half field effect transistors S5 and S6, and the control method of the present invention can also be used. Please refer to the ninth figure, which is a second variation of the interleaved two-switch forward converter of the fourth figure, wherein the converter 90 is only the primary side of the interleaved two-switch forward converter of the fourth figure. The freewheeling diode is replaced with a gold-oxygen half-field effect transistor S5~S8, which can also use the control method of the present invention. Please refer to the tenth figure, which is a third variation circuit of the interleaved two-switch forward converter of the fourth figure. If the circuit block 1001 is regarded as a main conversion circuit, the converter 100 is composed of one main conversion. The circuits are constructed in parallel with each other, of which Μ-3, which can also use the control of the present case. 18 200812208 Please refer to the eleventh figure, which is the eleventh figure of the present invention, the road interleaved double-tube forward switching transistor switch Timing diagram when performing control. Wide, in the tenth-graph timing diagram, within one control period, at the time of to for the first main conversion circuit gate, keep conducting; then at time t1, for the second
路同時導通其開關S3及S4;再於t瞎别關你轉換電 # t ^ t3 af „1 M ^ §| S3 . ^ ^ ^ ^ ^ 主轉換電路同時導通其開關S5 & S6 ;再於h 斷開關S4Wt6時刻關斷開關 第乂 ： =:w通其開關…;於=: ，關％。由弟六圖及第十—圖可歸納出本案應用於多 路交錯式雙管正激轉換器時之控制方法，其中轉換哭 係由Μ個主轉換電路彼此並聯所構成： 在一控制週期之内， (a) 於tp時刻針對第ρ個主轉換電路關斷其第一控 制開關同時其第二控制開關保持導通狀態；、工 (b) 於Vh時刻針對第p+1個主轉換電路同時導通 其第一、第二控制開關； (c) 於tp+2時刻針對第p個主轉換電路關斷該第二 控制開關; (d)在之後的各個時刻依序針對第p+i個，第p+i+i 個主轉換電路重覆上述步驟(a)〜及 並於針對第一個主轉換電路同時導通其第一與第 19 200812208 二控制開關之後才關斷第Μ個主轉換電路的該第二個 控制開關； 其中，iKU”.，Μ-1，ρ=1,2，·.·，Μ。 對於第六圖所示的交錯式雙管正激轉換器之控制 方法來說，變壓器Τ1(Τ2)的復位開始於開關S2(S4)關 斷之後、激磁電流給開關S1(S3)、S2(S4)之結電容充 電的時刻；相對於第二圖所示的習用控制方法，變壓 器可利用的最大復位時間變短，所以其最大占空比減 小，因此不利於對占空比動態範圍要求較大（諸如保持 時間(hold up time))的場合下。對於這種缺點，一種改 善方案係在穩態過程中，採用第六圖所示的控制方 法，而在動態過程中，則可將控制模式切換到前述習 用的二種控制方法（第二圖及第五圖所示）。 除此之外，還可以使用美國US6,639,814 B2號案 件所提出的恆定電壓復位（CVR)電路，來增加占空比的 動態變化範圍，如第十二圖及第十三圖所示。 綜上所述，本案係提出一種交錯式雙管正激轉換 器之控制方法，其優點在於既可以減小二次側的反向 恢復損耗，又可以避免一次侧之續流二極體的反向恢 復。 本案得由熟悉本技藝之人士任施匠思而為諸般修 飾，然皆不脫如附申請專利範圍所欲保護者。 20 200812208 【圖式簡單說明】 各”體開關進行控二 第三圖：在配合第二圖之制方碑 -圖之交錯式雙管正激轉換各=叫形下、第 各二極體之電壓波形圖；、ϋ斋與其二次側The circuit turns on its switches S3 and S4 at the same time; then turns off your switching power at t瞎# t ^ t3 af „1 M ^ §| S3 . ^ ^ ^ ^ ^ The main conversion circuit turns on its switches S5 & S6 at the same time; h Shut-off switch S4Wt6 time to turn off the switch No.: =:w through its switch...; at =:, off%. From the six brothers and the tenth-graph can be summarized in the case of multi-channel interleaved two-switch forward conversion The control method of the device, wherein the switching cries are formed by connecting the main conversion circuits in parallel with each other: within a control period, (a) turning off the first control switch for the pth main conversion circuit at the time tp while The second control switch is kept in an on state; (b) simultaneously turning on the first and second control switches for the p+1th main conversion circuit at time Vh; (c) for the pth main conversion at time tp+2 The circuit turns off the second control switch; (d) sequentially repeats the above steps (a) to and for the first p+i, p+i+i main conversion circuits at each subsequent time The second control circuit turns off the second control of the second main conversion circuit after the first and the 19th 200812208 control switches are simultaneously turned on by the main conversion circuit. Off; wherein, iKU ", Μ-1, ρ = 1,2, · ·, Μ... For the control method of the interleaved two-switch forward converter shown in the sixth figure, the reset of the transformer Τ1 (Τ2) starts after the switch S2 (S4) is turned off, and the exciting current is supplied to the switches S1 (S3), S2 ( S4) The timing of charging the junction capacitor; compared with the conventional control method shown in the second figure, the maximum reset time available to the transformer becomes shorter, so the maximum duty ratio is reduced, which is not conducive to the duty cycle dynamic range requirement. Larger (such as hold up time). For this shortcoming, one improvement scheme is to use the control method shown in the sixth figure in the steady state process, and in the dynamic process, the control mode can be switched to the two conventional control methods (the second figure and Figure 5). In addition, a constant voltage reset (CVR) circuit as proposed in US Pat. No. 6,639,814 B2 can be used to increase the dynamic range of duty cycle, as shown in Figures 12 and 13. In summary, the present invention proposes a control method for an interleaved double-tube forward converter, which has the advantages of reducing the reverse recovery loss of the secondary side and avoiding the reverse of the free-wheel diode of the primary side. To recover. This case has been modified by people who are familiar with the art, but it is not intended to be protected by the scope of the patent application. 20 200812208 [Simple description of the diagram] Each of the "body switches is controlled by the second picture: in conjunction with the second picture of the square monument - the staggered double-tube forward conversion of each figure = the shape of the second, the second diode Voltage waveform diagram;
第四圖：日本特開平10_46 一種交錯式雙管正激轉換器的電路_案件所揭露之另 第五圖：針對第四圖之交錯式雙管正 各電:¾體開關進行控制時的時序圖；激轉換器的 第/、圖.使用本案所提出之控制方法 — 第四圖之交錯式雙管正激轉換器的 體開關= 控制時的時序圖； 開關進仃 第七圖：在配合第六圖之控制方法的情形下、第 —圖(或帛四圖)之交錯式雙管正激轉換器+各變壓哭 與其一次侧各一極體之電壓波形圖； 第八圖：第四圖之交錯式雙管正激轉換器 一 種變化型電路； 第九圖：第四圖之交錯式雙管正激轉換器的第二 種變化型電路； " 一 第十圖：第四圖之交錯式雙管正激轉換器的第二 種變化型電路； 第十一圖：使用本案所提出之控制方法對第十圖 之三路交錯式雙管正激轉換器的各電晶體開關進行控 21 200812208 制時的時序圖; 第十二圖：使用美國US6,639,814 B2號案件所提 出的恆定電壓復位(CVR)電路的第一種交錯式雙管正 激轉換器之電路圖；及 第十三圖:使用美國US6,639,814 B2號案件所提 出的恆定電壓復位（CVR)電路的第二種交錯式雙管正 激轉換器之電路圖。 鲁 【主要元件符號說明】 10交錯式雙管正激轉換器 40交錯式雙管正激轉換器 80交錯式雙管正激轉換器 90交錯式雙管正激轉換器 100交錯式雙管正激轉換器 1001主轉換電路 C濾波電容 • Cl、C2電容 D1〜D7二極體 滤、波電感 S1〜S8開關 T1〜T2變壓器 Vin輸入電壓源 22Figure 4: Japanese special Kaiping 10_46 Circuit of an interleaved two-switch forward converter _ The fifth picture revealed in the case: the interleaved double-tube positive electric power for the fourth figure: the timing when the 3⁄4 body switch is controlled Figure; the / / diagram of the converter. Use the control method proposed in this case - the body switch of the interleaved two-switch forward converter of the fourth figure = the timing diagram when controlling; the switch enters the seventh figure: in coordination In the case of the control method of the sixth figure, the interleaved double-tube forward converter of the first-graph (or four-figure diagram) + the voltage waveform diagram of each of the transformers and the one-side one of the first-side ones; A four-character interleaved two-switch forward converter is a variant circuit; a ninth diagram: a second variation of the interleaved two-switch forward converter of the fourth figure; " a tenth diagram: the fourth figure The second variation of the interleaved double-switch forward converter; Figure 11: Using the control method proposed in the present invention, the transistor switches of the three-way interleaved two-switch forward converter of the tenth figure are performed. Control 21 200812208 timing diagram; twelfth diagram: use US U Circuit diagram of a first interleaved two-switch forward converter of a constant voltage reset (CVR) circuit proposed in the case of S6,639,814 B2; and thirteenth diagram: a constant voltage proposed in the case of US Pat. No. 6,639,814 B2 A circuit diagram of a second interleaved two-switch forward converter of a reset (CVR) circuit. Lu [main component symbol description] 10 interleaved double-tube forward converter 40 interleaved double-tube forward converter 80 interleaved double-tube forward converter 90 interleaved double-tube forward converter 100 interleaved double-tube forward Converter 1001 main conversion circuit C filter capacitor • Cl, C2 capacitor D1 ~ D7 diode filter, wave inductor S1 ~ S8 switch T1 ~ T2 transformer Vin input voltage source 22