JPS6350955B2 - - Google Patents
Info
- Publication number
- JPS6350955B2 JPS6350955B2 JP55175841A JP17584180A JPS6350955B2 JP S6350955 B2 JPS6350955 B2 JP S6350955B2 JP 55175841 A JP55175841 A JP 55175841A JP 17584180 A JP17584180 A JP 17584180A JP S6350955 B2 JPS6350955 B2 JP S6350955B2
- Authority
- JP
- Japan
- Prior art keywords
- power supply
- positive
- negative
- output terminal
- terminal
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
Links
- 238000010586 diagram Methods 0.000 description 7
- 230000000903 blocking effect Effects 0.000 description 6
- 239000003990 capacitor Substances 0.000 description 2
- 238000010304 firing Methods 0.000 description 2
- 230000008929 regeneration Effects 0.000 description 2
- 238000011069 regeneration method Methods 0.000 description 2
- 238000007796 conventional method Methods 0.000 description 1
- 238000009499 grossing Methods 0.000 description 1
- 230000007257 malfunction Effects 0.000 description 1
- 238000004519 manufacturing process Methods 0.000 description 1
- 238000000034 method Methods 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/505—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means
- H02M7/515—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only
- H02M7/521—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only in a bridge configuration
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Inverter Devices (AREA)
Description
【発明の詳細な説明】
〔産業上の利用分野〕
本発明は大容量ほどメリツトが大きいPWMイ
ンバータに関するものである。DETAILED DESCRIPTION OF THE INVENTION [Field of Industrial Application] The present invention relates to a PWM inverter, which has greater advantages as the capacity increases.
現行の代表的PWMインバータの主回路は、ト
ランジスタ、逆阻止サイリスタ、逆導通サイリス
タ等より成るチヨツパ素子に帰還ダイオードを逆
並列に接続したものをブリツジに接続した回路構
成になつている。
The main circuit of a current typical PWM inverter has a circuit configuration in which a chopper element consisting of a transistor, a reverse blocking thyristor, a reverse conducting thyristor, etc. is connected with a feedback diode in antiparallel to a bridge.
第１図はチヨツパ素子として逆阻止サイリスタ
チヨツパC1〜C6を使用した場合を例示したもの
で、逆阻止サイリスタチヨツパをC1，C2，C3オ
ン→C2，C3，C4オン→C3，C4，C5オン→C4，C5，
C6オン→C5，C6，C1オン→C6，C1，C2オン→C1，
C2，C3オン→と順次動作させ、他はブロツクし
て直流電源Ｅから３相交流モータＭへ３相交流を
供給する。なおD1〜D6は帰還ダイオードである。 Figure 1 shows an example of the case where reverse blocking thyristors C 1 to C 6 are used as stopper elements . , C 4 on → C 3 , C 4 , C 5 on → C 4 , C 5 ,
C 6 on → C 5 , C 6 , C 1 on → C 6 , C 1 , C 2 on → C 1 ,
Turn on C 2 and C 3 in sequence, block the others, and supply three-phase AC from the DC power supply E to the three-phase AC motor M. Note that D 1 to D 6 are feedback diodes.
この第１図に示す現行PWMインバータの一点
鎖線で囲まれた回路を見ると、各相アームが２ケ
の逆阻止サイリスタチヨツパC1，C4，C3，C6，
C5，C2で直流電源Ｅを直に短絡する回路になつ
ているため、誤つて同時にサイリスタチヨツパに
点弧信号が与えられると短絡事故となる危険な回
路方式となつている。なお、第１図のPWMイン
バータにおいて、電源Eoと直列にリアクトル
（図示せず）を接続して短絡保護を行なう様にし
ようとしても、帰還ダイオードD1〜D6からの帰
還電流を電源Eoに吸収できない（帰還電流はD1
〜D6とモータＭ間で流れる）ため原理的に不可
能である。したがつて通常は電源Eoと直列にフ
エーズ（図示せず）を入れて短絡電流を遮断する
様にしているが、この方法では一旦電源短絡した
後に、溶断したフエーズを新しく取替えるための
わずらわしさや、サイリスタチヨツパの誤点弧に
よる短絡事故と無関係に起る外部ノイズ電圧によ
るフユーズの溶断などが問題となる欠点がある。 Looking at the circuit surrounded by the dashed line of the current PWM inverter shown in Fig. 1, each phase arm consists of two reverse blocking thyristor chips C 1 , C 4 , C 3 , C 6 ,
Since the circuit is configured to directly short-circuit the DC power supply E at C 5 and C 2 , this is a dangerous circuit system that could result in a short-circuit accident if firing signals are accidentally given to the thyristor chopper at the same time. Furthermore, in the PWM inverter shown in Fig. 1, even if a reactor (not shown) is connected in series with the power supply Eo to provide short-circuit protection, the feedback current from the feedback diodes D 1 to D 6 will not be transmitted to the power supply Eo. cannot be absorbed (the feedback current is D 1
〜D6 and motor M), it is impossible in principle. Therefore, normally a phase (not shown) is inserted in series with the power supply Eo to cut off the short-circuit current, but with this method, once the power supply is short-circuited, it is troublesome to replace the fused phase with a new one. There are drawbacks such as short-circuit accidents due to erroneous firing of the thyristor chopper and fuse blow-outs due to external noise voltage that occur unrelated.
交流機を駆動するインバータは、文字通り頻繁
な正逆（交流）を行うものであるので、上記２ケ
のサイリスタが同時に点弧されることが絶対にな
いように制御を行うようにすることは勿論、短絡
時の保護をどのように行なうかが重要な問題であ
る。 Since the inverter that drives the alternating current machine literally performs frequent forward and reverse changes (alternating current), it is of course necessary to control the two thyristors mentioned above so that they are never fired at the same time. An important issue is how to protect against short circuits.
この問題について、小容量のものについて従
来、ある程度の対策は行なわれているが、主回路
の構成が基本的に前述のような短絡事故発生の危
険が内在する回路構成となつているので、
1000KW以上の大容量PWMインバータを実現し
ようとする場合、信頼性の非常に高い制御回路と
保護回路を必要とする関係上、高価になり、あま
り実用されていない。 Regarding this problem, some measures have been taken in the past for small-capacity devices, but the main circuit configuration is basically a circuit configuration that has an inherent risk of short circuit accidents as described above.
When trying to realize a large-capacity PWM inverter of 1000KW or more, extremely reliable control circuits and protection circuits are required, making it expensive and not widely used.
そこで本発明は、保護回路の構成が簡単に済む
もの、従つて従来方式より遥かに安価に大容量
PWMインバータを製作し得るものを提供しよう
とするものである。 Therefore, the present invention is designed to simplify the configuration of the protection circuit, and therefore provides a large-capacity device at a much lower cost than the conventional method.
The purpose is to provide something that can be used to manufacture PWM inverters.
本発明は上記の問題点を解決するためになされ
たもので、独立した直流電圧の正、負端子P1，
N1と可変直流電流を出力する正、負出力端子P2，
N2を有し、前記正端子P1から前記正出力端子P2
へ電流が流れるように端子P1，P2間に接続され
た第１のチヨツパCh1と、前記負出力端子N2から
前記負端子N1へ電流が流れる方向に端子N1，N2
間に接続された第２のチヨツパCh2と、前記負端
子N1にアノードが接続され前記正出力端子P2に
カソードが接続されたダイオードD1と、前記正
端子P1にカソードが接続され、前記負出力端子
N2にアノードが接続されたダイオードD2とを備
えた可制御電源装置と、この可制御電源装置を２
個用いて、一方の装置の負出力端子と他方の装置
の正出力端子を接続した直列体を相数個並列接続
した並列体を備え、この並列体の出力端子間に直
流リアクトルと短絡電流によつて動作する遮断器
を直列に接続し、前記２個の可制御電源装置の接
続点をインバータ出力端子としたPWMインバー
タである。
The present invention has been made to solve the above problems, and has independent DC voltage positive and negative terminals P 1 ,
N 1 and positive and negative output terminals P 2 that output variable DC current,
N 2 and from the positive terminal P 1 to the positive output terminal P 2
A first chopper Ch 1 is connected between the terminals P 1 and P 2 so that the current flows to the terminals P 1 and P 2 , and the terminals N 1 and N 2 are connected in the direction that the current flows from the negative output terminal N 2 to the negative terminal N 1 .
a second chopper Ch 2 connected between them; a diode D 1 whose anode is connected to the negative terminal N 1 and a cathode connected to the positive output terminal P 2 ; and a diode D 1 whose cathode is connected to the positive terminal P 1 . , the negative output terminal
A controllable power supply with a diode D2 whose anode is connected to N2 , and a controllable power supply with a diode D2 whose anode is connected to N2.
It is equipped with a parallel body in which the negative output terminal of one device is connected to the positive output terminal of the other device, and several phases are connected in parallel. This is a PWM inverter in which the operating breakers are connected in series and the connection point of the two controllable power supplies is used as an inverter output terminal.
以下図面に基づき、本発明の更に特徴とすると
ころ、並びに実施の態様について説明すれば次の
通りである。 Further features and embodiments of the present invention will be described below with reference to the drawings.
第２図は本発明において可制御電源装置と称す
る基器の回路図を示すもので、Ｅは直流定電圧電
源、Ch1，Ch2は逆阻止サイリスタを使つたチヨ
ツパ、D1，D2は帰還ダイオードである。 Fig. 2 shows a circuit diagram of a basic device called a controllable power supply in the present invention, where E is a DC constant voltage power supply, Ch 1 and Ch 2 are choppers using reverse blocking thyristors, and D 1 and D 2 are choppers using reverse blocking thyristors. It is a feedback diode.
直流電源Ｅとしては、通常、後記実施例の如
く、商用交流電源を整流回路で直流に変換したも
のが使われる。 As the DC power source E, a commercial AC power source converted to DC by a rectifier circuit is usually used, as in the embodiments described later.
本可制御電源装置の特徴は、チヨツパCh1，
Ch2と帰還ダイオードD1，D2の接続を相対する辺
に接続するものを同種となるようにブリツジに接
続し、チヨツパCh1，Ch2は順方向に、帰還ダイ
オードD1，D2は逆方向に接続したことである。 The features of this controllable power supply are Chiyotupa Ch 1 ,
Connect Ch 2 and feedback diodes D 1 and D 2 to the bridge so that they are connected to the opposite side so that they are of the same type. It was connected in the opposite direction.
そして、チヨツパCh1，Ch2の制御は同時に点
弧した時負荷Ｌに電圧が印加するようにしたこと
である。 The control of the choppers Ch 1 and Ch 2 is such that a voltage is applied to the load L when they are fired at the same time.
即ち、第２図に示す可制御電源装置は、直流電
源Ｅの正、負端子P1，N1と可変直流電流を出力
する正、負出力端子P2，N2を有し、前記正端子
P1から前記正出力端子P2へ電流が流れるように
端子P1，P1間に第１のチヨツパCh1を接続し、そ
して前記負出力端子N2から前記負端子N1へ電流
が流れる方向に端子N1，N2間に第２のチヨツパ
Ch2を接続し、且つ前記負端子N1にアアノードが
接続され前記正出力端子P2にカソードが接続さ
れたダイオードD1と、前記正端子P1にカソード
が接続され、前記負出力端子N2にアノードが接
続されたダイオードD2とを設けたものである。 That is, the controllable power supply device shown in FIG. 2 has positive and negative terminals P 1 and N 1 of a DC power source E, and positive and negative output terminals P 2 and N 2 that output variable DC current, and the positive terminal
A first chopper Ch 1 is connected between terminals P 1 and P 1 so that a current flows from P 1 to the positive output terminal P 2 , and a current flows from the negative output terminal N 2 to the negative terminal N 1 . A second chopper between terminals N 1 and N 2 in the direction
Ch 2 is connected to the diode D 1 whose anode is connected to the negative terminal N 1 and whose cathode is connected to the positive output terminal P 2 ; 2 and a diode D2 whose anode is connected to D2.
第３図は、チヨツパCh1，Ch2の動作を示すも
ので、何れもPWM制御される。即ち、点弧期間
TonはＯ〜Tcまで幅制御される。その結果出力
電圧Eoutは
Eout＝Ｅ・2Ton−Tc／Tc
となり−Ｅ〜＋Ｅまで連続的に制御される。 FIG. 3 shows the operation of the choppers Ch 1 and Ch 2 , both of which are PWM controlled. i.e. ignition period
The width of Ton is controlled from O to Tc. As a result, the output voltage Eout becomes Eout=E.multidot.2Ton-Tc/Tc and is continuously controlled from -E to +E.
本発明は、以上の基器（可制御電源装置）を従
来のインバータのようにブリツジ回路状に組み、
その直流電源に対応する部分に１組の保護回路を
設けるようにしたものである。 The present invention combines the above base (controllable power supply device) into a bridge circuit like a conventional inverter,
A set of protection circuits is provided in a portion corresponding to the DC power source.
第４図は本発明の実施例を示すもので、前述の
構成から成る基器（可制御電源装置）S1〜S6を２
組ずつ直列に接続し、その３組の直列接続回路を
並列に接続し、その両端子Ｘ，Ｙ間に短絡電流に
よつて動作する遮断器Swと直流リアクトルＬを
直流に接続し、前記各組の可制御電源装置の共通
接続点Ｕ，Ｖ，Ｗを出力端子とし、それに３相交
流モータＭを接続したものである。図中、CTは
電流検出器、MCは高速度直流遮断機Swを動作
させる電磁装置である。
FIG. 4 shows an embodiment of the present invention, in which the bases (controllable power supplies) S 1 to S 6 having the above-mentioned configuration are connected to two
Three sets of series connected circuits are connected in parallel, and a circuit breaker Sw operated by a short circuit current and a DC reactor L are connected to DC between both terminals X and Y, and each of the above The common connection points U, V, and W of the set of controllable power supply devices are used as output terminals, and a three-phase AC motor M is connected thereto. In the figure, CT is a current detector, and MC is an electromagnetic device that operates the high-speed DC circuit breaker Sw.
この実施例では、直流電源E1として第５図に
示すように商用交流電源E2から変圧器Ｔを介し
て夫々絶縁して交流を取出し、それをダイオード
ブリツジ整流回路DBで整流し、直流コンデンサ
Ｃで平滑化する構造のものを使用した。 In this embodiment, as shown in Fig. 5, the DC power source E1 is used to extract AC from a commercial AC power source E2 through transformers T, respectively insulated, and rectify it in a diode bridge rectifier circuit DB. A structure with a smoothing structure using capacitor C was used.
このPWMインバータは各可制御電源S1，S4，
S3，S6，S5，S2が互いに120゜位相差をもつ可変電
圧可変周波数の正弦波電流を送出するように制御
することにより負荷Ｍに３相可変電圧、可変電流
正弦交流を供給するものである。 This PWM inverter connects each controllable power supply S 1 , S 4 ,
By controlling S 3 , S 6 , S 5 , and S 2 to send out variable voltage variable frequency sine wave currents with a 120° phase difference from each other, three-phase variable voltage, variable current sine AC is supplied to load M. It is something to do.
そして、その場合負荷Ｍに流れる電流は整流さ
れてリアクトルＬに流れる。 In that case, the current flowing through the load M is rectified and flows through the reactor L.
若し、誤動作により、S1とS4，S3とS6又はS5と
S2が同時にオンした場合は、短絡電流が直流リア
クトルＬと高速遮断器Swの直列回路（保護回路）
に流れる。その場合直流リアクトルＬは短絡電流
の立上りを遅くする作用若くは抑制する作用を
し、その間電流検出器CTが短絡電流を検出して
故障を事前に検出し、S1〜S6を制御することによ
りこの電流を抑制する。しかしそれが不可能の場
合は、高速遮断器Swを電磁装置MCが動作させ
てその直列回路を遮断して装置を保護する。 If a malfunction occurs, S 1 and S 4 , S 3 and S 6 , or S 5
If S 2 turns on at the same time, the short circuit current will flow through the series circuit (protection circuit) of DC reactor L and high-speed circuit breaker Sw.
flows to In that case, the DC reactor L acts to slow down or suppress the rise of the short circuit current, while the current detector CT detects the short circuit current to detect a failure in advance and control S1 to S6 . This current is suppressed by However, if this is not possible, the electromagnetic device MC operates the high-speed circuit breaker Sw to interrupt the series circuit and protect the device.
即ち、本発明装置では、高価な高価遮断器Sw
と直流リアクトルＬが全装置に対して一組で済む
特長があり、従来装置に比し非常に優れたところ
である。 That is, in the device of the present invention, the expensive circuit breaker Sw
It has the advantage that only one set of DC reactor L is required for the entire device, which is very superior to conventional devices.
以上説明した第４図に示した実施例は、E1が
整流電源なので、電力を負荷から元の商用電源
E1に戻すことはできない。 In the embodiment shown in Fig. 4 explained above, since E1 is a rectified power supply, power is transferred from the load to the original commercial power supply.
It is not possible to return to E1 .
電力の回生を必要とするときは、回生用PWM
変換装置C11を今一組設け、第４図と同様に接続
し、出力端子にはモータＭの代りに元の電源へ接
続すればよい。 When power regeneration is required, use PWM for regeneration.
Another set of converters C11 may be provided and connected in the same manner as shown in FIG. 4, and the output terminals may be connected to the original power source instead of the motor M.
第６図はその実施例回路を示すもので、E3は
３相商用電源である。この場合６ケの直流電源
E1は第５図のようにして作られるが、第４図の
場合と異なり、バツクパワーを必要としない。第
５図のコンデンサＣを初期充電すれば良く、単な
るポテンシヤル電源である。 FIG. 6 shows the circuit of this embodiment, where E3 is a three-phase commercial power supply. In this case, 6 DC power supplies
E1 is made as shown in Figure 5, but unlike the case in Figure 4, it does not require back power. It is only necessary to initially charge the capacitor C shown in FIG. 5, and it is just a potential power source.
なお第６図における３相交流モータＭ及び商用
電源E3以外に負荷や電源を作りたい場合は、６
ケのPWM変換装置C11と直流リアクトルと高速
遮断器とを増設し、第６図に示すシステムを並列
に接続することにより可能である。 If you want to create a load or power source other than the 3-phase AC motor M and commercial power source E 3 in Figure 6, use 6.
This can be achieved by adding a PWM converter C11 , a DC reactor, and a high-speed circuit breaker, and connecting the system shown in Figure 6 in parallel.
以上のように、本発明によれば保護回路は簡単
な１組の回路装置だけで済むので、近時大型化し
つゝある産業用大容量可変速駆動系を対象とした
PWMインバータの構造として非常に優れたもの
である。
As described above, according to the present invention, the protection circuit requires only one simple set of circuit devices, so it is suitable for industrial large-capacity variable-speed drive systems that are becoming larger in recent years.
This is an extremely superior PWM inverter structure.
こゝでは産業用３相商用電源を用いる産業用大
容量可変速駆動系を対象として説明したが、鉄道
用１相交流電源に適用し、極めて有効であること
は自明である。 Although the description has been made here for an industrial large-capacity variable speed drive system using an industrial three-phase commercial power supply, it is obvious that it is extremely effective when applied to a one-phase AC power supply for railways.
またこゝではチヨツパとして逆阻止サイリスタ
を使用した場合のみ図示したが、トランジスタや
大容量で高速性、耐圧性に優れている逆導通サイ
リスタを使用することもあることは説明する迄も
ないところである。 Also, although only the case where a reverse blocking thyristor is used as a chopper is illustrated here, it goes without saying that a transistor or a reverse conducting thyristor, which has a large capacity, high speed, and excellent voltage resistance, may also be used. .
第１図は従来のPWMインバータの電気回路
図、第２図は本発明に使用する可制御電源装置の
電気回路図、第３図はそのチヨツパの動作を示す
図、第４図は本発明の実施例のブロツク図、第５
図はその可制御電源装置の詳細図、第６図は異な
る実施例のブロツク図である。
S1〜S5……可制御電源装置、E1……直流電源、
C11……PWM変換装置、Ｍ……３相交流モータ、
Ｌ……直流リアクトル、Sw……高速遮断器、CT
……電流検出器、MC……電磁装置。
Fig. 1 is an electric circuit diagram of a conventional PWM inverter, Fig. 2 is an electric circuit diagram of a controllable power supply used in the present invention, Fig. 3 is a diagram showing the operation of the chopper, and Fig. 4 is a diagram of the controllable power supply device used in the present invention. Block diagram of the embodiment, No. 5
The figure is a detailed view of the controllable power supply device, and FIG. 6 is a block diagram of a different embodiment. S 1 to S 5 ... Controllable power supply, E 1 ... DC power supply,
C 11 ...PWM converter, M...3-phase AC motor,
L...DC reactor, Sw...High speed circuit breaker, CT
...Current detector, MC...Electromagnetic device.
Claims (1)
変直流電流を出力する正、負出力端子P2，N2を
有し、前記正端子P1から前記正出力端子P2へ電
流が流れるように端子P1，P2間に接続された第
１のチヨツパCh1と、前記負出力端子N2から前記
負端子N1へ電流が流れる方向に端子N1，N2間に
接続された第２のチヨツパCh2と、前記負端子N1
にアノードが接続され前記正出力端子P2にカソ
ードが接続されたダイオードD1と、前記正端子
P1にカソードが接続され、前記負出力端子N2に
アノードが接続されたダイオードD2とを備えた
可制御電源装置と、この可制御電源装置を２個用
いて、一方の装置の負出力端子と他方の装置の正
出力端子を接続した直列体を相数個並列接続した
並列体を備え、この並列体の出力端子間に直流リ
アクトルと短絡電流によつて動作する遮断器を直
列に接続し、前記２個の可制御電源装置の接続点
をインバータ出力端子としたことを特徴とする
PWMインバータ。1 It has positive and negative terminals P 1 and N 1 of an independent DC power supply and positive and negative output terminals P 2 and N 2 that output variable DC current, and the current flows from the positive terminal P 1 to the positive output terminal P 2 . A first chopper Ch 1 is connected between the terminals P 1 and P 2 so that the current flows, and a first chopper Ch 1 is connected between the terminals N 1 and N 2 in the direction in which the current flows from the negative output terminal N 2 to the negative terminal N 1 . the second tipper Ch 2 and the negative terminal N 1
a diode D 1 whose anode is connected to the positive output terminal P 2 and a cathode connected to the positive output terminal P 2;
Using a controllable power supply device including a diode D2 having a cathode connected to P1 and a diode D2 having an anode connected to the negative output terminal N2 , and two controllable power supply devices, the negative output of one device is It is equipped with a parallel body in which several phases of series bodies are connected in parallel, in which the terminal and the positive output terminal of the other device are connected, and a DC reactor and a circuit breaker operated by short circuit current are connected in series between the output terminals of this parallel body. and a connection point between the two controllable power supplies is an inverter output terminal.
PWM inverter.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP55175841A JPS57101572A (en) | 1980-12-15 | 1980-12-15 | Pwm inverter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP55175841A JPS57101572A (en) | 1980-12-15 | 1980-12-15 | Pwm inverter |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS57101572A JPS57101572A (en) | 1982-06-24 |
| JPS6350955B2 true JPS6350955B2 (en) | 1988-10-12 |
Family
ID=16003147
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP55175841A Granted JPS57101572A (en) | 1980-12-15 | 1980-12-15 | Pwm inverter |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS57101572A (en) |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2508874Y2 (en) * | 1990-06-20 | 1996-08-28 | 株式会社小松製作所 | Mounting structure of hydraulically operated valve |
Families Citing this family (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS5971283A (en) * | 1982-10-15 | 1984-04-21 | 富士電波工機株式会社 | Device for protecting induction heating inverter |
| JPS5971282A (en) * | 1982-10-15 | 1984-04-21 | 富士電波工機株式会社 | Induction heating inverter |
-
1980
- 1980-12-15 JP JP55175841A patent/JPS57101572A/en active Granted
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2508874Y2 (en) * | 1990-06-20 | 1996-08-28 | 株式会社小松製作所 | Mounting structure of hydraulically operated valve |
Also Published As
| Publication number | Publication date |
|---|---|
| JPS57101572A (en) | 1982-06-24 |
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