JPS6322481B2 - - Google Patents
Info
- Publication number
- JPS6322481B2 JPS6322481B2 JP55085047A JP8504780A JPS6322481B2 JP S6322481 B2 JPS6322481 B2 JP S6322481B2 JP 55085047 A JP55085047 A JP 55085047A JP 8504780 A JP8504780 A JP 8504780A JP S6322481 B2 JPS6322481 B2 JP S6322481B2
- Authority
- JP
- Japan
- Prior art keywords
- band
- filter
- frequency
- wavelength
- transmission
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
Links
- 230000005540 biological transmission Effects 0.000 claims description 54
- 238000001914 filtration Methods 0.000 claims description 32
- 238000003379 elimination reaction Methods 0.000 claims description 4
- 230000000903 blocking effect Effects 0.000 claims 4
- 239000003990 capacitor Substances 0.000 description 2
- 238000000034 method Methods 0.000 description 2
- 230000000712 assembly Effects 0.000 description 1
- 238000000429 assembly Methods 0.000 description 1
- 230000004888 barrier function Effects 0.000 description 1
- 238000010586 diagram Methods 0.000 description 1
- 230000000694 effects Effects 0.000 description 1
- 230000005672 electromagnetic field Effects 0.000 description 1
- 238000002955 isolation Methods 0.000 description 1
- 230000004048 modification Effects 0.000 description 1
- 238000012986 modification Methods 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P1/00—Auxiliary devices
- H01P1/20—Frequency-selective devices, e.g. filters
- H01P1/201—Filters for transverse electromagnetic waves
- H01P1/203—Strip line filters
- H01P1/2039—Galvanic coupling between Input/Output
Landscapes
- Physics & Mathematics (AREA)
- Electromagnetism (AREA)
- Control Of Motors That Do Not Use Commutators (AREA)
- Waveguide Connection Structure (AREA)
Description
【発明の詳細な説明】
本発明は、分布常数を有し、特にマイクロスト
リツプ技術によつて平面構造に形成された高周波
伝送ライン用の帯域阻止フイルタに関するもので
ある。DETAILED DESCRIPTION OF THE INVENTION The present invention relates to a band-stop filter for high-frequency transmission lines, which has a distributed constant and is formed in a planar structure, in particular by microstrip technology.
高周波信号の受信を確実にする従来の方法は、
受信機に混合器を設けることである。この混合器
は、一方では周波数がSの有効な高周波信号を受
信し、他方では局部発振器によつて発生される周
波数がOLの信号を受信し、周波数SとOLとの差
に等しい中間周波数FIを発生する。この混合器
には、周波数SおよびOLの伝達を阻止し、最も
弱い周波数FIの伝達を促進させるフイルタ、す
なわち低域通過フイルタまたは少なくとも帯域阻
止フイルタが続かなければならない。 The traditional method of ensuring reception of high frequency signals is
The method is to provide a mixer in the receiver. This mixer receives on the one hand a useful high-frequency signal of frequency S , and on the other hand a signal of frequency OL generated by a local oscillator, with an intermediate frequency FI equal to the difference between frequencies S and OL . occurs. This mixer must be followed by a filter, ie a low-pass filter or at least a band-stop filter, which blocks the transmission of the frequencies S and OL and promotes the transmission of the weakest frequency FI .
このようなフイルタは、“Proceedings of the
４ th European Microwave Conference”，
Montreux，1974年９月，97〜100ページ（第２
図参照）に記載されている増幅器段に、あるいは
“Proceedings of the ５ th European
Microwave Conference”，Hamburg，1975年９
月，296ページ（第４図参照）に記載されている
発振器段に設けられている。しかし、後者の文献
に記載されているように、このフイルタを単独で
用いる場合には、このフイルタの非常に狭い帯域
がしや断され、上述のような目的には適さない。
逆に、数個のフイルタを一緒に用いるならば、広
い帯域がしや断されるが、これは他の欠点が生じ
るという事実によつて、特にこのようにして実現
された総合フイルタは大形となり、混合器に対す
るフイルタの正確な配置が不可能であるという事
実によつて相殺される。 Such a filter is called “Proceedings of the
4th European Microwave Conference”
Montreux, September 1974, pp. 97-100 (Second
(see figure) or “Proceedings of the 5th European
Microwave Conference”, Hamburg, September 1975
It is provided in the oscillator stage described on page 296 (see Figure 4). However, as described in the latter document, when this filter is used alone, its very narrow band is often cut off, making it unsuitable for the purpose mentioned above.
On the contrary, if several filters are used together, a wide band is cut off, but this is due to the fact that other disadvantages arise, especially since the integrated filter thus realized is not very large. , which is offset by the fact that exact placement of the filter relative to the mixer is not possible.
本発明の目的は、あまり満足すべきでないこの
ような妥協を要せず、非常にコンパクトであり、
十分に大きいしや断帯域を有し、混合器に対し適
切に定められた短絡面を与えてこの混合器の効率
を最適にする高周波用の帯域阻止フイルタを提供
することにある。 The object of the invention is to avoid such unsatisfactory compromises and to be very compact;
The object of the present invention is to provide a band-stop filter for high frequencies which has a sufficiently large cut-off band and which provides a properly defined shorting surface to the mixer to optimize the efficiency of the mixer.
本発明帯域阻止フイルタは、特許請求の範囲に
記載の如くの特徴を有する。 The band rejection filter of the present invention has the features as described in the claims.
この第２ろ波素子を、λ2に等しい電気長を有す
る閉ループとし、λ2／４に等しい相互距離にこの
ループ上に設けられた帯域阻止フイルタの入力点
および出力点において高周波伝送ラインに横方向
に接続し、第１ろ波素子をこのループ内に設ける
のが好適である。 This second filtering element is a closed loop with an electrical length equal to λ 2 and transverse to the high frequency transmission line at the input and output points of a band-stop filter provided on this loop at a mutual distance equal to λ 2 /4. Preferably, the first filtering element is provided within this loop.
このようにして構成された帯域阻止フイルタ
は、非常に効率的に非常に小さいスペースを占め
る。その理由は、これら２個のろ波素子の組合わ
せおよびそれらの寸法の適切な選択が、所望のし
や断帯域幅を随意に得らるようにするからであ
る。さらに、これら２個のろ波素子をフイルタの
入力点で同じ箇所に接続することによつて、伝達
を阻止したい信号の短絡面を正確に定める。これ
は、実際にはフイルタの作用をしや独帯域の周波
数と無関係にする（20〜30％）。このフイルタに
よつてしや断される帯域をさらに広くし、および
第１および第１ろ波素子によつてすでに除去され
た２つの周波数帯域の一方または他方のいずれか
の中心周波数の第２調波を除去するためには、こ
のフイルタは、第１周波数帯域の中心周波数の２
倍の周波数の周辺で中心となつている第３周波数
帯域の伝達を阻止し、（ｎ−１）λ2／２に等しい
帯域阻止フイルタの入力点からの距離に２本の伝
送路のうちの一方に並列に設けられた電気長が
λ1／８の４分の１波長フイルタを少なくとも具
え、前記ｎを伝送路の長さに適合する正の整数と
し、あるいは第２周波数帯域の中心周波数の２倍
の周波数の周辺で中心となつている第３周波数帯
域の伝達を阻止し、（ｎ−１）λ2／２に等しい帯
域阻止フイルタの入力点からの距離に２本の伝送
路のうちの一方に並列に設けられた電気長がλ2／
８の４分の１波長フイルタを少なくとも具え、前
記ｎを伝送路の長さに適合する正の整数とするこ
とができる。 Band-stop filters constructed in this way are very efficient and occupy very little space. The reason is that the combination of these two filtering elements and the appropriate selection of their dimensions make it possible to obtain the desired cutting bandwidth at will. Furthermore, by connecting these two filtering elements to the same point at the input point of the filter, the shorting plane of the signal whose transmission is to be prevented is precisely determined. This actually makes the filter's action independent of the frequency of the band (20-30%). The band cut off by this filter is further widened and the second harmonic of the center frequency of either one or the other of the two frequency bands already removed by the first and first filtering elements is In order to remove waves, this filter should be
The transmission of a third frequency band centered around the double frequency is blocked, and one of the two transmission paths is placed at a distance from the input point of the band-stop filter equal to (n-1)λ 2 /2. One side is provided with at least a quarter-wavelength filter with an electrical length of λ 1 /8 installed in parallel, and the n is a positive integer that matches the length of the transmission path, or the center frequency of the second frequency band. The transmission of a third frequency band centered around twice the frequency is blocked, and one of the two transmission paths is placed at a distance from the input point of the band-stop filter equal to (n-1)λ 2 /2. The electrical length provided in parallel to one side is λ 2 /
It may include at least an 8/4 wavelength filter, and the n may be a positive integer matching the length of the transmission path.
以下、本発明を図面に基いて説明する。 Hereinafter, the present invention will be explained based on the drawings.
第１図は、本発明帯域阻止フイルタの２個のろ
波素子を有する第１実施例を示す。この帯域阻止
フイルタは、フイルタを組み入れる伝送ラインの
上部Leが接続される入力点Ｅと、この伝送ライ
ンの下部Lsが接続される出力点Ｓとを有してい
る。本発明によれば、この帯域阻止フイルタは、
第１ろ波素子１０と第２ろ波素子２０とを具えて
いる。これら素子は、第１周波数帯域とこの第１
周波数帯域に隣接する第２周波数帯域との伝送を
それぞれ阻止する。 FIG. 1 shows a first embodiment of the band-stop filter according to the invention with two filtering elements. This band-stop filter has an input point E to which the upper part Le of the transmission line incorporating the filter is connected, and an output point S to which the lower part Ls of this transmission line is connected. According to the invention, this band-stop filter:
It includes a first filtering element 10 and a second filtering element 20. These elements have a first frequency band and a first frequency band.
Transmission with a second frequency band adjacent to the frequency band is respectively blocked.
素子１０は、第１周波数帯域の中心周波数に関
連する４分の１波長λ1に等しい電気長を有する４
分の１波長フイルタを具え、帯域阻止フイルタの
入力点Ｅに設けられている。素子２０は、第１ろ
波素子１０の存在によつて定められる短絡面内で
入力点Ｅにおいて分離され、素子１０をバイパス
し、出力点Ｓにおいて再び一緒になる２本の平行
伝送路２１および２２のアセンブリを具えてい
る。ここに説明する実施例では、第１伝送路２１
は、電気長がλ2／４（λ2は第２周波数帯域の中心
周波数に関連する波長である）円の弧の形をして
おり、第２伝送路２２は、電気長が3λ2／４の円
の余弧の形をしている。伝送路２１および２２が
再び集合する出力点Ｓでは、波長λ2に相当する周
波数を有する信号が逆位相で出力点Ｓに到達し、
この信号のいかなる信号も伝送ラインの部分LSに
は伝達されない。 The element 10 has an electrical length equal to a quarter wavelength λ 1 associated with the center frequency of the first frequency band.
A half-wavelength filter is provided at the input point E of the band-stop filter. The element 20 consists of two parallel transmission lines 21 and It has 22 assemblies. In the embodiment described here, the first transmission line 21
has the shape of a circular arc with an electrical length of λ 2 /4 (λ 2 is a wavelength related to the center frequency of the second frequency band), and the second transmission line 22 has an electrical length of 3λ 2 /4. It has the shape of a co-arc of a circle of 4. At the output point S where the transmission lines 21 and 22 come together again, a signal having a frequency corresponding to the wavelength λ 2 reaches the output point S with an opposite phase,
None of this signal is transmitted to part L S of the transmission line.
明らかなように、この帯域阻止フイルタは、非
常に小さい円周を有している。その理由は、素子
２０のために採用された円形が非常に小さい空間
を要求し、第１ろ波素子が第２ろ波素子の中に設
けられるからである。さらに、本発明帯域阻止フ
イルタによつて与えられる絶縁が優れており、Ｅ
とＳとの間に現われる寄生結合（高次モード）に
よつて制限される（たとえば、数パーセントより
大きい通過帯域を有することを望まないならば、
60dBの減衰を得ることができる）。 As can be seen, this band-stop filter has a very small circumference. The reason is that the circular shape adopted for the element 20 requires very little space and the first filtering element is arranged inside the second filtering element. Furthermore, the isolation provided by the band-stop filter of the present invention is superior and
(e.g., if we do not want to have a passband larger than a few percent,
60dB of attenuation can be obtained).
２本の伝送路の電気長を上述した例の電気長よ
りも長くできることは明らかである。すなわち、
唯一の重要な事実は、２つの電気長のそれぞれが
４分の１波長λ2の奇数倍に等しくなければなら
ず、それらの長さの差がλ2／２（2m−１）に等し
く、出力点Ｓにおいて逆位相が適切に得られるよ
うにすることである（ｍは正の整数である）。ｍ
＝１に相当する上述の例は、最もコンパクトな実
施例に相当する。これは、一方では素子の小さな
寸法が最も重要である応用に対し、他方では電磁
界の良好な集中を与える最も効果的な実施例であ
り、これによつてフイルタが近接効果にあまり応
答しないようにする。 It is clear that the electrical length of the two transmission lines can be made longer than the electrical length of the example described above. That is,
The only important fact is that each of the two electrical lengths must be equal to an odd multiple of the quarter wavelength λ 2 and the difference between their lengths is equal to λ 2 /2 (2m−1), The purpose is to ensure that an appropriate antiphase is obtained at the output point S (m is a positive integer). m
The above example corresponding to =1 corresponds to the most compact embodiment. This is the most effective embodiment, on the one hand, for applications where the small dimensions of the element are of the utmost importance, and on the other hand, giving a good concentration of the electromagnetic field, which makes the filter less sensitive to proximity effects. Make it.
前述した応用においては、波長λ1は混合器（た
とえば高周波ダイオード）に対して企図された周
波数Sの受信した有効な高周波信号に関連した波
長であり、波長λ2は局部発振器により発生された
周波数OLの信号に関連した波長である。伝送ラ
インの下部LSは、混合器を形成する非線形素子に
より発生される周波数がFIの信号のみを受信し、
ろ波素子１０および２０の組み合わせ作用のため
に、周波数SおよびOLの信号は伝送ラインの下
部LSには到達できない。 In the application described above, the wavelength λ 1 is the wavelength associated with the received useful radio frequency signal of frequency S intended for the mixer (e.g. a radio frequency diode), and the wavelength λ 2 is the wavelength generated by the local oscillator. This is the wavelength associated with the OL signal. The lower L S of the transmission line receives only the signal whose frequency is FI , which is generated by the nonlinear element forming the mixer;
Due to the combined action of filtering elements 10 and 20, signals at frequencies S and OL cannot reach the lower part L S of the transmission line.
本発明フイルタによりしや断される周波数帯域
の増大は、第２ａ図に示すように第３ろ波素子３
０を有する場合に得られる。この第３ろ波素子の
目的は、第２周波数帯域の中心周波数の２倍の周
波数の中心にある第３周波数帯域の伝達を阻止す
ることにある。実際には、前述の使用に関連し
て、局部発振器によつて発生される周波数がOL
の信号は、周波数がSの受信された高周波の振幅
より一般に十分に大きい振幅を有し、従つて周波
数がOLのこの信号の第２調波の存在はエネルギ
ーのかなりの損失に相当する。第３ろ波素子３０
の導入によつて、この調波の伝達を阻止し、この
ような伝達から生じる効率の低下を避けることが
できる。必要ならば、第１周波数帯域および第２
周波数帯域の中心周波数の第２調波の周辺で中心
となる第３周波数帯域の伝送を阻止するために第
３ろ波素子を設けることも勿論可能である。 The increase in the frequency band cut off by the filter of the present invention is achieved by the third filter element 3 as shown in FIG. 2a.
It is obtained when it has 0. The purpose of this third filtering element is to block transmission of a third frequency band centered at twice the center frequency of the second frequency band. In practice, in connection with the aforementioned use, the frequency generated by the local oscillator is OL
The signal at has an amplitude that is generally much larger than the amplitude of the received radio frequency at frequency S , so the presence of the second harmonic of this signal at frequency OL corresponds to a significant loss of energy. Third filtering element 30
By introducing , it is possible to prevent the transmission of this harmonic and avoid the loss of efficiency resulting from such transmission. If necessary, the first frequency band and the second
Of course, it is also possible to provide a third filtering element to block transmission of a third frequency band centered around the second harmonic of the center frequency of the frequency band.
両方の場合に、第３ろ波素子３０は、λ2／２に
等しい帯域阻止フイルタの入力端子Ｅからの距離
に第２伝送路２２に並列に設けた４分の１波長フ
イルタである（あるいは伝送路がnλ2／２に等し
い図に示す実施例の伝送路よりも長い場合、ここ
にｎはその伝送路の長さに適合する正の整数であ
る）。第２ろ波素子２０によりろ波された信号の
第２調波を除去することが必要な場合には、前記
フイルタの長さはλ2／８であり、第１ろ波素子１
０によつてろ波された信号の第２調波を除去する
ことが必要な場合にはλ1／８である。 In both cases, the third filtering element 30 is a quarter-wave filter (or alternatively If the transmission line is longer than the transmission line of the embodiment shown in the figure equal to nλ 2 /2, where n is a positive integer matching the length of the transmission line). If it is necessary to remove the second harmonic of the signal filtered by the second filtering element 20, the length of said filter is λ 2 /8 and the length of the first filtering element 1
λ 1 /8 if it is necessary to remove the second harmonic of the signal filtered by 0.
第３ろ波素子３０をリングの外部の伝送路２０
に接続た第２ａ図に対して、第２ｂ図は素子３０
をリングの内部に向けた実施例の変形を示す。追
加のろ波素子の存在にもかかわらず本発明帯域阻
止フイルタが極端にコンパクトであるため、前記
変形例は非常に好適である。 The third filtering element 30 is connected to the transmission line 20 outside the ring.
2a, the element 30 is connected to the element 30 in FIG. 2b.
A modification of the embodiment is shown in which the arrows are directed toward the inside of the ring. Said variant is highly preferred because, despite the presence of additional filtering elements, the band-stop filter according to the invention is extremely compact.
前述したところでは、本発明フイルタの主要な
使用、すなわち高周波受信機における使用につい
て説明した。第３図は、本発明の他の応用を示
す。すなわち、帯域阻止フイルタを、高周波トラ
ンジスタのバイアス回路に設ける。本発明帯域阻
止フイルタを、伝送ライン４１に並列に設けた伝
送ラインの部分４０にその入力点Ｅにおいて（こ
の場合には垂直に）接続する。伝送ライン４１
は、高周波トランジスタ４２およびコンデンサ４
５を具えている。部分４０の長さは、伝送ライン
４１を通過する高周波信号に関連した４分の１波
長に等しい。さらに、このフイルタをその出力点
Ｓにおいて、トランジスタ４２の電力供給回路４
３に（垂直に）接続する。この配置は、ライン部
分４４と帯域阻止フイルタ（たとえば第１図に示
すフイルタ）ライン部４０とライン４１とを経て
バイアス電圧を伝達することによつて、回路４３
はトランジスタ４２のバイアスを行なうことがで
きる。逆に、帯域阻止フイルタによつて形成され
る有効障壁のために、前記ライン４１を流れる高
周波信号は回路４３に達することができない。部
分４０に可能な最高のインピーダンスが与えられ
るときでも、ろ波作用は高効率である。 In the foregoing, the main use of the filter of the present invention, namely the use in a high frequency receiver, has been explained. FIG. 3 shows another application of the invention. That is, a band rejection filter is provided in the bias circuit of the high frequency transistor. A band-rejection filter according to the invention is connected at its input point E to a section 40 of the transmission line parallel to the transmission line 41 (in this case vertically). transmission line 41
is the high frequency transistor 42 and the capacitor 4
It has 5. The length of section 40 is equal to a quarter wavelength associated with the high frequency signal passing through transmission line 41. Further, this filter is connected to the power supply circuit 4 of the transistor 42 at its output point S.
3 (vertically). This arrangement allows the circuit 43 by transmitting the bias voltage through the line portion 44 and the band-stop filter (eg, the filter shown in FIG. 1) through the line portion 40 and line 41.
can bias transistor 42. Conversely, high frequency signals flowing through the line 41 cannot reach the circuit 43 due to the effective barrier formed by the band-stop filter. Even when section 40 is given the highest possible impedance, the filtering action is highly efficient.
本発明は、前述した実施例に限定されるもので
はなく、これら実施例に基づいて本発明の範囲内
で他の実施例も実現できることは明らかである。
特に、第２ろ波素子の２本の伝送路の環状配置
は、明らかに最もコンパクトな配置であり、たと
えば正方形または長方形配置は非常にコンパクト
なままであり、従つて前述の配置と同様に効果的
である。 It is clear that the invention is not limited to the embodiments described above, but that other embodiments can be realized on the basis of these embodiments within the scope of the invention.
In particular, the annular arrangement of the two transmission paths of the second filtering element is clearly the most compact arrangement, for example a square or rectangular arrangement remains very compact and is therefore as effective as the previously described arrangement. It is true.
第１図は本発明帯域阻止フイルタの２個のろ波
素子を有する第１実施例を示す図、第２ａ図およ
び第２ｂ図は本発明帯域阻止フイルタの３個のろ
波素子を有する他の２つの実施例を示す図、第３
図は高周波トランジスタをバイアスするために本
発明をいかに用いることができるかを示す図であ
る。
１０…第１ろ波素子、２０…第２ろ波素子、２
１，２２…伝送路、３０…第３ろ波素子、４１…
伝送ライン、４２…高周波トランジスタ、４３…
電力供給回路、４５…コンデンサ、Le…伝送ラ
インの上部、Ls…伝送ラインの下部、Ｅ…入力
点、Ｓ…出力点。
FIG. 1 shows a first embodiment of the band-elimination filter of the present invention having two filtering elements, and FIGS. 2a and 2b show other embodiments of the band-elimination filter of the present invention having three filtering elements. Diagram showing two embodiments, 3rd
The figure shows how the invention can be used to bias high frequency transistors. 10...first filtering element, 20...second filtering element, 2
1, 22...Transmission line, 30...Third filtering element, 41...
Transmission line, 42...High frequency transistor, 43...
Power supply circuit, 45... Capacitor, L e ... Upper part of the transmission line, L s ... Lower part of the transmission line, E... Input point, S... Output point.
Claims (1)
術によつて平面構造に形成された高周波伝送ライ
ン用の帯域阻止フイルタにおいて、 ａ 入力端子と、 ｂ 第１周波数帯域の伝達を阻止し、この第１周
波数帯域の中心周波数に関連する波長λ1の４分
の１に等しい電気長を有し、帯域阻止フイルタ
の入力端子に接続され、この入力端子の個所に
短絡面を形成する４分の１波長フイルタを具え
る第１ろ波素子と、 ｃ 第１周波数帯域に隣接する第２周波数帯域の
伝達を阻止する閉ループ形の２本の並列伝送路
のアセンブリを具え、これらの伝送路は、帯域
阻止フイルタの入力点と出力点において、前記
高周波伝送ラインを横方向に橋絡する如く接続
され、かつ帯域阻止フイルタの入力点で分離さ
れており、これら２本の伝送路のそれぞれの電
気長を第２周波数帯域の中心周波数に関連する
波長λ2の４分の１の奇数倍に等しくし、これら
電気長の差をこの波長の半分の奇数倍に等しく
し、かつろ波素子を前記閉ループ内に設けた第
２ろ波素子と、 を具えることを特徴とする帯域阻止フイルタ。 ２ 分布常数を有し、特にマイクロストリツプ技
術によつて平面構造に形成された高周波伝送ライ
ン用の帯域阻止フイルタにおいて、 ａ 入力端子と、 ｂ 第１周波数帯域の伝達を阻止し、この第１周
波数帯域の中心周波数に関連する波長λ1の４分
の１に等しい電気長を有し、帯域阻止フイルタ
の入力端子に接続され、この入力端子の個所に
短絡面を形成する４分の１波長フイルタを具え
る第１ろ波素子と、 ｃ 第１周波数帯域に隣接する第２周波数帯域の
伝達を阻止する閉ループ形の２本の並列伝送路
のアセンブリを具え、これらの伝送路は、帯域
阻止フイルタの入力点と出力点において、前記
高周波伝送ラインを横方向に橋絡する如く接続
され、かつ帯域阻止フイルタの入力点で分離さ
れており、これら２本の伝送路のそれぞれの電
気長を第２周波数帯域の中心周波数に関連する
波長λ2の４分の１の奇数倍に等しくし、これら
電気長の差をこの波長の半分の奇数倍に等しく
し、かつろ波素子を前記閉ループ内に設けた第
２ろ波素子とを具え、 第２周波数帯域の中心周波数の２倍の周波数
の周辺で中心を有する第３周波数帯域の伝達を
阻止し、２本の伝送路のうちの一方に並列に設
けられた電気長がλ1／８の４分の１波長フイル
タを具え、かつ帯域阻止フイルタの入力点より
（ｎ−１）λ2／２の距離に位置する（ただしｎ
は伝送路の長さに適合する正の整数）第３ろ波
素子を少なくとも 具えることを特徴とする帯域阻止フイルタ。[Scope of Claims] 1. A band rejection filter for a high frequency transmission line having a distributed constant and formed in a planar structure by microstrip technology in particular, comprising: a) an input terminal; b) transmission of a first frequency band; is connected to the input terminal of the band-stop filter, and has an electrical length equal to a quarter of the wavelength λ 1 associated with the center frequency of this first frequency band, and is connected to the input terminal of the band-stop filter, and has a short-circuited surface at the location of this input terminal. a first filtering element comprising a quarter-wavelength filter forming a filter; c an assembly of two parallel transmission lines in closed loop form for blocking transmission of a second frequency band adjacent to the first frequency band; The transmission line is connected at the input point and output point of the band-elimination filter so as to bridge the high-frequency transmission line in the horizontal direction, and is separated at the input point of the band-elimination filter, and these two transmission lines are equal to an odd multiple of a quarter of the wavelength λ 2 associated with the center frequency of the second frequency band, the difference between these electrical lengths is equal to an odd multiple of a half of this wavelength, and a second filtering element in which a wave element is provided in the closed loop; 2. In a band rejection filter for a high frequency transmission line having a distributed constant and formed in a planar structure by microstrip technology in particular, a. a quarter having an electrical length equal to a quarter of the wavelength λ 1 associated with the center frequency of one frequency band and being connected to the input terminal of the band-stop filter and forming a short-circuit surface at this input terminal; c a first filtering element comprising a wavelength filter; c an assembly of two parallel transmission lines in a closed loop configuration for blocking transmission of a second frequency band adjacent to the first frequency band; The input point and output point of the blocking filter are connected to bridge the high frequency transmission line in the horizontal direction, and are separated at the input point of the band blocking filter, and the electrical length of each of these two transmission lines is the wavelength associated with the center frequency of the second frequency band is equal to an odd multiple of a quarter of this wavelength, the difference between these electrical lengths is equal to an odd multiple of a half of this wavelength, and the filtering element is placed within said closed loop. and a second filtering element provided in one of the two transmission lines to block transmission of a third frequency band centered around a frequency twice the center frequency of the second frequency band. A quarter-wavelength filter with an electrical length of λ 1 /8 is provided in parallel, and is located at a distance of (n-1)λ 2 /2 from the input point of the band rejection filter (however, n
is a positive integer adapted to the length of the transmission path) A band rejection filter comprising at least a third filtering element.
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| FR7916260A FR2460049A1 (en) | 1979-06-25 | 1979-06-25 | BANDWHEEL FILTER FOR A HYPERFREQUENCY TRANSMISSION LINE AND A MICROWAVE TRANSISTOR POLARIZATION CIRCUIT COMPRISING THE FILTER |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS566501A JPS566501A (en) | 1981-01-23 |
| JPS6322481B2 true JPS6322481B2 (en) | 1988-05-12 |
Family
ID=9227049
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP8504780A Granted JPS566501A (en) | 1979-06-25 | 1980-06-23 | Band rejection filter |
Country Status (7)
| Country | Link |
|---|---|
| EP (1) | EP0021523B1 (en) |
| JP (1) | JPS566501A (en) |
| AU (1) | AU536334B2 (en) |
| BR (1) | BR8003890A (en) |
| CA (1) | CA1159118A (en) |
| DE (1) | DE3071590D1 (en) |
| FR (1) | FR2460049A1 (en) |
Families Citing this family (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| FR2510326A1 (en) * | 1981-07-24 | 1983-01-28 | Thomson Csf | LINEAR RESONATOR PASSER FILTER OPEN TO THEIR TWO ENDS |
| FR2517491A1 (en) * | 1981-11-27 | 1983-06-03 | Labo Electronique Physique | COMBINER-MIXER WITH DOUBLE SOURCE TRANSISTOR |
| EP0731521B1 (en) * | 1992-04-30 | 2002-08-28 | Matsushita Electric Industrial Co., Ltd. | Strip dual mode ring resonator and band-pass filter composed of the resonators |
| JP5749133B2 (en) * | 2011-10-04 | 2015-07-15 | 古河電気工業株式会社 | High frequency module |
| JP7133486B2 (en) * | 2019-01-16 | 2022-09-08 | 日立Astemo株式会社 | signal transmission device, signal transmission system |
Citations (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS5352336A (en) * | 1976-10-22 | 1978-05-12 | Mitsubishi Electric Corp | Dividing filter |
Family Cites Families (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| FR72524E (en) * | 1951-05-23 | 1960-04-14 | Int Standard Electric Corp | Transmission system for high frequency |
| BE527584A (en) * | 1952-05-08 | |||
| US3150325A (en) * | 1962-04-12 | 1964-09-22 | Donald J Blattner | Wide band traveling wave parametric amplifier |
| DE2453605B2 (en) * | 1974-11-12 | 1976-09-09 | Siemens AG, 1000 Berlin und 8000 München | WAVE GUIDE COUPLER FOR EQUAL DISTRIBUTION OR INTERCONNECTION OF SIGNAL ENERGY |
| DE2804118C2 (en) * | 1978-01-31 | 1982-03-04 | Siemens AG, 1000 Berlin und 8000 München | Microwave ring hybrid circuit in stripline technology |
| US4185252A (en) * | 1978-05-10 | 1980-01-22 | The United States Of America As Represented By The Secretary Of The Army | Microstrip open ring resonator oscillators |
| FR2451110A1 (en) * | 1979-03-06 | 1980-10-03 | Labo Electronique Physique | MICROWAVE IMAGE FREQUENCY REFLECTION FILTER |
-
1979
- 1979-06-25 FR FR7916260A patent/FR2460049A1/en active Granted
-
1980
- 1980-06-17 DE DE8080200567T patent/DE3071590D1/en not_active Expired
- 1980-06-17 EP EP19800200567 patent/EP0021523B1/en not_active Expired
- 1980-06-18 CA CA000354236A patent/CA1159118A/en not_active Expired
- 1980-06-23 JP JP8504780A patent/JPS566501A/en active Granted
- 1980-06-23 BR BR8003890A patent/BR8003890A/en not_active IP Right Cessation
- 1980-06-23 AU AU59514/80A patent/AU536334B2/en not_active Ceased
Patent Citations (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS5352336A (en) * | 1976-10-22 | 1978-05-12 | Mitsubishi Electric Corp | Dividing filter |
Also Published As
| Publication number | Publication date |
|---|---|
| EP0021523A1 (en) | 1981-01-07 |
| BR8003890A (en) | 1981-01-13 |
| FR2460049B1 (en) | 1983-07-08 |
| FR2460049A1 (en) | 1981-01-16 |
| JPS566501A (en) | 1981-01-23 |
| AU536334B2 (en) | 1984-05-03 |
| AU5951480A (en) | 1981-01-08 |
| CA1159118A (en) | 1983-12-20 |
| DE3071590D1 (en) | 1986-06-12 |
| EP0021523B1 (en) | 1986-05-07 |
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