JPS6173408A - Controlling method of transmitting output - Google Patents
Controlling method of transmitting outputInfo
- Publication number
- JPS6173408A JPS6173408A JP19601884A JP19601884A JPS6173408A JP S6173408 A JPS6173408 A JP S6173408A JP 19601884 A JP19601884 A JP 19601884A JP 19601884 A JP19601884 A JP 19601884A JP S6173408 A JPS6173408 A JP S6173408A
- Authority
- JP
- Japan
- Prior art keywords
- output
- voltage
- control
- amplifier
- directional coupler
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
Classifications
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03G—CONTROL OF AMPLIFICATION
- H03G1/00—Details of arrangements for controlling amplification
- H03G1/04—Modifications of control circuit to reduce distortion caused by control
Landscapes
- Control Of Amplification And Gain Control (AREA)
Abstract
Description
【発明の詳細な説明】
産業上の利用分野
本発明は基地局と移動局から成る無線通信システムにお
いて基地局の受信レベルが過大にならないように基地局
から移動局へ送信出力を規制する信号を送り、例えば移
動局の送信出力を１０数ワツトから数ミリワットまで安
定に制御出来る送信出力の制御方法に関するものである
。DETAILED DESCRIPTION OF THE INVENTION Field of Industrial Application The present invention is a wireless communication system consisting of a base station and a mobile station, in which a signal is sent from the base station to the mobile station to regulate the transmission output so that the reception level of the base station does not become excessive. The present invention relates to a transmission output control method that can stably control the transmission output of a mobile station, for example, from 10-odd watts to several milliwatts.
従来例の構成とその問題点
従来、移動通信用の基地局アンテナには垂直側
゛波、水平面無指性の高利得アンテナが使用されるが
、下方ロブの利得をダイポールアンテナの利得と同程度
に抑圧したものが使用されている。基地局受信機の受信
入力ＰＲは送信電力をＰＴ、伝播損失″ｆ：Ｌｐ、基地
アンテナ利得をＧａ移動■１アンテナ利得ｆ Ｇａ’と
すれば、これらの関係は次式で表される。即ち、ＰＲ＝
ＰＴ−Ｌｐ ＋ Ｇａ ＋ Ｇａ’ となる。Conventional configurations and their problems Traditionally, base station antennas for mobile communications have vertical side antennas.
A high-gain antenna that is omnidirectional in the horizontal plane is used, and one in which the gain of the lower lobe is suppressed to the same degree as the gain of a dipole antenna is used. Assuming that the received input PR of the base station receiver is PT, the transmission power is PT, the propagation loss is f: Lp, and the base antenna gain is Ga. ,PR=
PT-Lp + Ga + Ga'.
ココテ例えば送信電力Ｐ７ ＝ １２ Ｗ （４２ｄＢ
ｍ ）で、基地局アンテナ高が低く、下方ロープに対
する基地局と移動局間距離が７０ｍのときの、周波数９
００ ＭＨｚに対する伝播損失（、Ｌｐ）を求めると約
ｅ ａ ｄＢ となる。また、下方ロープのアンテナ利
得および移動局アンテナの利得をｏ ｄＢとすると基地
局受信入力（ＰＲ）は−２２ｄＢｍ（９１ｄＢｐ ）と
なる。いま、基地局受信機の規容最犬入力ＰＲＱを−４
８ｄＢｍ（６５ｃｉＢｐ ）とすれば、受信入力ＰＲは
許容受信入力ＰＲｏ ｆ ２６ ｄＢも上廻り、これが
基地局受信障害の原因の１つであり、これを軽減するに
は、基地局に近接した移動局の送信出力を低下させる必
要が生じている。For example, transmission power P7 = 12 W (42 dB
m ), when the base station antenna height is low and the distance between the base station and mobile station with respect to the downward rope is 70 m, frequency 9
The propagation loss (, Lp) for 00 MHz is approximately e a dB. Further, if the antenna gain of the lower rope and the gain of the mobile station antenna are odB, the base station reception input (PR) is -22 dBm (91 dBp). Now, the maximum input PRQ of the base station receiver is -4.
8 dBm (65 ciBp), the reception input PR exceeds the allowable reception input PRof 26 dB, and this is one of the causes of base station reception interference.To alleviate this, mobile stations close to the base station It has become necessary to reduce the transmission power of the
従来、移動局の送信出力の制御には第１図のような回路
が用いられる。第１図において、１は送信機の前段部で
あシ、原発振器、変調部、また必要により周波数逓信部
、緩衝増幅部を備えている。Conventionally, a circuit as shown in FIG. 1 is used to control the transmission output of a mobile station. In FIG. 1, reference numeral 1 denotes a front stage section of a transmitter, which includes an original oscillator, a modulation section, and, if necessary, a frequency transmission section and a buffer amplifier section.
原発振器は周波数シンセサイザ等によシ複数のチャネル
にアクセスするように制御されており、数十〜数百ｍＷ
を出力するものである。２は励振部、３は電力増幅ユニ
ット（以下ＰＡ部という）、４は方向性結合器、５はア
イソレータ、６は帯域フィルタ（ＢＰＦ）、７はアンテ
ナを表わしている。The original oscillator is controlled to access multiple channels by a frequency synthesizer, etc., and has a power output of several tens to hundreds of mW.
This outputs the following. Reference numeral 2 represents an excitation unit, 3 a power amplification unit (hereinafter referred to as a PA unit), 4 a directional coupler, 5 an isolator, 6 a bandpass filter (BPF), and 7 an antenna.
一般には送受共用器（図示せず）を経てアンテナに出力
きれる。８は励振部２およびＰＡ部３の電源（ＶＣＣ）
供給端子、９は出力制御端子であり、出力制御信号は受
信機内の制御部（図示せず）から供給される。１ｏは励
振部２およびＰＡ部３への供給電力制御部、１１は電圧
比較器、１６は進行波、１６は直流電圧の可変減衰器、
１８は前記可変減衰器１６の切替スイッチ、１９は送信
出力を制御する基準電圧発生部である。Generally, the signal can be output to an antenna via a duplexer (not shown). 8 is the power supply (VCC) for the excitation section 2 and PA section 3
The supply terminal 9 is an output control terminal, and an output control signal is supplied from a control section (not shown) in the receiver. 1o is a supply power control unit to the excitation unit 2 and PA unit 3, 11 is a voltage comparator, 16 is a traveling wave, 16 is a variable attenuator for DC voltage,
18 is a changeover switch for the variable attenuator 16, and 19 is a reference voltage generator for controlling the transmission output.
次に、上記従来例の動作を説明する。送信機の前段部１
の出力は送信周波数（ｆＴ ’）と同じでその出力は数
十ｍＷ〜数百ｍＷとして励振部２へ加えられる。励振部
２はこの周波数成分を増幅してＰＡ部３を励振する。Ｐ
Ａ部３の出力は方向性結合器４、アイソレータ５ 、Ｂ
ＰＦｅを介してアンテナ７へ出力される。方向性結合器
４では進行波成分の一部を取出し、検波器１６で検波し
、その直流出力は可変減衰器１６を介して電圧比較器１
１に供給される。ここで、基準電圧発生部１９の出力と
比較され、その結果に基いて供給電力制御部１０に制御
電圧を与える。供給電力制御部１Ｑは電圧比較器１１の
電圧により、励振部２およびＰＡ部３の供給電圧を自動
調整して出力を変化させる。Next, the operation of the above conventional example will be explained. Transmitter front section 1
The output is the same as the transmission frequency (fT'), and the output is applied to the excitation section 2 as several tens of mW to several hundred mW. The excitation section 2 amplifies this frequency component and excites the PA section 3. P
The output of part A 3 is directional coupler 4, isolator 5, and B
It is output to the antenna 7 via PFe. A part of the traveling wave component is extracted in the directional coupler 4 and detected by the detector 16, and its DC output is sent to the voltage comparator 1 via the variable attenuator 16.
1. Here, it is compared with the output of the reference voltage generation section 19, and a control voltage is provided to the power supply control section 10 based on the result. The power supply control unit 1Q automatically adjusts the voltage supplied to the excitation unit 2 and the PA unit 3 based on the voltage of the voltage comparator 11, and changes the output.
検波器１５の検波電圧Ｅｄが基準電圧Ｅｓより低い場合
Ｅｄ＜Ｅｓは供給電力制御部１ｏの出力をより高圧にし
、Ｅｄ＞ Ｅ３の場合は供給電力制御部１０からの制御
電圧ＥＣを低下させて、ＰＡ部３の出力があらかじめ設
定された出力に接近するように制御される。切替スイッ
チ１８は出力制御端子９の入力により可変減衰器１６乞
変化させて電圧比較器１１に出力させる。第２図は検波
器１５の検波特性を表わしたものであり、方向性結合器
４からアンテナ７への送信出力の進行波成分Ｐｄに対す
る検波電圧Ｅｄを表したものである。こ＼で検波電圧Ｅ
ｄは送信出力が１０ｄＢの低下に対して３．７■に、２
０ｄＢの低下に対しては１ｖに変化することを示してい
る。しかし、ダイオード検波器の入力が低下して直線検
波領域を外れた場合は検波出力は急激に低下し、−２０
ｄＢ以下ではその変化の判別が困難となり、正確な出力
制御が不可能となる。又−２ｏｄＢ附近で能率良く検波
するためには方向性結合器４の結合を密にする必要があ
るがこれにより挿入損失が増加してアンテナ７からの出
力が低下する欠点がある。これを補償して規定出力を得
るにはその分だけ大出力のＰＡ部が必要となり、電源利
用効率を低下させる欠点があるため、送信出力に関係な
く効率良く出力制御が可能な出力制御方法が要求されて
いる。When the detected voltage Ed of the detector 15 is lower than the reference voltage Es, if Ed<Es, the output of the power supply controller 1o is made higher, and if Ed>E3, the control voltage EC from the power supply controller 10 is lowered. , the output of the PA unit 3 is controlled so as to approach a preset output. The changeover switch 18 changes the level of the variable attenuator 16 according to the input from the output control terminal 9, and outputs the result to the voltage comparator 11. FIG. 2 shows the detection characteristics of the detector 15, and shows the detected voltage Ed for the traveling wave component Pd of the transmission output from the directional coupler 4 to the antenna 7. Here is the detection voltage E
d becomes 3.7■ for a 10dB decrease in transmission output, and 2
It is shown that the voltage changes to 1v for a decrease of 0dB. However, if the input of the diode detector decreases and goes out of the linear detection area, the detection output will drop rapidly and -20
Below dB, it becomes difficult to distinguish the change, and accurate output control becomes impossible. Furthermore, in order to efficiently detect waves around -2 odB, it is necessary to make the coupling of the directional coupler 4 dense, but this has the disadvantage that the insertion loss increases and the output from the antenna 7 decreases. To compensate for this and obtain the specified output, a PA section with a correspondingly high output is required, which has the disadvantage of reducing power usage efficiency, so an output control method that can efficiently control the output regardless of the transmission output is needed. requested.
発明の目的
本発明は前記従来例の欠点を除去するものであり、広範
囲の出力制御を可能とする送信出力の制御方法を提供す
ることを目的とするものである。OBJECTS OF THE INVENTION The present invention eliminates the drawbacks of the conventional example, and aims to provide a transmission output control method that enables a wide range of output control.
発明の構成
本発明は前記目的を達成するために、方向性結合器を疎
結合としてその挿入損失を低下させると共に、増幅器を
用いて進行波成分を増幅したのち検波を行ない送信出力
が極端に低下した状態においても、そのレベル検波器を
直線検波領域で動作可能にして制御誤差を軽減すると共
に、方向結合器と増幅器の間に高周波可変減衰器を挿入
制御して送信出力が大きいときでも前記高周波増幅器の
飽和を防止し、常に直線動作域で動作させて正確な送信
出力の制御を可能にしたものであり、広い出力範囲に亘
って安定確実な出力制限を可能にする効果を得るもので
ある。Structure of the Invention In order to achieve the above-mentioned object, the present invention lowers the insertion loss by loosely coupling the directional coupler, and also uses an amplifier to amplify the traveling wave component and then performs detection, so that the transmission output is extremely reduced. Even when the transmission output is large, the level detector can operate in the linear detection region to reduce control errors, and a high frequency variable attenuator is inserted between the directional coupler and the amplifier to control the high frequency even when the transmission output is large. This prevents the amplifier from saturating and allows it to always operate in the linear operating range, allowing accurate control of the transmission output, and has the effect of enabling stable and reliable output limiting over a wide output range. .
実施例の説明
以下に本発明の一実施例の構成について、図面とともに
説明する。DESCRIPTION OF EMBODIMENTS The configuration of an embodiment of the present invention will be described below with reference to the drawings.
第３図は本発明の制御方法を採用した装置の構成を示す
ブロック図であり、１は送信機の前段部、２は励振部、
３はＰＡ部、４は方向性結合器、５はアイソレータ、６
はＢＰＦ、 ７（ｄアンテナ、８は電源ｖｃｃの電源供
給端子、９は出方制御端子、１０は供給電力制御部、１
１は電圧比較器、１６は検波器であり、これらは第１図
と同様の構成であり、また前段部１．励振部２．ＦＡ部
３によシミ力増幅部を構成する。１２および１３は第１
図の基準電圧発生部１９に相当する部分であり、１３は
出力制御信号で動作する出力の切替スイッチ、１２は基
準電圧発生器である０１４は高部ｇ′帯の可変減衰器、
１８は可変減衰器１４の切替スイッチ、１５は高周波増
幅器、１ｅは検波器、１７は直流増幅器であり、この出
力と基準電圧発生器１２の電圧を比較して送信出方を制
御している。FIG. 3 is a block diagram showing the configuration of a device that employs the control method of the present invention, in which 1 is a front section of a transmitter, 2 is an excitation section,
3 is a PA section, 4 is a directional coupler, 5 is an isolator, 6
is a BPF, 7 (d antenna, 8 is a power supply terminal of the power supply VCC, 9 is an output control terminal, 10 is a supply power control unit, 1
1 is a voltage comparator, 16 is a detector, and these have the same configuration as in FIG. Excitation part 2. The FA section 3 constitutes a stain force amplification section. 12 and 13 are the first
This part corresponds to the reference voltage generation section 19 in the figure, and 13 is an output changeover switch operated by an output control signal, 12 is a reference voltage generator, 014 is a variable attenuator for the upper G' band,
18 is a changeover switch for the variable attenuator 14, 15 is a high frequency amplifier, 1e is a detector, and 17 is a DC amplifier, whose output is compared with the voltage of the reference voltage generator 12 to control the transmission method.
次に、第３図の回路動作について説明する。送信周波数
、／Ｔ酸成分送信機の前段部１から励振部２に入り、そ
の増１福した励振出方をＰＡ部３に加える。その送信出
力はＰＡ部３．方向性結合器４゜フイ７Ｌ／ −夕５．
ＢＰＦｅを経てアンテナへ出力される。方向性結合器４
では送信周波数７丁の進行波成分を検出端子４ａから取
出し、その進行波成分を可変減衰器１４を介して高周波
増幅器１５へ導いて増幅した後検波器１６で検波し、更
に動作を確実にするため増幅して電圧比較器１１に加え
、その出力を供給電力制御部１０へ負帰還し、送信出力
を所定の値に制御している。上記のように方向性結合器
４の進行波成分を検出端子４ａから微小電力として取出
し、検波器」６の直線検波領域まで増幅した後で検波す
るので、検波電圧Ｅｄは送信出力ＰＴの平方根に比例す
る形となるが、それでも送信出力を３０ｄＢｉ度低下さ
せる場合には最高出力と最低出方の検波電圧の比は２０
倍にもなり、これが送信出力制御の誤差の原因となって
いる。Next, the operation of the circuit shown in FIG. 3 will be explained. The transmission frequency /T enters the excitation section 2 from the front section 1 of the acid component transmitter, and its amplified excitation output is applied to the PA section 3. The transmission output is transmitted from the PA section 3. Directional coupler 4°fi 7L/-5.
It is output to the antenna via BPFe. Directional coupler 4
Then, the traveling wave components of seven transmission frequencies are taken out from the detection terminal 4a, and the traveling wave components are guided to the high frequency amplifier 15 via the variable attenuator 14, amplified, and then detected by the detector 16 to further ensure operation. Therefore, the output is amplified and applied to the voltage comparator 11, and its output is negatively fed back to the power supply control section 10 to control the transmission output to a predetermined value. As described above, the traveling wave component of the directional coupler 4 is taken out as a minute power from the detection terminal 4a, amplified to the linear detection range of the detector 6, and then detected, so the detected voltage Ed is the square root of the transmission output PT. However, if the transmission output is still reduced by 30 dBi degrees, the ratio of the detected voltage at the highest output and the lowest output is 20.
This is twice as much, and this causes an error in transmission output control.
第３図の実施例では高周波増幅器１６の飽和出力特性お
よびシリコンダイオードの検波特性の両特性を利用して
指数直線に似た出方特性を得ている。直線域と見做され
る久方変化幅は約２０ｄＥ以下であるので、方向性結合
器４の出力側に設けられた高周波減衰器１４により１６
〜１７ ｄＥの減食を与えて直線検波領域を２＠に拡大
している。In the embodiment shown in FIG. 3, an output characteristic resembling an exponential straight line is obtained by utilizing both the saturation output characteristic of the high frequency amplifier 16 and the detection characteristic of the silicon diode. Since the long-term variation width considered as a linear range is approximately 20 dE or less, the high frequency attenuator 14 provided on the output side of the directional coupler 4
The linear detection area is expanded to 2@ by giving a reduction of ~17 dE.
従って、検波出力の直線領域は３２〜３４ｄＢ以上が得
られる。もし、更に広範囲の制御が要求される場合は減
衰器切替段数を増せばよい。この検波電圧は直流増＠器
およびレベル調整器で制御範囲が直線範囲となるように
調整され、電圧比較器１１に加えて他端の基準電圧発生
器１２の電圧ＥＳと比較される。その出力は励邊部２お
よびＰＡ部３の出力調整のだめの供給電力制御部１０に
加えられる０供給電力制御部１ｏは基準電圧Ｅｓと直流
増幅器１７の出力電圧ＥＡとを比較し、出力電圧ＥＡが
基準電圧ＥｓＫ近着ぐように供給電力制御部１０を調整
すればよい。い−ま、基準電圧Ｅｓに対してＥｓ＜ＥＡ
の場合には供給電力制御部１０の制＃電圧ＥＣを低レベ
ルに、Ｅｓ＞ Ｅｐ、 （Ｄ場合は、制御電圧ＥＣを高
レベルとするよう自動的に制御される。Therefore, a detection output in the linear region of 32 to 34 dB or more can be obtained. If a wider range of control is required, the number of attenuator switching stages may be increased. This detected voltage is adjusted by a DC amplifier and a level adjuster so that the control range becomes a linear range, and is compared with the voltage ES of the reference voltage generator 12 at the other end in addition to the voltage comparator 11. The output is applied to the supply power control section 10 for adjusting the output of the excitation section 2 and the PA section 3. The supply power control section 1o compares the reference voltage Es with the output voltage EA of the DC amplifier 17, and outputs the output voltage EA. The power supply control unit 10 may be adjusted so that the voltage EsK approaches the reference voltage EsK. Now, with respect to the reference voltage Es, Es<EA
In the case of D, the control voltage EC of the power supply control unit 10 is automatically controlled to a low level, and in the case of Es>Ep, the control voltage EC is automatically controlled to a high level.
基準電圧Ｅｓの発生方法には２つ方法が実施されており
、第１の方法は移動局側の受信レベルにより、自局の送
信出力を制御する方法である。勿論、制御に当っては基
地局の実効送信出力Ｐｂと移動局の実効送信出力Ｐｍの
差： １ｏ ｌｏｑ （Ｐｂ／Ｐｍ）と移動局の受信電
力Ｐ１、基地局受信許容レベルＰＲや種々の損失等の補
正値ＣＰを考慮してＰｒ＝ＲＲ−ＣＰ として制限す
る方法である。第２の方法は基地局の受信レベルが許容
受信レベルＰＲに達したとき、又はその以前に移動局に
制御信号を送って、その送信出力を低下させる方法であ
る。Two methods are used to generate the reference voltage Es. The first method is to control the transmission output of the mobile station based on the reception level of the mobile station. Of course, during control, the difference between the effective transmission output Pb of the base station and the effective transmission output Pm of the mobile station: 1o loq (Pb/Pm), the reception power P1 of the mobile station, the base station reception tolerance level PR, and various losses are taken into consideration. This is a method of limiting Pr=RR-CP by taking into consideration the correction value CP such as. The second method is to send a control signal to the mobile station to reduce its transmission output when or before the reception level of the base station reaches the permissible reception level PR.
次に送信出力の変化の仕方であるが、第１の方法は多段
に低下または増加させ、これを通話終了まで基地局の指
示を維持することである。第２の方法は成る制御信号を
受けて送信出力を低下させた場合に、一定時間経過後は
自動的に１段または数段前の制限状態に戻したり、或い
は制限を解除する方法である０第３の方法は成る制限信
号を受けて送信出力を制限しているときに移動局の受信
レベルが大きく変動した場合には自動的に出力制限を解
除するか、或いは数段前の制限状態に戻す方法である。Next, regarding the method of changing the transmission power, the first method is to decrease or increase it in multiple stages and maintain this as instructed by the base station until the end of the call. The second method is to reduce the transmission output in response to a control signal, and after a certain period of time has passed, automatically return to the previous limit state of one or several steps, or cancel the limit. The third method is to automatically cancel the output limit or return to the previous limit state if the reception level of the mobile station changes significantly while the transmit power is being limited in response to a limit signal. This is the way to return it.
この送信機の出力制御は１ｏｄＢステツプのように大き
くしてもよく、また、数ｄＢステップで行なってもよい
。これをディジタル制御信号でロロジック回路により３
０ｄＢ程度の制御を行なわせるには、例えば２段の場合
は１ｓｄＢとｏ ｄＢ 。The output control of the transmitter may be performed in large steps such as 1 odB, or may be performed in steps of several dB. This is controlled by a logic circuit using a digital control signal.
In order to perform control of about 0 dB, for example, in the case of two stages, 1 sdB and o dB are required.
４段の場合はｓ ｄＢステップ、８段では４ ｄＢ 、
１６段では２ ｄＢステップとすればＯ〜３２ｄＢの制
御を行なうことができる。s dB step for 4 stages, 4 dB for 8 stages,
With 16 stages, control of 0 to 32 dB can be performed in 2 dB steps.
第４図は方向性結合器４の進行波成分を高周波増幅器１
６で僧都し、検波器１６の出力Ｅｄを直流増幅器１７の
増幅出力ＥＡを示す図である。曲線ａは可変減衰器１４
が不動作のときの送信出力対ＥＡの特性である。曲線す
は可変減衰器１４を動作させたときの送信出力対ＥＡの
特性である。Figure 4 shows the traveling wave component of the directional coupler 4
6 is a diagram showing the output Ed of the detector 16 and the amplified output EA of the DC amplifier 17. Curve a is the variable attenuator 14
This is the characteristic of transmission output versus EA when EA is inactive. The curve represents the transmission output versus EA characteristic when the variable attenuator 14 is operated.
曲線ａは送信出力を大幅に低下するときの検波電圧とし
て電圧比較器１１に供給される。曲線すは送信出力を小
量低下させるときの横糸電圧として電圧比較器１１に供
給される。曲線すはこの場合−１３〜＋１０ｄＢＷ の
出力制御に、曲線δは−８〜−３５ｄＢ ’Ｗの出力制
御に使用される。さらに広い制御範囲を必要とする場合
は可変減衰器をさらに多段に設ければよい。なお高周波
増幅器の飽和特性により検波電圧の直線域は出力の変化
範囲よりや＼広くなっている。Curve a is supplied to voltage comparator 11 as a detection voltage when the transmission output is significantly reduced. The curve is supplied to the voltage comparator 11 as the weft voltage when reducing the transmission power by a small amount. The curve S is used in this case for a power control of -13 to +10 dBW, and the curve δ is used for a power control of -8 to -35 dB'W. If a wider control range is required, variable attenuators may be provided in more stages. Note that due to the saturation characteristics of the high frequency amplifier, the linear range of the detected voltage is slightly wider than the range of change in the output.
第５図は第３図のブロック図を実現するだめの１実施例
であり、送信電力制御方法をより具体的に示している。FIG. 5 is a final embodiment of the block diagram shown in FIG. 3, and more specifically shows a transmission power control method.
図において１〜１８は第３図の同番号の機能に対応する
ものである。５０１，５０２゜５０３は電源端子８を詳
細に示したものであり、５０１はアース端子、５０２は
電池直結端子、５０３は定電圧ｖＤＤの供給端子である
。５０６゜５０７．５０８は基地局から送られる送信出
力制御信号の入力端子であり、第３図の出力制御端子９
に相当する。各端子には１又はｏｔ位が供給され、並列
信号により制御され、２３＝８の異なる送信状態が指示
される。この信号により切替スイッチ１３の集積回路Ｉ
Ｃ１３０および基準電圧発生器１２から電圧比較器１１
のトランジスタ１１１のペースに所定の電圧が供給され
る。いま切替スイッチ１３０ＩＣ１３０（７）端子Ａ、
Ｂ、Ｃは出力制御信号の入力端子であり、出力制御端子
９に当る入力端子５０６．５０７．５０８がｏ、ｏ、ｏ
の場合は出力端子ちに、また１、１．１の場合はＸ７端
子に、それぞれの入力データにより８通りに定電圧ｖＤ
Ｄ を切替えて出力する。こ＼で１３１゜１３２．１３
３，１３４，１３５，１３６，１３７は抵抗器、１３８
、１３９はバイパスコンデンサである。また基準電圧
発生器１２で５０９〜５１６はそれぞれＩＣ１３０の端
子”Ｏ〜ｘ７に接続された直列抵抗、５１７〜５２０は
可変抵抗、５２１は終端抵抗であり、端子チ〜ｘ３から
の定電圧ｖＤＤは第４図の曲線すによって与えられた基
準電圧ＥＢを電圧比較器１１のトランジスタ１１１のペ
ースに加える０また、ｘ４〜Ｘ７のｖＤＤは第４図の曲
線ａによって与えられる基準電圧を電圧比較器１１へ加
えてレベル比較を行なわせる０電圧比較器１１はトラン
ジスタ１１１および１１２エミツタ抵抗１１３およびバ
イパスコンデンサ１１４から構成され、供給電力制御部
１０へ制御電圧を供給する０供給電力制御部１ｏは電力
トランジスタ１００およびバイパスコンデンサ１ｏ１か
ら構成されており、電圧比較２３１１の比較結果により
制御電圧ＥＣを励撮部２およびＰＡＡｓ２供給する。Ｐ
ＡＡｓ２出力は方向性結合器４．アイソレータ５ＢＰＦ
６を経てアンテナ７から送信波として放射される０他方
、方向性結合器４の進行波電力検出端子４ａの出力は可
変減衰器１４゜高周波増幅器１６．検波器１６および直
増幅１ｇ器１７を経て増幅され、電圧比較器１１のトラ
ンジスタ１１２のペース側に負帰環され、基準電圧Ｅｓ
と比較され、直流増幅器１７の出力−がＥ８＜弘の場合
は供給電力制御部１Ｑの電力トランジスタ１ｏｏのコレ
クタ電圧を低下させる０″＆だ、Ｅ５） ＥＡの場合は
トランジスタ１００のコレクタ電圧を昇圧することによ
ってＥｓ″；ＥＡとされる０出力制御信号の入力端子５
０６．５０７，５０８の内、出力制御曲線ｂＶｃよる入
力端子を６ｏ６゜５０７のみを使用して２２＝４通りの
出力制御を行なう。次に出力制御曲線ａに対しては５０
８を含む４通りとし、５０８に信号が加えられたとき、
その出力を切替器１８に加えて可変減衰器１４により方
向性結合器４の出力端子４ａと高周波増幅器１６の入力
の間に第４図では２１ ｄＢの減衰を与えている。いま
電圧比較器１１に与える基準電圧Ｅｓを４ｖとしたとき
曲線ａの場合の出力Ｐｄは一２ｓｄＢＷ、制御入力５０
８に信号がある場合には可変減衰器１４が動作し、出力
Ｐ、は曲線すにより−４ｄＢＷとなる。In the figure, numerals 1 to 18 correspond to the functions with the same numbers in FIG. Reference numerals 501, 502, and 503 show details of the power supply terminal 8, in which 501 is a ground terminal, 502 is a battery direct connection terminal, and 503 is a constant voltage vDD supply terminal. 506, 507, and 508 are input terminals for the transmission output control signal sent from the base station, and are the output control terminals 9 in Fig. 3.
corresponds to Each terminal is supplied with 1 or ot and is controlled by a parallel signal, indicating 23=8 different transmission states. By this signal, the integrated circuit I of the selector switch 13
C130 and reference voltage generator 12 to voltage comparator 11
A predetermined voltage is supplied to the transistor 111 of the transistor 111. Now changeover switch 130IC130 (7) terminal A,
B and C are input terminals for output control signals, and input terminals 506, 507, and 508 corresponding to output control terminal 9 are o, o, o.
In the case of , the constant voltage vD is applied to the output terminal, and in the case of 1 and 1.1, the constant voltage vD is applied to the X7 terminal in 8 ways depending on the input data.
Switch D and output. This is 131°132.13
3, 134, 135, 136, 137 are resistors, 138
, 139 are bypass capacitors. Further, in the reference voltage generator 12, 509 to 516 are series resistors connected to the terminals O to x7 of the IC 130, 517 to 520 are variable resistors, and 521 is a terminating resistor, and the constant voltage vDD from the terminals C to x3 is The reference voltage EB given by the curve a in FIG. The zero voltage comparator 11 that performs level comparison in addition to the voltage comparator 11 is composed of transistors 111 and 112, an emitter resistor 113, and a bypass capacitor 114. and a bypass capacitor 1o1, and supplies a control voltage EC to the excitation unit 2 and PAAs2 according to the comparison result of the voltage comparison 2311.
AAs2 output is directional coupler 4. Isolator 5BPF
On the other hand, the output of the traveling wave power detection terminal 4a of the directional coupler 4 is transmitted through a variable attenuator 14, a high frequency amplifier 16. It is amplified through a detector 16 and a direct amplifier 17, and is negatively fed back to the pace side of the transistor 112 of the voltage comparator 11, and the reference voltage Es
If the output of the DC amplifier 17 is E8<Hiro, the collector voltage of the power transistor 1oo of the power supply control unit 1Q is lowered. By doing so, the input terminal 5 of the 0 output control signal is set to Es'';EA.
Output control is performed in 22=4 ways by using only 6o6°507 input terminals based on the output control curve bVc among 06.507 and 508. Next, for output control curve a, 50
There are 4 ways including 8, and when a signal is added to 508,
The output is applied to the switch 18, and the variable attenuator 14 provides attenuation of 21 dB between the output terminal 4a of the directional coupler 4 and the input of the high frequency amplifier 16 in FIG. Now, when the reference voltage Es given to the voltage comparator 11 is 4V, the output Pd in the case of curve a is -2sdBW, and the control input is 50V.
When there is a signal at 8, the variable attenuator 14 operates, and the output P becomes -4 dBW due to the curve.
第６図は可変減衰器を電子回路で構成したものであり、
４は方向性結合器、４ａは進行波検出端子、１４，１５
．１６は第３図と同じ番号の機能を有しており、可変減
衰器１４の０１１Ｃ２は結合コンデンサ、Ｃ３ハバイパ
スコンデンサ、Ｄｌ、Ｄ２はビンダイオードのようなス
イッチングダイオード、ｌｔｄコイルＳ、ｙ、 、Ｓ１
２はストリップラインによる微小インダクタンス、１４
ａはスイッチ電力供給端子であり、制御入力５０８に信
号が与えられたときに切替スイッチ１８から制御電力が
供給される。上記実施例では可変減衰器１４をスイッチ
ングダイオードによる電子回路として示したが、これは
高周波を所定値だけ減衰でき、切替できるものであれば
よい。Figure 6 shows a variable attenuator configured with an electronic circuit.
4 is a directional coupler, 4a is a traveling wave detection terminal, 14, 15
．． 16 has the same numbered functions as in FIG. 3, 011C2 of the variable attenuator 14 is a coupling capacitor, C3 is a bypass capacitor, Dl and D2 are switching diodes such as bin diodes, and ltd coils S, y, , S1
2 is the minute inductance due to the strip line, 14
a is a switch power supply terminal, and control power is supplied from the selector switch 18 when a signal is applied to the control input 508. In the above embodiment, the variable attenuator 14 is shown as an electronic circuit using a switching diode, but it may be any other device as long as it can attenuate high frequencies by a predetermined value and can be switched.
前述の動作は２３＝８による８段切替えについて説明し
たものであるが、切替段数が２”（ｎ：整数）でないも
のや８以上の細かな制御にも応用できる。Although the above-mentioned operation was explained for 8-stage switching based on 23=8, it can also be applied to fine control where the number of switching stages is not 2" (n: integer) or 8 or more.
発明の効果
本発明は前記のような構成であり、以下に示す種々の効
果が得られるものである。Effects of the Invention The present invention has the above-mentioned configuration, and various effects shown below can be obtained.
ａ）送信機の最大出力に対して例えば３０ｄＢ以上低い
ときの進行波成分を方向性結合器から得ようとする場合
、従来は結合度の増加が必要であり、送信出力素不用に
低下させていた。また、制御範囲が４０ｄＢ以上も必要
な場合は低出力において制御誤差が大きく変動を生じ易
い欠点があったが、本発明では方向性結合器から微小電
力を抽出し、これを高周波増幅して検波ダイオードの直
線検波領域で使用すると共に、方向性結合器と高周波増
幅器の間に高周波可変減衰器を設けて送信出力の範囲に
よって減衰器の動作を切替るので、常に適当な制御電圧
を和ることかできるので制御誤差を小さくできる。a) When trying to obtain a traveling wave component that is 30 dB or more lower than the maximum output of the transmitter from a directional coupler, conventionally it was necessary to increase the degree of coupling, and the transmission output was unnecessarily lowered. Ta. In addition, when a control range of 40 dB or more is required, there is a drawback that control errors tend to fluctuate greatly at low outputs, but in the present invention, a small amount of power is extracted from the directional coupler, and this is amplified at high frequency and detected. In addition to being used in the diode linear detection region, a high frequency variable attenuator is installed between the directional coupler and the high frequency amplifier, and the operation of the attenuator is switched depending on the transmission output range, so the appropriate control voltage can always be summed. control error can be reduced.
第１図は従来の送信出力制御装置のブロック図、第２図
は同制御器の進行波成分の検波出力特性を示す図、第３
図は本発明の一実施例における送信出力の制御方法を説
明するためのブロック図、第４図は同方法の検波出力特
性を示す図、第５図は第３図の構成の詳細回路図、第６
図は可変減衰器の一実施例を示すプロンクダイアグラム
図である０１４・・・・・可変減衰器、１６・・・・・
・高周波増幅器、１６・・・・・検波器、１７・・・・
・・直流増幅器、１８・・・・・切替スイッチ、１１・
・・・・電圧比較器、１２・・・・・・基準電圧発生器
、１３・・・・・・切替スイッチ。
代理人の氏名 弁理士 中 尾 敏 男 ほか１名（′
；１図
第２図
（θｄＢｗ−・・送イ↓出、／１７１４ｇ４−φイ直ン
・−３１７１
第 ４ 図
ｆｆ）Fig. 1 is a block diagram of a conventional transmission output control device, Fig. 2 is a diagram showing the detection output characteristics of the traveling wave component of the same controller, and Fig. 3
The figure is a block diagram for explaining a transmission output control method in an embodiment of the present invention, FIG. 4 is a diagram showing the detection output characteristics of the same method, and FIG. 5 is a detailed circuit diagram of the configuration of FIG. 3. 6th
The figure is a pronk diagram showing an example of a variable attenuator. 014... Variable attenuator, 16...
・High frequency amplifier, 16...Detector, 17...
...DC amplifier, 18... Selector switch, 11.
... Voltage comparator, 12 ... Reference voltage generator, 13 ... Changeover switch. Name of agent: Patent attorney Toshio Nakao and one other person ('
;1 Figure 2 (θdBw-...Transmission A ↓ out, /1714g4-φI direct-in -3171 Figure 4 ff)
Claims (1)
、前記送信出力の一部を方向性結合器を介して分岐し、
可変減衰器を経由して高周波増幅し、前記高周波出力を
検波した後基準電圧と比較して前記制御電圧を得るよう
にすると共に、所要の送信出力に対応して前記可変減衰
器の減衰度と前記基準電圧を切替える送信出力の制御方
法。A power amplification section whose transmission output can be controlled by a control voltage is provided, and a part of the transmission output is branched via a directional coupler,
High frequency is amplified via a variable attenuator, and after detecting the high frequency output, it is compared with a reference voltage to obtain the control voltage, and the attenuation degree of the variable attenuator is adjusted in accordance with the required transmission output. A method of controlling transmission output by switching the reference voltage.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP19601884A JPS6173408A (en) | 1984-09-19 | 1984-09-19 | Controlling method of transmitting output |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP19601884A JPS6173408A (en) | 1984-09-19 | 1984-09-19 | Controlling method of transmitting output |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| JPS6173408A true JPS6173408A (en) | 1986-04-15 |
Family
ID=16350853
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP19601884A Pending JPS6173408A (en) | 1984-09-19 | 1984-09-19 | Controlling method of transmitting output |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS6173408A (en) |
Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| EP0392132A2 (en) * | 1989-04-10 | 1990-10-17 | Mitsubishi Denki Kabushiki Kaisha | Radio transceiver apparatus with booster |
| JPH04100426A (en) * | 1990-08-20 | 1992-04-02 | Matsushita Electric Ind Co Ltd | Transmitting output control circuit |
| JPH04100427A (en) * | 1990-08-20 | 1992-04-02 | Matsushita Electric Ind Co Ltd | Transmitting output control circuit |
| JPH04316205A (en) * | 1991-04-16 | 1992-11-06 | Mitsubishi Electric Corp | High frequency power amplifier |
| JP2001094367A (en) * | 1999-09-20 | 2001-04-06 | Matsushita Electric Ind Co Ltd | Saturation output variable amplifier |
Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS57207408A (en) * | 1981-06-16 | 1982-12-20 | Nec Corp | High frequency power amplifier |
| JPS58138113A (en) * | 1982-02-12 | 1983-08-16 | Kokusai Electric Co Ltd | Automatic power controlling circuit for transmitter |
| JPS591244B2 (en) * | 1978-06-23 | 1984-01-11 | 三菱レイヨン株式会社 | Method for producing methacrolein, methacrylic acid and 1,3↓-butadiene |
-
1984
- 1984-09-19 JP JP19601884A patent/JPS6173408A/en active Pending
Patent Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS591244B2 (en) * | 1978-06-23 | 1984-01-11 | 三菱レイヨン株式会社 | Method for producing methacrolein, methacrylic acid and 1,3↓-butadiene |
| JPS57207408A (en) * | 1981-06-16 | 1982-12-20 | Nec Corp | High frequency power amplifier |
| JPS58138113A (en) * | 1982-02-12 | 1983-08-16 | Kokusai Electric Co Ltd | Automatic power controlling circuit for transmitter |
Cited By (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| EP0392132A2 (en) * | 1989-04-10 | 1990-10-17 | Mitsubishi Denki Kabushiki Kaisha | Radio transceiver apparatus with booster |
| JPH04100426A (en) * | 1990-08-20 | 1992-04-02 | Matsushita Electric Ind Co Ltd | Transmitting output control circuit |
| JPH04100427A (en) * | 1990-08-20 | 1992-04-02 | Matsushita Electric Ind Co Ltd | Transmitting output control circuit |
| JPH0771054B2 (en) * | 1990-08-20 | 1995-07-31 | 松下電器産業株式会社 | Transmission output control circuit |
| JPH0783326B2 (en) * | 1990-08-20 | 1995-09-06 | 松下電器産業株式会社 | Transmission output control circuit |
| JPH04316205A (en) * | 1991-04-16 | 1992-11-06 | Mitsubishi Electric Corp | High frequency power amplifier |
| JP2001094367A (en) * | 1999-09-20 | 2001-04-06 | Matsushita Electric Ind Co Ltd | Saturation output variable amplifier |
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