JPS6033618A - Ac constant current supply device - Google Patents
Ac constant current supply deviceInfo
- Publication number
- JPS6033618A JPS6033618A JP58142554A JP14255483A JPS6033618A JP S6033618 A JPS6033618 A JP S6033618A JP 58142554 A JP58142554 A JP 58142554A JP 14255483 A JP14255483 A JP 14255483A JP S6033618 A JPS6033618 A JP S6033618A
- Authority
- JP
- Japan
- Prior art keywords
- output
- current
- constant current
- amplifiers
- transformer
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/337—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in push-pull configuration
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Continuous-Control Power Sources That Use Transistors (AREA)
Abstract
Description
【発明の詳細な説明】
本発明は出力側のインピーダンスの変化にかかわりなく
、交流の定電流を供給できる交流定電流源装置に関する
。DETAILED DESCRIPTION OF THE INVENTION The present invention relates to an AC constant current source device that can supply a constant AC current regardless of changes in impedance on the output side.
電力計、亀力歇計の校正試験等に使用される交流定電流
源回路には、一般に高い出力安に度と設定精度が要求さ
れる。このため、従来から交流定電流源回路として種々
の回路方式が提案されている。AC constant current source circuits used for calibration tests of wattmeters, power meters, etc. generally require high output stability and setting accuracy. For this reason, various circuit systems have been proposed as AC constant current source circuits.
添付回向の第１図乃至第３図を参照して従来装置を説明
する。第１図は交流電圧を父流屯流に変換する回路方式
の一構成例の回路図である。交流信号源■１の出力は抵
抗Ｒ１を介して反転増幅器Ａ１のｅ端子に与えられる。The conventional device will be explained with reference to FIGS. 1 to 3 of the attached drawings. FIG. 1 is a circuit diagram of a configuration example of a circuit system for converting an alternating current voltage into a father current. The output of the AC signal source 1 is applied to the e terminal of the inverting amplifier A1 via a resistor R1.
反転増幅器Ａ１の■端子は接」也され、出力はＮＰＮ）
ランジスタＱ１およびＰＮＰトランジスタＱ２のそれぞ
れのペースに与えられる。トランジスタＱｌｌ Ｑ２の
コレクタにはそれぞれ＋Ｖｃｃ、−Ｖｃｃ電源が与えら
れており、エミッタからの出力は変流器ＣＴの一次側に
与えられる。The ■ terminal of the inverting amplifier A1 is also connected, and the output is NPN)
applied to the respective paces of transistor Q1 and PNP transistor Q2. +Vcc and -Vcc power supplies are applied to the collectors of the transistors Qll and Q2, respectively, and the output from the emitter is applied to the primary side of the current transformer CT.
変流器ｃ’ｒの他端は抵抗Ｒを介して接地され、その電
位は抵抗Ｒｆを介して反転増幅器Ａ１の○端子に帰還さ
れる。なお、定電流出力Ｉ。は変流器ＣＴの二次側から
取り出される。The other end of the current transformer c'r is grounded via a resistor R, and its potential is fed back to the O terminal of the inverting amplifier A1 via a resistor Rf. In addition, constant current output I. is taken out from the secondary side of current transformer CT.
第１図の如き回路によれば、出力は抵抗Ｒ，、ＲＢ
Ｒｆの比によってのみ設定されるので、高い電流安定度
と設定精度が得られ、かつ回路も簡単になるという長所
がある。しかしながら、トランジスタＱ□＋ Ｑ２は導
電型が異なり、ｖｏＢにほぼ２ｖｃｃの耐圧が必要とな
るため、出力ＶＡが制限されて電源の大容量化に適さな
いという欠点がある。According to the circuit shown in FIG. 1, since the output is set only by the ratio of the resistors R, RB Rf, it has the advantage that high current stability and setting accuracy can be obtained, and the circuit can be simplified. However, the transistor Q□+Q2 has a different conductivity type and requires a withstand voltage of approximately 2 vcc for voB, which limits the output VA and has the disadvantage that it is not suitable for increasing the capacity of the power supply.
そこで、電源の犬容歌化に適するものとして、第２図お
よび第３図に示すような導電型の同じトランジスタを用
いたプッシュプル回路が提案されている。第２図はその
要部の回路図で、第１図と同一要素は同一符号で示しで
ある。交流信号源Ｖ。Therefore, push-pull circuits using transistors of the same conductivity type as shown in FIGS. 2 and 3 have been proposed as suitable for converting the power source into a compact type. FIG. 2 is a circuit diagram of the main part, and the same elements as in FIG. 1 are indicated by the same symbols. AC signal source V.
の出力は反転？５Ａ２および抵抗ｒ ｌ ｌ ｒ ２か
らなる回路によって位相が反転され、ＮＰＮトランジス
タＱ３のベースに与えられる。また、交流信号源Ｖ、の
出力はそのままの位相でＮＰＮ）ランジスタＱ４のに一
スに与えられる。トランジスタＱ３＊ Ｑ４のエミッタ
は共に接地され、エレクタはそれぞれ変流器ＣＴの一次
側に接続される。そして、−矢引１１の中（１１タツプ
には＋■ｃｃ酸源が与えられており、出力は変流器Ｃ′
ｒの二次側から取り出される。Is the output inverted? 5A2 and resistor r l l r 2, the phase is inverted and applied to the base of NPN transistor Q3. Further, the output of the AC signal source V is applied to the NPN transistor Q4 with its phase unchanged. The emitters of transistors Q3*Q4 are both grounded, and the erectors are each connected to the primary side of a current transformer CT. Then, in the -arrow arrow 11 (+■cc acid source is given to the 11 tap, the output is from the current transformer C'
It is taken out from the secondary side of r.
ところで、第２図の回路は帰還がなされていないので、
低い出力インピーダンスの定電流源として動作し、商い
精度と安定性を得ること−７にできない。そこで、第２
図の回路を用いて交流５岨「区がＬ源回路を第１り成す
るためには、例えば第３図に示すようにする必要がある
。By the way, the circuit in Figure 2 has no feedback, so
It is not possible to operate as a constant current source with low output impedance and obtain quotient accuracy and stability. Therefore, the second
In order to form the first L source circuit using the circuit shown in FIG. 3, it is necessary to do as shown in FIG.
４３図は第２図の回路を゛電流出力モードで勤１′「さ
せるときの回路図で、第１図および第２（菌と１ｉｉＪ
−要素は同一符号で示しである。交流ｌ１ｇ−号源■、
の出力は反転器Ａ２で位相が反転され、反転器１唱暑誇
Ａ ダイオードＤ□および抵抗ｒ ３＋ ｒ ４ ’ｌ
）’らなる１
回路を介してトランジスタＱ３のペースに与えられる。Figure 43 is a circuit diagram when the circuit in Figure 2 is operated in the current output mode.
-Elements are designated by the same reference numerals. AC l1g-gen ■,
The phase of the output of the inverter A2 is inverted, and the phase of the output of the inverter A2 is inverted.
)' is applied to the pace of transistor Q3 through a circuit.
捷た、交流信号源ｖｉの出力は反ｉｉ叡ｊ曽１１帖ンＫ
Ａ４、ダイオードＤ２および抵抗ｒ５．ｒ６ｆｉ”らな
る回路を介してトランジスタＱ４のに一スＶこ力、えら
れる。トランジスタＱ３＋ Ｑ４のエミッタはそね、ぞ
れ抵抗Ｒ８ｔ、Ｒ８□を介して接地され、エミッタの電
位は低域ｄｊ波器ＬＰＦＩ、 ＬＰＦ２、反転器Ａ５、
差分検出のための積分器Ａ６等からなる直流帰還回路１
によって、反転器Ａ２および反転増幅器Ａ４σ）○端子
に帰還される。このｉ■流帰還回路１はそれぞれのトラ
ンジスタに流れるエミッタ電流平均値の差を検出し、こ
れを零にするためのものである。The output of the switched AC signal source vi is
A4, diode D2 and resistor r5. One voltage is applied to the transistor Q4 through a circuit consisting of "r6fi. Inverter LPFI, LPF2, inverter A5,
DC feedback circuit 1 consisting of integrator A6 etc. for difference detection
is fed back to the inverter A2 and the inverting amplifier A4σ)○ terminal. This i-current feedback circuit 1 is for detecting the difference in the average value of the emitter current flowing through each transistor and reducing it to zero.
他方、変流器ＣＴの出力電流Ｉ。は変流器ＣＴＤおよび
抵抗Ｒｓｔｉにより間圧信号として検出され、抵抗ｒ７
を介して反転”／？幅器Ａ７に与えられる（交流Ｊ＋１
ｊＦｔ）。反転増幅器Ａ７は抵抗ｒｓ＋ｒｇと結合され
て、信号源の（に圧ｖ１の犬へさと出力ｕ １）ＩＵ検
出用の変流器ｅＴＤの出力の大きさとを比較し、回路を
電流出力モードで動作させるためのものである。On the other hand, the output current I of the current transformer CT. is detected as a pressure signal by current transformer CTD and resistor Rsti, and resistor r7
(AC J+1
jFt). The inverting amplifier A7 is coupled to the resistor rs+rg to compare the magnitude of the voltage v1 of the signal source and the output u1 of the current transformer eTD for IU detection, and operates the circuit in current output mode. It is for the purpose of
このように第３図の回路は、トランジスタＱ３＋Ｑ を
同じ４成型のものにしつつ、エミッタ電流を抵抗Ｒ８，
＋ Ｒｓ□によって検出して直流帰還させると共に、最
終出力電流Ｉ。を変流器ＣＴＤおよび′抵抗Ｒｓ□で検
出して交流帰還させたので、４１ｊｌｊ出カモードで動
作させることができ、かつ太き庁１１１力をイりること
かできろ。しかし、直流！７１ ｊＷ Ｉｉ月路と交流
ｍ （！を回路が独立して必甥なためＩｔ−ｉｌ Ｎ＆
力くｔ夏Ｈｔイヒするグビけでなく、直流・届償回路の
伝達！Ｍｉ （主力；復箔〔になって回路定数の設定が
・ｌｃ Ｌ くなるという欠７へがある。In this way, the circuit in Figure 3 uses the same 4-type transistors Q3+Q, and the emitter current is controlled by resistors R8 and
+ Rs□ to detect and feed back DC, and the final output current I. Since it is detected by the current transformer CTD and the resistor Rs□ and fed back with AC feedback, it can be operated in the 41jlj output mode and can also receive the thick 111 power. But DC! 71 jW Ii Tsukiji and AC m (! Since the circuit is independent and necessary, it-il N&
Powerfully transmits direct current and compensation circuits without being too stiff! There is a drawback that the circuit constant setting becomes ・lc L after becoming Mi (main force).
本免明は上記の従来技術の欠点を克服１″るた、ｖ）に
なされたもので、回路が簡単でかつ大３１ＪＪて１商す
る交流定電流υπ回路を提供することを目１１勺と−す
る。The present invention has been made to overcome the drawbacks of the above-mentioned prior art, and its 11th objective is to provide an AC constant current υπ circuit which is simple and has a quotient of 31JJ. - to do.
上記の目的を実現１−るため本発明は、Ｊｆ’−１言号
源から県幅の炸しい逆相の信号ｔｍ’で、単−ｆｉ号源
の出力と同相および逆相の１ａ号によって−ズ；１σ）
１反Ａ４３接地形’５’ｌＡ幅器をそれらの半周朗のあ
１．／Ｎ ７’ビヤｔ℃ぞれ定電流モードで動作させ、
その半波定１１ｆ、流出ブ］を抵抗器で検出することに
より運航した１３号ケシ・吊還し、変流器で２つの半波
足＋１も流出カンｆひとつ１１７）全波定１戊流出力に
合成する父流定屯がしσグ１ｒｉｌ Ｔｈ’；Ｓを４Ｍ
供するものである。In order to achieve the above-mentioned object 1-, the present invention provides a signal tm' with an opposite phase that is as wide as a prefecture from a Jf'-1 word source, and a signal 1a which is in phase and opposite phase with the output of a single-fi signal source. -z; 1σ)
1 anti-A43 grounding surface '5' lA width vessel of those half-circle 1. /N 7'Via t℃ are operated in constant current mode,
By detecting the half-wave constant 11f and outflow bu] with a resistor, the No. 13 poppy was operated, and with a current transformer, two half-wave legs + 1 also flowed out. The father who synthesizes it into power is σg1ril Th';S is 4M
This is what we provide.
以ト、重付図面の第４図および・刊５１／、１を４１１
貧して本発明の一実施例を説明１−る。第４図は同実施
例の回路図で、第１図乃至７１１３図と同一要素は同一
符号で示しである。反転器Ａ２の出力は抵抗Ｒ，１を介
して仮想後地形増幅器Ａ３の○端子に与えられ、父流信
号源Ｖ、の出力は抵抗Ｒ，□を介して仮；１す襟地形増
幅器Ａ４のＯ端子に与えられる。Hereinafter, Figure 4 of the weighted drawings and Publication 51/1 are referred to as 411
One embodiment of the present invention will now be briefly described. FIG. 4 is a circuit diagram of the same embodiment, and the same elements as in FIGS. 1 to 7113 are indicated by the same symbols. The output of the inverter A2 is given to the ○ terminal of the virtual topography amplifier A3 via the resistor R, 1, and the output of the father current signal source V is given to the terminal of the virtual back topography amplifier A4 via the resistor R, □. given to the O terminal.
仮想後地展増幅器Ａ′３＋ Ａ４のｅ端子と出力・ｒ高
子との間には、トラン、ジスタＱ３＋Ｑ４のベース・エ
ミッタ間に逆バイアス４１１圧が加わるのを防ぐダイオ
ードＤＩ、Ｉ）２が設けられ、出力信号はＮＰＮＩ・う
／ジスタＱ３＋ Ｑ４のペースに与えられる。トランジ
スタＱ３＋ Ｑ４のコレクタには＋Ｖ −ｔに諒が与え
られ、エミッタ出力は変流器ＣＴの一次側に与えられる
。A diode DI, I)2 is connected between the e terminal and the output/r high voltage of the virtual rear expansion amplifier A'3+A4 to prevent reverse bias voltage from being applied between the base and emitter of the transformer and transistor Q3+Q4. and the output signal is provided to the pace of the NPNI registers Q3+Q4. The collectors of transistors Q3+Q4 are connected to +V-t, and the emitter outputs are applied to the primary side of current transformer CT.
仮想接柚形増幅器Ａ′３．Ａ′４のｅ端子の間には帰還
用の抵抗Ｒｆｌ、Ｒｆ２が直列接続され、それらの接続
点は変流器ＣＴの中間タップに接続され、ちと共に、抵
抗Ｒ８を介して接地される。このようにして、帰、鑞回
路の摺電を簡単にすることができる。Virtual grounded amplifier A'3. Feedback resistors Rfl and Rf2 are connected in series between the e terminal of A'4, and their connection point is connected to the center tap of the current transformer CT, and is also grounded via a resistor R8. In this way, the sliding of the return and solder circuits can be simplified.
次に、ｒ窮４図および第５１９１を参照して−３４図に
示す実施例の動作を説明する。・１１５図Ｉ′ｉ第４図
の回路の各部に訃けるＩｔ（圧、’）！ｊ流波形１・￥
１である。こコｆ、■、は交流信号１１ｉｆｉＶ、ノ出
ｊＪ ｒ？１．ＩＪＥ、Ｉ０３゜Ｉお、はトランジスタ
Ｑ、３＋ Ｑ、ｉのエミッタ電流、■、は抵抗ＲＢ＋
Ｒ，、＋ Ｒ，２の接続点の＋ＩＪ ｌｉ″１′、、Ｉ
。Next, the operation of the embodiment shown in Fig. 34 will be explained with reference to Fig. 4 and No. 5191.・It (pressure, ') that is damaged in each part of the circuit of 115 figure I'i figure 4! j flow waveform 1・￥
It is 1. Here f, ■, is AC signal 11ifiV, output jJ r? 1. IJE, I03゜I, is the emitter current of the transistor Q, 3+ Q, i, ■ is the resistor RB+
+IJ li″1′,,I of the connection point of R,,+R,2
.
はＪ挺終出カル流に４応する。なお、第４図において１
１１＋ ＋、２１ ｔ８． Ｉｆ１＊ Ｉｆｚ＋ ’Ｅ
３’ Ｉ。４ｆま矢印の向きが正である。4 corresponds to the J-terminal exit Cal style. In addition, in Figure 4, 1
11+ +, 21 t8. If1* Ifz+ 'E
3'I. The direction of the arrow until 4f is positive.
時刻ｔ。−１１においては、ｖ１≧０であるので、抵抗
Ｒ，１に流れるｒｉ（流は
■ｉ１’／Ｒ，曲・・・凹曲（］）
Ｉ
となる。このとき、反１伝Ｊ冑幅器Ａ′３のＱ人カ・＜
Ｍ子は仮想接地状態にあり、出力端には正のｊｌｌ、圧
が現れているので、ダイオードＤ１はカットオノ状に１
にある。＋ｔｅつてｌ’＋５．ｊＡｔ Ｉ 、 、はＩ
＋ ｔ ” Ｉｆ ｌ−８／Ｒ（ｔ ・・・・・・・・
・・・・・・（２）となる。Time t. -11, since v1≧0, the flow is ri (flow is ■i1'/R, curve...concave curve (]) I in the resistance R, 1. At this time, Q person of vessel A'3 <
The M element is in a virtual ground state, and positive jll and pressure appear at the output terminal, so the diode D1 is connected to 1 in a cut-on shape.
It is in. +tetsutel'+5. jAt I, , is I
+ t ” If l-8/R(t ・・・・・・・・・
...(2).
同１主に、反転Ｊｆ４幅器Ａ′４のθ人カ・りＭ子ｔよ
仮、Ｖ、１接地状態にあるので、
工ｉ２ ” Ｖｉ”’ｉ２” ＋２＝工ｆ２ ＝■Ｓ／
Ｒｆ２”””（３）となる。1 Mainly, since the inverted Jf4 width device A'4's θ person force and M child t are temporarily in the grounded state, V and 1 are in the grounded state, 芬i2 ``Vi'''i2'' +2= 工f2 =■S/
Rf2""" (3).
トランジスタＱ３に関しては、反転増幅器Ａ′ノ出力電
圧は正であるのでトランジスタ。３は導通状態になり、
電流ＩＥ３が現れる。この電流工。３は
ＩＥ３ ＝’ｆ□＋Ｉｆ２＋Ｉ８ ・・・曲・・・・曲
（４）となる。ここで、（１） 、 （２）式よりＶＳ
＝Ｉ３１ＸＲｆｌ
＝（Ｒｆ０／Ｒ，□）・ｖ、・・・凹曲曲（５）となる
ので、（４） 、 （５）式よりが得られる。Regarding transistor Q3, the output voltage of the inverting amplifier A' is positive, so it is a transistor. 3 becomes conductive,
A current IE3 appears. This electrician. 3 becomes IE3='f□+If2+I8...song...song (4). Here, from equations (1) and (2), VS
= I31
ここでＸＲｆｌｏＲｆ ２＝Ｒｆ ＸＲｉ ｌ ＝”ｉ
２ ＝ Ｒｉとすると、
となる。従って、電流”Ｅ３は信号Ｒｖ、と抵抗Ｒ，Ｉ
Ｒ，・Ｒｓの値のみで設定できる。Here, XRfloRf 2=Rf XRi l=”i
When 2 = Ri, it becomes. Therefore, the current "E3 is the signal Rv, and the resistors R, I
It can be set only with the values of R, ·Rs.
トランジスタＱ４に関しては、増幅器Ａ′４の出力電圧
は負であるので、トランジスタ。４は非導通状態になり
、電流ＩＦ、４−ｏである。Regarding transistor Q4, the output voltage of amplifier A'4 is negative, so the transistor Q4. 4 becomes non-conductive, and the current IF is 4-o.
このようにして、時刻ｔ。−ｔｏにおいて変流器ＣＴの
出力側（二次側）には正方向ＶＣ心流工。が誘起される
。In this way, time t. -to, the output side (secondary side) of the current transformer CT has a positive direction VC core current. is induced.
時刻１１〜ｔ２においては、ｖＩ≦０でありトランジス
タＱ３が非導通、トランジスタＱ４が導通状態であるの
で、エミッタ電流工Ｉｉ、３” Ｅ４はとなる。従って
、電流ＩＥ４は信号源ｖｉと抵抗Ｒ１＋ Ｒｆ＋ Ｒ３
の値のみで定めることができる。From time 11 to t2, vI≦0, the transistor Q3 is non-conducting, and the transistor Q4 is conducting, so the emitter current Ii, 3" E4 becomes. Therefore, the current IE4 is connected to the signal source vi and the resistor R1+ Rf+R3
It can be determined only by the value of .
上記の如く、変流器ＣＴの一次側には２つの半波正弦波
止流’Ｅ３１ ＩＦ、４が交互に逆方向に流れるので、
二次側からはひとつの全波正弦波電流■。を得ることが
できる。As mentioned above, two half-wave sine wave stop currents 'E31 IF, 4 alternately flow in opposite directions on the primary side of the current transformer CT.
One full-wave sine wave current ■ from the secondary side. can be obtained.
上記の如く本発明によれば、単一信号源の出力およびそ
れと逆相の信号によって一対の仮想接地形増幅器を半周
期づつ定電流モー＋＝で動作させ、その出力を変流器で
合成させて全波定電流を出力すると共に、半波定電流出
力を１個の抵抗器Ｒ８で検出して連続した検出信号全帰
還させるようにしたので、回路が商学で出力の設定４６
度が高く、かつ安ボ１規の高い大容量の出力を４’４る
ことのできる変形ブツシュゾル形の交流定電流源回路を
イクることができる。As described above, according to the present invention, a pair of virtual ground plane amplifiers are operated at a constant current mode for half a cycle by the output of a single signal source and a signal having the opposite phase thereof, and the outputs are combined by a current transformer. In addition to outputting a full-wave constant current, the half-wave constant current output is detected by one resistor R8 and all continuous detection signals are fed back.
It is possible to create a modified Bushsol-type AC constant current source circuit that has high power and is capable of producing a large-capacity output of 4'4.
すなわち、抵抗Ｒｆ１．Ｒｆ２等によって帰還回路を摺
電したので、例えば第２図および第３図に示す叩き従来
装置に比べて著しく回路を１１１１単にしながら、太容
瞬の出力を維持することができる。他方、同じ導１戎型
のトランジスタ（例えばＮＰＮ）ラン、ジスタ）を出力
に用いて大きな出力を得ること゛ができる。That is, the resistance Rf1. Since the feedback circuit is powered by Rf2 or the like, the circuit can be significantly simplified by 1111 times compared to the conventional hitting devices shown in FIGS. 2 and 3, for example, and yet a large output can be maintained. On the other hand, it is possible to obtain a large output by using the same conductor type transistor (for example, NPN transistor, transistor) for the output.
また、出力電流Ｉ はエミッタＦｇ流■Ｅ３” Ｅ４に
より定められ、電流Ｉ、、 Ｉゎ、は（７） 、 （８
）式より２組の抵抗Ｒ１，とＲ，ｌ ＲｆｌとＲｆ２と
Ｒｓの大きさによって定められるので、出力電流■。大
きさの設定はこれら抵抗１直によって容易に行なうこと
ができ、かつ容易に出力ｉｔ流■。ｔｙ）歪みを除去で
き、さらに按易に信号源Ｖ、と出力電流工。の位相を一
致させることができる。In addition, the output current I is determined by the emitter Fg current ■E3''E4, and the currents I,, Iゎ, are (7), (8
) From the formula, the output current is determined by the magnitudes of the two sets of resistors R1, R, l, Rfl, Rf2, and Rs. The size can be easily set using one of these resistors, and the output can be easily adjusted. ty) Distortion can be removed and the signal source V and output current can be easily arranged. The phases of the two can be matched.
なお、さらに高いｔ■℃流安定度と設定珀興を１惇るた
め（て、峡終出力屯流全検出して人力４１１１１にジ涜
還してもよく、この場ばの伝達特性は本方式のものが単
純である７ｔめに容易に行うことができろ。In addition, in order to obtain even higher t■℃ flow stability and one set of settings (in order to obtain one set of settings), it is also possible to detect all the final force of the gorge and return it to the human power 41111, and the transfer characteristics in this case are the same as the original. The method is simple and can be done easily.
召）１図は従来装置の一４ｎ １ＪＩｔ、１＋ｌの回路
図、第２図はｌｉｔ来裟置装他のＩ１ｇ成例の鉤部の回
路図、第３図は第２図の回路を用いて摺電した従来装置
ぺの池の１１・〒成例の回路図、第４図は本発明の一実
施例の回路図、第５図は第４図に示す回路の各部の１１
１．圧、ｉｔ流波形図である。
Ａ−１＋ Ａ３ ＋ Ａ３ ＋ Ａ４ ＋ Ａ’４ ＋
Ａ７・・・反転増幅器、Ａ２． Ａ５・・・反転器、
Ａ６・・・積分器、Ｑ□＋ Ｑ３ｔ Ｑ４・・・ＮＰＮ
）ランジスタ、Ｑ２・・・ｐ、ｒＪＰ ）ランジスタ、
ＣＴ、ＣＴＤ・・・変流器。
出願人代理人 猪 股 清
−Ｊ ’つ 文 噂 ０
５ １ １ Ｓ →
ト トFig. 1 is a circuit diagram of a conventional device, 4n 1JIt, 1+l, Fig. 2 is a circuit diagram of a hook part of an I1g example of a conventional device, and Fig. 3 is a circuit diagram of a conventional device using the circuit of Fig. 2. 4 is a circuit diagram of an example of an embodiment of the present invention, and FIG. 5 is a circuit diagram of an example of 11.
1. It is a pressure and IT flow waveform diagram. A-1+ A3 + A3 + A4 + A'4 +
A7...inverting amplifier, A2. A5... Inverter,
A6...Integrator, Q□+Q3t Q4...NPN
) transistor, Q2...p, rJP) transistor,
CT, CTD...Current transformer. Applicant's agent Kiyoshi Inomata-J'tsu Rumor 0 5 1 1 S → To To
Claims (1)
幅が等しく位相の反転した信号に変換する反転増幅器と
、前記交流信号源の出力および反転増幅器の出力のそれ
ぞれの半周期のあいだ定電流モードで動作し、それぞれ
半波定鑞流を出力する一対の仮想接地形増幅器と、前記
２つの半波足蹴流を直流結合で検出する抵抗器を有し、
検出信号を前記一対の仮想接地形増幅器に帰還する手段
と、前記２つの単波定電流を合成してひとつの全波定電
流とする変流器とを備える交流定電流源装置。 ２、抵抗器は１個であることを特徴とする特許請求の範
囲第１項記載の交流定電流源装置。[Claims] 1. One alternating current signal source, an inverting amplifier that converts the output of this alternating signal source into a signal with equal amplitude and inverted phase, and each of the output of the alternating current signal source and the output of the inverting amplifier. a pair of virtual ground plane amplifiers that operate in a constant current mode during a half period of , each outputting a half-wave constant current, and a resistor that detects the two half-wave foot currents by direct current coupling;
An AC constant current source device comprising means for feeding back a detection signal to the pair of virtual ground plane amplifiers, and a current transformer for combining the two single wave constant currents into one full wave constant current. 2. The AC constant current source device according to claim 1, wherein the number of resistors is one.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP58142554A JPS6033618A (en) | 1983-08-05 | 1983-08-05 | Ac constant current supply device |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP58142554A JPS6033618A (en) | 1983-08-05 | 1983-08-05 | Ac constant current supply device |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| JPS6033618A true JPS6033618A (en) | 1985-02-21 |
Family
ID=15318037
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP58142554A Pending JPS6033618A (en) | 1983-08-05 | 1983-08-05 | Ac constant current supply device |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS6033618A (en) |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS63257165A (en) * | 1987-04-13 | 1988-10-25 | Nissin Electric Co Ltd | Ion source device |
| JPH02152150A (en) * | 1988-12-02 | 1990-06-12 | Hitachi Ltd | Ion source |
Citations (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS5054270A (en) * | 1973-05-29 | 1975-05-13 |
-
1983
- 1983-08-05 JP JP58142554A patent/JPS6033618A/en active Pending
Patent Citations (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS5054270A (en) * | 1973-05-29 | 1975-05-13 |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS63257165A (en) * | 1987-04-13 | 1988-10-25 | Nissin Electric Co Ltd | Ion source device |
| JPH02152150A (en) * | 1988-12-02 | 1990-06-12 | Hitachi Ltd | Ion source |
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