JPS6024679B2 - Back electromotive force compensation control method for synchronous machine - Google Patents
Back electromotive force compensation control method for synchronous machineInfo
- Publication number
- JPS6024679B2 JPS6024679B2 JP55184037A JP18403780A JPS6024679B2 JP S6024679 B2 JPS6024679 B2 JP S6024679B2 JP 55184037 A JP55184037 A JP 55184037A JP 18403780 A JP18403780 A JP 18403780A JP S6024679 B2 JPS6024679 B2 JP S6024679B2
- Authority
- JP
- Japan
- Prior art keywords
- back electromotive
- current
- electromotive force
- control system
- compensation control
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
Links
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
- H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
- H02P25/022—Synchronous motors
- H02P25/024—Synchronous motors controlled by supply frequency
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Control Of Ac Motors In General (AREA)
- Control Of Motors That Do Not Use Commutators (AREA)
Description
【発明の詳細な説明】
この発明は、同期機の逆起電圧補償制御方式に関するも
のであり、特にサイクロコンバータ等で駆動される同期
電動機の逆起電圧を演算しこれを補償制御する方式に関
するものである。DETAILED DESCRIPTION OF THE INVENTION The present invention relates to a back electromotive voltage compensation control method for a synchronous motor, and particularly to a method for calculating and compensating the back electromotive voltage of a synchronous motor driven by a cycloconverter or the like. It is.
一般に、同期電動機の駆動系にサィクロコンバータを使
用する場合、サィクロコンバータの出力周波数を１０Ｈ
Ｚ以上とし、電源周波数の１／３畠度まで次第に上げて
いくと、サィクロコンバータの出力電流の追従特性が悪
化してくることが知られている。Generally, when using a cycloconverter in the drive system of a synchronous motor, the output frequency of the cycloconverter is set to 10H.
It is known that when the power supply frequency is set to above Z and gradually increased to 1/3 of the power supply frequency, the follow-up characteristic of the output current of the cycloconverter deteriorates.
これは、電流制御系の応答性、サィリスタコンバータの
周波数分解能および逆起電圧の電圧増分等に起因してい
る。すなわち、サィクロコンバータの出力周波数が高く
なるに従い、同期電動機の逆起電圧も大きくなり、サィ
クロコンバータはこの逆起電圧に見合った出力電圧を出
そうとするため、その制御信号が大振幅となりかつ出力
の周波数で正弦波状に変化する。従って、この種の同期
電動機の駆動系においては、できるだけ出力の周波数を
上げ、電流を指令値通りに追従させ得ることが望まれる
。This is due to the responsiveness of the current control system, the frequency resolution of the thyristor converter, the voltage increment of the back electromotive force, etc. In other words, as the output frequency of the cycloconverter increases, the back electromotive force of the synchronous motor also increases, and as the cycloconverter attempts to output an output voltage commensurate with this back electromotive force, its control signal becomes large in amplitude. And it changes sinusoidally with the output frequency. Therefore, in the drive system of this type of synchronous motor, it is desirable to increase the output frequency as much as possible so that the current can follow the command value.
このため、従来においては、電流指令値に前記逆起電圧
分の補償を加えてサィクロコンバータの電流指令とした
り、電流調節器の出力側に前記逆起電圧分の補償を加え
てサィクロコンバータを制御する方式等が提案され実施
されている。第１図は、前記電流調節器の出力側に逆起
電圧分の補償を加える従釆の制御方式を実施する回路図
を示す。For this reason, in the past, compensation for the back electromotive voltage was added to the current command value to obtain the current command for the cycloconverter, or compensation for the back electromotive voltage was added to the output side of the current regulator to obtain the current command for the cycloconverter. Methods for controlling this have been proposed and implemented. FIG. 1 shows a circuit diagram implementing a secondary control method that adds compensation for the back electromotive force to the output side of the current regulator.
すなわち、第１図において、参照符号１０は同期電動機
、１２はサィクロコンバータを示し、それぞれ１相分の
結線につき簡略化して示したものである。サィクロコン
バータ１２の制御系は、電流指令演算器１４、電流調節
器１６、一点弧位相讃節器１８およびパルス増幅器２０
を備える。電流指令演算器１４は、ユニット正弦波信号
（１・ｓｉｎ）からなる一方の電流指令と、波高値（Ｉ
Ｐ）からなる他方の電流指令とを掛け算して電流指令を
得るものである。なお、ユニット正弦波信号（１・ｓｉ
ｎ）は、位置検出器等の信号を同期整形して理想的な正
弦波とした信号である。しかるに、前記電流指令演算器
１４で得られた電流指令は、電流調節器１６、点弧位相
調節器１８およびパルス増幅器２０を順次経てサィクロ
コンバータ１２を制御する。この場合、同期電動機１０
の逆起電圧を補償するために、サイクロコンバータ１２
の出力側に電圧検出器２２および電流検出器２４をそれ
ぞれ設けて、出力電圧（Ｅｃ）と出力電流（１）とを検
出する。このようにして、検出された出力電圧（Ｅｃ）
と出力電流（１）とを逆起電圧演算器２６に入力して、
逆起電圧（ＥＭ）を次式により微分演算を行う。ＥＮ＝
ＢＣ−（Ｌ鼓十Ｒ耳） …‘１｝但し、Ｌ， Ｒは
負荷ィンピダンスを示し、１はリアクトル分、Ｒは抵抗
分である。That is, in FIG. 1, reference numeral 10 indicates a synchronous motor, and 12 indicates a cycloconverter, each of which is shown in a simplified manner for connection for one phase. The control system of the cycloconverter 12 includes a current command calculator 14, a current regulator 16, a single-point arc phase adjuster 18, and a pulse amplifier 20.
Equipped with The current command calculator 14 calculates one current command consisting of a unit sine wave signal (1·sin) and a peak value (I
The current command is obtained by multiplying the other current command consisting of P). In addition, the unit sine wave signal (1・si
n) is a signal obtained by synchronously shaping a signal from a position detector or the like into an ideal sine wave. However, the current command obtained by the current command calculator 14 sequentially passes through a current regulator 16, an ignition phase regulator 18, and a pulse amplifier 20 to control the cycloconverter 12. In this case, the synchronous motor 10
In order to compensate for the back electromotive voltage, the cycloconverter 12
A voltage detector 22 and a current detector 24 are respectively provided on the output side of the circuit to detect the output voltage (Ec) and the output current (1). In this way, the detected output voltage (Ec)
and output current (1) are input to the back electromotive force calculator 26,
Differential calculation is performed on the back electromotive force (EM) using the following equation. EN=
BC-(L drum 1 R ear)...'1} However, L and R indicate load impedance, 1 is a reactor component, and R is a resistance component.
そこで、前記式‘１’で得られた逆起電圧（ＥＮ）に見
合った制御信号を電流調節器１６の出力側に加算（正帰
還）して、電流調節系（電流検出器２４で検出された出
力電流（１）を電流指令演算器１４の出力側に負帰還さ
せる）とは独立に補助制御を行う。Therefore, a control signal commensurate with the back electromotive voltage (EN) obtained by the above formula '1' is added to the output side of the current regulator 16 (positive feedback), and the current regulator system (detected by the current detector 24) Auxiliary control is performed independently of the negative feedback of the output current (1) to the output side of the current command calculator 14.
この結果、電流調節器１６は、負荷インピーダンス（Ｌ
， Ｒ）分に見合った小振幅の動作のみ行えばよいこと
になる。なお、実用上においては、先の式【１’を簡略
化して、ＥＭニＥｏとみなし、電圧検出器２２によって
検出される出力電圧（Ｅｃ）を直接的に正帰還させるこ
とが多い。前述した従来の制御方式において、サィクロ
コンバータ１２は、順逆変換器を毎サイクル切換えて所
望の交流出力電圧および電流を発生するよう動作するも
のであるから、順逆変換器の切換動作において電流のい
まり込みを良くしかつ切換むだ時間を短縮するため、通
常パルスシフトの操作が行われる。このため、サイクロ
コンバータの出力電圧に短いヒゲ状の電圧が現われたり
、また出力電圧および電流には必ず有限の切換むだ時間
が存在し、理想的な正弦波とはならない欠点がある。こ
のような実際的に発生するサィクロコンバータの出力電
圧および電流の波形歪みに対し、従来方式においては逆
起電圧演算結果の出力に前記波形歪みに起因する歪みを
具え、望ましい制御信号を得ることはできない。場合に
よっては、前記逆起電圧の演算結果は、さらに制御の悪
化を招いて不安定な制御となることすらある。また、こ
のような問題を解決するため、例えば逆起電圧の演算結
果をフィル夕に掛けることも考えられるが、この場合に
は位相ずれが生じて、前記と同様に望ましい制御は不可
能となる。そこで、本発明者等は、前記従来における同
期電動機の制御方式における問題点を全て克服すべく種
々検討並びに試作を重ねた結果、サィクロコンバータの
電流制御系における電流指令の位相が逆起電圧の位相と
略同位相にあることを利用し、電流制御系に供給される
ユニット正弦波電流とサィクロコンバータの出力電圧を
整流して得られる実効値とを乗算器により掛け算して逆
起電圧を演算し、この逆起電圧に相当する制御信号を電
流制御系の電流調節器の出力に加算、すなわち正帰還す
ることにより、前記問題点を一挙に解消し、後述するよ
うに逆起電圧の補償制御を有効に達成し得ることを突き
止めた。As a result, the current regulator 16 has a load impedance (L
, R), it is only necessary to perform a small amplitude operation commensurate with the amount. In addition, in practice, the above equation [1' is often simplified, EM-Eo is assumed, and the output voltage (Ec) detected by the voltage detector 22 is directly fed back positively. In the conventional control method described above, the cycloconverter 12 operates to generate a desired AC output voltage and current by switching the forward/reverse converter every cycle. To improve integration and reduce switching dead time, a pulse shift operation is usually performed. For this reason, a short whisker-like voltage appears in the output voltage of the cycloconverter, and there is always a finite switching dead time in the output voltage and current, which has the disadvantage that an ideal sine wave is not formed. In response to such waveform distortion of the output voltage and current of the cycloconverter that actually occurs, in the conventional method, the output of the back electromotive voltage calculation result is provided with distortion due to the waveform distortion, and a desired control signal is obtained. I can't. In some cases, the calculation result of the back electromotive voltage may even lead to further deterioration of control, resulting in unstable control. In addition, in order to solve this problem, it may be possible to apply the calculation result of the back electromotive force to the filter, but in this case, a phase shift will occur, making it impossible to perform the desired control as described above. . Therefore, the present inventors conducted various studies and made prototypes in order to overcome all the problems in the conventional control system for synchronous motors. As a result, the present inventors found that the phase of the current command in the current control system of the cycloconverter is Taking advantage of the fact that they are in approximately the same phase, the unit sine wave current supplied to the current control system is multiplied by the effective value obtained by rectifying the output voltage of the cycloconverter using a multiplier to generate the back electromotive voltage. By calculating the control signal corresponding to this back electromotive force and adding it to the output of the current regulator of the current control system, that is, by performing positive feedback, the above problems can be solved at once, and the back electromotive force can be compensated as described later. We have found that control can be effectively achieved.
従って、本発明の目的は、理想的な正弦波となるような
逆起電圧の演算を行い、同期機の駆動系における逆起電
圧の安定した補償制御を達成することができる制御方式
を提供するにある。Therefore, an object of the present invention is to provide a control method that can calculate the back electromotive force to form an ideal sine wave and achieve stable compensation control of the back electromotive force in the drive system of a synchronous machine. It is in.
前記の目的を達成するため、本発明においては、所定の
電源を可変周波数変換装置を介して同期機に後続し、可
変周波数変換装置に電流制御系を接続してなる同期機の
駆動方式において、電流制御系の電流指令と可変周波数
変換装置の出力電圧を整流して得られる実効値とを乗算
器に入力して逆起電圧を演算し、この逆起電圧に相当す
る制御信号を電流制御系に正帰還することを特徴とする
。In order to achieve the above object, the present invention provides a driving method for a synchronous machine in which a predetermined power source is connected to a synchronous machine via a variable frequency converter, and a current control system is connected to the variable frequency converter. The current command of the current control system and the effective value obtained by rectifying the output voltage of the variable frequency converter are input to a multiplier to calculate the back electromotive force, and a control signal corresponding to this back electromotive force is sent to the current control system. It is characterized by positive feedback.
前記の逆起電圧補償制御方式において、可変周波数変換
装置はサィクロコンバ−夕で構成することができる。In the above-mentioned back electromotive voltage compensation control system, the variable frequency converter can be configured with a cycloconverter.
また、電流制御系は、電流指令演算器、電流調節器、点
弧位相調節器、パルス増幅器を備え、逆起電圧に相当す
る制御信号を電流調節器の出力に加算するよう礎成すれ
ば好適である。Preferably, the current control system includes a current command calculator, a current regulator, an ignition phase regulator, and a pulse amplifier, and is configured to add a control signal corresponding to the back electromotive force to the output of the current regulator. It is.
さらに、逆起電圧を演算する乗算器は、電流制御系の電
流指令演算器に供給されるユニット正弦波信号と、可変
周波数変換装置の出力電圧をダイオードおよびフィル夕
を介して得られる実効値とを入力して掛け算を行うよう
構成すれば好適である。Furthermore, the multiplier that calculates the back electromotive voltage converts the unit sine wave signal supplied to the current command calculator of the current control system and the output voltage of the variable frequency converter into an effective value obtained via a diode and a filter. It is preferable to perform multiplication by inputting .
次に、本発明に係る同期機の逆起電圧補償制御方式の実
施例につき、添付図面を参照しながら以下詳細に説明す
る。Next, an embodiment of the back electromotive force compensation control method for a synchronous machine according to the present invention will be described in detail below with reference to the accompanying drawings.
なお、説明の便宜上第１図に示す従来の制御回路と同一
の構成部分については同一の参照符号を付してその詳細
な説明を省略する。第２図は、本発明制御方式の一実施
例を示す制御回路である。For convenience of explanation, the same reference numerals are given to the same components as those of the conventional control circuit shown in FIG. 1, and detailed explanation thereof will be omitted. FIG. 2 is a control circuit showing an embodiment of the control method of the present invention.
本実施例においては、第１図に示す従来の制御回路に設
けた逆起電圧演算器に代えて、サイクロコンバータ１２
の出力側に設けた電圧検出器２２で検出された電圧（Ｅ
ｃ）を整流ダイオード２８、検出フィル夕３０および乗
算器３２をそれぞれ設けて逆起電圧を演算するよう構成
したものである。すなわち、本実施例では、同期電動機
の駆動系において、逆起電圧が電流指令の位相と略一致
していることを利用し、一方において電流指令演算器１
４に供給される理想的な正弦波であるユニット正弦波電
流指令（１・ｓｉｎ）を前記乗算器３２に入力し、他方
において前記電圧検出器２２で得られる瞬時の出力電圧
（Ｅｃ）を整流ダイオード２８で整流した後、検出フィ
ル夕３０を介して充分フィル夕をかけて実効的（平均的
）な値にした出力電圧を乗算器３２に入力し、この乗算
器において掛け算を行って逆起電圧を演算するものであ
る。すなわち、この種の同期電動機はいわゆる無整流子
電動機として運転され、電流指令の位相（／ｓｉｎ）は
磁極位置角度（したがって逆起電圧位相）に基づいて与
えられることにより、負荷力率が略１で運転され、この
ことは逆起電力位相と電流位相とが一致することを意味
する。したがって、電流位相は電流制御系により指令さ
れた位相（／ｓｉｎ）通りに制御されることを考え合せ
ることにより、逆起電力の大きさ（実効値）さえ検出で
きれば、これと電流指令の位相信号（正弦波信号）とを
選算して逆起電力の瞬時値が求まることになる。第２図
による実施例では、負荷インピーダンスによる電圧虫峯
下分を無視できるとして、逆起電力の実効値の代わりに
出力電圧の実効値を用いている。この場合、逆起電圧は
、同期電動機１０の回転速度に比例する程の時定数の大
きなものであることから、前記検出フィル夕３０を使用
することは何ら支障とならない。このようにして、乗算
器３２で演算された逆起電圧に基づいて得られた制御信
号を、従来と同様に電流調節器１６の出力側に加算（正
帰還）して、サイクロコンバータ１２における逆起電圧
による補償制御を達成することができる。すなわち「本
発明方式は、サィクロコンバータ１２の電流指令の位相
が逆起電圧の位相と略同位相にあることを利用して、位
相成分は電流指令を利用し、振幅成分は検出、演算等の
方法で規定し、これら両信号の単純な掛け算により逆起
電圧を演算し、この逆起電圧に基づいて得られた制御信
号を電流調節器１６の出力側に加算して逆起電圧の補償
制御を有効に達成することができる。なお、第２図に示
す実施例において、乗算器３２におけるユニット正弦波
電流指令と掛け合わせる他方の逆起電圧の規定の仕方に
種々の方法を採用することができる。In this embodiment, a cycloconverter 12 is used instead of the back electromotive force calculator provided in the conventional control circuit shown in FIG.
The voltage (E
c) is constructed so that a rectifier diode 28, a detection filter 30, and a multiplier 32 are provided to calculate the back electromotive force. That is, in this embodiment, in the drive system of the synchronous motor, the fact that the back electromotive force substantially matches the phase of the current command is utilized, and on the other hand, the current command calculator 1
A unit sine wave current command (1·sin), which is an ideal sine wave supplied to the voltage detector 22, is input to the multiplier 32, and on the other hand, the instantaneous output voltage (Ec) obtained by the voltage detector 22 is rectified. After being rectified by the diode 28, the output voltage, which has been sufficiently filtered through the detection filter 30 to an effective (average) value, is input to the multiplier 32. It calculates voltage. That is, this type of synchronous motor is operated as a so-called non-commutator motor, and the phase (/sin) of the current command is given based on the magnetic pole position angle (therefore, the back electromotive force phase), so that the load power factor is approximately 1. This means that the back electromotive force phase and the current phase match. Therefore, by considering that the current phase is controlled according to the phase (/sin) commanded by the current control system, if only the magnitude (effective value) of the back electromotive force can be detected, this and the phase signal of the current command can be detected. (sine wave signal), the instantaneous value of the back electromotive force can be found. In the embodiment shown in FIG. 2, the effective value of the output voltage is used instead of the effective value of the back electromotive force, assuming that the voltage under the voltage due to the load impedance can be ignored. In this case, since the back electromotive voltage has a time constant so large that it is proportional to the rotational speed of the synchronous motor 10, there is no problem in using the detection filter 30. In this way, the control signal obtained based on the back electromotive force calculated by the multiplier 32 is added to the output side of the current regulator 16 (positive feedback) as in the conventional case, and the reverse Compensatory control using electromotive force can be achieved. In other words, "The method of the present invention utilizes the fact that the phase of the current command of the cycloconverter 12 is approximately in phase with the phase of the back electromotive force, and uses the current command for the phase component, and detects, calculates, etc. the amplitude component. The back electromotive force is calculated by simply multiplying both signals, and the control signal obtained based on this back electromotive force is added to the output side of the current regulator 16 to compensate for the back electromotive force. Control can be effectively achieved.In the embodiment shown in FIG. 2, various methods may be adopted for defining the other back electromotive voltage to be multiplied by the unit sine wave current command in the multiplier 32. I can do it.
例えば、逆起電圧を検出して演算の上規定するのではな
く、逆起電氏に相当する速度指令があれば、この速度指
令を使用して補償制御ループを構成してもよい。また、
速度検出器が存在する時には、この速度検出器を使用し
てもよい。さらに、必要に応じて、第３図に示すように
、微分演算器３４を設けて、この微分演算器３４に電流
指令演算器１４で得られた電流指令を入力して微分演算
し、この微分演算出力を前記乗算器３２で得られる制御
信号とを加算して電流調節器１６の出力側に加算するよ
う構成して、負荷インピーダンスの補償も行うことがで
きる。なお、この場合に使用する微分演算器３４は、入
力の電流指令が理想的な正弦波であるため、演算出力も
理想的な正弦波となり、制御系が不安定となることはな
い。前述した実施例から明らかなように、本発明によれ
ば、制御信号を得るために演算される逆起電圧は理想的
な正弦波となるため、この制御信号を電流調節器の出力
側に加算（正帰還）して補償制御ル−プを構成しても、
制御系に何ら悪い影響を及ぼすことなく、安定した逆起
電圧の補償制御を達成することができる。For example, if there is a speed command corresponding to the back electromotive force, the compensation control loop may be configured using this speed command, instead of detecting the back electromotive force and calculating the specified value. Also,
A speed detector may be used when present. Furthermore, if necessary, as shown in FIG. It is also possible to compensate for the load impedance by adding the calculation output and the control signal obtained from the multiplier 32 and adding the result to the output side of the current regulator 16. In addition, since the input current command of the differential calculator 34 used in this case is an ideal sine wave, the calculated output also becomes an ideal sine wave, and the control system will not become unstable. As is clear from the embodiments described above, according to the present invention, the back electromotive force calculated to obtain the control signal is an ideal sine wave, so this control signal is added to the output side of the current regulator. Even if a compensation control loop is configured with (positive feedback),
Stable back electromotive force compensation control can be achieved without any adverse effect on the control system.
すなわち、本発明方式では、従来方式のような微分演算
器を含まないため、本質的に安定して演算動作を行う。
また、本発明方式は、従来方式のように３相の出力電圧
を個別に検出する必要がなく、実効的な値を求めること
から本質的に検出器を１個設ければよく、構成が極めて
簡単となる利点を有する。以上、本発明の好適な実施例
について説明したが、本発明は前述したサィクロコンバ
ータで駆動される通常の回転形同期電動機に適用し得る
ばかりでなく、リニアシンクロナスモータにも適用する
ことができ、さらには可変電圧可変周波数の電源で駆動
する各種同期電動機の逆起電圧補償制御にも応用するこ
とができる。That is, since the method of the present invention does not include a differential calculator unlike the conventional method, the calculation operation is essentially stable.
In addition, unlike the conventional method, the method of the present invention does not require the detection of the output voltages of the three phases individually, and since the effective value is determined, essentially only one detector is required, and the configuration is extremely simple. It has the advantage of being simple. Although the preferred embodiments of the present invention have been described above, the present invention can be applied not only to a normal rotary synchronous motor driven by the cycloconverter described above, but also to a linear synchronous motor. Furthermore, it can also be applied to back electromotive force compensation control of various synchronous motors driven by variable voltage and variable frequency power supplies.
その他、本発明の精神を逸脱しない範囲内において種々
の設計変更をなし得ることは勿論である。It goes without saying that various other design changes can be made without departing from the spirit of the invention.
第１図は従来の同期電動機の逆起電圧補償制御方式を示
す回路図、第２図は本発明に係る同期機の逆起電圧補償
制御方式の−実施例を示す回路図、第３図は本発明方式
の変形例を示す回路図である。
１０・・・・・・同期電動機、１２…・・・サィクロコ
ンバータ、１４・・…・電流指令演算器、１６・・・・
・・電流調節器、１８・・・・・・点弧位相調節器、２
０・・・・・・パルス増幅器、２２・・・・・・電圧検
出器、２４・・・・・・電流検出器、２６・・・・・・
逆起電圧演算器、２８・・・・・・整流ダイオード、３
０……検出フィル夕、３２…・・・乗算器、３４・・・
・・・微分演算器。
ＦＩＧ．Ｉ
ＦＩＧ．２
ｎ
○
いFIG. 1 is a circuit diagram showing a conventional back electromotive voltage compensation control method for a synchronous motor, FIG. 2 is a circuit diagram showing an embodiment of the back electromotive force compensation control method for a synchronous machine according to the present invention, and FIG. FIG. 3 is a circuit diagram showing a modification of the method of the present invention. 10...Synchronous motor, 12...Cyclo converter, 14...Current command calculator, 16...
...Current regulator, 18...Ignition phase regulator, 2
0...Pulse amplifier, 22...Voltage detector, 24...Current detector, 26...
Back electromotive force calculator, 28... Rectifier diode, 3
0...detection filter, 32...multiplier, 34...
...differential calculator. FIG. IFIG. 2 n ○
Claims (1)
接続し、可変周波数変換装置に電流制御系を接続してな
る同期機の駆動方式において、電流制御系の電流指令と
可変周波数変換装置の出力電圧を整流して得られる実効
値とを乗算器に入力して逆起電圧を演算し、この逆起電
圧に相当する制御信号を電流制御系に正帰還することを
特徴とする同期機の逆起電圧補償制御方式。 ２ 特許請求の範囲第１項記載の逆起電圧補償制御方式
において、可変周波数変換装置はサイクロコンバータか
らなる同期機の逆起電圧補償制御方式。 ３ 特許請求の範囲第１項または第２項記載の逆起電圧
補償制御方式において、電流制御系は、電流指令演算器
、電流調節器、点弧位相調節器、パルス増幅器を備え、
逆起電圧に相当する制御信号を電流調節器の出力に加算
するよう構成してなる同期機の逆起電圧補償制御方式。 ４ 特許請求の範囲第１項乃第３項のいずれかに記載の
逆起電圧補償制御方式において、逆起電圧を演算する乗
算器は、電流制御系の電流指令演算器に供給されるユニ
ツト正弦波電流と、可変周波数変換装置の出力電圧をダ
イオードおよびフイルタを介して得られる実効値とを入
力して掛け算を行うことからなる同期機の逆起電圧補償
制御方式。[Claims] 1. In a drive system for a synchronous machine in which a predetermined power source is connected to a synchronous machine via a variable frequency converter, and a current control system is connected to the variable frequency converter, a current command for the current control system is provided. and the effective value obtained by rectifying the output voltage of the variable frequency converter are input into a multiplier to calculate a back electromotive voltage, and a control signal corresponding to this back electromotive force is positively fed back to the current control system. Features a back electromotive voltage compensation control method for synchronous machines. 2. In the back electromotive force compensation control system as set forth in claim 1, the variable frequency conversion device is a back electromotive voltage compensation control system for a synchronous machine including a cycloconverter. 3. In the back electromotive force compensation control system according to claim 1 or 2, the current control system includes a current command calculator, a current regulator, an ignition phase regulator, and a pulse amplifier,
A back electromotive voltage compensation control method for a synchronous machine configured to add a control signal corresponding to the back electromotive force to the output of a current regulator. 4. In the back electromotive voltage compensation control method according to any one of claims 1 to 3, the multiplier for calculating the back electromotive voltage is a unit sine multiplier supplied to a current command calculator of the current control system. A back electromotive force compensation control method for a synchronous machine that involves inputting and multiplying the wave current and the effective value obtained from the output voltage of a variable frequency converter via a diode and a filter.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP55184037A JPS6024679B2 (en) | 1980-12-26 | 1980-12-26 | Back electromotive force compensation control method for synchronous machine |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP55184037A JPS6024679B2 (en) | 1980-12-26 | 1980-12-26 | Back electromotive force compensation control method for synchronous machine |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS57110097A JPS57110097A (en) | 1982-07-08 |
| JPS6024679B2 true JPS6024679B2 (en) | 1985-06-14 |
Family
ID=16146249
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP55184037A Expired JPS6024679B2 (en) | 1980-12-26 | 1980-12-26 | Back electromotive force compensation control method for synchronous machine |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS6024679B2 (en) |
Families Citing this family (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH01206885A (en) * | 1988-02-09 | 1989-08-21 | Fanuc Ltd | Control method for servomotor |
-
1980
- 1980-12-26 JP JP55184037A patent/JPS6024679B2/en not_active Expired
Also Published As
| Publication number | Publication date |
|---|---|
| JPS57110097A (en) | 1982-07-08 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| EP0490024B1 (en) | Induction motor vector control | |
| JPS5928159B2 (en) | Excitation adjustment device | |
| JPS6024679B2 (en) | Back electromotive force compensation control method for synchronous machine | |
| KR100269450B1 (en) | Motor controller | |
| KR100637674B1 (en) | Motor driving control device | |
| JPH0783599B2 (en) | Control method of circulating current type cycloconverter | |
| JPH02261059A (en) | Dc voltage pulsation correcting power source device | |
| JP2781602B2 (en) | Power converter control device and system thereof | |
| JPS5819169A (en) | Controlling method for pwm control converter | |
| JP3367341B2 (en) | Control method of PWM control self-excited rectifier | |
| JP3824206B2 (en) | Linear induction motor electric vehicle control device | |
| JPH0634614B2 (en) | AC motor controller | |
| KR100226056B1 (en) | Elevator velocity control apparatus | |
| JPS6330236Y2 (en) | ||
| JPS60261383A (en) | Controlling method and device of power converter | |
| KR20000008594A (en) | Motor driving control device | |
| JPS638709B2 (en) | ||
| JPS63133885A (en) | Controller for ac motor | |
| JPH08214543A (en) | Dc-dc converter and controlling method therefor | |
| JP2519078Y2 (en) | Frequency control device for main shaft drive generator | |
| JPH0731192A (en) | Controller and control method for variable speed drive system | |
| JPH07118937B2 (en) | Synchronous motor controller | |
| JP2589070B2 (en) | Converter phase controller | |
| JP2000209864A (en) | Current reference circuit for rectifier | |
| JPH1080199A (en) | Automatic voltage regulator of synchronous generator |