JPS5944819B2 - Crosstalk component cancellation circuit in angle modulated wave signal transmission line - Google Patents

Crosstalk component cancellation circuit in angle modulated wave signal transmission line

Info

Publication number
JPS5944819B2
JPS5944819B2 JP4759477A JP4759477A JPS5944819B2 JP S5944819 B2 JPS5944819 B2 JP S5944819B2 JP 4759477 A JP4759477 A JP 4759477A JP 4759477 A JP4759477 A JP 4759477A JP S5944819 B2 JPS5944819 B2 JP S5944819B2
Authority
JP
Japan
Prior art keywords
modulated wave
angle
signal
crosstalk
wave signals
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired
Application number
JP4759477A
Other languages
Japanese (ja)
Other versions
JPS53132907A (en
Inventor
宣明 高橋
富士男 鈴木
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Victor Company of Japan Ltd
Original Assignee
Victor Company of Japan Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Victor Company of Japan Ltd filed Critical Victor Company of Japan Ltd
Priority to JP4759477A priority Critical patent/JPS5944819B2/en
Priority to US05/899,891 priority patent/US4211978A/en
Publication of JPS53132907A publication Critical patent/JPS53132907A/en
Publication of JPS5944819B2 publication Critical patent/JPS5944819B2/en
Expired legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04H—BROADCAST COMMUNICATION
    • H04H40/00—Arrangements specially adapted for receiving broadcast information
    • H04H40/18—Arrangements characterised by circuits or components specially adapted for receiving
    • H04H40/27—Arrangements characterised by circuits or components specially adapted for receiving specially adapted for broadcast systems covered by groups H04H20/53 - H04H20/95
    • H04H40/36—Arrangements characterised by circuits or components specially adapted for receiving specially adapted for broadcast systems covered by groups H04H20/53 - H04H20/95 specially adapted for stereophonic broadcast receiving
    • H04H40/45—Arrangements characterised by circuits or components specially adapted for receiving specially adapted for broadcast systems covered by groups H04H20/53 - H04H20/95 specially adapted for stereophonic broadcast receiving for FM stereophonic broadcast systems receiving
    • H04H40/63—Arrangements characterised by circuits or components specially adapted for receiving specially adapted for broadcast systems covered by groups H04H20/53 - H04H20/95 specially adapted for stereophonic broadcast receiving for FM stereophonic broadcast systems receiving for separation improvements or adjustments
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/06—Receivers
    • H04B1/10—Means associated with receiver for limiting or suppressing noise or interference
    • H04B1/12—Neutralising, balancing, or compensation arrangements
    • H04B1/123—Neutralising, balancing, or compensation arrangements using adaptive balancing or compensation means
    • H04B1/126—Neutralising, balancing, or compensation arrangements using adaptive balancing or compensation means having multiple inputs, e.g. auxiliary antenna for receiving interfering signal
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B14/00—Transmission systems not characterised by the medium used for transmission
    • H04B14/002—Transmission systems not characterised by the medium used for transmission characterised by the use of a carrier modulation
    • H04B14/006—Angle modulation

Landscapes

  • Engineering & Computer Science (AREA)
  • Signal Processing (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Noise Elimination (AREA)
  • Stereo-Broadcasting Methods (AREA)

Description

【発明の詳細な説明】 本発明は被角度変調波信号伝送路におけるクロストーク
成分打消し回路に係り、希望チャンネルと隣接するチャ
ンネルの被角度変調波信号の一部がクロストーク成分と
して混入している希望チャンネルの被角度変調波信号か
ら、上記クロストーク成分を打消すに際し、上記両チャ
ンネルの被角度変調波信号の同期性の有無を判別する同
期検波器の出力に応じて回路動作を制御することにより
、上記両チャンネルの被角度変調波信号が同一の角度偏
移を有する場合でも回路を誤動作することなく、不必要
なりロストーク成分の打消し動作を行なうことがないよ
うにし得るクロストーク成分打消し回路を提供すること
を目的とする。DETAILED DESCRIPTION OF THE INVENTION The present invention relates to a crosstalk component cancellation circuit in an angle-modulated wave signal transmission line, and a crosstalk component canceling circuit in which a part of the angle-modulated wave signal of a channel adjacent to a desired channel is mixed as a crosstalk component. When canceling the crosstalk component from the angle modulated wave signal of the desired channel, the circuit operation is controlled according to the output of a synchronous detector that determines whether the angle modulated wave signals of both channels are synchronized. By this, even if the angle-modulated wave signals of both channels have the same angular deviation, the crosstalk component can be canceled without causing the circuit to malfunction and without unnecessary losstalk component cancellation. The purpose is to provide a circuit.

複数の被角度変調波信号を伝送する伝送路、例えばマル
チチャンネルレコードの記録、再生系におけるマルチチ
ャンネルの差信号伝送路において、希望チャンネルの被
角度変調波信号（以下本チャンネル信号ともいう）に、
この希望チャンネルと隣接するチャンネルの被角度変調
波信号（以下隣接チャンネル信号ともいう）の一部がク
ロストーク成分として混入することがある。In a transmission line that transmits a plurality of angle-modulated wave signals, for example, a multi-channel difference signal transmission line in a multi-channel record recording and reproduction system, the angle-modulated wave signal of the desired channel (hereinafter also referred to as main channel signal) is
A part of the angle modulated wave signal (hereinafter also referred to as an adjacent channel signal) of a channel adjacent to the desired channel may be mixed as a crosstalk component.

ここで、マルチチャンネルレコードは、マルチチャンネ
ルのオーディオ信号を例えば和信号と差信号とし、差信
号を更に角度変調して得られた被角度変調波信号が、直
接波の和信号と多重されて１本の音溝壁に録音されてい
る。このため、マルチチャンネルレコードの記録系及び
再生系において、両音溝壁の被角度変調波信号間にクロ
ストークを生じやすく、この場合、被角度変調波信号の
角度が変化して相互変調歪を生ずる。上記のような複数
の被角度変調波信号伝送路において、本チヤンネル信号
に隣接チヤンネル信号の一部がクロストークとして含ま
れていると、上記のように相互変調歪を生じ、検波出力
に歪を生ずる。Here, in a multi-channel record, the multi-channel audio signal is, for example, a sum signal and a difference signal, and the angle-modulated wave signal obtained by further angle-modulating the difference signal is multiplexed with the sum signal of the direct wave. It is recorded on the sound groove wall of the book. For this reason, in the recording and playback systems of multi-channel records, crosstalk tends to occur between the angle-modulated wave signals on both sound groove walls, and in this case, the angle of the angle-modulated wave signals changes, causing intermodulation distortion. arise. In the multiple angle modulated wave signal transmission paths as described above, if part of the adjacent channel signal is included as crosstalk in the main channel signal, intermodulation distortion will occur as described above, and the detected output will be distorted. arise.

そこで、このクロストーク成分低減のために、被角度変
調波信号の復調信号を、被角度変調波信号の包絡線に応
じてレベル制御する等の方法が考えられる（例えば特公
昭５２−２５９５号公報記載の発明）。Therefore, in order to reduce this crosstalk component, a method such as controlling the level of the demodulated signal of the angle-modulated wave signal according to the envelope of the angle-modulated wave signal can be considered (for example, Japanese Patent Publication No. 52-2595 described invention).

しかし、このように復調後にクロストーク成分の低減を
行なう方法では、クロストーク成分を完全に除去するの
はなかなか容易ではない。一方、クロストーク量を検出
し、この検出量が零になるように、本チヤンネル信号に
隣接チヤンネル信号及びこれとは極件が異なる隣接チヤ
ンネル信号を夫々混合してクロストーク成分を打消すと
いう、本出願人の同日付の特許出願記載の発明によれば
、復調前にクロストーク成分を打消すことができるため
、希望チヤンネルの被角度変調波信号を高忠実度で復調
せしめ得る。゛然るに、この提案発明は本チヤンネル信
号と隣接チヤンネル信号とが別々の変調信号で所定周波
数の搬送波を角度変調した信号である場合は問題ないの
であるが、両チヤンネル信号が全く等しい角度偏移を有
する場合は、隣接チヤンネル信号の包絡線の大小関係が
即クロストーク成分を打消す条件と対応しないため、回
路中の素子のバラツキによつて誤動作することがあると
いう問題点があつた。However, with this method of reducing crosstalk components after demodulation, it is not easy to completely remove crosstalk components. On the other hand, the crosstalk component is canceled by detecting the amount of crosstalk and mixing the main channel signal with an adjacent channel signal and an adjacent channel signal with a different polarity, respectively, so that the detected amount becomes zero. According to the invention described in the patent application filed on the same date by the present applicant, crosstalk components can be canceled before demodulation, so that the angle-modulated wave signal of the desired channel can be demodulated with high fidelity. However, with this proposed invention, there is no problem if the main channel signal and the adjacent channel signal are signals obtained by angle-modulating a carrier wave of a predetermined frequency using different modulation signals, but if both channel signals have exactly the same angular shift, In this case, the magnitude relationship of the envelopes of adjacent channel signals does not correspond to the conditions for immediately canceling the crosstalk component, so there is a problem that malfunction may occur due to variations in elements in the circuit.

本発明は上記の問題点を解決したものであり、以下図面
と共にその一実施例について説明する。The present invention solves the above problems, and one embodiment thereof will be described below with reference to the drawings.

図は本発明回路の一実施例の回路系統図で、１は本チヤ
ンネル信号入力端子、２は隣接チヤンネル信号入力端子
である。入力端子１に入来した本チヤンネル信号ＳＡは
、入力端子２に入来する隣接チヤンネル信号ＳＢがクロ
ストークとして一部（δＳＢ）混入されており、上記隣
接チヤンネル信号ＳＢと共に同期検波器３に供給され、
ここで両者の角度偏移が一致しているか否か、すなわち
同期性が判別される。同期検波器３は、この同期性の有
無に応じて、増幅器４にその動作制御用信号を出力する
。まず、両チヤンネル信号の角度偏移が互いに異なる場
合について説明する。The figure is a circuit system diagram of one embodiment of the circuit of the present invention, where 1 is a main channel signal input terminal, and 2 is an adjacent channel signal input terminal. The main channel signal SA that has entered the input terminal 1 has a portion (δSB) mixed with the adjacent channel signal SB that has entered the input terminal 2 as crosstalk, and is supplied to the synchronous detector 3 together with the adjacent channel signal SB. is,
Here, it is determined whether the two angular deviations match, that is, the synchronization. The synchronous detector 3 outputs an operation control signal to the amplifier 4 depending on the presence or absence of this synchronism. First, a case will be described in which the angular shifts of both channel signals are different from each other.

この場合、入力端子２より入来した隣接チヤンネル信号
ＳＢは、同期検波器３の出力信号により、通常の増幅動
作を行なうよう制御されている増幅器４に供給され、こ
こでＫ倍に増幅されて取り出された後、位相反転器５で
１８『位相が推移される。従つて、抵抗Ｒ２の一端と増
幅器４の出力側との接続点ａにはＫＳＢなる信号が生じ
、位相反転器５の出力側と抵抗Ｒ６の一端及び後述する
可変減衰器６の入力側との接続点ｂには−ＫＳＢなる信
号が生ずる。ここで、入力端子１は抵抗Ｒ１を介して、
上記抵抗Ｒ２の他端及び抵抗Ｒ３，Ｒ５，Ｒ７の一端、
本チヤンネル信号出力端子１６に夫々接続されている。
抵抗Ｒ，と抵抗Ｒ２，Ｒ３との接続点ｃとする。また、
抵抗Ｒ３の他端は可変減衰器６の入力側に接続されてい
る。ここで、いまＲ１くＲ２，Ｒ３とすると、ｃ点のイ
ンピーダンスはほぼＲ１となるが、信号ＫＳＢは抵抗Ｒ
１とＢ５，の各抵抗値により定められる信号分割比αに
より分割されてαＫＳＢなる信号としてｃ点に生じる。In this case, the adjacent channel signal SB input from the input terminal 2 is supplied to the amplifier 4 which is controlled to perform normal amplification operation by the output signal of the synchronous detector 3, where it is amplified by K times. After being taken out, the phase is shifted by the phase inverter 5. Therefore, a signal KSB is generated at the connection point a between one end of the resistor R2 and the output side of the amplifier 4, and a signal KSB is generated between the output side of the phase inverter 5, one end of the resistor R6, and the input side of the variable attenuator 6, which will be described later. A signal -KSB is generated at connection point b. Here, input terminal 1 is connected via resistor R1,
The other end of the resistor R2 and one end of the resistors R3, R5, R7,
They are respectively connected to the main channel signal output terminal 16.
It is assumed that the connection point c is between the resistor R and the resistors R2 and R3. Also,
The other end of the resistor R3 is connected to the input side of the variable attenuator 6. Now, if R1 times R2 and R3, the impedance at point c will be approximately R1, but the signal KSB will be connected to the resistance R.
The signal is divided by the signal division ratio α determined by the resistance values of B1 and B5, and is generated at point c as a signal αKSB.

一方、ｂ点の信号は、減衰量Ｌの可変減衰器６と、抵抗
Ｒ，とＲ３の各抵抗値により定められる信号分割比βに
より分割されて一βＫＬＳＢなる信号としてｃ点に生じ
る。On the other hand, the signal at point b is divided by the variable attenuator 6 with the attenuation amount L and the signal division ratio β determined by the resistance values of the resistors R and R3, and is generated at point c as a signal of 1 βKLSB.

このｃ点にはδＳＢなるクロストーク成分を含有する本
チヤンネル信号ＳＡが抵抗Ｒ１を介して加えられている
ため、結局、ｃ点の電圧ｃは次式で表わされる。Since the main channel signal SA containing the crosstalk component δSB is applied to this point c via the resistor R1, the voltage c at the point c is finally expressed by the following equation.

上記ａ点のＫＳＢなる信号は、抵抗Ｒ４，Ｒ５で分割さ
れて包絡線検出器７に供給され、ここで包絡線検波され
て電圧比較器９の一方の入力端子に供給される。The signal KSB at point a is divided by resistors R4 and R5 and supplied to the envelope detector 7, where the envelope is detected and supplied to one input terminal of the voltage comparator 9.

同様に、ｂ点の−ＫＳＢなる信号は抵抗Ｒ６，Ｒ７で分
割されて包絡線検出器８に供給され、ここで包絡線検波
されて電圧比較器９の他方の入力端子に供給される。一
方、上記電圧Ｖｃは抵抗Ｒ４とＲ５の接続点ｄ、及び抵
抗Ｒ６とＲ７の接続点ｅに夫々所定の分割比、ハ←、，
占で分割されて加えられている。Similarly, the signal -KSB at point b is divided by resistors R6 and R7 and supplied to envelope detector 8, where the envelope is detected and supplied to the other input terminal of voltage comparator 9. On the other hand, the voltage Vc is applied to the connection point d between the resistors R4 and R5 and the connection point e between the resistors R6 and R7 at a predetermined division ratio, C←, ,
It is divided and added by fortune-telling.

従つて、ｄ点における電圧Ｖｄは次式で表わされる。Therefore, the voltage Vd at point d is expressed by the following equation.

同様に、点ｅにおける電圧ｅは次式で表わされる。Similarly, the voltage e at point e is expressed by the following equation.

ここで 〜 とおく、 従つて、クロストーク量が少ない信号と大きい信号とを
夫々比較すると、クロストーク量の大なる方が包絡線の
変化量も大きく、従つて立上り時間よりも立下り時間の
方が長い時定数回路を有している７，８のような一般的
な包絡線検出器の出力は、クロストーク量の大なる方が
より大きな直流出力となる。Here, ~. Therefore, if we compare a signal with a small amount of crosstalk and a signal with a large amount of crosstalk, the larger the amount of crosstalk, the larger the amount of change in the envelope, and therefore the fall time is smaller than the rise time. The output of general envelope detectors such as Nos. 7 and 8, which have a longer time constant circuit, has a larger amount of crosstalk, resulting in a larger DC output.

電圧比較器９は信号Ｖｄの包絡線の大きな部分と信号ｅ
の包絡線の大きな部分とをレベル比較し、信号ｄの包絡
線の大きな部分のレベルが信号Ｖｅの包絡線の大きな部
分のレベルよりも大であるときは可変減衰器６の減衰量
Ｌが小になるように動作せしめる制御電圧を出力し、信
号Ｖｄの包絡線の大きな部分のレベルが信号ｅの包絡線
の大きな部分のレベルよりも小であるときは可変減衰器
６の減衰量Ｌが大になるように動作せしめる制御電圧を
出力する。The voltage comparator 9 compares a large part of the envelope of the signal Vd with the signal e.
When the level of the large part of the envelope of the signal d is higher than the level of the large part of the envelope of the signal Ve, the attenuation amount L of the variable attenuator 6 is reduced. When the level of the large part of the envelope of the signal Vd is lower than the level of the large part of the envelope of the signal e, the attenuation amount L of the variable attenuator 6 is large. Outputs a control voltage to operate the device so that the

すなわち、信号Ｖｄ及び信号Ｖｅは、それぞれ信号Ｖｃ
に正相及び逆相のクロストーク分を加えたものであるか
ら、信号Ｖｃに正相のクロストーク分が多く含まれてい
る場合には、信号ｄのクロストーク分は増加し、信号ｅ
のクロストーク分は減少し、信号Ｖｄの包絡線の大きな
部分が信号ｅの包絡線の大きな部分よりもレベルが大と
なり、ｃ点には逆相の信号がより多く加えられることに
なり、また、信号ｃに逆相のクロストーク分が多く含ま
れている場合には、信号ｄのクロストーク分は減少し、
信号Ｖｅのクロストーク分は増加し、信号Ｖｅの包絡線
の大きな部分が信号Ｖｄの包絡線の大きな部分よりもレ
ベルが大となり、ｃ点には逆相の信号がより少なく加え
られることになる。That is, the signal Vd and the signal Ve are respectively the signal Vc
is the sum of the positive-phase and negative-phase crosstalk components, so if the signal Vc contains a large amount of positive-phase crosstalk components, the crosstalk component of the signal d increases, and the signal e
The crosstalk component of will decrease, and the level of the large part of the envelope of signal Vd will be higher than the large part of the envelope of signal e, and more signals of the opposite phase will be added to point c, and , if signal c contains a large amount of anti-phase crosstalk, the crosstalk of signal d decreases,
The crosstalk component of the signal Ve increases, and the large part of the envelope of the signal Ve has a higher level than the large part of the envelope of the signal Vd, and less signals of the opposite phase are added to the point c. .

従つて、信号ｃの正相のクロストーク分と逆相のクロス
トーク分とが等しくなるように作用することになり、−
その結果、信号ｄの包絡線の大きな部分のレベルが同一
になる時点で回路の動作が安定する。すなわち、上記の
包絡線のピーク値は又は包絡線の変化分が等しくなるよ
うに、電圧比較器９及び可変減衰器６は動作せしδ＋α
Ｋ″Ｋ．Ｋ；．↑：ｉ：２０仇枠：；．．＆４っ４．、
そのクロストーク成分が相殺除去される。Therefore, it acts so that the positive phase crosstalk component and the negative phase crosstalk component of signal c are equal, and -
As a result, the operation of the circuit becomes stable when the levels of a large portion of the envelope of the signal d become the same. That is, the voltage comparator 9 and the variable attenuator 6 are not operated so that the peak value of the envelope or the change in the envelope is equal.
K″K.K;.↑:i:20 enemy frame:;..&4 4.,
The crosstalk components are canceled out and removed.

しかし、ここで、本チヤンネル信号に隣接チヤンネル信
号のクロストーク成分が混入する時点と、このクロスト
ーク成分を打消すための回路が動作させられる時点とに
おける両信号間の時間差は、その伝送経路の相違等のた
め常に一定であるとは限らない。However, here, the time difference between the two signals between the time when the crosstalk component of the adjacent channel signal is mixed into the main channel signal and the time when the circuit for canceling this crosstalk component is activated is the difference between the two signals. It is not always constant due to differences, etc.

これらの時間差が被角度変調波信号のキヤリアの波長λ
に対してキλ（ｎ−１，２，・・・・・・）の関係にあ
るときは、クロストークが付加される時点に対し、クロ
ストークを打消そうとする時点で両信号間に９０゜の位
相差が生じ、上記のように位相差０゜の増幅器４の出力
信号並びに位相差１８０゜の位相反転器５の出力信号に
よつてはクロストーク成分を打消すことはできない。The time difference between these is the carrier wavelength λ of the angle modulated wave signal.
When there is a relationship of λ(n-1, 2,...) with respect to A phase difference of 0.degree. is generated, and as described above, the crosstalk component cannot be canceled by the output signal of the amplifier 4 with a phase difference of 0.degree. and the output signal of the phase inverter 5 with a phase difference of 180.degree.

そこで、このような状態、更には両時点での位相差が任
意であつてもクロストーク成分を打消し得るよう、図示
の実施例では以下の回路を設けている。Therefore, in order to cancel out the crosstalk component even in such a state, and furthermore, even if the phase difference between the two points is arbitrary, the following circuit is provided in the illustrated embodiment.

すなわち、増幅器４の出力信号は９０゜移相器１０に供
給され、ここで９０゜移相された後位相反転器１１によ
り位相反転されて結局２７０゜移相された信号が取り出
され可変減衰器１２に供給される。That is, the output signal of the amplifier 4 is supplied to a 90° phase shifter 10, where the phase is shifted by 90°, the phase is inverted by a phase inverter 11, and a signal whose phase is shifted by 270° is taken out and sent to a variable attenuator. 12.

この可変減衰器１２の出力端は抵抗Ｒ，３を介して抵抗
Ｒｌ２の一端に接続されている。移相器１０の出力端は
抵抗Ｒｌ４及びＲｌ５を直列に介して出力端子１６に接
続される一方、上記抵抗Ｒ，２の他端に接続されている
。また位相反転器１１の出力端は抵抗Ｒｌ６及びＲｌ７
を直列に介して出力端子１６に接続されている。抵抗Ｒ
ｌ２〜Ｒｌ７は夫々抵抗Ｒ２〜Ｒ７に対応している。移
相器１０の出力信号は抵抗Ｒｌ４とＲｌ５により分圧さ
れ、かつ、抵抗Ｒｌ４とＲｌ５とにより分圧された抵抗
Ｒｌ２及びＲｌ３の接続点ｆの信号と混合されて包絡線
検出器１３に供給される。The output end of this variable attenuator 12 is connected to one end of a resistor Rl2 via a resistor R,3. The output end of the phase shifter 10 is connected to the output terminal 16 via resistors Rl4 and Rl5 in series, and is connected to the other end of the resistors R and 2. Further, the output terminal of the phase inverter 11 is connected to resistors Rl6 and Rl7.
are connected to the output terminal 16 through the terminals in series. Resistance R
l2 to Rl7 correspond to resistors R2 to R7, respectively. The output signal of the phase shifter 10 is voltage-divided by resistors Rl4 and Rl5, mixed with the signal at the connection point f of resistors Rl2 and Rl3, which is voltage-divided by resistors Rl4 and Rl5, and then supplied to the envelope detector 13. be done.

一方、位相反転器１１の出力信号は抵抗Ｒｌ６とＲｌ７
とにより分圧された上記ｆ点の信号と混合されて包絡線
検出器１４に供給される。包絡線検出器１３，１４より
包絡線に応じてレベルが異なる直流電圧が電圧比較器１
５に供給され、ここでレベル比較された後可変減衰器１
２に制御電圧として供給される。電圧比較器１５は前記
電圧比較器９と同様に、包絡線検出器１３，１４の入力
信号の包絡線のピーク値若しくはその変化分が互に等し
くなるように可変減衰器１２の減衰量を可変制御する。
この場合、移相器１０の出力は９０゜移相されており、
位相反転器１１の出力は２７００移相されているから、
ｆ点の信号のクロストークの９『成分が多い場合には、
包絡線検出器１３の入力信号のピーク値若しくはその変
化分が多くなり、包絡線検出器１４の入力信号のピーク
値若しくはその変化分が少なくなる。On the other hand, the output signal of the phase inverter 11 is connected to the resistors Rl6 and Rl7.
The signal is mixed with the voltage-divided signal at point f and supplied to the envelope detector 14. The voltage comparator 1 detects a DC voltage whose level differs depending on the envelope from the envelope detectors 13 and 14.
5, where the levels are compared and then variable attenuator 1.
2 as a control voltage. Like the voltage comparator 9, the voltage comparator 15 varies the amount of attenuation of the variable attenuator 12 so that the peak values of the envelopes of the input signals of the envelope detectors 13 and 14 or the changes thereof are equal to each other. Control.
In this case, the output of the phase shifter 10 is phase shifted by 90°,
Since the output of the phase inverter 11 is phase shifted by 2700,
If there are many crosstalk components of the signal at point f,
The peak value of the input signal of the envelope detector 13 or the amount of change thereof increases, and the peak value of the input signal of the envelope detector 14 or the amount of change thereof decreases.

また、ｆ点の信号のクロストークの２７００成分が多い
場合には、包絡線検出器１４の入力信号のピーク値若じ
くはその変化分が多くなり、包絡線検出器１３の入力信
号のピーク値若しくはその変化分が少なくなることにな
る。これにより、図中、左半分の回路によりクロストー
クの実成分（０゜又は１８『成分）が打消されているｆ
点の被角度変調波信号は、図中右半分の回路によりクロ
ストークの虚成分（９０右又は２７０゜成分）を打ち消
されて出力端子１６より出力される。Furthermore, when there are many 2700 components of crosstalk in the signal at point f, the peak value of the input signal to the envelope detector 14 or its variation increases, and the peak value of the input signal to the envelope detector 13 increases. The value or the amount of change thereof will be reduced. As a result, the real component (0° or 18' component) of crosstalk is canceled by the circuit on the left half of the figure.
The angle-modulated wave signal at the point is output from the output terminal 16 after the imaginary component of crosstalk (90° right or 270° component) is canceled by the circuit on the right half of the figure.

一方、上記のように、本チヤンネル信号に混入している
隣接チヤンネル信号のクロストーク成分が、入力端子２
に入来する隣接チヤンネル信号ＳＢに対して００、１８
００又は９『、２７『の位相差を有しておらず、その他
の位相差を有している場合、例えば３０゜の位相差があ
る場合には、０場方向のＣＯｓ３Ｏ゜成分と９００方向
のＳｉｎ３『成分にクロストーク成分が分けられ、ＣＯ
ｓ３Ｏ゜成分は図中左半分の回路により、またＳｉｎ３
Ｏ゜成分は図中右半分の回路により夫々その成分に応じ
たクロストーク量の打消しが行なわれる。On the other hand, as mentioned above, the crosstalk component of the adjacent channel signal mixed into the main channel signal is
00, 18 for the adjacent channel signal SB coming into the
If the phase difference is not 00 or 9', 27', but has another phase difference, for example, 30°, the COs3O° component in the 0-field direction and the 900-field direction Sin3 of ``The crosstalk component is separated into the components, and the CO
The s3O゜ component is generated by the circuit on the left half of the figure, and the s3O゜ component is
For the O° component, the crosstalk amount corresponding to each component is canceled by the circuit on the right half of the figure.

従つて、このような場合でも出力端子１６より隣接チヤ
ンネル信号からのクロストーク成分が打消された本チヤ
ンネル信号が出力される。次に本チヤンネル信号と隣接
チヤンネル信号の角度偏移が共に等しい場合の実施例回
路の動作について説明する。同期検波器３はこのとき増
幅器４に対し、その利得を減少せしめ、電圧比較器９よ
り信号が出力されないようにする制御信号を出力する。
これにより、増幅器４、位相反転器５，１１及び９０゜
移相器１０の各出力は極めて小になるｇ従つて、ｃ点、
ｆ点にて混合されるこれらの隣接チヤンネル信号は極め
て小になる。従つて、クロストーク打消用回路は非動作
となるので、回路中の素子のバラツキによつて誤動作す
ることはなく、不必要な打消し動作を行なうことを防止
できる。Therefore, even in such a case, the output terminal 16 outputs the main channel signal in which the crosstalk components from the adjacent channel signals have been canceled. Next, an explanation will be given of the operation of the embodiment circuit when the angular deviations of the main channel signal and the adjacent channel signal are both equal. At this time, the synchronous detector 3 outputs a control signal to the amplifier 4 to reduce its gain and prevent the voltage comparator 9 from outputting a signal.
As a result, the outputs of the amplifier 4, phase inverters 5, 11, and 90° phase shifter 10 become extremely small. Therefore, at point c,
These adjacent channel signals mixed at point f become extremely small. Therefore, since the crosstalk canceling circuit is inactive, it will not malfunction due to variations in elements in the circuit, and unnecessary canceling operations can be prevented.

なお、この場合、本チヤンネル信号に混入しているクロ
ストーク成分は本チヤンネル信号の角度偏移と同一であ
るから歪特性を悪化することはないので、上記のように
クロストーク打消し回路を非動作としても何ら差し支え
ない。なお、上記実施例における各電圧比較器９，１５
は、ともに単に２入力の差の電圧を発生させる回路であ
るが、包絡線検出器７，８に供給される信号は、０゜方
向の信号と被角度変調波信号とが混合されたものであり
、包絡線検出器１３，１４に供給される信号は、９０゜
方向の信号と被角度変調波信号とが混合されたものであ
るので、被角度変調波信号の有するクロストーク分の０
゜方向の成分と９『方向の成分とに応じて、各電圧比較
器９，１５の出力レベルが異なることになり、これによ
り、０゜方向の成分と９０゜方向の成分とに応じてそれ
ぞれ可変減衰器６，１２を制御することができるのであ
る。なお、本発明回路は上記の実施例に限定されるもの
ではなく、同期性があると判定されたときの同期検波器
３の出力により、電圧比較器９，１５等の出力信号をオ
フとするよう構成してもよい。In this case, the crosstalk component mixed into the main channel signal is the same as the angular deviation of the main channel signal, so it will not deteriorate the distortion characteristics, so the crosstalk cancellation circuit is not used as described above. There is no problem with the operation. Note that each voltage comparator 9, 15 in the above embodiment
Both are circuits that simply generate a voltage difference between two inputs, but the signals supplied to the envelope detectors 7 and 8 are a mixture of a 0° direction signal and an angle modulated wave signal. Since the signal supplied to the envelope detectors 13 and 14 is a mixture of the 90° direction signal and the angle modulated wave signal, the crosstalk component of the angle modulated wave signal is
The output level of each voltage comparator 9, 15 will differ depending on the component in the 0° direction and the component in the 90° direction. This allows the variable attenuators 6 and 12 to be controlled. Note that the circuit of the present invention is not limited to the above-described embodiment, and the output signals of the voltage comparators 9, 15, etc. are turned off by the output of the synchronous detector 3 when it is determined that there is synchronization. It may be configured as follows.

上述の如く、本発明になる被角度変調波信号伝送路にお
けるクロストーク成分打消し回路は、希望チヤンネルと
隣接するとチンネルの第１の被角度変調波信号とこの第
１の被角度変調波信号と所定の位相差を有しかつ互いに
位相角が異なるように移相せしめられた１又は複数の第
２の被角度変調波信号とを、レベル可変手段を介して、
上記隣接チヤンネルの第１の被角度変調波信号の一部が
クロストーク成分として混入されている希望チヤンネル
の被角度変調波信号に夫々混合し、この混合信号を上記
第１及び第２の被角度変調波信号に夫々所定量ずつ混合
して第３及び第４の被角度変調波信号を得ると共に、上
記希望チヤンネル並びに隣接チヤンネルの両被角度変調
波信号からそれらの角度偏移の一致の有無を同期検波器
により検出し、上記角度偏移が一致していないときはク
ロストーク量検出回路により第３及び第４の被角度変調
波信号の包絡線を検出し、これらの検出した包絡線のピ
ーク値又は変化分が夫々等しくなるように上記第１及び
第２の被角度変調波信号のうち少なくともいずれか一方
の信号のレベルを、上記レベル可変手段を動作して可変
制御せしめ、上記角度偏移が一致しているときは上記同
期検波器の出力信号により上記クロストーク量検出回路
の動作又は上記第１の被角度変調波信号の伝送を停止す
るようにしたため、希望チヤンネル及び隣接チヤンネル
の両被角度変調波信号が同一の場合に、誤動作によりレ
ベル可変手段を制御してしまうことを防止でき、またこ
の場合に不必要なりロストーク打消し動作を行なつてク
ロストークを逆に付加してしまうという現象を防止でき
、また上記両被角度変調波信号が異なる場合は、上記ク
ロストーク成分を打消すことができ、従つて上記レベル
可変手段により信号が混合された希望チヤンネルの被角
度変調波信号を復調する構成とすることにより、各被角
度変調波信号間のクロストークにより発生される干渉歪
が有効に除去された復調信号が高忠実度に得られる等の
特長を有するものである。As described above, the crosstalk component cancellation circuit in the angle-modulated wave signal transmission line according to the present invention, when adjacent to the desired channel, cancels the first angle-modulated wave signal of the channel and this first angle-modulated wave signal. one or more second angle-modulated wave signals having a predetermined phase difference and phase-shifted so that the phase angles are different from each other, through a level variable means,
A part of the first angle modulated wave signal of the adjacent channel is mixed with the angle modulated wave signal of the desired channel mixed as a crosstalk component, and this mixed signal is mixed with the angle modulated wave signal of the first and second angle modulated wave signals. A predetermined amount of each of the modulated wave signals is mixed to obtain third and fourth angle modulated wave signals, and whether or not their angular deviations match is determined from both angle modulated wave signals of the desired channel and the adjacent channel. Detected by a synchronous detector, and when the angle deviations do not match, a crosstalk amount detection circuit detects the envelopes of the third and fourth angle-modulated wave signals, and the peaks of these detected envelopes are detected. The level varying means is operated to variably control the level of at least one of the first and second angle modulated wave signals so that the values or changes are equal, respectively, and the angular deviation is When they match, the output signal of the synchronous detector is used to stop the operation of the crosstalk amount detection circuit or the transmission of the first angle modulated wave signal. It is possible to prevent the level variable means from being controlled due to malfunction when the angle modulated wave signals are the same, and in this case, unnecessary losstalk canceling operation is performed and crosstalk is added instead. If the angle-modulated wave signals are different from each other, the crosstalk component can be canceled, and the angle-modulated wave signal of the desired channel in which the signals are mixed by the level variable means can be prevented. By employing a demodulating configuration, it is possible to obtain a demodulated signal with high fidelity in which interference distortion caused by crosstalk between angle-modulated wave signals is effectively removed.

【図面の簡単な説明】[Brief explanation of drawings]

図は本発明になる被角度変調波信号伝送路におけるクロ
ストーク成分打消し回路の一実施例の回路系統図である
。 １・・・・・・希望チヤンネルの被角度変調波信号入力
端子、２・・・・・・隣接チヤンネルの被角度変調波信
号入力端子、３・・・・・・同期検波器、５，１１・・
・・・・位相反転器、６，１２・・・・・・可変減衰器
、７，８，１３，１４・・・・・・包絡線検出器、９，
１５・・・・・・電圧比較器。The figure is a circuit system diagram of an embodiment of a crosstalk component canceling circuit in an angle-modulated wave signal transmission line according to the present invention. 1... Angle modulated wave signal input terminal of desired channel, 2... Angle modulated wave signal input terminal of adjacent channel, 3... Synchronous detector, 5, 11・・・
... Phase inverter, 6, 12 ... Variable attenuator, 7, 8, 13, 14 ... Envelope detector, 9,
15... Voltage comparator.

Claims (1)

【特許請求の範囲】[Claims] １ 複数の被角度変調波信号の伝送路において、希望チ
ャンネルと隣接するチャンネルの第１の被角度変調波信
号と該第１の被角度変調波信号と所定の位相差を有しか
つ互いに位相角が異なるように移相せしめられた１又は
複数の第２の被角度変調波信号とを、レベル可変手段を
介して、上記隣接チャンネルの第１の被角度変調波信号
の一部がクロストーク成分として混入されている希望チ
ャンネルの被角度変調波信号に夫々混合し、この混合信
号を該第１及び第２の被角度変調波信号に夫夫所定量ず
つ混合して第３及び第４の被角度変調波信号を得ると共
に、上記希望チャンネル並びに隣接チャンネルの両被角
度変調波信号からそれらの角度偏移の一致の有無を同期
検波器により検出し、該角度偏移が一致していないとき
はクロストーク量検出回路により第３及び第４の被角度
変調波信号の包絡線を検出し、該検出した包絡線のピー
ク値又は変化分が夫々等しくなるように該第１及び第２
の被角度変調波信号のうち少なくともいずれか一方の信
号のレベルを、該レベル可変手段を動作して可変制御せ
しめ、上記角度偏移が一致しているときは該同期検波器
の出力信号により該クロストーク量検出回路の動作又は
該第１の被角度変調波信号の伝送を停止するよう構成し
たことを特徴とする被角度変調波信号伝送路におけるク
ロストーク成分打消し回路。1. In a transmission path for a plurality of angle modulated wave signals, a desired channel and a first angle modulated wave signal of an adjacent channel have a predetermined phase difference and a phase angle with each other. A part of the first angle-modulated wave signal of the adjacent channel is a crosstalk component through a level variable means, and one or more second angle-modulated wave signals whose phases are shifted to be different from each other. A predetermined amount of each mixed signal is mixed with the first and second angle modulated wave signals of the desired channel to generate the third and fourth modulated wave signals. Obtain the angle modulated wave signal, and use a synchronous detector to detect whether or not the angular deviations of the desired channel and adjacent channel angularly modulated wave signals match, and if the angular deviations do not match, The crosstalk amount detection circuit detects the envelopes of the third and fourth angle-modulated wave signals, and the crosstalk amount detection circuit detects the envelopes of the third and fourth angle-modulated wave signals, and the crosstalk amount detection circuit detects the envelopes of the first and second angle-modulated wave signals so that the peak values or changes of the detected envelopes are equal, respectively.
The level of at least one of the angle-modulated wave signals is variably controlled by operating the level variable means, and when the angle deviations match, the output signal of the synchronous detector is used to control the level of at least one of the angle-modulated wave signals. 1. A crosstalk component cancellation circuit in an angle-modulated wave signal transmission line, characterized in that the circuit is configured to stop the operation of the crosstalk amount detection circuit or the transmission of the first angle-modulated wave signal.
JP4759477A 1977-04-25 1977-04-25 Crosstalk component cancellation circuit in angle modulated wave signal transmission line Expired JPS5944819B2 (en)

Priority Applications (2)

Application Number Priority Date Filing Date Title
JP4759477A JPS5944819B2 (en) 1977-04-25 1977-04-25 Crosstalk component cancellation circuit in angle modulated wave signal transmission line
US05/899,891 US4211978A (en) 1977-04-25 1978-04-25 Cross-talk component cancellation circuit in an angle-modulated wave signal transmission system

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
JP4759477A JPS5944819B2 (en) 1977-04-25 1977-04-25 Crosstalk component cancellation circuit in angle modulated wave signal transmission line

Publications (2)

Publication Number Publication Date
JPS53132907A JPS53132907A (en) 1978-11-20
JPS5944819B2 true JPS5944819B2 (en) 1984-11-01

Family

ID=12779565

Family Applications (1)

Application Number Title Priority Date Filing Date
JP4759477A Expired JPS5944819B2 (en) 1977-04-25 1977-04-25 Crosstalk component cancellation circuit in angle modulated wave signal transmission line

Country Status (1)

Country Link
JP (1) JPS5944819B2 (en)

Also Published As

Publication number Publication date
JPS53132907A (en) 1978-11-20

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