JPS592579A - Controller for inverter - Google Patents
Controller for inverterInfo
- Publication number
- JPS592579A JPS592579A JP57111178A JP11117882A JPS592579A JP S592579 A JPS592579 A JP S592579A JP 57111178 A JP57111178 A JP 57111178A JP 11117882 A JP11117882 A JP 11117882A JP S592579 A JPS592579 A JP S592579A
- Authority
- JP
- Japan
- Prior art keywords
- phase
- output
- current
- level
- electric valve
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
- H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
- H02M7/53873—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current with digital control
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Inverter Devices (AREA)
Abstract
Description
【発明の詳細な説明】
〔発明の技術分野〕
本発明はインバータ制御装置の改良に係り、特に中性点
端子のない交流電動機等の駆動制御に適するインバータ
制御装置に関する。DETAILED DESCRIPTION OF THE INVENTION [Technical Field of the Invention] The present invention relates to an improvement of an inverter control device, and particularly to an inverter control device suitable for drive control of an AC motor or the like without a neutral point terminal.
交流電動機の駆動制御にはインバータ制御装置が広く用
いられている。Inverter control devices are widely used for drive control of AC motors.
第１図は従来から、三相交流電動機の電流瞬時値制御に
用いられている三相インバータ制御装置の構成例を示ず
もので、正側電源ＩＰと負側電源ＩＮの直列回路に接続
された正、負母線２Ｐ 、 ２Ｎ間には、ゲートターン
オフサイリスタあるいはジャイアントトランジスタ等か
ら成る電気弁ＧＵ、 ＧＸ 、 ＧＶ。Figure 1 does not show a configuration example of a three-phase inverter control device conventionally used for instantaneous current value control of a three-phase AC motor. Between the positive and negative bus lines 2P and 2N, there are electric valves GU, GX, and GV consisting of gate turn-off thyristors or giant transistors.
ＧＹ、 ＧＷ 、 Ｇｚ が２個ずつ直列して接続され
ている。Two each of GY, GW, and Gz are connected in series.
これらの電気弁には夫々整流、素子りが逆並列に接続さ
れている。Each of these electric valves has a rectifier and an element connected in antiparallel.
各直列電気弁の中点と、負荷電動機３の各相巻線Ｕ 、
Ｖ 、Ｗの間は導線４Ｕ 、 ４ｖ 、 ４ｗ で接続
されており、また負荷電動機３の中性点Ｎと、直流電諒
１ｐ、ＩＮの中点の間は導線４Ｎで連結されている。The midpoint of each series electric valve and each phase winding U of the load motor 3,
Conductive wires 4U, 4v, and 4w connect V and W, and a conductive wire 4N connects the neutral point N of the load motor 3 and the midpoint of the DC currents 1p and IN.
導４ｊ１４ｔｒ、４ｖ、４ｗ には夫々、電流検出器５
Ｕ 、 ５ｖ 。A current detector 5 is installed for each of the conductors 4j14tr, 4v, and 4w.
U, 5v.
５ｗが結合されており、それらの出カニｕ、工ｖｔ：Ｉ
ｗは各相用の電流指令発生器６σ、 ６Ｖ 、 ６１ｙ
からの電流指令値工晶、工；、■番と共に比較器７υ、
７Ｖ 、 ７Ｗにインプットされて比較される。5w are combined, and their output u, engineering vt:I
w is the current command generator for each phase 6σ, 6V, 61y
The current command value from the comparator 7υ,
It is input to 7V and 7W and compared.
比較器７Ｕ、 ７Ｖ 、 ７Ｗは各相電流指令値１二、
ｌ：！工÷が各相゛屯流検出器出力ｌＵ、工Ｖ、工Ｗ
より大きい時にはレベル１１１を、そうでない時にはレ
ベルｌＯ″を出力する。これらの比較器の出カフυＯｖ
７Ｖｏｗ’７ｗｏは夫々、増巾器ｓＵ、 ８Ｖ 、
ｓｗにインプットされると共に、否定回路９Ｕ、 ９Ｖ
、 ９Ｗを経た後、増巾器８ｘ、８Ｙ、８ｚ にインプ
ットされる。Comparators 7U, 7V, 7W each phase current command value 12,
l:! Work ÷ is each phase's tonnage flow detector output lU, work V, work W
When it is greater than 111, it outputs level 111, and when it is not, it outputs level lO''.The output cuff of these comparators υOv
7Vow'7wo are amplifiers sU, 8V,
Input to sw and negative circuit 9U, 9V
, 9W, and then input to amplifiers 8x, 8Y, and 8z.
増巾器ｓＵ、 ｓｖ、 ｓｗ、 ８Ｘ、 ８Ｙ、 ｓｚ
の出力は夫々、電気弁ＧＵ 、 Ｇｙ 、 Ｇｗ 、
Ｇｘ 、 Ｇｙ 、 Ｇｚ の各ベース端子にインプ
ットされる。従って、比較器’ｙ、、 、 ７ｖ 、７
Ｗの出力がレベル“１１０時には正側電気弁ＧＵ、 Ｇ
ｖ。Amplifier sU, sv, sw, 8X, 8Y, sz
The outputs of electric valves GU, Gy, Gw,
It is input to each base terminal of Gx, Gy, and Gz. Therefore, the comparator 'y, , , 7v , 7
When the output of W is level “110”, the positive side electric valves GU, G
v.
Ｇｗカオンとなり、負側電気弁Ｇｘ、ＧＹ、Ｇ２はオフ
となる。反対に、比較器の出力レベルが自０１になると
、正側電気発がオフとなり、負側電気弁はオンとなる。Gw is turned on, and the negative side electric valves Gx, GY, and G2 are turned off. Conversely, when the output level of the comparator becomes 01, the positive side electric generator is turned off and the negative side electric valve is turned on.
なお、比較器？０ 、７ｖ 、 ７Ｗ にはヒステリシ
ス特性を持たせるため、出力端に接続した分圧抵抗１０
Ｕ 、 １０ｖ 、 ｉｏｗ 、 ＩＩＵ 、 ｌｌｖ
、 ｌｌｖ、の中点電圧が入力側にフィードバックさ
れるよう構成されている。Also, a comparator? In order to provide hysteresis characteristics to 0, 7V, and 7W, a voltage dividing resistor 10 connected to the output terminal is used.
U, 10v, iow, IIU, llv
, llv, is configured to be fed back to the input side.
第２図は上述のように構成したインバータ制御装置にお
ける０相の電流制御動作波形を示している。同図中、工
Ｐは比較器７Ｕのヒステリシス特性の上限値であり、よ
りはその下限値を示し、比較器７Ｕの出力は電流検出器
５Ｕの出力Ｉ、が工Ｐとよりの間にあるときは変化しな
い。FIG. 2 shows the zero-phase current control operation waveform in the inverter control device configured as described above. In the figure, P is the upper limit value of the hysteresis characteristic of the comparator 7U, and Yari indicates its lower limit, and the output of the comparator 7U is between the output I of the current detector 5U and P. Time does not change.
前述のように比較器７Ｕの出カフＵＱがレベル１１１の
ときには電気弁ＧＵけオン、ＧＸはオフとなり、出力？
ｔｒｏがレベルｗ０１のときには電気弁Ｇυはオフ、Ｇ
Ｘはオンとなる。As mentioned above, when the output cuff UQ of the comparator 7U is at level 111, the electric valve GU is turned on, GX is turned off, and the output?
When tro is at level w01, electric valve Gυ is off, G
X is turned on.
負荷電動機３に流れるＵ相狗Ｐ電流に比例する電流検出
器５Ｕの出力電流ＩＵが減少してきて、比較器７Ｕのヒ
ステリシス下限値ＩＢニ達した時点（ｔｏ）で、比較器
用カフＵＱはレベル１１１となり、電気弁ＧＵがオン、
ＧＸがオフとなる。従って、Ｕ相負荷電流は正側電源工
Ｐ−導線２Ｐ−電気弁Ｇυ−負荷電動機のＵ相巻線−中
性点Ｎ−導線４Ｎ−電源中点Ｏの経路で流れる。When the output current IU of the current detector 5U, which is proportional to the current flowing through the load motor 3, decreases and reaches the hysteresis lower limit value IB of the comparator 7U (to), the comparator cuff UQ reaches level 111. Then, electric valve GU turns on.
GX is turned off. Therefore, the U-phase load current flows through the path of the positive power source P, the conductor 2P, the electric valve Gυ, the U-phase winding of the load motor, the neutral point N, the conductor 4N, and the power supply midpoint O.
［Ｊａ亀電流増加して電流検出器５Ｕの出力電流工Ｕが
ヒステリシス上限値ＩＰに膿」達し、た時点ｔ１で比較
器用カフＵＯはレベル１０１となり、電気弁はＧ、がオ
フ、Ｇｘがオンとなる。従って、Ｕ相電流は負側電源ｉ
Ｎ−電源中点〇−導線４Ｎ−中性点Ｎ−負荷のＵ相巻線
−導線４Ｕ−電気弁Ｄｘ−Ｎ−２Ｎの経路で流れる。The current increases and the output current U of the current detector 5U reaches the hysteresis upper limit IP, and at time t1 the comparator cuff UO reaches level 101, the electric valve G is off and Gx is on. becomes. Therefore, the U-phase current is negative side power supply i
It flows through the path of N - power supply middle point - conductor 4N - neutral point N - load U phase winding - conductor 4U - electric valve Dx - N - 2N.
０相電流が減少し、検出器出力電流Ｉ、が再びヒステリ
シス下限値■Ｐに達した時点ｔ２以降においても、上記
と同様に電気弁ＧＵ、 ＧＸの切替えば行なわれ、負荷
電流は導線２Ｐまたは２Ｎと、導線４Ｎを流して流れる
。Even after time t2 when the 0-phase current decreases and the detector output current I reaches the hysteresis lower limit ■P again, switching of the electric valves GU and GX is performed in the same way as above, and the load current is changed to the conductor 2P or 2N and conductor wire 4N.
以上はＵ相負荷における動作波形であるが、■相および
Ｗ相負荷においても同様である。The above is the operating waveform for the U-phase load, but the same applies to the ■-phase and W-phase loads.
従って負荷電動機３の各相巻線には１２０°の相差角を
もって正弦波近似の負荷電流が流れるととＫなる。この
場合、中性点Ｈにおける負荷電流の基本波は互いに打消
し合うので導線４Ｎを流れることはないが、高調波成分
が残るため、電源中点０と負荷中性点Ｎの間を導線、４
Ｎで接続せずに各相の電流瞬時値を独立に制御しようと
すると、各相電流が干渉し合い、良好な制御を行なうこ
とができない。Therefore, if a load current approximately like a sine wave flows through each phase winding of the load motor 3 with a phase difference angle of 120°, then K is obtained. In this case, the fundamental wave of the load current at the neutral point H cancels each other, so it does not flow through the conductor 4N, but since harmonic components remain, the conductor between the power supply neutral point 0 and the load neutral point N, 4
If an attempt is made to control the instantaneous current values of each phase independently without connecting with N, the currents of each phase will interfere with each other, making it impossible to perform good control.
上述の如く、背景技術においては、負荷に流れる各相電
流を独立して瞬時値制御する場合には電源中点と負荷中
性点の間を短絡しておく必要があるため、中性点端子を
有する特殊仕様の電動機にしか適用できず、標準の電動
機を使用することができないという欠点があった。また
、電源も正側と負側の２個を必要とするため、回路格成
が複雑化し、コストアップを招来するという欠点があっ
た。As mentioned above, in the background technology, when controlling the instantaneous value of each phase current flowing through the load independently, it is necessary to short-circuit between the power supply neutral point and the load neutral point. It has the disadvantage that it can only be applied to a special specification electric motor with a standard electric motor. Furthermore, since two power supplies are required, one on the positive side and one on the negative side, there is a drawback that the circuit layout becomes complicated and the cost increases.
本発明は背景技術における上述の如き不都合を除去し、
中性点端子のない標準の交流電動機でも良好に電流制御
ができ、また、電源設備も１回路で済むインバータ制御
装置を提供１−ることを目的とするものである。The present invention eliminates the above-mentioned disadvantages in the background art,
It is an object of the present invention to provide an inverter control device that can perform good current control even with a standard AC motor without a neutral point terminal, and that requires only one power supply circuit.
本発明のインバータ制御装置は、直流電源にｍ組（ｍは
２以上の整数）の直列電気弁を接続し、これらの直列電
気弁の各中点なｍ摺電荷端子に接続したインバータ回路
において、各摺電荷電流に応じた電流検出器出力と各相
電源指令値とを入力して両者を比較し、レベル１１１ま
たはレベル１０１の論理出力を生ずる比較器と、これら
のｍ相の比較器とレベル検出器の出力を人力し、電流瞬
時値制御される（ｍ−’１）相の電気弁のオン・オフ状
態に応じて残りの１相の正側および負側の電気弁を前記
比較器の出力に無関係にオン・オフ制御し、出力電流位
相の所定位相毎に前記（ｍ−１３相の電気弁と残りの１
相の電気弁を順次切換える出力を生ずる論理ンーケンス
回路を備えたことを主たる特徴とするものである。The inverter control device of the present invention has an inverter circuit in which m sets (m is an integer of 2 or more) of series electric valves are connected to a DC power source, and connected to m sliding charge terminals at the midpoint of each of these series electric valves. A comparator that inputs the current detector output corresponding to each sliding charge current and each phase power supply command value and compares the two to generate a logic output of level 111 or level 101, and a comparator for these m phases and a level The output of the detector is manually input, and the positive side and negative side electric valves of the remaining one phase are controlled by the comparator according to the on/off state of the electric valve of the (m-'1) phase, which is controlled by the instantaneous current value. On/off control is performed regardless of the output, and the above (m-13 phase electric valve and the remaining 1
The main feature is that it is equipped with a logic sequence circuit that produces an output that sequentially switches the phase electric valves.
以下、第３図および第４図を参照して本発明装領の実施
例と作動を説明する。なお、これらの図では、第１図に
おけると同一の部品にはそれらと同じ符号を付しである
。Hereinafter, embodiments and operations of the device of the present invention will be described with reference to FIGS. 3 and 4. In these figures, the same parts as in FIG. 1 are given the same reference numerals.
直流′電源１には導線２Ｆ 、 ２Ｎを介して電気弁Ｇ
Ｕ。An electric valve G is connected to the DC' power source 1 via conductors 2F and 2N.
U.
ＧＸ、 Ｇｖ、 ＧＹ 、 ＧＷ、、 ＧＺ が２個ず
つ直列接続されており、また各電気弁にはダイオードＤ
が逆並列に接続されている。直列接続した各相電気弁の
中点と負荷電動機３の各相巻線の間を連結する導線４Ｕ
。Two GX, Gv, GY, GW, and GZ are connected in series, and each electric valve has a diode D.
are connected in antiparallel. Conductive wire 4U connecting between the midpoint of each phase electric valve connected in series and each phase winding of load motor 3
.
４ｖ 、 ４Ｗには夫々各相電流を検出する電流検出器
５Ｕ 、 ５Ｖ 、 ５Ｗが結合されており、それらの
出力ｌｕ。Current detectors 5U, 5V, and 5W are coupled to 4V and 4W to detect the current of each phase, respectively, and their outputs lu.
工ｖ、工ｗは各相用の電流指令発生器６Ｕ 、 ６Ｖ
、 ６Ｗからの電流指令値■δ、工６ 、１番と共に、
比較器７［。Engineering v and Engineering w are current command generators 6U and 6V for each phase.
, current command value ■δ from 6W, engineering 6, together with No. 1,
Comparator 7 [.
７ｖ 、 ７Ｗにインプットされ、電流指令値工品、■
受、工番が電流検出器出力ｌＵ、工Ｖ、工Ｗより大きい
時にはレベル１１”、そうでないときはレベル１０Ｉを
出力する。なお、各比較器の出力端には夫々に分圧抵抗
ｉｏＵ 、 １０ｙ 、 ＩＯＷとＩＩＵ 、 ＩＩＶ
、 ｌ１ｗが直列に接続されており、これらの直列抵
抗の中点電圧は比較器７Ｕ 、 ７ｖ 、 ７Ｗ の入
力側にフィードバックされ、各比較器に、第２図におけ
ると同様のヒステリシスｌｈ゛性を付与する。Input to 7V, 7W, current command value, ■
When the input and engineering numbers are larger than the current detector outputs lU, engineering V, and engineering W, level 11" is output; otherwise, level 10I is output. In addition, at the output terminal of each comparator, there is a voltage dividing resistor ioU, 10y, IOW and IIU, IIV
, l1w are connected in series, and the midpoint voltage of these series resistors is fed back to the input side of the comparators 7U, 7v, 7W, giving each comparator a hysteresis lh' property similar to that in FIG. Give.
電流指令発生器６Ｕ、６ｖ、６Ｗがらの市、流指令値工
も、６．Ｉ斉は、また、レベル検出器１２σ、１２ｖ。Current command generator 6U, 6V, 6W, current command value generator, 6. I also have a level detector 12σ, 12v.
１２Ｗに導かれる。これらのレベル検出器は電流指令値
工♂、工吊、工；が正の時にはレベル１１１を出力し、
負の時にはレベル１０１を出力する。Guided by 12W. These level detectors output level 111 when the current command values ♂, ♂, ♂ are positive,
When it is negative, level 101 is output.
比較器７Ｕ、７ｖ、 ７Ｗおよびレベル・検出器１２Ｕ
、１２ｖ。Comparator 7U, 7v, 7W and level detector 12U
, 12v.
１２ｗの出カフＵＯ＋ １２ＵＯｔ ７ｖｏ ｌ １２
ｖＱ ｔ ７ＷＯｙ １２ＷＯは夫々、論理シーケンス
回路１３のアドレス入力Ａｏ〜Ａ５にインプットされる
。この論理シーケンス回路は例えばリードオンリーメモ
リー（ＲＯＭ）で４１゛り成されており、その出力姑子
Ｄｏ、Ｄ２．Ｄ４ に生ずる制御信号は増巾＆Ｓυ、
８ｖ、８ｗで増巾された後、正側電気弁制御信号８ＵＯ
＋ ｓｖＱ ｔ ８１０として電気弁ＧＵ、Ｇｖ、ＧＷ
のベース端子に入力される。また、出力端子Ｄ１．Ｄ３
．Ｄ５に生ずる制御信号は増巾器ｓｘ 、 ｓｙ 、
ｓｚ で増巾された後、負側電気弁制御信号ｓｘｏ ｔ
８ＹＯｔ ８ｚＯとして電気弁Ｇｘ、ＧＹ、Ｃ２のペ
ース端子に入力され為。12w output cuff UO+ 12UOt 7vo l 12
vQ t 7WOy 12WO are input to address inputs Ao to A5 of the logic sequence circuit 13, respectively. This logic sequence circuit is made up of, for example, 41 read-only memories (ROM), and its outputs are Do, D2. The control signal generated at D4 is increased in width &Sυ,
After being amplified by 8V and 8W, the positive electric valve control signal 8UO
+ electric valve GU, Gv, GW as svQ t 810
is input to the base terminal of Moreover, the output terminal D1. D3
．． The control signals generated at D5 are transmitted through amplifiers sx, sy,
After being amplified by sz, the negative side electric valve control signal sxo t
8YOt 8zO is input to the pace terminals of electric valves Gx, GY, and C2.
次に、上述のように構成した本発明のインバータ制御装
置の作動を第４図を参照して説明する。Next, the operation of the inverter control device of the present invention configured as described above will be explained with reference to FIG.
本発明においては、電流指令値、例えばｌＧ の−周期
を第４図のモードＮｏに示すように■〜■のモードに分
解し、先ず、各モードで電流指令値工３＋１÷、工灸
の軌対値が最大となる相に対応する電気弁（第４図中の
ａＳに示す）を比較器７Ｕ、７Ｗ７ｗ の出力に無関係
に開弁させる。In the present invention, the -period of the current command value, for example lG, is decomposed into modes 1 to 2 as shown by mode numbers in Fig. 4, and first, in each mode, the current command value
The electric valve (indicated by aS in FIG. 4) corresponding to the phase in which the trajectory value of is the maximum is opened regardless of the outputs of the comparators 7U and 7W7w.
即ち、モード■では、電流指令値の絶対値は工※が最大
であり、その極性はマイナスであるので、論理シーケン
ス回路１３の出力端子Ｄ３には、比較器７■の出力に無
関係に開弁指令が出力され、電気弁制御信号８ＹＯによ
って電気弁ＧＹが開弁する。この場合、他のＵ相、Ｗ相
の電気弁は比較器７Ｕ、７ｗの出力に従って電流瞬時値
制御される。従って、Ｕ相、Ｗ相の電流の和がＶ相に泥
土することになる。In other words, in mode ■, the absolute value of the current command value is maximum *, and its polarity is negative, so the output terminal D3 of the logic sequence circuit 13 has an open valve regardless of the output of the comparator 7■. A command is output, and the electric valve GY is opened by the electric valve control signal 8YO. In this case, the other U-phase and W-phase electric valves are controlled by instantaneous current values according to the outputs of the comparators 7U and 7W. Therefore, the sum of the currents of the U-phase and W-phase flows into the V-phase.
次に、Ｕ相、Ｗ相の電流検出器用カニＵ、工Ｗが増加し
、比較器７Ｕ 、 ’ｙｗの出力が両者ともレベル１０
１となると、電気弁Ｇ［、ＧＷはオフ、Ｇｘ、Ｇｚはオ
ンとなる。このように負（ｉｌｌｌの電気弁Ｇｘ、 Ｇ
Ｙ。Next, the current detectors U and W for the U phase and W phase are increased, and the outputs of the comparators 7U and 'yw are both level 10.
When it becomes 1, the electric valves G[ and GW are turned off, and Gx and Gz are turned on. Thus negative (ill the electric valve Gx, G
Y.
Ｇｚのみがオンしている状憚では、負荷電流を制御でき
なくなるので、比較器７Ｕ 、 ７Ｗの出力がレベル１
０１となった時点で、それまでオンしていた電気弁ＧＹ
をオフにし、負側電気弁ＧｘＧｚはオンのまま、正側電
気弁Ｇｖをオンさせる。 これによって負荷のＵ相、Ｗ
相電流は減少する。When only Gz is on, the load current cannot be controlled, so the output of comparators 7U and 7W is level 1.
01, the electric valve GY that had been turned on until then
is turned off, and the positive side electric valve Gv is turned on while the negative side electric valve GxGz remains on. As a result, the load U phase, W phase
Phase current decreases.
このように、モード■の期間では、電気弁Ｇ、とＧＷが
同時にオフしている間はＧｖを連続的にオンとし、それ
以外ではＧＹを連続的にオンさせることにより、電流１
瞬時値制御が行なわれる。In this way, during the mode ■ period, Gv is turned on continuously while electric valves G and GW are turned off at the same time, and GY is turned on continuously at other times, so that the current 1
Instantaneous value control is performed.
モード■においては、第４図の制御信号ｃ８によって、
先ず電気弁ＧＵがオンとなり、■相とｗ相の負荷電流は
比較器７ｖ、 ７Ｗによって瞬時値制御される。この場
合も、比較ｂ ７ｙ 、 ７１ｙの出カフＶＱ。In mode ■, the control signal c8 in FIG.
First, the electric valve GU is turned on, and the load currents of the ■ phase and the W phase are instantaneously controlled by the comparators 7V and 7W. Also in this case, the output cuff VQ of comparison b 7y, 71y.
７ＷＯがともにレベル甲になると、電気弁Ｇｖ、Ｇ。When both 7WO reach level A, electric valves Gv and G.
がオンとなり、開弁しているのは正側電気弁ＧＵ。is turned on, and the valve that is open is the positive electric valve GU.
Ｇｙ 、 Ｇｗのみとなる。そこで、この時点では論理
シーケンス回路１３の出力によって電気弁Ｇυをオフ、
Ｇｘをオンとする。このようにすれば電気弁ＧＶ。Only Gy and Gw are available. Therefore, at this point, the output of the logic sequence circuit 13 turns off the electric valve Gυ.
Turn on Gx. In this way, the electric valve GV.
軸から負荷に流れ込む電流は負側電気弁ＧＸを通して電
源１に還流するので、負荷電流を増加させる制御が可能
である。Since the current flowing into the load from the shaft flows back to the power supply 1 through the negative electric valve GX, control to increase the load current is possible.
以上はモード■および■における作動であるが、モード
■〜■においても上記と同様にして各摺電荷電流を電流
指令値に従って瞬時値制御することができる。The above is the operation in modes (1) and (2), but in modes (2) to (2), each sliding charge current can be instantaneously controlled in accordance with the current command value in the same manner as described above.
上記各モードにおける動作シーケンスはレベル検出器１
２Ｕ 、 １２ｖ 、 １２Ｗと比較器７Ｕ、７ｙ、７
Ｈの出力によって一義的に決定されるので、それらのデ
ータをＲＯＭに書き込んでおくことにより、容易に実行
できる。The operation sequence in each mode above is for level detector 1.
2U, 12v, 12W and comparator 7U, 7y, 7
Since it is uniquely determined by the output of H, it can be easily executed by writing the data into ROM.
なお、以上の説明では３相交流電動機を負荷とする例に
つき述べたが、本発明はこれに限定されるものではなく
、介ンダクタンス負荷にも適用でき、また相数も３相に
限らず、ｍ相（ｍは２以上の整数）に広く適用すること
ができる。In addition, although the above explanation has been given with respect to an example in which a three-phase AC motor is used as the load, the present invention is not limited to this, and can also be applied to an intervening inductance load, and the number of phases is not limited to three phases. It can be widely applied to m-phase (m is an integer of 2 or more).
上述の如く、本発明においてはｍ相正弦波電流を瞬時値
制御するインバータ制御装置において、電流瞬時値制御
される（ｍ−１）相の′電気弁のオン・オフ制御状態に
応じて、残りの１相の電気弁を比較器の出力に無関係に
オン・オフ制御し、出力電流位相の所定角度毎に前記（
ｍ−１）相と残りの１相の電気弁を順次切換えて行（よ
うにしたものであるから、ｍ相全部を瞬時値制御する場
合に生ずる千渉は防止され、負荷中性点を的流眠源に接
続しなくとも良好な制御を行なうことができる。As described above, in the present invention, in an inverter control device that instantaneously controls the m-phase sine wave current, the remaining The one-phase electric valve of (
Since the electric valves of the m-1) phase and the remaining 1 phase are switched sequentially, it is possible to prevent the interference that occurs when instantaneous value control is applied to all m-phases, and to set the load neutral point to the target. Good control can be achieved without connection to a sleep source.
従って、中性点端子を有しない標準電動機を負荷とする
ことができ、また直流電源も１個でよく、回路を簡略化
することができる。Therefore, a standard electric motor without a neutral point terminal can be used as a load, and only one DC power supply is required, and the circuit can be simplified.
第１図は従来のインバータ制御装置を例示する回路図、
第２図はその動作波形図、第３図は本発明装備の実施例
を示す回路図、第４図はその動波説明図である。
１ ＋ Ｉｐ ＊ ＩＮ ・・・面派電源、３・・・負
荷、５Ｕ ｔ ５ｙｔ ５ｙ・・・電流検出器、ｃｔ、
、 、 ６Ｖ 、 ６Ｗ・・・電流指令発生器、７Ｕ
、 ７Ｖ 、 ７Ｗ ”’比較器、８Ｕ、８ｖ、８Ｗ、
８Ｘ、８Ｙ、８ｚ・・・増巾器、ＩＯＵ、 ＩＯＶ、
１０ｙ、 １１ｔ７． Ｉｌｙ、 ＩＩＷ・・・分圧抵
抗、１２Ｕ、 １２Ｖ、 １２Ｗ・・・レベル検出器、
１３・・・論理シーケンス回路。
出願人代理人 猪 股 清も １ 図
２ρ
鱈 ２ 図
も ４ 図FIG. 1 is a circuit diagram illustrating a conventional inverter control device,
FIG. 2 is an operating waveform diagram, FIG. 3 is a circuit diagram showing an embodiment of the equipment of the present invention, and FIG. 4 is an explanatory diagram of its dynamic waves. 1 + Ip * IN... Surface power supply, 3... Load, 5Ut 5yt 5y... Current detector, ct,
, , 6V, 6W...Current command generator, 7U
, 7V, 7W'' comparator, 8U, 8v, 8W,
8X, 8Y, 8z...amplifier, IOU, IOV,
10y, 11t7. Ily, IIW...Voltage dividing resistor, 12U, 12V, 12W...Level detector,
13...Logic sequence circuit. Applicant's agent Kiyoshi Inomata 1 Figure 2 Rho 2 Figure 4 Figure
Claims (1)
を接続し、これらの直列電気弁の各中点なｍ相負荷端子
に接続したインバータ回路において、各相に対応して設
けられ各相負荷電流に応じた電流検出器出力と各相電流
指令値とを入力して両者を比較し、レベル１１″または
レベルｌ ｇ ｍの論理出力を生ずる比較器と、各相に
対応して設けられ前記各相電流指令値の正、負に応じて
レベル１１″またはレベル“０“の論理出力を生ずるレ
ベル検出器と、これらのｍ組の比較器とレベル検出器の
出力を入力し、電流瞬時値制御される（ｍ−１）相の電
気弁のオン・オフ状態に応じて残りの１相の正側および
負側の電気弁を前記比較器の出力に無関係にオン・オフ
制御し、゛出力電流位相の所定位相毎に前記（ｍ−１）
相の電気弁と残りの１相の電気弁を順次切換える出力を
生ずる論理シーケンス回路とを備えたことを特徴とする
インバータ制御装置、。 ２、論理シーケンス回路がリードオンリーメモリーから
成ることを特徴とする特許請求の範囲第１項記載のイン
バータ制御装置。 ３、 ｍ相負荷が中性点端子を有しない３相交流電動機
であることを特徴とする特許請求の範囲第１項または第
２項に記載のインバータ制御装置。[Claims] 1. In an inverter circuit in which m sets (m is an integer of 2 or more) of series electric valves are connected to a DC power source and connected to an m-phase load terminal at the midpoint of each of these series electric valves, A comparator that is provided corresponding to each phase and inputs the current detector output corresponding to the load current of each phase and the current command value of each phase, compares the two, and generates a logic output of level 11'' or level l g m. , a level detector provided corresponding to each phase and generating a logical output of level 11'' or level ``0'' depending on whether the current command value of each phase is positive or negative, and m sets of comparators and level detectors. The output of the detector is input, and the positive side and negative side electric valves of the remaining one phase are controlled according to the on/off state of the electric valve of the (m-1) phase, which is controlled by the instantaneous current value, and the output of the comparator is The above (m-1) is controlled for each predetermined phase of the output current phase.
1. An inverter control device comprising: a logic sequence circuit that generates an output to sequentially switch one phase electric valve and the remaining one phase electric valve. 2. The inverter control device according to claim 1, wherein the logic sequence circuit comprises a read-only memory. 3. The inverter control device according to claim 1 or 2, wherein the m-phase load is a three-phase AC motor without a neutral point terminal.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP57111178A JPS592579A (en) | 1982-06-28 | 1982-06-28 | Controller for inverter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP57111178A JPS592579A (en) | 1982-06-28 | 1982-06-28 | Controller for inverter |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| JPS592579A true JPS592579A (en) | 1984-01-09 |
Family
ID=14554463
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP57111178A Pending JPS592579A (en) | 1982-06-28 | 1982-06-28 | Controller for inverter |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS592579A (en) |
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS60204270A (en) * | 1984-03-28 | 1985-10-15 | Origin Electric Co Ltd | Inverter device |
| EP0268046A2 (en) * | 1986-11-20 | 1988-05-25 | Villamosipari Kutato Intézet | Method and circuit arrangement for the control and regulation of three-phase inverters with sequence regulation |
| WO2019012915A1 (en) * | 2017-07-14 | 2019-01-17 | 株式会社デンソー | Rotating electric machine drive system |
-
1982
- 1982-06-28 JP JP57111178A patent/JPS592579A/en active Pending
Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS60204270A (en) * | 1984-03-28 | 1985-10-15 | Origin Electric Co Ltd | Inverter device |
| EP0268046A2 (en) * | 1986-11-20 | 1988-05-25 | Villamosipari Kutato Intézet | Method and circuit arrangement for the control and regulation of three-phase inverters with sequence regulation |
| WO2019012915A1 (en) * | 2017-07-14 | 2019-01-17 | 株式会社デンソー | Rotating electric machine drive system |
| JP2019022299A (en) * | 2017-07-14 | 2019-02-07 | 株式会社デンソー | Drive system of rotary electric machine |
| US11038453B2 (en) | 2017-07-14 | 2021-06-15 | Denso Corporation | Rotating electric machine drive system |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| US4777579A (en) | Integrated current sensor configurations for AC motor drives | |
| US4507724A (en) | Pulse width modulated inverter for unbalanced and variable power factor loads | |
| JPH01214267A (en) | Apparatus and method for feedback current control of multphase load | |
| JPH0799959B2 (en) | Inverter with winding switching function | |
| JP3716152B2 (en) | Power converter | |
| JPS592579A (en) | Controller for inverter | |
| JPH10271823A (en) | Power factor improved three-phase converter | |
| JPS61196788A (en) | Speed controller of motor | |
| US4961129A (en) | Current controlled active flywheel type neutral point clamped inverter | |
| JP3249349B2 (en) | Transformer | |
| JP3070314B2 (en) | Inverter output voltage compensation circuit | |
| JPS6016179A (en) | Current controller of pulse width modulation inverter | |
| JPS61231889A (en) | Controlling method for voltage type inverter | |
| JPH06245588A (en) | Pwm inverter control method | |
| JPS59127575A (en) | Single-phase/3-phase converter circuit | |
| JPS58151879A (en) | Control circuit for alternating current/direct current converting circuit | |
| JPH0433574A (en) | Inverter | |
| JPH0937552A (en) | Pwm converter | |
| JPS6173584A (en) | Controlling method of power regenerative circuit | |
| JPH03265486A (en) | Inverter control system | |
| SU1575265A1 (en) | Filter-symmetring device for three-phase four-wire networks with non-linear unsteady loads | |
| JPH01218302A (en) | Controller for electric rolling stock | |
| JPS59149776A (en) | Ground protecting device for power converter | |
| JP2019004657A (en) | Single-phase three-wire inverter and voltage compensation device | |
| JPH0331778A (en) | Semiconductor aging device |