JPS587832Y2 - phase control circuit - Google Patents
phase control circuitInfo
- Publication number
- JPS587832Y2 JPS587832Y2 JP1976094667U JP9466776U JPS587832Y2 JP S587832 Y2 JPS587832 Y2 JP S587832Y2 JP 1976094667 U JP1976094667 U JP 1976094667U JP 9466776 U JP9466776 U JP 9466776U JP S587832 Y2 JPS587832 Y2 JP S587832Y2
- Authority
- JP
- Japan
- Prior art keywords
- voltage
- capacitor
- power supply
- bridge circuit
- transformer
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
Links
Landscapes
- Control Of Electrical Variables (AREA)
- Power Conversion In General (AREA)
Description
【考案の詳細な説明】
本考案に′！、位相制御回路に関し、電源電圧が変動し
た時に、双方向性制御素子のゲート端子をトリガするト
リガ素子の点弧時期を変化させて、負荷電力な略一定に
制御するに当り、電源電圧の変動に対しトリガ素子の点
弧時期を常に一定の関係で滑らかに変化させ得るように
したものである。[Detailed explanation of the invention] This invention! Regarding the phase control circuit, when the power supply voltage fluctuates, the firing timing of the trigger element that triggers the gate terminal of the bidirectional control element is changed to control the load power to be approximately constant. On the other hand, the firing timing of the trigger element can always be changed smoothly in a constant relationship.
第１園は従来例を示し、１は負荷、２はこれを位相制御
するトライアックで、そのゲート端子をトリガする弛張
発振回路３は、抵抗４とコンデンサ５とトリガ素子６と
により構成される。The first diagram shows a conventional example, in which 1 is a load, 2 is a triac for controlling the phase of the load, and a relaxation oscillation circuit 3 for triggering the gate terminal is composed of a resistor 4, a capacitor 5, and a trigger element 6.
７はトランス、８及び９は定電圧ダイオード、１０は抵
抗である。7 is a transformer, 8 and 9 are constant voltage diodes, and 10 is a resistor.
なお定電圧ダイオード８，９に代えて、第２図に示す如
く単相ブリッジ回路１１と定電圧ダイオード１２とを用
いたものもある。Note that instead of the constant voltage diodes 8 and 9, there is also a device using a single-phase bridge circuit 11 and a constant voltage diode 12 as shown in FIG.
この構成によれ＆東トランス７の出力電圧が電源電圧に
対して逆極性であるため、ａ−ａ’間の電圧は、第３図
に示すように定電圧ダイオード８゜９のツェナー電圧Ａ
とトランス７の出力電圧Ｂとを重畳した波形Ｃとなる。According to this configuration, the output voltage of the east transformer 7 has the opposite polarity to the power supply voltage, so the voltage between a and a' is equal to the Zener voltage A of the constant voltage diode 8°9, as shown in FIG.
A waveform C is obtained by superimposing the output voltage B of the transformer 7 and the output voltage B of the transformer 7.
そして、この電圧は、電源電圧が上昇すると低下し、低
下すると上昇すると云う関係にあり、この電圧によって
コンデンサ５を充電し、電源電圧の上昇時には遅くなり
低下時には早くなるように、電源電圧の変動に応じてト
リガ素子６の点弧時期を変化させて負荷電力な略一定に
制御している。This voltage is in a relationship such that it decreases when the power supply voltage rises, and rises when it decreases, and this voltage charges the capacitor 5, and when the power supply voltage increases, it becomes slower and when it decreases, it becomes faster. The firing timing of the trigger element 6 is changed according to the load power, thereby controlling the load power to be substantially constant.
しかし、これは、単にトランス７の出力電圧Ｂを定電圧
ダイオード８゜９のツェナー電圧に重畳しているだけで
あるため、ａ−ａ’間の電圧には第３図に示す如く頂部
に谷ができた形となり、コンデンサ５を充電する電圧が
一定せず、コンデンサ５の充電電圧Ｖｃがトリガ素子６
の点弧型ＥＦ、ｖ１に達するまでに山と谷ができる。However, since this simply superimposes the output voltage B of the transformer 7 on the Zener voltage of the constant voltage diode 8.9, the voltage between a and a' has a valley at the top as shown in Figure 3. The voltage that charges the capacitor 5 is not constant, and the charging voltage Vc of the capacitor 5 is
The ignition type EF has peaks and valleys before reaching v1.
従って電源電圧の変動に対するトリガ素子６の点弧時期
Ｃが常に一定の関係で滑らかに変化しないと云う欠点が
あった。Therefore, there is a drawback that the firing timing C of the trigger element 6 with respect to fluctuations in the power supply voltage does not always change smoothly in a constant relationship.
即ち、電源電圧を変化させた時、第４図りに示す如（ａ
−ａ’間の電圧波形の頂部に山谷ができるため、トリガ
素子６の点弧時期がＥ〜Ｇのように電源電圧の変動した
割合をこえて大きく変化し、成る電圧で急に点弧時期が
早くなったりすることがあり、定電化を図る上で安定性
に欠ける問題があった。That is, when the power supply voltage is changed, as shown in the fourth diagram (a
Since peaks and troughs are formed at the top of the voltage waveform between -a', the ignition timing of the trigger element 6 changes greatly, exceeding the rate at which the power supply voltage fluctuates, as shown in E to G, and the ignition timing suddenly changes at the voltage where However, there was a problem of lack of stability when trying to maintain constant electricity.
本考案は、このような従来の問題点を解消することを目
的として提供されたものであって、その特徴とする処＆
人電源電圧を入力とするトランスを有し、このトランス
の出力電圧を定電圧ダイオードのツェナー電圧に逆方向
に重畳し、その重畳電圧によりコンデンサの印加電圧を
制御し、このコンデンサの充電電圧によりトリガ素子を
介して双方向性制御素子をトリガして負荷電力を略一定
に制御するようにした位相制御回路において、前記トラ
ンスの出力電圧を整流する第１整流ブリッジ回路と、そ
の整流電圧を平滑する平滑コンデンサとを設け、第２整
流ブリッジ回路の直流側に、前記平滑コンデンサの平滑
電圧が逆方向に印加しかつ前記定電圧ダイオードが順方
向となるように該平滑コンデンサと定電圧ダイオードと
の直列回路を接続し、この第２整流ブリッジ回路の交流
側を前記コンデンサに、該コンデンサの印加電圧が電源
電圧の上昇時に小に低下時に大となるように接続した点
にある。The present invention was provided with the aim of solving these conventional problems, and its features include:
It has a transformer that takes the human power supply voltage as input, and the output voltage of this transformer is superimposed in the opposite direction on the Zener voltage of the voltage regulator diode, and the voltage applied to the capacitor is controlled by the superimposed voltage, and the trigger is triggered by the charging voltage of this capacitor. In the phase control circuit that controls the load power to be substantially constant by triggering the bidirectional control element via the element, the phase control circuit includes a first rectifier bridge circuit that rectifies the output voltage of the transformer, and a first rectifier bridge circuit that smooths the rectified voltage. A smoothing capacitor is provided on the DC side of the second rectifying bridge circuit, and the smoothing capacitor and the voltage regulator diode are connected in series so that the smoothed voltage of the smoothing capacitor is applied in the reverse direction and the voltage regulator diode is applied in the forward direction. The AC side of the second rectifying bridge circuit is connected to the capacitor in such a way that the voltage applied to the capacitor becomes small when the power supply voltage rises and becomes large when it falls.
以下、図示の実施例について本考案を詳述すると、第５
図にｋいて、１３は負荷、１４は双方向性制御素子とし
てのトライアック、１５はそのゲート端子をトリガする
弛張発振回路で、抵抗１６とコンデンサ１１とトリガ素
子１８とから成る。Hereinafter, the present invention will be described in detail with reference to the illustrated embodiment.
In the figure, 13 is a load, 14 is a triac as a bidirectional control element, and 15 is a relaxation oscillation circuit for triggering its gate terminal, which is composed of a resistor 16, a capacitor 11, and a trigger element 18.
１９は第２整流ブリッジ回路で、交流側は抵抗１６とコ
ンデンサ１１との直列回路に並列接続されている。Reference numeral 19 denotes a second rectifying bridge circuit, and the AC side thereof is connected in parallel to the series circuit of the resistor 16 and the capacitor 11.
２０は電源電圧を入力とするトランス、２１はこのトラ
ンス２０の出力電圧を整流する第１整流ブリッジ回路、
２２は整流電圧を平滑する平滑コンデンサである。20 is a transformer that inputs the power supply voltage; 21 is a first rectifier bridge circuit that rectifies the output voltage of this transformer 20;
22 is a smoothing capacitor for smoothing the rectified voltage.
２３は定電圧ダイオードで、平滑コンデンサ２２と共に
第２整流ブリッジ回路１９の直流側に直列接続されてい
る。23 is a constant voltage diode, which is connected in series with the smoothing capacitor 22 to the DC side of the second rectifying bridge circuit 19.
平滑コンデンサ２２は平滑電圧が第２整流ブリッジ回路
１９の直流側に逆方向に印加するように接続されている
。The smoothing capacitor 22 is connected so that a smoothing voltage is applied to the DC side of the second rectifying bridge circuit 19 in the opposite direction.
２４は抵抗である。上記構成によれば、トランス２０の
出力電圧を第１整流ブリッジ回路２１で整流し、平滑コ
ンデンサ２２により平滑した後、この平滑電圧を第２整
流ブリッジ回路１９の直流側にある定電圧ダイオード２
３のツェナー電圧に逆方向に印加するのである。24 is a resistance. According to the above configuration, the output voltage of the transformer 20 is rectified by the first rectifier bridge circuit 21 and smoothed by the smoothing capacitor 22, and then this smoothed voltage is transferred to the constant voltage diode 2 on the DC side of the second rectifier bridge circuit 19.
The Zener voltage of No. 3 is applied in the opposite direction.
この場合、ツェナー電圧が箒６図Ｈに示す通りであるの
に対し、電源電圧の変動に比例した電圧が同Ｉに示すよ
うに整流し平滑されて、この平滑電圧がツェナー電圧に
重畳するので、第２整流ブリッジ回路１９の交流側であ
るｂ−ｂ’間の電圧波形は同Ｊに示すように頂部が平坦
な台形交流波形となり、このｂ−ｂ’間雷電圧頂部の山
谷をなくし直線的にすることができる。In this case, while the Zener voltage is as shown in Figure 6H, the voltage proportional to the fluctuation of the power supply voltage is rectified and smoothed as shown in Figure I, and this smoothed voltage is superimposed on the Zener voltage. , the voltage waveform between b and b' on the AC side of the second rectifying bridge circuit 19 becomes a trapezoidal AC waveform with a flat top as shown in J. can be made into a target.
このｂ−ｂ’間の電圧は抵抗１６を介してダイオード１
１に印加し、そのダイオード１１の印加電圧でトリガ素
子１８を点弧されてトライアック１４をトリガするので
あるが、ツェナー電圧が一定であるのに対し、平滑電圧
は電源電圧の変動に比例した直流電圧であって、これが
ツェナー電圧に逆方向に印加するため、ｂ−ｂ’間の電
圧、即ちコンデンサ１７の印加電圧は電源電圧の上昇時
に小に低下時に大となり、しかもその電圧波形は頂部が
平坦であるから、電源電圧の変動に対してトリガ素子１
８の点弧時期が常に一定の関係で滑かに変化するように
なり、負荷電力の安定性が良好になる。The voltage between b and b' is applied to the diode 1 through the resistor 16.
1, and the voltage applied to the diode 11 ignites the trigger element 18 and triggers the triac 14. Whereas the Zener voltage is constant, the smoothed voltage is a direct current proportional to fluctuations in the power supply voltage. Since this voltage is applied in the opposite direction to the Zener voltage, the voltage between b and b', that is, the voltage applied to the capacitor 17, becomes small when the power supply voltage rises and becomes large when it falls, and the top of the voltage waveform is Since it is flat, the trigger element 1 is
The ignition timing of No. 8 will always change smoothly in a constant relationship, and the stability of the load power will be improved.
なお、第６図Ｈ２■の電圧波形を気筒５図のＣ点をＯレ
ベルとして示したものである。In addition, the voltage waveform of FIG. 6 H2■ is shown with point C in the cylinder diagram 5 set at O level.
第７図は抵抗２４をトライアック１４のアノード側に接
続したものであり、この場合、トライアック１４がオン
した後、抵抗２４に電流が流れなくなるため、この抵抗
２４での電力損がなくなる利点がある。In FIG. 7, a resistor 24 is connected to the anode side of the triac 14. In this case, after the triac 14 is turned on, no current flows through the resistor 24, which has the advantage of eliminating power loss in the resistor 24. .
他の動作は第５図と同様である。第８図は第２整流ブリ
ッジ回路１９の交流側をコンデンサ２４と直列に接続し
、このＭ２整流７”リッジ回路１９の直流側に平滑コン
デンサ２２゜定電圧ダイオード２３の他にトランジスタ
２５、抵抗２６，２７を接続したものである。Other operations are the same as in FIG. 5. In FIG. 8, the AC side of the second rectifier bridge circuit 19 is connected in series with a capacitor 24, and the DC side of this M2 rectifier 7" ridge circuit 19 includes a smoothing capacitor 22, a voltage regulator diode 23, a transistor 25, and a resistor 26. , 27 are connected.
この場合は、定電圧ダイオード２３のツェナー電圧と平
滑コンデンサ２２の平滑電圧との重畳電圧によりトラン
ジスタ２５０ベース電流を流しており、電源電圧が高く
なると、平滑コンデンサ２２の平滑電圧が犬になるため
、トランジスタ２５０ペース電流が低下し、トランジス
タ２５のコレクタ・エミッタ電流が低下する。In this case, the base current of the transistor 250 is caused to flow due to the superimposed voltage of the Zener voltage of the constant voltage diode 23 and the smoothed voltage of the smoothing capacitor 22, and as the power supply voltage increases, the smoothed voltage of the smoothing capacitor 22 becomes negative. The transistor 250 pace current decreases and the collector-emitter current of transistor 25 decreases.
従って、コンデンサ１７の充電時間が犬となり、トリガ
素子１Ｂの点弧時期が遅れることになる。Therefore, the charging time of the capacitor 17 is shortened, and the ignition timing of the trigger element 1B is delayed.
この場合にも、第２整流ブリッジ回路１９の交流側の電
圧は第６図Ｊに示すようになり、同様の作用効果を奏す
る。In this case as well, the voltage on the AC side of the second rectifying bridge circuit 19 becomes as shown in FIG. 6J, and the same effect is achieved.
以上実施例に詳述したように本考案によれば、トランス
の出力電圧を第１整流ブリッジ回路で整流し平滑コンデ
ンサで平滑した後、第２整流ブリッジ回路の直流側に順
方向に接続された定電圧ダイオードのツェナー電圧に対
して平滑コンデンサの平滑電圧を逆方向に印加し、この
第２整流ブリッジ回路の交流側で、コンデンサの印加電
圧が電源電圧の上昇時に小に低下時に犬となるように制
御しているので、コンデンサの印加電圧は頂部が直線的
で平坦な台形波状となり、従来の頂部の山谷がなくなる
ため、電源電圧の変動に対して常に一定の関係でトリガ
素子の点弧時期を滑らかに変化させることができ、負荷
電力の定電力化を図る上で安定性が良好である。As detailed in the embodiments above, according to the present invention, the output voltage of the transformer is rectified by the first rectifier bridge circuit and smoothed by the smoothing capacitor, and then connected in the forward direction to the DC side of the second rectifier bridge circuit. The smoothing voltage of the smoothing capacitor is applied in the opposite direction to the Zener voltage of the constant voltage diode, and on the AC side of this second rectifier bridge circuit, the voltage applied to the capacitor becomes a dog when the power supply voltage increases and decreases slightly. As a result, the voltage applied to the capacitor becomes a trapezoidal waveform with a straight and flat top, eliminating the conventional peaks and valleys at the top, so that the firing timing of the trigger element is always maintained in a constant relationship with fluctuations in the power supply voltage. can be changed smoothly, and stability is good for making the load power constant.
第１図及び第２図は従来例を示す回路図、第３図及び第
４図はその動作説明用の波形図、第５図は本考案の一実
施例を示す回路図、第６図はその波形図、第７図及び第
８図は他の実施例を示す回路図である。
１３・・・・・・負荷、１４・・・・・・トライアック
、１５・・・・・・弛張発振回路、１７・・・・・・コ
ンデンサ、１８・・・・・・トリガ素子、１９・・・・
・・第２整流ブリッジ回路、２０・・・・・・トランス
、２１・・・・・・第１整流ブリッジ回路、２２・・・
・・・平滑コンデンサ、２３・・・・・・定電圧ダイオ
ード。1 and 2 are circuit diagrams showing a conventional example, FIGS. 3 and 4 are waveform diagrams for explaining its operation, FIG. 5 is a circuit diagram showing an embodiment of the present invention, and FIG. 6 is a circuit diagram showing a conventional example. The waveform diagram, FIGS. 7 and 8 are circuit diagrams showing other embodiments. 13... Load, 14... Triac, 15... Relaxation oscillation circuit, 17... Capacitor, 18... Trigger element, 19. ...
...Second rectifier bridge circuit, 20...Transformer, 21...First rectifier bridge circuit, 22...
... Smoothing capacitor, 23 ... Constant voltage diode.
Claims (1)
出力電圧を定電圧ダイオードのツェナー電圧に逆方向に
重畳し、その重畳電圧によりコンデンサの印加電圧を制
御し、このコンデンサの充電電圧によりトリガ素子を介
して双方向性制御素子をトリガして負荷電力な略一定に
制御するようにした位相制御回路において、前記トラン
スの出力電圧を整流する第１整流ブリッジ回路と、その
整流電圧を平滑する平滑コンデンサとを設け、第２整流
ブリッジ回路の直流側に、前記平滑コンデンサの平滑電
圧が逆方向に印加しかつ前記定電圧ダイオードが順方向
となるように該平滑コンデンサと定電圧ダイオードとの
直列回路を接続し、この第２整流ブリッジ回路の交流側
を前記コンデンサに、該コンデンサの印加電圧が電源電
圧の上昇時に小い低下時に大となるように接続したこと
を特徴とする位相制御回路。It has a transformer that receives the power supply voltage as input, and the output voltage of this transformer is superimposed on the Zener voltage of the voltage regulator diode in the opposite direction.The superimposed voltage controls the voltage applied to the capacitor, and the charging voltage of this capacitor controls the trigger element. In the phase control circuit which controls the load power to be substantially constant by triggering the bidirectional control element through and a series circuit of the smoothing capacitor and the voltage regulator diode so that the smoothed voltage of the smoothing capacitor is applied in the reverse direction and the voltage regulator diode is applied in the forward direction on the DC side of the second rectifying bridge circuit. and the AC side of the second rectifying bridge circuit is connected to the capacitor in such a way that the voltage applied to the capacitor becomes small when the power supply voltage increases and becomes large when the power supply voltage decreases.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP1976094667U JPS587832Y2 (en) | 1976-07-14 | 1976-07-14 | phase control circuit |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP1976094667U JPS587832Y2 (en) | 1976-07-14 | 1976-07-14 | phase control circuit |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS5313066U JPS5313066U (en) | 1978-02-03 |
| JPS587832Y2 true JPS587832Y2 (en) | 1983-02-10 |
Family
ID=28705185
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP1976094667U Expired JPS587832Y2 (en) | 1976-07-14 | 1976-07-14 | phase control circuit |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS587832Y2 (en) |
Families Citing this family (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS5812022A (en) * | 1981-06-15 | 1983-01-24 | Matsushita Electric Works Ltd | Phase controlling circuit |
Citations (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS5012904A (en) * | 1973-06-05 | 1975-02-10 |
Family Cites Families (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS5331150Y2 (en) * | 1973-08-22 | 1978-08-03 |
-
1976
- 1976-07-14 JP JP1976094667U patent/JPS587832Y2/en not_active Expired
Patent Citations (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS5012904A (en) * | 1973-06-05 | 1975-02-10 |
Also Published As
| Publication number | Publication date |
|---|---|
| JPS5313066U (en) | 1978-02-03 |
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