JPH10126138A - Adaptive array receiver - Google Patents
Adaptive array receiverInfo
- Publication number
- JPH10126138A JPH10126138A JP8273355A JP27335596A JPH10126138A JP H10126138 A JPH10126138 A JP H10126138A JP 8273355 A JP8273355 A JP 8273355A JP 27335596 A JP27335596 A JP 27335596A JP H10126138 A JPH10126138 A JP H10126138A
- Authority
- JP
- Japan
- Prior art keywords
- signal
- antenna
- received
- sector
- signals
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
- 230000003044 adaptive effect Effects 0.000 title claims abstract description 7
- 239000002131 composite material Substances 0.000 claims description 3
- 230000000694 effects Effects 0.000 abstract description 2
- 238000001514 detection method Methods 0.000 description 8
- 230000005540 biological transmission Effects 0.000 description 6
- 238000010586 diagram Methods 0.000 description 6
- 238000004891 communication Methods 0.000 description 3
- 238000010295 mobile communication Methods 0.000 description 3
- 238000005070 sampling Methods 0.000 description 3
- 230000006866 deterioration Effects 0.000 description 2
- 238000005562 fading Methods 0.000 description 2
- 238000005516 engineering process Methods 0.000 description 1
- 238000000034 method Methods 0.000 description 1
- 230000001360 synchronised effect Effects 0.000 description 1
Classifications
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02D—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN INFORMATION AND COMMUNICATION TECHNOLOGIES [ICT], I.E. INFORMATION AND COMMUNICATION TECHNOLOGIES AIMING AT THE REDUCTION OF THEIR OWN ENERGY USE
- Y02D30/00—Reducing energy consumption in communication networks
- Y02D30/70—Reducing energy consumption in communication networks in wireless communication networks
Landscapes
- Variable-Direction Aerials And Aerial Arrays (AREA)
- Noise Elimination (AREA)
- Mobile Radio Communication Systems (AREA)
- Radio Transmission System (AREA)
Abstract
Description
【0001】[0001]
【発明の属する技術分野】この発明は、ディジタル無線
通信において干渉波による劣化を抑圧するアダプティブ
・アレー受信機に関するものである。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to an adaptive array receiver for suppressing deterioration due to an interference wave in digital radio communication.
【0002】[0002]
【従来の技術】ディジタル移動通信においては、周波数
の有効利用を図るため同一周波数を用いるゾーン(セ
ル)を干渉が生じない程度に離して繰り返し配置してい
る。さらに周波数利用効率を上げるため、セルのセクタ
化を行っている。その一例を図2Aに示す。同図の六角
形の領域11は1基地局12がカバーする、つまり移動
機との通信が可能なエリア(領域)、即ちセルを表す。
セクタ化はこのセル11を基地局12を中心に角度的に
等分割し、各セクタでの使用周波数チャネルを互いに異
なるものを割当てる。ここではセル11を3分割し、A
セクタ、Bセクタ、Cセクタに分け、それぞれ異なる周
波数チャネルを割当てている。従って、Aセクタに居る
移動機と、Bセクタに居る移動機とでは、相異なる周波
数チャネルを使用する。このセクタ化を行う為には、ア
ンテナゲインに指向性があるセクタアンテナを基地局1
2に用いる必要がある。現行ディジタル移動通信方式に
おける基地局セクタアンテナの配置を図2Bに示す。3
組のセクタアンテナ群、13aと14a,13bと14
b,13cと14cがあり、各セクタアンテナ群はアン
テナ指向性が同じ2本のアンテナ素子で構成されてい
る。Aセクタをカバーするのはアンテナ素子13a,1
4aであり、これらのアンテナゲインはAセクタのみを
カバーするため角度θ=120度の範囲にのみ指向性が
ある。このようにすると、Aセクタ以外の方向に電波を
送信せず、また、Aセクタ以外のセクタに居る移動機か
らの電波を受信しないようにすることが出来る。同様
に、Bセクタをカバーするのはアンテナ素子13b,1
4b、Cセクタをカバーするのはアンテナ素子13c,
14cであり、その指向性はそれぞれBセクタ、Cセク
タのみをカバーするよう設定されている。2. Description of the Related Art In digital mobile communication, zones (cells) using the same frequency are repeatedly arranged so as not to cause interference in order to use frequencies effectively. In order to further increase the frequency use efficiency, cells are sectorized. One example is shown in FIG. 2A. The hexagonal area 11 in FIG. 2 represents an area (area) covered by one base station 12, that is, a cell in which communication with a mobile device is possible, that is, a cell.
In the sectorization, the cell 11 is equally divided angularly around the base station 12, and different frequency channels are used in each sector. Here, the cell 11 is divided into three parts,
It is divided into a sector, a B sector, and a C sector, and different frequency channels are assigned to them. Therefore, different frequency channels are used for the mobile station in the sector A and the mobile station in the sector B. In order to perform this sectoring, a sector antenna having a directivity in the antenna gain is set to the base station 1.
2 must be used. FIG. 2B shows an arrangement of base station sector antennas in the current digital mobile communication system. 3
Set of sector antennas, 13a and 14a, 13b and 14
b, 13c and 14c, and each sector antenna group is composed of two antenna elements having the same antenna directivity. The antenna elements 13a and 1 cover the A sector.
4a, and since these antenna gains cover only the A sector, they have directivity only in the range of the angle θ = 120 degrees. By doing so, it is possible to prevent transmission of radio waves in directions other than the sector A and to prevent reception of radio waves from mobile devices located in sectors other than the sector A. Similarly, the antenna elements 13b, 1 cover the sector B.
4b, the antenna element 13c, which covers the sector C,
14c, and the directivity is set to cover only the B sector and the C sector, respectively.
【0003】ここで、セクタアンテナ群が2本のアンテ
ナ素子で構成されているのは、受信時にダイバーシチ効
果を得るためである。従来技術においては、ダイバーシ
チ技術として検波後選択ダイバーシチを採用しており、
その受信機構成を図3に示す。ここで、Aセクタに居る
移動機からの電波を受信するものとして、アンテナ素子
13a,14aの受信信号を用いるものとする。Here, the reason that the sector antenna group is composed of two antenna elements is to obtain a diversity effect during reception. In the prior art, selection diversity after detection is adopted as the diversity technology,
FIG. 3 shows the configuration of the receiver. Here, it is assumed that a signal received by the antenna elements 13a and 14a is used to receive a radio wave from a mobile station in the sector A.
【0004】まず、アンテナ13aから受信した受信波
は、低雑音アンプ15で増幅された後にハイブリッド1
6で2分岐される。その1つの信号は、キャリア信号発
生器17が出力するキャリア信号と乗算器18で乗算さ
れた後にローパスフィルタ19へ入力され、A/D変換
器21でサンプリング周期Ts ごとにサンプリングさ
れ、ディジタル信号に変換される。ハイブリッド16よ
りの他方の信号は移相器22で90度位相回転したキャ
リア信号と乗算器23で乗算され、ローパスフィルタ2
4へ入力された後にA/D変換器25でサンプリング周
期Ts ごとにサンプリングされ、ディジタル信号に変換
される。この操作は準同期検波であり、ローパスフィル
タ21,25の出力は準同期検波信号の同相成分及び直
交成分に相当し、ここで2つを合わせて時刻iTS (i
は整数)の受信信号x1 (i)とする。ここで、低雑音
アンプ15、ハイブリッド16、乗算器18及び23、
移相器22、ローパスフィルタ19及び24、A/D変
換器21及び25はベースバンド受信信号発生器26を
構成する。同様に、アンテナ14aから受信した受信波
はベースバンド受信信号発生器27で準同期検波され、
時刻iTS の受信信号x2 (i)が出力される。以下の
記述では、信号は全て同相成分及び直交成分を有し、同
相成分を実部に直交成分を虚部に表示する複素表示を用
いて信号を表すことにする。また、A/D変換器21及
び22のサンプリング周期TS は変調のシンボル周期T
とする。First, a received wave received from an antenna 13a is amplified by a low noise amplifier 15 and then
6 branches into two. One signal that is input to the low pass filter 19 after the carrier signal generator 17 is multiplied by the carrier signal multiplier 18 for outputting, it is sampled every sampling period T s by the A / D converter 21, a digital signal Is converted to The other signal from the hybrid 16 is multiplied by the multiplier 23 with the carrier signal whose phase has been rotated by 90 degrees by the phase shifter 22, and the low-pass filter 2
After being input to 4 is sampled every sampling period T s by the A / D converter 25, it is converted into a digital signal. This operation is quasi-synchronous detection output of the low pass filter 21 and 25 corresponds to the in-phase and quadrature components of the quasi-synchronized detection signal, wherein the combined two by time iT S (i
Is an integer) received signal x 1 (i). Here, the low noise amplifier 15, the hybrid 16, the multipliers 18 and 23,
The phase shifter 22, the low-pass filters 19 and 24, and the A / D converters 21 and 25 constitute a baseband received signal generator 26. Similarly, the reception wave received from the antenna 14a is quasi-synchronously detected by the baseband reception signal generator 27,
Received signal x 2 (i) is outputted at time iT S. In the following description, all signals have an in-phase component and a quadrature component, and the signal will be represented using a complex representation that displays the in-phase component as a real part and the quadrature component as an imaginary part. The sampling period T S of the A / D converters 21 and 22 is the symbol period T of the modulation.
And
【0005】受信信号x1 (i)は、その同相成分の2
乗が2乗演算回路28で出力され、直交成分の2乗が2
乗演算回路29で出力される。これらの和が加算器31
で求められ、受信信号x1 (i)のレベル信号として出
力される。ここで、2乗演算回路28及び29と加算器
31はレベル検出器32を構成する。同様に受信信号x
2 (i)についても、レベル検出器33は受信信号x2
(i)を入力とし、そのレベル信号を出力する。選択回
路34は受信信号x1 (i)及びx2 (i)、これらの
信号に対応するレベル信号を入力として、レベル信号の
大きい受信信号を選択して出力する。従って、フェージ
ングにより片方のアンテナ素子からの受信信号がレベル
が落ち込んだ場合でも、他方の受信信号を選択すること
により、フェージングによる劣化を補償できる。検波器
35はこの選択回路34の出力信号を入力して信号判定
を行い、判定信号の同相成分及び直交成分を出力端子3
6から出力する。この検波器35としては、例えば遅延
検波回路、同期検波回路等を用いることができる。The received signal x 1 (i) has the in-phase component 2
The square is output by the square operation circuit 28, and the square of the orthogonal component is 2
It is output by the multiplication circuit 29. The sum of these is the adder 31
And output as a level signal of the received signal x 1 (i). Here, the square operation circuits 28 and 29 and the adder 31 constitute a level detector 32. Similarly, the received signal x
2 (i), the level detector 33 outputs the received signal x 2
(I) is input and its level signal is output. The selection circuit 34 receives the received signals x 1 (i) and x 2 (i) and level signals corresponding to these signals, and selects and outputs a received signal having a large level signal. Therefore, even if the level of the received signal from one antenna element drops due to fading, deterioration due to fading can be compensated by selecting the other received signal. The detector 35 receives the output signal of the selection circuit 34 and performs signal determination, and outputs the in-phase component and the quadrature component of the determination signal to the output terminal 3.
6 to output. As the detector 35, for example, a delay detection circuit, a synchronous detection circuit, or the like can be used.
【0006】さて、この受信機構成において図4Aに示
す伝搬状況の場合を考える。同図において、Aセクタに
おける移動機37からの送信波は反射などによりパス1
及びパス2の経路を通って基地局12に到来したとす
る。パス1の経路を通る電波はアンテナ素子13a,1
4aで受信できるが、パス2の経路を通る電波はアンテ
ナ素子13a,14aで受信できず、アンテナ素子13
b,14bでしか受信できない。従って、この受信機構
成においてはアンテナ素子13a,14aからの受信信
号しか用いないので、パス2の経路を通る電波の電力を
有効に使うことができない。また同図に示すように、受
信電力が無視できない干渉波が到来する場合、検波後選
択ダイバーシチを採用しているので、干渉波を除去する
ことが出来ず伝送特性が劣化する。Now, consider the case of a propagation situation shown in FIG. 4A in this receiver configuration. In the figure, a transmission wave from the mobile device 37 in the sector A is reflected on a path 1 due to reflection or the like.
And it arrives at the base station 12 via the path of the path 2. Radio waves passing through the path 1 pass through the antenna elements 13a, 1
4a, but the radio waves passing through the path 2 cannot be received by the antenna elements 13a and 14a,
b, 14b. Therefore, in this receiver configuration, since only the received signals from the antenna elements 13a and 14a are used, the power of the radio wave passing through the path 2 cannot be used effectively. As shown in the figure, when an interference wave whose reception power is not negligible arrives, the selection diversity after detection is employed, so that the interference wave cannot be removed and the transmission characteristics deteriorate.
【0007】[0007]
【発明が解決しようとする課題】以上説明したように、
従来技術においては、マルチパス伝搬路で到来する受信
電力を全て受信することが出来ず、かつ受信電力が無視
できない干渉波が到来する場合、伝送特性が劣化すると
いう欠点がある。この発明の課題は、マルチパス伝搬路
及び干渉波が無視できない状況で良好に動作するアダプ
ティブ・アレー受信機を提供することにある。As described above,
In the related art, there is a drawback that transmission characteristics are deteriorated when not all received power arriving on a multipath propagation path can be received and an interference wave whose received power cannot be ignored arrives. An object of the present invention is to provide an adaptive array receiver that operates well in a situation where multipath propagation paths and interference waves cannot be ignored.
【0008】[0008]
【課題を解決するための手段】この発明におけるアダプ
ティブ・アレー受信機は、(1)異なるアンテナ指向性
を有する複数組のセクタアンテナ群から構成され、各セ
クタアンテナ群はアンテナ指向性が同じ複数本のアンテ
ナ素子から成り、これらアンテナ素子からの受信信号を
出力するアンテナ受信手段、(2)全セクタアンテナ群
の中から特定のセクタアンテナ群を選択し、その受信信
号を重み付け係数で線形合成することにより合成信号を
生成するアレー合成手段、(3)合成信号、判定信号、
線形合成される受信信号とを入力として、重み付け係数
を制御するパラメータ推定手段、(4)合成信号を入力
として判定信号を出力する信号判定手段とから成る。The adaptive array receiver according to the present invention comprises (1) a plurality of sets of sector antenna groups having different antenna directivities, and each of the sector antenna groups has the same antenna directivity. And (2) selecting a specific sector antenna group from all sector antenna groups and linearly combining the received signals with weighting coefficients. (3) a synthesized signal, a determination signal,
It comprises: a parameter estimating means for controlling a weighting coefficient by receiving a received signal to be linearly combined; and (4) a signal determining means for outputting a determination signal by receiving a combined signal as an input.
【0009】[0009]
【作用】この発明における基本的な作用は次のようなも
のである。(1)アンテナ受信手段は、異なるアンテナ
指向性を有する複数組のセクタアンテナ群から構成さ
れ、各セクタアンテナ群はアンテナ指向性が同じ複数本
のアンテナ素子から成り、アンテナ素子からの受信信号
を出力する。(2)アレー合成手段は、全セクタアンテ
ナ群の中から特定のセクタアンテナ群を選択し、その受
信信号を重み付け係数で線形合成することで干渉除去と
ダイバーシチ合成を行い、合成信号を生成する。(3)
パラメータ推定手段は、合成信号、判定信号、線形合成
される受信信号とを入力として、誤差信号の平均2乗が
最小となるように重み付け係数を制御する。(4)信号
判定手段は、合成信号を入力として信号判定を行い判定
信号を出力する。The basic operation of the present invention is as follows. (1) The antenna receiving means is composed of a plurality of sets of sector antenna groups having different antenna directivities, each sector antenna group being composed of a plurality of antenna elements having the same antenna directivity, and outputting a received signal from the antenna element. I do. (2) The array combining means selects a specific sector antenna group from among all the sector antenna groups, and performs interference removal and diversity combining by linearly combining the received signals with weighting coefficients to generate a combined signal. (3)
The parameter estimating means receives the combined signal, the determination signal, and the received signal to be linearly combined, and controls the weighting coefficient so that the mean square of the error signal is minimized. (4) The signal determination means performs signal determination using the composite signal as input and outputs a determination signal.
【0010】従来技術とは、全セクタアンテナ群の中か
ら特定のセクタアンテナ群を予め選択し、その受信信号
を重み付け係数で線形合成することで、干渉除去とダイ
バーシチ合成を行う点が異なる。The difference from the prior art is that a specific sector antenna group is selected in advance from all sector antenna groups and the received signals are linearly combined with weighting coefficients to thereby perform interference cancellation and diversity combining.
【0011】[0011]
【発明の実施の形態】この発明の実施例の構成を図1に
示す。ここでは、セクタアンテナ群の数Mは3、各セク
タアンテナ群のアンテナ素子数Lを2とし、図2Bに示
したセクタアンテナと同じ構成とした。また、重み付け
合成されるセクタアンテナ群の数Nは3として、全セク
タアンテナ群の受信信号が重み付け合成されるものとす
る。FIG. 1 shows the configuration of an embodiment of the present invention. Here, the number M of the sector antenna groups is 3, and the number L of antenna elements of each sector antenna group is 2. The configuration is the same as that of the sector antenna shown in FIG. 2B. Further, it is assumed that the number N of the sector antenna groups to be weighted and combined is 3, and the reception signals of all the sector antenna groups are weighted and combined.
【0012】まず、アンテナ素子13aから受信した受
信波は、ベースバンド受信信号発生器21aにおいてキ
ャリア信号発生器17が出力するキャリア信号を用いて
準同期検波され、受信信号x1 (i)が出力される。同
様に、アンテナ素子14a,13b,14b,13c,
14cからそれぞれ受信した受信波は、ベースバンド受
信信号発生器27a,21b,27b,21c,27c
でキャリア信号発生器17が出力するキャリア信号を用
いて準同期検波され、受信信号x2 (i)〜x 6 (i)
が出力される。ここで、アンテナ素子13a,14a,
13b,14b,13c,14c及びベースバンド受信
信号発生器21a,27a,21b,27b,21c,
27c、キャリア信号発生器17はアンテナ受信手段に
相当する。First, the reception received from the antenna element 13a is performed.
The transmitted wave is keyed in baseband received signal generator 21a.
Using the carrier signal output from the carrier signal generator 17
Quasi-synchronous detection, received signal x1(I) is output. same
Thus, the antenna elements 14a, 13b, 14b, 13c,
14c respectively receive the baseband signals.
Communication signal generators 27a, 21b, 27b, 21c, 27c
Uses the carrier signal output by the carrier signal generator 17
Quasi-synchronous detection and the received signal xTwo(I) -x 6(I)
Is output. Here, the antenna elements 13a, 14a,
13b, 14b, 13c, 14c and baseband reception
The signal generators 21a, 27a, 21b, 27b, 21c,
27c, the carrier signal generator 17 is used as an antenna receiving means.
Equivalent to.
【0013】全ての受信信号x1 (i)〜x6 (i)が
複素乗算器41〜46で各々重み付け係数を乗算され、
その乗算結果が複素加算器47で足し合わされる。即
ち、受信信号x1 (i)〜x6 (i)が線形合成され、
その結果が合成信号として複素加算器47から出力され
る。ここで、複素乗算機41〜46及び複素加算器47
はアレー合成手段に相当する。判定器48は、合成信号
を入力として硬判定による信号判定を行い、その判定結
果の同相成分と直交成分を判定信号として出力端子36
から出力する。ここで、信号は図4Bに示すように、先
頭に既知のトレーニング信号が配置され、データ信号が
続くフレーム構成で送信されるものとする。トレーニン
グ信号区間においては、上記の判定信号として既知のト
レーニング信号が出力されるものとする。ここで、判定
器48は信号判定手段に相当する。複素減算器49は合
成信号と判定信号の差分を誤差信号として出力する。重
み付け係数推定回路51は受信信号x1 (i)〜x
6 (i)と誤差信号を入力として、誤差信号の平均2乗
が最小となるように最小2乗法により重み付け係数を推
定し、複素乗算器41〜46に設定する。前記のトレー
ニング信号は、重み付け係数の推定を速く収束させるた
めに用いられる。ここで、複素減算器49と重み付け係
数推定回路51はパラメータ推定手段に相当する。All of the received signals x 1 (i) to x 6 (i) are multiplied by weighting coefficients in complex multipliers 41 to 46, respectively.
The result of the multiplication is added by the complex adder 47. That is, the received signals x 1 (i) to x 6 (i) are linearly synthesized,
The result is output from the complex adder 47 as a composite signal. Here, complex multipliers 41 to 46 and complex adder 47
Corresponds to an array combining means. The decision unit 48 makes a signal decision by hard decision using the synthesized signal as an input, and uses the in-phase component and the quadrature component of the decision result as decision signals as output terminals 36.
Output from Here, as shown in FIG. 4B, the signal is transmitted in a frame configuration in which a known training signal is arranged at the beginning and a data signal follows. In the training signal section, a known training signal is output as the determination signal. Here, the decision unit 48 corresponds to a signal decision unit. The complex subtractor 49 outputs a difference between the combined signal and the determination signal as an error signal. The weighting coefficient estimating circuit 51 receives the received signals x 1 (i) to x
With 6 (i) and the error signal as inputs, the weighting coefficient is estimated by the least squares method so that the mean square of the error signal is minimized, and set to the complex multipliers 41 to 46. The training signal is used to quickly converge the weighting factor estimation. Here, the complex subtractor 49 and the weighting coefficient estimation circuit 51 correspond to parameter estimation means.
【0014】この実施例では、1つのセクタアンテナ群
だけでなく複数のセクタアンテナ群の受信信号を用いて
いるので、マルチパス伝搬路条件で効率良く受信電力を
得ることができる。図4Aに示した伝搬状況で具体的に
説明すると、アンテナ素子13a,14aからの受信信
号だけでなく、アンテナ素子13b,14bからの受信
信号を用いているので、パス1の電力だけでなくパス2
の電力を受信することができる。また、図4Aに示すよ
うに受信電力が無視できない干渉波が到来する場合、受
信信号を線形合成するので干渉波を除去することが可能
となる。In this embodiment, since the received signals of not only one sector antenna group but also a plurality of sector antenna groups are used, it is possible to obtain the received power efficiently under multipath propagation path conditions. More specifically, in the propagation situation shown in FIG. 4A, not only the power of the path 1 but also the power of the path 1 is used because not only the signals received from the antenna elements 13a and 14a but also the signals received from the antenna elements 13b and 14b are used. 2
Of power can be received. Also, as shown in FIG. 4A, when an interference wave whose received power cannot be ignored arrives, the received signal is linearly combined, so that the interference wave can be removed.
【0015】ここでは、全セクタアンテナ群の受信信号
を用いて線形合成する場合を説明したが、アンテナ素子
13a,14a,13b,14bの受信信号を用いる場
合も同様である。Here, the case where the linear combination is performed using the received signals of all the sector antenna groups has been described, but the same applies to the case where the received signals of the antenna elements 13a, 14a, 13b, and 14b are used.
【0016】[0016]
【発明の効果】以上説明したようにこの発明では、マル
チパス伝搬路条件で効率良く受信電力を得ることがで
き、かつ干渉波を除去することが可能となり、マルチパ
ス伝搬路条件で干渉波が無視できない状況でも良好に動
作するアダプティブ・アレー受信機を実現できる。As described above, according to the present invention, it is possible to efficiently obtain the received power under the multipath propagation path condition and to remove the interference wave, and the interference wave can be removed under the multipath propagation path condition. An adaptive array receiver that operates well even in a situation that cannot be ignored can be realized.
【0017】この発明は移動通信のセクタ化を導入した
セル方式に利用すると効果的である。The present invention is effective when used in a cell system in which sectorization of mobile communication is introduced.
【図1】この発明の実施例の機能構成を示すブロック
図。FIG. 1 is a block diagram showing a functional configuration of an embodiment of the present invention.
【図2】Aはセクタ化を導入したセルの構成図、Bは基
地局のセクタアンテナの配置図である。FIG. 2A is a configuration diagram of a cell in which sectorization is introduced, and FIG. 2B is a layout diagram of sector antennas of a base station.
【図3】従来の基地局受信機の構成図。FIG. 3 is a configuration diagram of a conventional base station receiver.
【図4】Aは従来技術の伝送特性が劣化する伝搬状況を
示す図、Bは伝送に用いるフレーム構成図である。FIG. 4A is a diagram showing a propagation state in which transmission characteristics of the related art deteriorate, and FIG. 4B is a diagram showing a frame configuration used for transmission.
Claims (1)
上の整数)組のセクタアンテナ群から構成され、各セク
タアンテナ群はアンテナ指向性が同一のL(2以上の整
数)本のアンテナ素子から成り、これらアンテナ素子か
らの受信信号を出力するアンテナ受信手段と、 予め定めたN(1以上M以下の整数)組の上記セクタア
ンテナ群が出力するNL個の受信信号を、重み付け係数
で線形合成することにより合成信号を生成するアレー合
成手段と、 上記合成信号と、判定信号と、線形合成される上記NL
個の受信信号とを入力とし、上記合成信号と上記判定信
号との差分を誤差信号として、その誤差信号の平均2乗
が最小となるように上記重み付け係数を制御するパラメ
ータ推定手段と、 上記合成信号を入力として信号判定を行い、上記判定信
号を出力する信号判定手段とから構成されることを特徴
とするアダプティブ・アレー受信機。1. An antenna system comprising: M (an integer of 2 or more) sets of sector antenna groups having different antenna directivities, wherein each sector antenna group includes L (an integer of 2 or more) antenna elements having the same antenna directivity. An antenna receiving means for outputting received signals from these antenna elements, and a linear combination of NL received signals output from a predetermined set of N (an integer of 1 or more and M or less) sector antenna groups by weighting coefficients. Array combining means for generating a combined signal, and the NL which is linearly combined with the combined signal and the determination signal.
Parameter estimating means for receiving the received signals as input, controlling the weighting coefficient such that the average square of the error signal is minimized, using a difference between the composite signal and the determination signal as an error signal; An adaptive array receiver comprising: a signal determination unit that performs a signal determination using a signal as an input and outputs the determination signal.
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP27335596A JP3287538B2 (en) | 1996-10-16 | 1996-10-16 | Adaptive array receiver |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP27335596A JP3287538B2 (en) | 1996-10-16 | 1996-10-16 | Adaptive array receiver |
Publications (2)
Publication Number | Publication Date |
---|---|
JPH10126138A true JPH10126138A (en) | 1998-05-15 |
JP3287538B2 JP3287538B2 (en) | 2002-06-04 |
Family
ID=17526751
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP27335596A Expired - Fee Related JP3287538B2 (en) | 1996-10-16 | 1996-10-16 | Adaptive array receiver |
Country Status (1)
Country | Link |
---|---|
JP (1) | JP3287538B2 (en) |
Cited By (10)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
WO2002021722A1 (en) * | 2000-09-04 | 2002-03-14 | Sanyo Electric Co., Ltd. | Radio base system, sampling error reducing method, and sampling error reducing program |
KR100337248B1 (en) * | 1998-04-03 | 2002-05-17 | 루센트 테크놀러지스 인크 | Adaptive antenna |
JP2002204227A (en) * | 2000-12-28 | 2002-07-19 | Kyocera Corp | Frame synchronizing circuit |
EP1315311A1 (en) * | 2000-08-10 | 2003-05-28 | Fujitsu Limited | Transmission diversity communication device |
JP2003529262A (en) * | 2000-03-27 | 2003-09-30 | 電信科学技術研究院 | Method of improving coverage of intelligent antenna array |
US6792033B1 (en) | 1998-09-03 | 2004-09-14 | Nec Corporation | Array antenna reception apparatus |
US7031755B2 (en) * | 2000-02-24 | 2006-04-18 | China Academy Of Telecommuncations Technology | Distributed smart antenna system |
KR100625451B1 (en) * | 1999-12-18 | 2006-09-18 | 주식회사 케이티 | Interference cancellation method in composite structure of smart antenna and interference cancellator |
CN100392425C (en) * | 2004-05-21 | 2008-06-04 | 粟毅 | Wave beam forming system applied for linear array under super broad band signal excitation |
WO2009028116A1 (en) * | 2007-08-30 | 2009-03-05 | Mitsubishi Electric Corporation | Radio signal demodulating device |
-
1996
- 1996-10-16 JP JP27335596A patent/JP3287538B2/en not_active Expired - Fee Related
Cited By (16)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
KR100337248B1 (en) * | 1998-04-03 | 2002-05-17 | 루센트 테크놀러지스 인크 | Adaptive antenna |
US6792033B1 (en) | 1998-09-03 | 2004-09-14 | Nec Corporation | Array antenna reception apparatus |
KR100625451B1 (en) * | 1999-12-18 | 2006-09-18 | 주식회사 케이티 | Interference cancellation method in composite structure of smart antenna and interference cancellator |
US7031755B2 (en) * | 2000-02-24 | 2006-04-18 | China Academy Of Telecommuncations Technology | Distributed smart antenna system |
JP4786110B2 (en) * | 2000-03-27 | 2011-10-05 | 電信科学技術研究院 | How to improve the coverage of intelligent antenna arrays |
JP2003529262A (en) * | 2000-03-27 | 2003-09-30 | 電信科学技術研究院 | Method of improving coverage of intelligent antenna array |
EP1612966A1 (en) * | 2000-08-10 | 2006-01-04 | Fujitsu Limited | Transmitting diversity communications apparatus |
EP1603253A1 (en) * | 2000-08-10 | 2005-12-07 | Fujitsu Limited | Transmitting diversity communications apparatus |
EP1315311A4 (en) * | 2000-08-10 | 2005-01-19 | Fujitsu Ltd | Transmission diversity communication device |
US7099634B2 (en) | 2000-08-10 | 2006-08-29 | Fujitsu Limited | Transmitting diversity communications apparatus |
EP1315311A1 (en) * | 2000-08-10 | 2003-05-28 | Fujitsu Limited | Transmission diversity communication device |
WO2002021722A1 (en) * | 2000-09-04 | 2002-03-14 | Sanyo Electric Co., Ltd. | Radio base system, sampling error reducing method, and sampling error reducing program |
JP2002204227A (en) * | 2000-12-28 | 2002-07-19 | Kyocera Corp | Frame synchronizing circuit |
CN100392425C (en) * | 2004-05-21 | 2008-06-04 | 粟毅 | Wave beam forming system applied for linear array under super broad band signal excitation |
WO2009028116A1 (en) * | 2007-08-30 | 2009-03-05 | Mitsubishi Electric Corporation | Radio signal demodulating device |
US8179948B2 (en) | 2007-08-30 | 2012-05-15 | Mitsubishi Electric Corporation | Radio signal demodulating device |
Also Published As
Publication number | Publication date |
---|---|
JP3287538B2 (en) | 2002-06-04 |
Similar Documents
Publication | Publication Date | Title |
---|---|---|
JP3092798B2 (en) | Adaptive transceiver | |
US6292135B1 (en) | Adaptive array antenna system | |
JP3375139B2 (en) | Adaptive array transceiver | |
CA2397131C (en) | Linear signal separation using polarization diversity | |
JP3591581B2 (en) | Adaptive antenna receiver | |
WO2004083998A2 (en) | Genetic algorithm-based adaptive antenna array processing method and system | |
JPH11266180A (en) | Array antenna system for radio base station | |
CA2261841C (en) | Adaptive receiving device for antennas | |
JP3287538B2 (en) | Adaptive array receiver | |
WO2000031909A1 (en) | Receiver and demodulator applied to mobile communication system | |
JPH07231278A (en) | Reke receiver by direct spread spectrum communication system | |
Nishio et al. | A high-speed adaptive antenna array with simultaneous multibeam-forming capability | |
JPH10190540A (en) | Performance improving device for digital radio receiver and method therefor | |
JP2010068305A (en) | Mobile communication system, base station, method of removing interference | |
US7043217B2 (en) | Combining reception method and apparatus | |
JP2006041562A (en) | Base station device and radio receiving method | |
JP2003087039A (en) | Adaptive array antenna apparatus | |
Lee et al. | A digital adaptive beamforming QAM demodulator IC for high bit-rate wireless communications | |
JP3582343B2 (en) | Received signal processing device | |
JP2010021919A (en) | Mobile communication system, base station, and interference cancellation method | |
JPH06334575A (en) | Spread spectrum communication reception equipment | |
JP3723384B2 (en) | Adaptive antenna device | |
JP3138243B2 (en) | Adaptive array device | |
MORIYAMA et al. | A CMA adaptive array antenna system with a single receiver using time-division multiplexing | |
US7778366B2 (en) | Wireless system having channel fading compensation using zero-forcing |
Legal Events
Date | Code | Title | Description |
---|---|---|---|
R250 | Receipt of annual fees |
Free format text: JAPANESE INTERMEDIATE CODE: R250 |
|
R250 | Receipt of annual fees |
Free format text: JAPANESE INTERMEDIATE CODE: R250 |
|
R250 | Receipt of annual fees |
Free format text: JAPANESE INTERMEDIATE CODE: R250 |
|
FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20080315 Year of fee payment: 6 |
|
FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20090315 Year of fee payment: 7 |
|
FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20090315 Year of fee payment: 7 |
|
FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20100315 Year of fee payment: 8 |
|
FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20100315 Year of fee payment: 8 |
|
FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20110315 Year of fee payment: 9 |
|
FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20110315 Year of fee payment: 9 |
|
FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20120315 Year of fee payment: 10 |
|
FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20120315 Year of fee payment: 10 |
|
FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20130315 Year of fee payment: 11 |
|
FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20130315 Year of fee payment: 11 |
|
FPAY | Renewal fee payment (event date is renewal date of database) |
Free format text: PAYMENT UNTIL: 20140315 Year of fee payment: 12 |
|
LAPS | Cancellation because of no payment of annual fees |