JPH0630565A - High frequency electric power source unit - Google Patents
High frequency electric power source unitInfo
- Publication number
- JPH0630565A JPH0630565A JP4124823A JP12482392A JPH0630565A JP H0630565 A JPH0630565 A JP H0630565A JP 4124823 A JP4124823 A JP 4124823A JP 12482392 A JP12482392 A JP 12482392A JP H0630565 A JPH0630565 A JP H0630565A
- Authority
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- Japan
- Prior art keywords
- circuit
- power supply
- current
- active filter
- voltage
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
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- Inverter Devices (AREA)
- Circuit Arrangements For Discharge Lamps (AREA)
Abstract
Description
【０００１】[0001]
【産業上の利用分野】本発明は高周波電源装置の力率改
善に関し、さらに詳細には、アクティブフィルター回路
のスイッチングを出力スイッチング回路のスイッチング
トランジスタで併用させることにより回路の簡素化を図
りつつ力率を改善した高周波電源装置に関するものであ
る。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to power factor improvement of a high frequency power supply device. More specifically, the power factor is improved while the switching transistor of the output switching circuit is used in combination with the switching of the active filter circuit. The present invention relates to a high-frequency power supply device having improved.
【０００２】[0002]
【従来の技術】代表的な従来の電源装置における整流回
路例を図５〜図８を基に説明する。2. Description of the Related Art An example of a rectifier circuit in a typical conventional power supply device will be described with reference to FIGS.
【０００３】図５（Ａ）はコンデンサ入力型倍電圧整流
・平滑回路であり、歴史的に多く使用されてきたもので
あるが、力率が悪く省エネルギーの観点から改善要請が
高まっている。FIG. 5 (A) shows a capacitor input type voltage doubler rectifying / smoothing circuit, which has been used many times historically, but its power factor is poor and demand for improvement is increasing from the viewpoint of energy saving.
【０００４】即ち、図中において商用電源（５０／６０
Ｈｚ）１は本回路の入力（Ｖｉｎ）となり、２は整流回
路、３は平滑回路であり、ダイオードＤ１にて正極側を
整流し電解コンデンサＣ１を充電する。また、ダイオー
ドＤ２にて負極側を整流し電解コンデンサＣ２を充電す
る。このため、出力電圧Ｖｏ他各電圧・電流が図５
（Ｂ）に示す波形となり、半サイクル毎に正負の入力電
流Ｉｉｎが少ない流通角αで流入する。That is, in the figure, a commercial power source (50/60
Hz) 1 becomes an input (Vin) of this circuit, 2 is a rectifying circuit, 3 is a smoothing circuit, and the positive electrode side is rectified by the diode D1 to charge the electrolytic capacitor C1. Further, the negative electrode side is rectified by the diode D2 to charge the electrolytic capacitor C2. Therefore, the output voltage Vo and other voltages and currents are shown in FIG.
The waveform is as shown in (B), and the positive and negative input currents Iin flow in at a small distribution angle α every half cycle.
【０００５】前記回路は簡易であり効率がよいので使用
される機会が多いが、流通角αが狭いが故に力率は５０
〜７０％程度となり皮相電力が大きく電送経路の電力損
失が無視できないという問題を含んでいる。The circuit is often used because it is simple and efficient, but the power factor is 50 because the distribution angle α is narrow.
The problem is that the apparent power is large at about 70% and the power loss in the transmission path cannot be ignored.
【０００６】上記問題の対策として古くからチョークイ
ンプット型が使用されてきたが、チョーク自体が大き
く、コスト、重量、スペースの点から敬遠され、最近で
は殆ど使用されない状況にある。（図省略） 次に、図６（Ａ）に示す電流補償型整流・平滑回路の場
合は、ブリッジ整流回路４のダイオードＤ１〜Ｄ４にて
両波整流され、平滑・電流補償回路５で電解コンデンサ
Ｃ１→ダイオードＤ６→コイルＬ１→電解コンデンサＣ
２の経路にてＣ１，Ｃ２がｔ１期間充電される（図６
（Ｂ）参照）。この際電解コンデンサＣ１，Ｃ２は同一
容量とすることが必要条件となる。Although a choke input type has been used for a long time as a measure against the above problem, the choke itself is large, and it has been shunned from the viewpoint of cost, weight and space, and recently it is almost not used. Next, in the case of the current compensation type rectifying / smoothing circuit shown in FIG. 6 (A), both waves are rectified by the diodes D1 to D4 of the bridge rectifying circuit 4, and the electrolytic capacitor is used by the smoothing / current compensating circuit 5. C1 → diode D6 → coil L1 → electrolytic capacitor C
C1 and C2 are charged along the route 2 for the period t1 (see FIG. 6).
(See (B)). At this time, it is a necessary condition that the electrolytic capacitors C1 and C2 have the same capacitance.
【０００７】整流後の電圧Ｖｏが時間とともに減少して
ピーク値の５０％に達した時点で電解コンデンサＣ１お
よびＣ２に蓄積された電荷が電解コンデンサＣ１→負荷
→ダイオードＤ５、電解コンデンサＣ２→ダイオードＤ
７→負荷の各々の経路を通って並列に負荷に電力をｔ２
期間供給することとなる（図６（Ｂ）参照）。When the voltage Vo after rectification decreases with time and reaches 50% of the peak value, the charges accumulated in the electrolytic capacitors C1 and C2 are electrolytic capacitor C1 → load → diode D5, electrolytic capacitor C2 → diode D.
7 → t2 power is supplied to the load in parallel through each path of the load
It will be supplied for a period (see FIG. 6B).
【０００８】このようにして上記電流補償型整流・平滑
回路の場合は交流電圧ピーク値の５０％までの期間ｔ１
内で入力電流Ｉｉｎが流入し、図６（Ｂ）のようにコン
デンサ入力型倍電圧整流回路の場合に比較して流通角α
が拡大する結果となり、力率が改善される。As described above, in the case of the current compensation type rectifying / smoothing circuit, the period t1 of up to 50% of the AC voltage peak value is obtained.
The input current Iin flows in, and the distribution angle α is larger than that in the case of the capacitor input type double voltage rectifier circuit as shown in FIG. 6 (B).
The result is that the power factor is improved.
【０００９】上記回路では力率９０％前後まで改善可能
である。しかし、出力電圧が必然的に決定されるため
（最小値がピーク値の５０％）、高い電圧を要する場合
には別途昇圧する必要があるという欠点を有している。
さらに回路の構成上、電解コンデンサＣ１、Ｃ２の充電
電圧は最大Ｖｏの半分なので倍電圧整流回路の適用には
無理がある点も使用範囲を狭める要因となっている。In the above circuit, the power factor can be improved to about 90%. However, since the output voltage is inevitably determined (the minimum value is 50% of the peak value), there is a drawback that it is necessary to separately boost the voltage when a high voltage is required.
Further, in terms of the circuit configuration, since the charging voltage of the electrolytic capacitors C1 and C2 is half of the maximum Vo, it is difficult to apply the voltage doubling rectifier circuit, which is another factor that narrows the range of use.
【００１０】次に図７（Ａ）のアクティブフィルタ方式
（昇圧形）の場合は、基本的には力率１００％を目指し
たものであり、流入する電流Ｉｉｎが入力電圧Ｖｉｎに
比例するように制御回路６でアクティブフィルタ回路７
のスイッチング動作を制御し、図７（Ｂ）に示すように
高周波スイッチングされた入力電流８（Ｉｒ）の平均値
（入力平均電流９）が整流電圧１０（Ｖｉ）に比例する
ようにしている。Next, in the case of the active filter system (step-up type) of FIG. 7A, basically, the power factor is aimed at 100%, and the inflowing current Iin is proportional to the input voltage Vin. The control circuit 6 includes an active filter circuit 7
The switching operation is controlled so that the average value (input average current 9) of the high-frequency switched input current 8 (Ir) is proportional to the rectified voltage 10 (Vi) as shown in FIG. 7B.
【００１１】上記方式は力率改善の点からすればほぼ完
全に近いものの、図７（Ａ）より明らかなようにアクテ
ィブフィルタ回路はコイルＬ１、ダイオードＤ５、スイ
ッチングトランジスタＱ１、平滑コンデンサＣ１から構
成され、スイッチング制御回路６も複雑となってコスト
高となる。したがって前記方式は大電力用大型電源の適
用例が散見される程度である。最近ではアクティブフィ
ルタの制御回路６をＩＣ化した製品が市販されているが
高価である。Although the above method is almost perfect from the viewpoint of improving the power factor, the active filter circuit is composed of a coil L1, a diode D5, a switching transistor Q1 and a smoothing capacitor C1 as is apparent from FIG. 7A. The switching control circuit 6 also becomes complicated and the cost increases. Therefore, the above-mentioned method is only applicable to large power sources for large power sources. Recently, a product in which the control circuit 6 of the active filter is integrated is commercially available, but it is expensive.
【００１２】上記アクティブフィルタ回路７の機能につ
いて詳述すれば、ライン電圧、ライン電流の瞬時値を検
出し、ラインに直列に挿入されたチョークコイルＬ１、
およびトランジスタＱ１のスイッチにより、スイッチン
グの１サイクル内での実効値（ΔＶ／ΔＩ＝Ｒ）が一定
となるように制御するものである。なおスイッチング周
波数は数１０ｋＨｚ以上に選定されるのが一般的であ
る。また、制御方式は可変周波数方式、パルス幅制御方
式等があり、用途に適した方式が選定される。To explain the function of the active filter circuit 7 in detail, the instantaneous values of the line voltage and the line current are detected, and the choke coil L1 inserted in series in the line,
Also, the switch of the transistor Q1 controls the effective value (ΔV / ΔI = R) to be constant within one switching cycle. The switching frequency is generally selected to be several tens of kHz or higher. Further, the control method includes a variable frequency method, a pulse width control method, etc., and the method suitable for the application is selected.
【００１３】以上に述べた整流・平滑回路は直流電源と
して電力Ｖｏを該回路に接続された出力スイッチング回
路（所謂インバータ回路）に供給し該出力スイッチング
回路と共に高周波電源を構成する。The rectifying / smoothing circuit described above supplies electric power Vo as a DC power source to an output switching circuit (so-called inverter circuit) connected to the circuit, and constitutes a high frequency power source together with the output switching circuit.
【００１４】図８の（Ａ）は上記図７（Ａ）のアクティ
ブフィルタ回路を適用した高周波電源回路の回路例であ
る。この際、Ｑ１のスイッチングによりＬ１およびＡＣ
ラインに流れる電流はそれぞれ（Ｂ）、（Ｃ）のように
なる。図から判るようにスイッチング制御回路として２
つ必要であって全体の回路構成は複雑で且つコスト高と
なるのは避けられない。FIG. 8A is a circuit example of a high frequency power supply circuit to which the active filter circuit of FIG. 7A is applied. At this time, by switching Q1, L1 and AC
The currents flowing in the lines are as shown in (B) and (C), respectively. As can be seen from the figure, 2 as a switching control circuit
However, it is inevitable that the overall circuit configuration is complicated and costly.
【００１５】[0015]
【発明が解決しようとする課題】最近、電子機器から発
生する高調波に起因する電源ラインの波形歪が問題視さ
れているが、この波形歪が大きくなると同じ電源ライン
に接続される電子機器や電力供給源としての変電所機器
に誤動作や破損を引き起こすことがある（高調波妨
害）。Recently, the waveform distortion of the power supply line caused by the harmonics generated from the electronic equipment has been regarded as a problem. When the waveform distortion becomes large, the electronic equipment connected to the same power supply line or May cause malfunction or damage to substation equipment as a power supply source (harmonic interference).
【００１６】この点、電源ラインに接続される機器が純
粋な抵抗またはインダクタ、キャパシタのみで構成され
る場合には、電源ライン電圧と電流の位相差に応じ力率
が低下するので、無効電流が増加するもののライン電圧
を歪ませることはない。しかしながら、多くの機器で直
流化されるようになった現在、ダイオードとコンデンサ
で構成される整流回路は、電源ラインに対して非線形負
荷として作用し、電源ラインに流れる電流のピーク値は
平均電流の５〜１０倍も流れて電源ラインに著しい歪を
生じさせ、高調波妨害の問題が顕現する。したがって該
高調波歪を低減させるためには入力電圧波形（正弦波）
と入力電流波形を比例させること、即ち力率を高くする
必要がある。In this respect, when the device connected to the power supply line is composed of pure resistors, inductors, or capacitors, the power factor decreases according to the phase difference between the power supply line voltage and current, so that the reactive current is reduced. It increases but does not distort the line voltage. However, now that many devices have been converted to direct current, the rectifier circuit consisting of a diode and a capacitor acts as a non-linear load on the power supply line, and the peak value of the current flowing in the power supply line is the average current. The current flows 5 to 10 times and causes a significant distortion in the power supply line, and the problem of harmonic interference appears. Therefore, in order to reduce the harmonic distortion, the input voltage waveform (sine wave)
And the input current waveform must be proportional, that is, the power factor must be increased.
【００１７】一方、前述の如く従来の整流・平滑回路
（図５、図６）における力率の改善は満足できる状態で
はなく、力率の悪さは上記高調波歪の他に無効電力が大
きく電送路での損失増大を招き、また電源スイッチやコ
ネクタの負荷が増大して信頼性を損なう要因の一つにも
なっている。On the other hand, as described above, the improvement of the power factor in the conventional rectifying / smoothing circuit (FIGS. 5 and 6) is not satisfactory, and the poor power factor is caused by the large reactive power in addition to the above harmonic distortion. This is one of the factors that increase the loss in the road and increase the load of the power switch and the connector, which impairs the reliability.
【００１８】この点、前述のアクティブフィルタ方式
（図７）を用いて力率の向上を図ると、（１）入力電流
の減少、（２）入力電圧の広範囲化、（３）入力配線に
よる電圧降下減少、（４）高調波電流の減少、（５）入
力平滑コンデンサのリップル減少等の改善ができる。し
かしながら上記アクティブフィルタ回路は複雑であり、
集積化されたＩＣ製品が市販されてはいるものの高価で
あって、例えば蛍光灯用電源装置のようなコスト低減の
要請が厳しい高周波電源装置については単に電源装置の
整流・平滑回路としてアクティブフィルタ回路を採用す
ることは難しいのが現状であった。In this respect, when the power factor is improved by using the above-mentioned active filter method (FIG. 7), (1) the input current is reduced, (2) the input voltage is widened, and (3) the voltage due to the input wiring. It is possible to improve drop reduction, (4) reduction of harmonic current, and (5) reduction of ripple of input smoothing capacitor. However, the active filter circuit is complicated,
Although an integrated IC product is commercially available, it is expensive, and for a high-frequency power supply device such as a power supply device for a fluorescent lamp, for which there is a severe demand for cost reduction, an active filter circuit is simply used as a rectifying / smoothing circuit of the power supply device. It was the current situation that it was difficult to adopt.
【００１９】以上述べたように、従来の電源装置の整流
・平滑回路において、コンデンサ入力型は簡易であるが
力率が悪い点、電流補償型は力率はかなり改善されるも
のの回路構成的に出力電圧が低く昇圧の必要がある点お
よび倍電圧整流が適用出来ない点、アクティブフィルタ
方式は力率は理想的であるが回路が複雑で高コストにな
る点で各々問題があった。As described above, in the conventional rectifying / smoothing circuit of the power supply device, the capacitor input type is simple but the power factor is poor, while the current compensation type has a considerably improved power factor, but has a circuit configuration. There are problems that the output voltage is low and boosting is required, the voltage doubler rectification cannot be applied, and the active filter method has an ideal power factor, but the circuit is complicated and the cost is high.
【００２０】本発明は上記事情に鑑みてなされたもので
あり、回路の簡素化を図りコストを抑えつつ力率を改善
した高周波電源装置を提供するものである。The present invention has been made in view of the above circumstances, and provides a high frequency power supply device in which the power factor is improved while simplifying the circuit and suppressing the cost.
【００２１】[0021]
【課題を解決するための手段】本発明は、商用交流電源
を入力とし、整流回路と、平滑回路と、トランジスタの
スイッチング制御によるアクティブフィルタ回路と、出
力用電力スイッチング回路と、を備えた高周波電源装置
において、前記アクティブフィルタ回路のスイッチング
動作を前記出力用電力スイッチング回路のトランジスタ
のスイッチング動作にて併せ行うことにより、スイッチ
ング制御を１つの制御回路で行うようにしたことを特徴
とする高周波電源装置を提供することにより、上記目的
を達成するものである。SUMMARY OF THE INVENTION The present invention is a high frequency power supply which has a commercial AC power supply as an input and which comprises a rectifying circuit, a smoothing circuit, an active filter circuit by switching control of transistors, and an output power switching circuit. In the device, a high-frequency power supply device is characterized in that switching control is performed by one control circuit by simultaneously performing switching operation of the active filter circuit by switching operation of a transistor of the output power switching circuit. By providing it, the said objective is achieved.
【００２２】[0022]
【作用】本発明における高周波電源装置においては、出
力用電力スイッチング回路のスイッチングトランジスタ
でアクティブフィルタ回路のスイッチングを行う。した
がって、従来別個に構成されていたアクティブフィルタ
回路と高周波出力スイッチング回路を一体として制御す
るので制御回路が１つで済む。In the high frequency power supply device of the present invention, the active filter circuit is switched by the switching transistor of the output power switching circuit. Therefore, the active filter circuit and the high-frequency output switching circuit, which are conventionally separately configured, are integrally controlled, so that only one control circuit is required.
【００２３】また、使用する整流回路方式に制限は無
い。There is no limitation on the rectifier circuit system used.
【００２４】[0024]
【実施例】本発明に係わる力率改善型高周波電源装置の
実施例を図１を基に詳述する。DESCRIPTION OF THE PREFERRED EMBODIMENTS An embodiment of a power factor improving type high frequency power supply device according to the present invention will be described in detail with reference to FIG.
【００２５】図１は本発明に係わる高周波電源装置の回
路例であり、商用電源１を入力としてノイズフィルタ１
５、倍電圧整流回路（コンデンサ入力型）１６、アクテ
ィブフィルタ回路および出力スイッチング回路１７から
構成される。FIG. 1 is an example of a circuit of a high frequency power supply device according to the present invention, which uses a commercial power supply 1 as an input and a noise filter 1
5, a voltage doubler rectifier circuit (capacitor input type) 16, an active filter circuit and an output switching circuit 17.
【００２６】商用電源が正極性の半サイクル間について
説明すると、ダイオードＤ１により整流された入力電圧
は小容量のフィルムコンデンサＣ１を充電する。Explaining during the positive half cycle of the commercial power supply, the input voltage rectified by the diode D1 charges the small-capacity film capacitor C1.
【００２７】大容量の電解コンデンサＣ３への充電はト
ランジスタＱ１→ダイオードＤ５→チョークコイルＬ１
を通して行われる。但し、Ｃ３の電圧Ｅｃ３がＣ１の電
圧Ｅｃ１より低い間のみ充電される。Charging the large-capacity electrolytic capacitor C3 is performed by transistor Q1 → diode D5 → choke coil L1.
Done through. However, charging is performed only while the voltage Ec3 of C3 is lower than the voltage Ec1 of C1.
【００２８】該充電電流はＣ１とＣ３の電位差、Ｑ１の
オン時間に比例し、インダクタＬ１のインダクタンスに
反比例する関係にあり、次式が成り立つ。The charging current is proportional to the potential difference between C1 and C3, the on-time of Q1, and inversely proportional to the inductance of the inductor L1, and the following equation holds.
【００２９】 Ｉ１１（ｐｅａｋ）＝（Ｅｃ１−Ｅｃ３−Ｅｏｎ）×Ｔｏｎ／Ｌ１ ここにＴｏｎはＱ１のオン時間、Ｉ１１（ｐｅａｋ）は
Ｉ１１の最大値、ＥｏｎはＱ１およびＤ５のオン電圧
（電圧ロス）である。I11 (peak) = (Ec1-Ec3-Eon) × Ton / L1 Here, Ton is the ON time of Q1, I11 (peak) is the maximum value of I11, and Eon is the ON voltage (voltage loss) of Q1 and D5. Is.
【００３０】電源オンの初期状態では、小容量コンデン
サＣ１には電源電圧（半波）に近い位相で、ほぼ同電位
まで瞬時に充電されることになるが、コンデンサＣ３へ
の充電はＱ１がオンしている期間のみとなるので瞬間的
なＥｃ３の電位上昇はない。In the initial state when the power is turned on, the small-capacitance capacitor C1 is instantly charged to almost the same potential in a phase close to the power supply voltage (half wave), but when the capacitor C3 is charged, Q1 is turned on. There is no momentary rise in the potential of Ec3 because it is only during the period.
【００３１】時間の経過と共にＣ３は半波毎に充電さ
れ、Ｅｃ３は徐々に上昇していく。With the passage of time, C3 is charged every half wave, and Ec3 gradually rises.
【００３２】この結果、（Ｅｃ１−Ｅｃ３）は徐々に小
さくなり、充電は減少して負荷に流れる出力電流に応じ
た電圧（Ｅｃ１−Ｅｃ３）で安定することとなる。As a result, (Ec1-Ec3) gradually decreases, and the charge decreases and becomes stable at the voltage (Ec1-Ec3) corresponding to the output current flowing through the load.
【００３３】また、前記充電電流はＥｃ１＞Ｅｃ３の条
件で流れ、Ｅｃ３の電位の高低により入力電流の流通角
が決定される。よって力率はＥｃ３がＥｃ１に近付くほ
ど悪くなる。The charging current flows under the condition of Ec1> Ec3, and the distribution angle of the input current is determined by the level of the potential of Ec3. Therefore, the power factor becomes worse as Ec3 approaches Ec1.
【００３４】以上の動作における各部の波形を図２に示
す。図２において（Ａ）はＥｃ１〜Ｅｃ４の電圧波形、
（Ｂ）は図１中の各部の電流波形である。The waveform of each part in the above operation is shown in FIG. In FIG. 2, (A) is a voltage waveform of Ec1 to Ec4,
(B) is a current waveform of each part in FIG.
【００３５】なお、ダイオードＤ３の動作はＥｃ３の電
位がＥｃ１より高い場合にのみオンし、低い場合にはオ
フとなりオン時のみＣ３の電荷を負荷に供給する。ダイ
オードＤ５はＱ１がオンの時にＣ３への充電電流を流
し、Ｑ２がオンの時にＣ３の電荷を放電させない為のス
イッチとして動作する。The operation of the diode D3 is turned on only when the potential of Ec3 is higher than Ec1 and turned off when the potential of Ec3 is lower than Ec1, and the charge of C3 is supplied to the load only when it is turned on. The diode D5 operates as a switch for supplying a charging current to C3 when Q1 is on and for not discharging the charge of C3 when Q2 is on.
【００３６】また、ダイオードＤ７、Ｄ８はＱ１、Ｑ２
がオフした直後の逆電流路であり、所謂転流ダイオード
である。The diodes D7 and D8 are Q1 and Q2.
Is a reverse current path immediately after turning off, and is a so-called commutation diode.
【００３７】以上の結果、出力電流Ｉｏ１は図２に示す
とおり、Ｔ１の期間はＣ１の電荷を、Ｔ２の期間はＣ３
の電荷を利用して連続した電流を供給することとなる。As a result of the above, the output current Io1 is, as shown in FIG. 2, the electric charge of C1 during the period of T1 and C3 during the period of T2.
A continuous current will be supplied by utilizing the electric charges.
【００３８】本説明は電源入力が正極性の場合について
であったが、負極性の場合についても全く同様に説明さ
れるので省略する。Although the present description has been made for the case where the power supply input has a positive polarity, the description for the case of a negative polarity will be omitted because it is explained in the same manner.
【００３９】次に前記本発明に係わる高周波電源装置を
有する蛍光灯を負荷とする蛍光灯インバータ装置を例に
力率等の特性改善効果について述べる。Next, the effect of improving the characteristics such as power factor will be described by taking a fluorescent lamp inverter device having a fluorescent lamp as a load, which has the high frequency power supply device according to the present invention as an example.
【００４０】図３のような５つの３２ワット蛍光灯ＦＬ
１〜ＦＬ５および限流コイルＬ１〜Ｌ５、共振コンデン
サＣ１〜Ｃ５で構成されている複数組の蛍光灯から成る
負荷を本発明に係わる高周波電源回路（図１）に付加し
た場合の入力電力、入力皮相電力、入力ピーク電流、力
率についての測定データ表１に示す。Five 32-watt fluorescent lamps FL as shown in FIG.
1 to FL5, current-limiting coils L1 to L5, and resonance capacitors C1 to C5, a load consisting of a plurality of sets of fluorescent lamps is added to the high-frequency power supply circuit (FIG. 1) according to the present invention. Table 1 shows measured data on the apparent power, the input peak current, and the power factor.
【００４１】なお、図４に示される従来のコンデンサ入
力型倍電圧整流回路と出力スイッチング回路を組み合わ
せた高周波電源装置の同負荷条件における特性データを
比較のため表１に併記する。Characteristic data under the same load condition of the high frequency power supply device combining the conventional capacitor input type voltage doubler rectifier circuit and the output switching circuit shown in FIG. 4 are also shown in Table 1 for comparison.
【００４２】[0042]
【表１】 [Table 1]
【００４３】（注）入力電力を同一にした場合の比較で
ある。(Note) This is a comparison when the input powers are the same.
【００４４】上記表から明らかなように、入力電流のピ
ーク値で約４６％の減少、皮相電力で２５％の減少、力
率で約２０％の上昇となり、大幅な改善効果が確認され
た。As is clear from the above table, the peak value of the input current was reduced by about 46%, the apparent power was reduced by 25%, and the power factor was increased by about 20%, confirming a significant improvement effect.
【００４５】また、当然のことながら従来回路で必要で
あった突入防止回路１８もスイッチオン時の流入電流を
決定づける平滑回路コンデンサ容量が小さくなっている
ので削除可能となり突入防止回路部品の削減のみなら
ず、本回路の安全上の課題への配慮が不要となる（図４
比較参照）。Further, as a matter of course, the inrush prevention circuit 18, which is required in the conventional circuit, can be deleted because the capacity of the smoothing circuit capacitor that determines the inflow current at the time of switch-on is small. Therefore, it is not necessary to consider the safety issues of this circuit (Fig. 4).
See comparison).
【００４６】[0046]
【発明の効果】本発明に係わる高周波電源装置は、上記
のように構成されているため、以下に記載するような効
果を有する。Since the high frequency power supply device according to the present invention is configured as described above, it has the following effects.
【００４７】（１）力率の高いアクティブフィルタ回路
を有する高周波電源が簡単な回路構成で実現されるとい
う優れた効果を有する。(1) It has an excellent effect that a high-frequency power source having an active filter circuit having a high power factor can be realized with a simple circuit configuration.
【００４８】（２）力率が改善されることにより高調波
歪が減少するという優れた効果を有する。(2) It has an excellent effect that harmonic distortion is reduced by improving the power factor.
【図１】 本発明に係わる高周波電源装置の回路図FIG. 1 is a circuit diagram of a high frequency power supply device according to the present invention.
【図２】 （Ａ）は上記回路各部における電圧波形、
（Ｂ）は電流波形FIG. 2A is a voltage waveform in each part of the above circuit,
(B) Current waveform
【図３】 蛍光灯負荷回路図[Figure 3] Fluorescent lamp load circuit diagram
【図４】 従来のコンデンサ入力型倍電圧整流回路を有
する高周波電源装置FIG. 4 is a high frequency power supply device having a conventional capacitor input type voltage doubler rectifier circuit.
【図５】 （Ａ）は従来のコンデンサ入力型倍電圧整流
・平滑回路図、（Ｂ）は同電圧・電流波形FIG. 5A is a conventional capacitor input type voltage doubler rectifying / smoothing circuit diagram, and FIG. 5B is the same voltage / current waveform.
【図６】 （Ａ）は従来の電流補償型整流・平滑回路
図、（Ｂ）は同電圧・電流波形6A is a conventional current compensation type rectifying / smoothing circuit diagram, and FIG. 6B is the same voltage / current waveform.
【図７】 （Ａ）は従来のアクティブフィルタ回路図、
（Ｂ）は入力電流波形FIG. 7A is a conventional active filter circuit diagram,
(B) Input current waveform
【図８】 （Ａ）は従来のアクティブフィルタ回路を有
する高周波電源装置の回路図、（Ｂ）はチョークコイル
Ｌ１に流れる電流、（Ｃ）はＡＣライン電流8A is a circuit diagram of a high-frequency power supply device having a conventional active filter circuit, FIG. 8B is a current flowing through a choke coil L1, and FIG. 8C is an AC line current.
Ｃ１〜Ｃ５ 電解コンデンサまたはフィルムコンデン
サ Ｄ１〜Ｄ７ ダイオード Ｌ１〜Ｌ３ コイル Ｑ１〜Ｑ３ スイッチングトランジスタ Ｖｏ 出力電圧 Ｖｉｎ 入力電圧 Ｉｉｎ 入力電流 α 流通角 １ 商用電源（５０／６０Ｈｚ） ２ 整流回路 ３ 平滑回路 ４ ブリッジ整流回路 ５ 平滑・電流補償回路 ６ 制御回路 ７ アクティブフィルタ回路 ８ スイッチング入力電流（Ｉｒ） ９ 入力平均電流 １０ 整流電流 １１ アクティブフィルタ回路 １２ 出力スイッチング回路 １３ ＡＣライン電流 １４ 平均電流 Ｔ 正の半サイクル １５ ノイズフィルタ回路 １６ コンデンサ入力型倍電圧整流回路 １７ アクティブフィルタ回路および出力スイッチン
グ回路 １８ 突入防止回路C1 to C5 electrolytic capacitor or film capacitor D1 to D7 diode L1 to L3 coil Q1 to Q3 switching transistor Vo output voltage Vin input voltage Iin input current α distribution angle 1 commercial power supply (50/60 Hz) 2 rectification circuit 3 smoothing circuit 4 bridge rectification Circuit 5 Smoothing / current compensation circuit 6 Control circuit 7 Active filter circuit 8 Switching input current (Ir) 9 Input average current 10 Rectifying current 11 Active filter circuit 12 Output switching circuit 13 AC line current 14 Average current T Positive half cycle 15 Noise Filter circuit 16 Capacitor input type voltage doubler rectifier circuit 17 Active filter circuit and output switching circuit 18 Inrush prevention circuit
Claims (1)
平滑回路と、トランジスタのスイッチング制御によるア
クティブフィルタ回路と、出力用電力スイッチング回路
と、を備えた高周波電源装置において、前記アクティブ
フィルタ回路のスイッチング動作を前記出力用電力スイ
ッチング回路のトランジスタのスイッチング動作にて併
せ行うことにより、スイッチング制御を１つの制御回路
で行うようにしたことを特徴とする高周波電源装置。1. A rectifier circuit using a commercial AC power supply as an input,
In a high-frequency power supply device including a smoothing circuit, an active filter circuit by switching control of transistors, and an output power switching circuit, switching operation of the active filter circuit is performed by switching operation of transistors of the output power switching circuit. A high-frequency power supply device characterized in that switching control is performed by one control circuit by performing it together.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP4124823A JP2622325B2 (en) | 1992-05-18 | 1992-05-18 | High frequency power supply |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP4124823A JP2622325B2 (en) | 1992-05-18 | 1992-05-18 | High frequency power supply |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPH0630565A true JPH0630565A (en) | 1994-02-04 |
| JP2622325B2 JP2622325B2 (en) | 1997-06-18 |
Family
ID=14894993
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP4124823A Expired - Lifetime JP2622325B2 (en) | 1992-05-18 | 1992-05-18 | High frequency power supply |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JP2622325B2 (en) |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US6212754B1 (en) | 1996-12-16 | 2001-04-10 | Ricoh Company, Ltd. | Method for sliding a seal with a lip onto a shaft, method for uncurling the lip, and apparatus for sliding the seal thereonto |
| EP2669404A1 (en) * | 2012-05-31 | 2013-12-04 | Enersaver UG | Method and system for enhancing operation and efficiency of an AC circuit |
Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS531819A (en) * | 1976-06-29 | 1978-01-10 | Sansui Electric Co | Power supply |
| JPS60134776A (en) * | 1983-12-23 | 1985-07-18 | Matsushita Electric Works Ltd | Power source |
-
1992
- 1992-05-18 JP JP4124823A patent/JP2622325B2/en not_active Expired - Lifetime
Patent Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS531819A (en) * | 1976-06-29 | 1978-01-10 | Sansui Electric Co | Power supply |
| JPS60134776A (en) * | 1983-12-23 | 1985-07-18 | Matsushita Electric Works Ltd | Power source |
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US6212754B1 (en) | 1996-12-16 | 2001-04-10 | Ricoh Company, Ltd. | Method for sliding a seal with a lip onto a shaft, method for uncurling the lip, and apparatus for sliding the seal thereonto |
| US6223424B1 (en) | 1996-12-16 | 2001-05-01 | Ricoh Company, Ltd. | Method for sliding a seal with a lip onto a shaft, method for uncurling the lip, and apparatus for sliding the seal thereonto |
| US6226851B1 (en) | 1996-12-16 | 2001-05-08 | Ricoh Company, Ltd. | Method for sliding a seal with a lip onto a shaft, method for uncurling the lip, and apparatus for sliding the seal thereonto |
| EP2669404A1 (en) * | 2012-05-31 | 2013-12-04 | Enersaver UG | Method and system for enhancing operation and efficiency of an AC circuit |
Also Published As
| Publication number | Publication date |
|---|---|
| JP2622325B2 (en) | 1997-06-18 |
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