JPH0342808B2 - - Google Patents
Info
- Publication number
- JPH0342808B2 JPH0342808B2 JP59159939A JP15993984A JPH0342808B2 JP H0342808 B2 JPH0342808 B2 JP H0342808B2 JP 59159939 A JP59159939 A JP 59159939A JP 15993984 A JP15993984 A JP 15993984A JP H0342808 B2 JPH0342808 B2 JP H0342808B2
- Authority
- JP
- Japan
- Prior art keywords
- frequency
- local oscillator
- oscillation
- oscillator
- oscillation frequency
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Lifetime
Links
- 230000010355 oscillation Effects 0.000 claims description 40
- 238000006243 chemical reaction Methods 0.000 description 6
- 239000003990 capacitor Substances 0.000 description 5
- 238000013459 approach Methods 0.000 description 3
- 238000000034 method Methods 0.000 description 3
- 230000010363 phase shift Effects 0.000 description 3
- 238000010586 diagram Methods 0.000 description 2
- 230000001934 delay Effects 0.000 description 1
- 238000001514 detection method Methods 0.000 description 1
- 238000004519 manufacturing process Methods 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03J—TUNING RESONANT CIRCUITS; SELECTING RESONANT CIRCUITS
- H03J7/00—Automatic frequency control; Automatic scanning over a band of frequencies
- H03J7/02—Automatic frequency control
- H03J7/16—Automatic frequency control where the frequency control is accomplished by mechanical means, e.g. by a motor
Landscapes
- Channel Selection Circuits, Automatic Tuning Circuits (AREA)
Description
【発明の詳細な説明】
「産業上の利用分野」
この発明は例えば方向探知機の受信機等に利用
される自動同調装置に関する。DETAILED DESCRIPTION OF THE INVENTION "Field of Industrial Application" The present invention relates to an automatic tuning device used, for example, in a direction finder receiver.
「従来の技術」
例えば方向探知機等ではモータにより受信同調
回路の同調素子を制御することにより、希望する
受信周波数の信号を自動的に受信できるようにし
た受信機が用いられている。従来のこの種受信機
は例えば「実公昭53−19697号公報、特公昭58−
41011号公報、特開昭51−33501号公報」等に開示
されるように局部発振器の発振信号と、局部発振
器の発振信号を局部同調回路を通じた信号とを移
相器によつて移相させて互いに90゜位相差を持た
せて位相検波器に与え、その位相検波出力によつ
てモータを駆動させ、モータによつて局部同調回
路の同調回路素子及び受信回路の同調回路素子を
可変させ、自動的に希望する受信周波数の信号を
受信するように構成されるものである。``Prior Art'' For example, in direction finders and the like, receivers are used in which a motor controls a tuning element of a reception tuning circuit to automatically receive a signal at a desired reception frequency. Conventional receivers of this type are disclosed in, for example, "Utility Model Publication No. 19697-1969, Special Publication No. 1969-1969-
41011, Japanese Patent Application Laid-Open No. 51-33501, etc., the oscillation signal of a local oscillator and the signal passed through a local tuning circuit are phase-shifted by a phase shifter. and a phase detector having a phase difference of 90° from each other, driving a motor by the phase detection output, and causing the motor to vary the tuning circuit elements of the local tuning circuit and the tuning circuit elements of the receiving circuit, It is configured to automatically receive a signal at a desired reception frequency.
このように従来の自動同調装置は移相器を利用
して二つの信号の位相に90゜の位相差を持たせて
位相検波器に与え、その検波出力によつてモータ
を駆動する構造のため次のような不都合が生じ
る。 In this way, conventional automatic tuning devices use a phase shifter to provide a 90° phase difference between the two signals and apply it to the phase detector, and the detected output drives the motor. The following inconveniences occur.
つまり移相器によつて二つの信号に位相差を持
たせるものであるが、移相器に与えられる信号の
周波数は広い帯域にわたつて変化する。このため
移相器の移相量を広い帯域にわたつて一定の例え
ば90゜の移相量となるように作ることはむずかし
い。移相器の移相量が周波数の変化に応じて90゜
の関係からずれると同調周波数に誤差が生じる不
都合が生じる。 In other words, the phase shifter causes two signals to have a phase difference, but the frequency of the signal applied to the phase shifter varies over a wide band. For this reason, it is difficult to create a phase shifter so that the amount of phase shift is constant over a wide band, for example, 90 degrees. If the amount of phase shift of the phase shifter deviates from the 90° relationship as the frequency changes, there will be an inconvenience that an error will occur in the tuning frequency.
このため例えば「特開昭54−75920号公報」に
は、局部発振器の発振周波数を設定するデイジタ
ル設定信号をDA変換してモータ制御回路の一方
の入力端子に与え、モータ制御回路の他方の入力
端子には可変周波数発振器の発振周波数を周波数
−電圧変換した信号を与え、モータ制御回路にお
いて、二つの入力端子に与えられたアナログ電圧
が互いに等しくなるように可変周波数発振器の発
振周波数を制御し、この制御に追従して受信周波
数を制御するように構成した「ヘテロダイン受信
機における高周波段の同調方式」が開示されてい
る。 For this reason, for example, in ``Japanese Unexamined Patent Publication No. 54-75920,'' a digital setting signal for setting the oscillation frequency of a local oscillator is converted from DA to one input terminal of a motor control circuit, and the other input terminal of the motor control circuit is A signal obtained by frequency-voltage conversion of the oscillation frequency of the variable frequency oscillator is applied to the terminal, and in the motor control circuit, the oscillation frequency of the variable frequency oscillator is controlled so that the analog voltages applied to the two input terminals are equal to each other, A "tuning method for a high frequency stage in a heterodyne receiver" configured to control the receiving frequency in accordance with this control is disclosed.
この公報に記載された同調方式によれば移相器
を用いていないから、移相器を用いることの不利
益は解消される。しかしながら、この方式では周
波数−電圧変換器５３とデイジタル−アナログ変
換器５７とによる直流化した信号により比較制御
しているため、この部分の回路構成が複雑になる
他に、これらの変換回路の構成精度によつて、制
御精度能力が左右される。また回路構成が複雑な
ため、装置を安価に提供し得ない不都合がある。
また受信周波数の領域変更のように大幅な周波数
変化に対し周波数−電圧変換器５３及びデイジタ
ル−アナログ変換器の動作領域を変更し、常に動
作領域を一定の領域で動作させようとする考えも
ない。 Since the tuning method described in this publication does not use a phase shifter, the disadvantages of using a phase shifter are eliminated. However, in this method, comparison control is performed using DC signals from the frequency-voltage converter 53 and the digital-to-analog converter 57, so the circuit configuration of this part becomes complicated, and the configuration of these conversion circuits is also complicated. Accuracy determines control accuracy capability. Further, since the circuit configuration is complicated, there is a problem that the device cannot be provided at a low cost.
Furthermore, there is no idea of changing the operating range of the frequency-voltage converter 53 and the digital-to-analog converter in response to a large frequency change such as a change in the receiving frequency range, so that the operating range always operates within a fixed range. .
また他の公知例として「特開昭55−83331号公
報」に開示された受信機の受信周波数設定装置が
ある。この公報に記載された特に第４図のものは
切替スイツチ２１，２２により交互に充電された
コンデンサ２３と２４の直流電圧を比較して制御
している。比較出力を得るのに、交互の切替えに
よる時系列的な充電バランスがそのまま制御に影
響しないようにするにはコンデンサに充分な充電
時間を与えた後に得られる出力を比較するように
構成しなければならず、制御に遅れが生じる欠点
がある。また交互切替えという回路の複雑さがあ
り、装置を安価に提供することができない不都合
がある。またこの公報にも受信周波数領域の大幅
な変更に対して周波数弁別器を常に一定の動作領
域で動作させようとする考えはない。 Another known example is a receiving frequency setting device for a receiver disclosed in ``Japanese Unexamined Patent Publication No. 55-83331.'' The one described in this publication, especially the one shown in FIG. 4, is controlled by comparing the DC voltages of capacitors 23 and 24 which are alternately charged by changeover switches 21 and 22. In order to obtain a comparison output and to prevent the time-series charging balance caused by alternating switching from affecting control, it is necessary to configure the output obtained after giving sufficient charging time to the capacitor to be compared. However, the disadvantage is that there is a delay in control. Furthermore, the circuit is complicated due to the alternating switching, and there is a disadvantage that the device cannot be provided at a low cost. Further, this publication also does not include any idea to always operate the frequency discriminator in a constant operating range even when the reception frequency range changes significantly.
「課題を解決するための手段」
この発明では、入力手段により入力される設定
値によつて発振周波数が規定される局部発振器
と、高周波増幅器の受信周波数と連動して発振周
波数が制御される可変周波数発振器とを具備し、
局部発振器の発振周波数と可変周波数発振器の発
振周波数とが互いに所定の関係（受信周波数と中
間周波数の関係）を維持するように制御ループを
構成し、この制御ループの制御によつて局部発振
器に与えた設定値に対応した周波数を受信する自
動同調装置において、
制御ループは局部発振器の発振信号及び可変周
波数発振器の発振信号とを位相比較する位相比較
器と、この位相比較器の比較出力を平滑化して取
出す低域通過波器と、この低域通過波器から
取り出される直流化信号によつて可変周波数発振
器の発振周波数と、高周波増幅器の受信周波数と
を制御し可変周波数発振器の発振周波数と、局部
発振器に設定された発振周波数とを常に所定の関
係を維持するように制御する周波数制御手段とに
よつて構成すると共に、
可変周波数発振器と位相比較器の間及び局部発
振器と位相比較器の間に局部発振器に設定される
周波数の値に応じて分周数が与えられ、局部発振
器に設定される発振周波数が大きく変わつても、
常に位相比較器に一定周波数の範囲に入る周波数
の信号を供給する二つの可変分周器を設けたこと
を特徴とする自動同調装置を構成したものであ
る。"Means for Solving the Problem" The present invention includes a local oscillator whose oscillation frequency is defined by a setting value inputted by an input means, and a variable oscillator whose oscillation frequency is controlled in conjunction with the reception frequency of a high-frequency amplifier. and a frequency oscillator,
A control loop is configured so that the oscillation frequency of the local oscillator and the oscillation frequency of the variable frequency oscillator maintain a predetermined relationship with each other (relationship between the reception frequency and the intermediate frequency), and the control of this control loop allows the oscillation frequency of the variable frequency oscillator to be In an automatic tuning device that receives a frequency corresponding to a set value, the control loop includes a phase comparator that compares the phases of the oscillation signal of the local oscillator and the oscillation signal of the variable frequency oscillator, and smoothes the comparison output of this phase comparator. The oscillation frequency of the variable frequency oscillator and the reception frequency of the high frequency amplifier are controlled by the direct current signal taken out from the low pass waveformer, and the oscillation frequency of the variable frequency oscillator and the local and a frequency control means that controls the oscillation frequency set in the oscillator so as to always maintain a predetermined relationship, and between the variable frequency oscillator and the phase comparator and between the local oscillator and the phase comparator. The frequency division number is given according to the frequency value set to the local oscillator, and even if the oscillation frequency set to the local oscillator changes significantly,
This automatic tuning device is characterized in that it is equipped with two variable frequency dividers that always supply a signal with a frequency within a fixed frequency range to a phase comparator.
「発明の実施例」
第１図にこの発明の実施例を示す。第１図にお
いて１１は制御器を示す。この制御器１１には入
力手段１２が付設され、入力手段１２から希望す
る受信周波数値を入力することにより制御器１１
は局部発振器１の発振周波数をその受信周波数よ
り例えば中間周波数相当分だけ高い周波数で発振
するように制御する。このため局部発振器１はフ
エイズロツクループによつて構成したシンセサイ
ザ形式の発振器として構成される。局部発振器１
の発振信号は周波数混合器７に与えられ受信信号
の周波数変換用として利用する外に、可変分周器
１３を通じて位相比較器３の一方の入力端子に与
えられる位相比較器３の他方の入力端子には可変
周波数発振器２の発振信号が可変分周器１４を通
じて与えられ、これら可変分周器１３と１４の分
周出力信号１５Ａと１５Ｂを位相比較器３におい
て位相比較する。"Embodiment of the Invention" FIG. 1 shows an embodiment of the invention. In FIG. 1, 11 indicates a controller. This controller 11 is provided with an input means 12, and by inputting a desired reception frequency value from the input means 12, the controller 11
controls the oscillation frequency of the local oscillator 1 so that it oscillates at a frequency higher than the receiving frequency by, for example, an amount equivalent to the intermediate frequency. Therefore, the local oscillator 1 is constructed as a synthesizer-type oscillator constructed from a phase lock loop. Local oscillator 1
The oscillation signal is applied to the frequency mixer 7 and used for frequency conversion of the received signal, and is also applied to one input terminal of the phase comparator 3 through the variable frequency divider 13 to the other input terminal of the phase comparator 3. The oscillation signal of the variable frequency oscillator 2 is applied through the variable frequency divider 14, and the phases of the divided output signals 15A and 15B of the variable frequency dividers 13 and 14 are compared in the phase comparator 3.
位相比較器３は信号１５Ａの周波数fRに対し信
号１５Ｂの周波数fOがfR＜fOのとき例えば第２図
Ａに示すように正極性のパルスPaを出力する。
また周波数fRとfOの関係が、fR＞fOとなると第２
図Ｂに示すように負極性のパルスPbを出力する。
fR＝fOになり、位相が合致すると位相比較器３の
出力はゼロとなる。つまり可変周波数発振器２側
の周波数fOがfRに高い方から近づくと正極性のパ
ルスPaが出力されそのパルス幅はfR＝fOの近くで
漸次狭くなりfR＝fOに完全に合致すると出力がゼ
ロとなる。また周波数fOが低い方からfRに近づく
と負極性のパルスPbが出力されそのパルス幅はfR
＝fOの近くで漸次狭くなりfR＝fOに完全に合致す
ると出力がゼロとなる。 The phase comparator 3 outputs a positive pulse P a as shown in FIG. 2A, for example, when the frequency f O of the signal 15B is f R <f O with respect to the frequency f R of the signal 15A.
Also, if the relationship between frequency f R and f O becomes f R > f O , the second
As shown in Figure B, a pulse P b of negative polarity is output.
When f R = f O and the phases match, the output of the phase comparator 3 becomes zero. In other words, when the frequency f O on the variable frequency oscillator 2 side approaches f R from a high side, a pulse P a of positive polarity is output, and its pulse width gradually narrows near f R = f O until it reaches f R = f O. If it matches, the output will be zero. Moreover, when the frequency f O approaches f R from the low side, a negative polarity pulse P b is output and its pulse width is f R
It gradually narrows near =f O , and when it completely matches f R =f O , the output becomes zero.
この正極性と負極性のパルスPaとPbは低域通
過波器４で波され平滑されて周波数制御手段
５に与えられる。周波数制御手段５はこの例では
増幅器５ＡとDCモード５Ｂとによつて構成した
場合を示す。つまり低域通過波器４からは周波
数fRとfOとの差に比例した極性と電圧値を持つ直
流電圧信号が出力され、その直流電圧信号を増幅
器５Ａで増幅し、サーボモータとして動作する
DCモータ５Ｂを駆動する。 These pulses P a and P b of positive polarity and negative polarity are waved and smoothed by a low-pass transducer 4 and given to a frequency control means 5 . In this example, the frequency control means 5 is composed of an amplifier 5A and a DC mode 5B. In other words, the low-pass wave generator 4 outputs a DC voltage signal with a polarity and voltage value proportional to the difference between the frequencies f R and f O , and the DC voltage signal is amplified by the amplifier 5A to operate as a servo motor.
Drives DC motor 5B.
DCモータ５Ｂは可変周波数発振器２の例えば
バリコンのような同調回路素子２Ａと、高周波増
幅器６の同調回路素子６Ａに結合され、これら同
調回路素子２Ａと６Ａの値を変化させる。DCモ
ータ５Ｂの駆動方向は可変周波数発振器２の発振
周波数を局部発振器１の発振周波数に近づく方向
に選定し、fR＝fOに合致するとDCモータ５Ｂが停
止し、その状態を維持する。 The DC motor 5B is coupled to a tuned circuit element 2A, such as a variable capacitor, of the variable frequency oscillator 2 and a tuned circuit element 6A of the high frequency amplifier 6, and changes the values of these tuned circuit elements 2A and 6A. The driving direction of the DC motor 5B is selected so that the oscillation frequency of the variable frequency oscillator 2 approaches the oscillation frequency of the local oscillator 1, and when f R =f O , the DC motor 5B stops and maintains that state.
なお可変分周器１３及び１４は局部発振器１と
可変周波数発振器２の発振周波数がバンド切替え
によつてどのような周波数に変化してもその分周
比を制御器１１によつて制御し、位相比較器３に
与える信号１５Ａ，１５Ｂの周波数が常に或る一
定の周波数範囲に入る信号となるようにするため
に設けたものである。このように可変分周器１
３，１４を設けることにより位相比較器３は常に
同一周波数領域の信号を比較すればよいから回路
常数の変更等を行うことなく、常に正しい位相比
較動作を行うことができる。 Note that the variable frequency dividers 13 and 14 have their frequency division ratios controlled by the controller 11, and the phase This is provided to ensure that the frequencies of the signals 15A and 15B applied to the comparator 3 always fall within a certain frequency range. In this way, variable frequency divider 1
By providing the phase comparator 3 and 14, the phase comparator 3 only needs to always compare signals in the same frequency range, so that it can always perform correct phase comparison operations without changing circuit constants or the like.
「実施例の動作」
或る受信状態において、その受信周波数より高
い周波数の希望周波数に受信周波数を変更するに
は入力手段１２からその希望周波数値を入力すれ
ばよい。この入力により局部発振器１は現在の発
振周波数より高い周波数に発振周波数を変更す
る。この局部発振器１の発振周波数の変更により
位相比較器３に入力される信号１５Ａ，１５Ｂの
周波数fRとfOの関係はfR＞fOとなる。"Operation of the Embodiment" In a certain receiving state, in order to change the receiving frequency to a desired frequency higher than the receiving frequency, the desired frequency value may be inputted from the input means 12. This input causes the local oscillator 1 to change the oscillation frequency to a higher frequency than the current oscillation frequency. By changing the oscillation frequency of the local oscillator 1, the relationship between the frequencies f R and f O of the signals 15A and 15B input to the phase comparator 3 becomes f R > f O.
この結果位相比較器３は第２図Ｂに示すように
負極性のパルスPbを出力し、よつて低域通過
波器４は負極性の直流電圧を出力する。この直流
電圧は増幅器５Ａによつて増幅されDCモータ５
Ｂを駆動し、可変周波数発振器２の同調回路素子
２Ａの値を変化させfR＝fOとなる方向に制御す
る。このとき高周波増幅器６の同調回路素子６Ａ
の値も変化され、受信周波数も高い周波数の側に
変更され、局部発振器１の発振周波数と可変周波
数発振器２の発振周波数が一致したときDCモー
タ５Ｂが停止し、高周波増幅器６の同調周波数は
入力手段１２から入力された周波数に設定され
る。 As a result, the phase comparator 3 outputs a pulse P b of negative polarity as shown in FIG. 2B, and the low-pass wave generator 4 outputs a DC voltage of negative polarity. This DC voltage is amplified by an amplifier 5A and the DC motor 5
B is driven to change the value of the tuned circuit element 2A of the variable frequency oscillator 2 and control it in the direction that f R =f O. At this time, the tuned circuit element 6A of the high frequency amplifier 6
The value of is also changed, the receiving frequency is also changed to a higher frequency side, and when the oscillation frequency of the local oscillator 1 and the oscillation frequency of the variable frequency oscillator 2 match, the DC motor 5B stops, and the tuning frequency of the high frequency amplifier 6 is changed to the input frequency. The frequency is set to the frequency input from the means 12.
一方受信周波数を現在の受信周波数より低い周
波数に変更した場合には、位相比較器３に入力さ
れる信号１５Ａと１５Ｂの周波数fRとfOの関係は
fR＜fOとなる。この結果位相比較器３は第２図Ａ
に示す正極性のパルスPaを出力し、このパルス
Paの平滑出力によつてDCモータ５Ｂが駆動され
fR＝fOの関係で停止する。よつてこれと連動して
高周波増幅器６の同調周波数は入力された周波数
に自動的に設定される。 On the other hand, when the receiving frequency is changed to a frequency lower than the current receiving frequency, the relationship between the frequencies f R and f O of the signals 15A and 15B input to the phase comparator 3 is
f R < f O. As a result, the phase comparator 3 is
Outputs the positive polarity pulse P a shown in
DC motor 5B is driven by the smooth output of P a .
It stops due to the relationship f R = f O. Therefore, in conjunction with this, the tuning frequency of the high frequency amplifier 6 is automatically set to the input frequency.
「発明の効果」
上述したようにこの発明によれば移相器を用い
ることなくフエイズロツクループによつて局部発
振器１の発振周波数と合致するように動作するサ
ーボ系を構成したから局部発振器１の発振周波数
をどのような周波数に設定しても、その周波数を
正確に検出し正しく合致した状態に安定させるこ
とができる。よつて高周波増幅器６の受信周波数
を希望する周波数に正確に合致した状態に自動設
定することができる。"Effects of the Invention" As described above, according to the present invention, the servo system that operates to match the oscillation frequency of the local oscillator 1 is constructed by the phase lock loop without using a phase shifter. No matter what oscillation frequency is set, the frequency can be detected accurately and stabilized to match correctly. Therefore, the receiving frequency of the high frequency amplifier 6 can be automatically set to exactly match the desired frequency.
しかもこの発明によれば位相比較器３の前段に
可変分周器１３と１４を設け、この可変分周器１
３と１４の分周比Ｉ／Ｎを局部発振器１に設定す
る発振周波数に応じて変化させ、これにより局部
発振器１の発振周波数を大きく変更し、受信周波
数を大きく変更しても可変分周器１３と１４は出
力周波数を予め決めた周波数範囲の信号に変換し
て出力するから、位相比較器３には常に同一周波
数領域の信号を入力することができる。よつて回
路常数の変更等を行うことなく、常に正しい位相
比較動作を行わせることができる利点が得られ
る。 Moreover, according to the present invention, variable frequency dividers 13 and 14 are provided before the phase comparator 3, and the variable frequency divider 1
The frequency division ratio I/N of 3 and 14 is changed according to the oscillation frequency set in the local oscillator 1, so that even if the oscillation frequency of the local oscillator 1 is changed greatly and the reception frequency is changed greatly, the variable frequency divider Since the signals 13 and 14 convert the output frequency into a signal in a predetermined frequency range and output it, the phase comparator 3 can always receive a signal in the same frequency range. Therefore, there is an advantage that a correct phase comparison operation can always be performed without changing circuit constants or the like.
また移相器を利用しないから移相器の移相量が
広い周波数にわたつて90゜を保つているように調
整しなくてよいから、製造が容易である。 Furthermore, since no phase shifter is used, there is no need to adjust the amount of phase shift of the phase shifter to maintain 90° over a wide range of frequencies, making manufacturing easy.
また「特開昭54−75920号公報」に開示された
ようにデイジタル−アナログ変換して直流化し、
その直流化した電圧を比較し、その比較出力によ
つてモータを制御するような複雑な回路構成を採
らないから安価に作ることができる。 In addition, as disclosed in ``Japanese Patent Application Laid-Open No. 54-75920'', digital-to-analog conversion is performed to convert to DC,
It can be manufactured at low cost because it does not require a complicated circuit configuration that compares the converted DC voltages and controls the motor based on the comparison output.
また「特開昭55−83331号公報」の第４図のよ
うに交互切替−充電−比較という複雑かつ時間遅
れのある回路構成によらず、この発明では分周信
号の波形をそのまま位相比較して得られる出力を
用いて、低域波して直流化しているため、デイ
ジタル−アナログ変換のような複雑な回路構成が
不要であり、また充電時間によるような遅れや交
互切替えなどの複雑な回路構成も不要である。 In addition, the present invention does not rely on a complicated circuit configuration of alternate switching-charging-comparison as shown in FIG. Since the output obtained from the battery is used to convert low-frequency waves to direct current, there is no need for complex circuit configurations such as digital-to-analog conversion, and there is no need for complex circuits such as delays and alternating switching caused by charging time. No configuration is required.
またデイジタル−アナログ変換回路の精度や、
充電回路のアンバランスなどによつて制御精度能
力が影響を受けないものを、簡便安価な構成で提
供することができる等の特徴がある。 Also, the accuracy of the digital-to-analog conversion circuit,
Features include the ability to provide a device with a simple and inexpensive configuration whose control accuracy is not affected by unbalance of the charging circuit or the like.
なお、上述では可変周波数発振器２と高周波増
幅器６の同調回路素子を可変コンデンサとし、そ
の可変コンデンサをDCモータ５Ｂによつて可変
させる構造とした場合を説明したが、可変コンデ
ンサとして電圧制御形のバリキヤツプを用い、こ
のバリキヤツプに周波数制御手段５から制御電圧
を与えて同調周波数を変化させるように構成する
こともできる。 In addition, in the above description, a case has been described in which the tuning circuit elements of the variable frequency oscillator 2 and the high frequency amplifier 6 are variable capacitors, and the structure is such that the variable capacitors are varied by the DC motor 5B. It is also possible to use a configuration in which a control voltage is applied to this varicap from the frequency control means 5 to change the tuning frequency.
第１図はこの発明の一実施例を説明するための
ブロツク図、第２図は第１図に示した実施例の動
作を説明するための波形図である。
１：局部発振器、２：可変周波数発振器、３：
位相比較器、４：低域通過波器、５：周波数制
御手段、５Ａ：増幅器、５Ｂ：DCモータ、６：
高周波増幅器、７：周波数混合器、８：中間周波
数増幅器、１１：制御器、１２：入力手段、１
３，１４：可変分周器。
FIG. 1 is a block diagram for explaining one embodiment of the present invention, and FIG. 2 is a waveform diagram for explaining the operation of the embodiment shown in FIG. 1: Local oscillator, 2: Variable frequency oscillator, 3:
Phase comparator, 4: Low pass wave generator, 5: Frequency control means, 5A: Amplifier, 5B: DC motor, 6:
High frequency amplifier, 7: Frequency mixer, 8: Intermediate frequency amplifier, 11: Controller, 12: Input means, 1
3, 14: Variable frequency divider.
Claims (1)
て発振周波数が規定される局部発振器と、高周
波増幅器の受信周波数と連動して発振周波数が
制御される可変周波数発振器とを具備し、上記
局部発振器の発振周波数と上記可変周波数発振
器の発振周波数とが互いに所定の関係を維持す
るように制御ループを構成し、この制御ループ
の制御によつて上記局部発振器に与えた設定値
に対応した周波数を受信する自動同調装置にお
いて、 Ｂ 上記制御ループは上記局部発振器の発振信号
及び上記可変周波数発振器の発振信号とを位相
比較する位相比較器と、この位相比較器の比較
出力を平滑化して取出す低域通過波器と、こ
の低域通過波器から取り出される直流化信号
によつて上記可変周波数発振器の発振周波数
と、上記高周波増幅器の受信周波数とを制御し
上記可変周波数発振器の発振周波数と上記局部
発振器に設定された発振周波数とを常に所定の
関係を維持するように制御する周波数制御手段
とによつて構成すると共に、 Ｃ 上記可変周波数発振器と位相比較器の間及び
上記局部発振器と位相比較器の間に上記局部発
振器に設定される周波数の値に応じて制御器か
ら分周数が与えられ、上記局部発振器に設定さ
れる発振周波数が大きく変わつても、常に上記
位相比較器に一定周波数の範囲に入る周波数の
信号を供給する二つの可変分周器を設けたこと
を特徴とする自動同調装置。[Scope of Claims] 1 A. Equipped with a local oscillator whose oscillation frequency is defined by a setting value inputted by an input means, and a variable frequency oscillator whose oscillation frequency is controlled in conjunction with the reception frequency of a high-frequency amplifier. A control loop is configured such that the oscillation frequency of the local oscillator and the oscillation frequency of the variable frequency oscillator maintain a predetermined relationship with each other, and the setting value given to the local oscillator is controlled by the control of this control loop. In an automatic tuning device that receives corresponding frequencies, B the control loop includes a phase comparator that compares the phases of the oscillation signal of the local oscillator and the oscillation signal of the variable frequency oscillator, and smoothes the comparison output of the phase comparator. The oscillation frequency of the variable frequency oscillator and the receiving frequency of the high frequency amplifier are controlled by a low-pass wave generator which is extracted from the low-pass wave generator, and a DC signal extracted from the low-pass wave generator. and a frequency control means for controlling the oscillation frequency set in the local oscillator so as to always maintain a predetermined relationship between the oscillation frequency and the oscillation frequency set in the local oscillator, and C. A frequency dividing number is given from the controller according to the frequency value set to the local oscillator between the phase comparators, and even if the oscillation frequency set to the local oscillator changes significantly, the frequency division number is always applied to the phase comparator. An automatic tuning device characterized in that it is provided with two variable frequency dividers that supply signals with frequencies within a fixed frequency range.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP15993984A JPS6139616A (en) | 1984-07-30 | 1984-07-30 | Automatic tuning device |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP15993984A JPS6139616A (en) | 1984-07-30 | 1984-07-30 | Automatic tuning device |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS6139616A JPS6139616A (en) | 1986-02-25 |
| JPH0342808B2 true JPH0342808B2 (en) | 1991-06-28 |
Family
ID=15704458
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP15993984A Granted JPS6139616A (en) | 1984-07-30 | 1984-07-30 | Automatic tuning device |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS6139616A (en) |
Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS5475920A (en) * | 1977-11-30 | 1979-06-18 | Sansui Electric Co | Hf stage tuning system for heterodyne receiver |
| JPS5583331A (en) * | 1978-12-20 | 1980-06-23 | Trio Kenwood Corp | Reception frequency setter of receiver |
-
1984
- 1984-07-30 JP JP15993984A patent/JPS6139616A/en active Granted
Patent Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS5475920A (en) * | 1977-11-30 | 1979-06-18 | Sansui Electric Co | Hf stage tuning system for heterodyne receiver |
| JPS5583331A (en) * | 1978-12-20 | 1980-06-23 | Trio Kenwood Corp | Reception frequency setter of receiver |
Also Published As
| Publication number | Publication date |
|---|---|
| JPS6139616A (en) | 1986-02-25 |
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