JPH03235675A - Power regenerative voltage inverter - Google Patents
Power regenerative voltage inverterInfo
- Publication number
- JPH03235675A JPH03235675A JP2030292A JP3029290A JPH03235675A JP H03235675 A JPH03235675 A JP H03235675A JP 2030292 A JP2030292 A JP 2030292A JP 3029290 A JP3029290 A JP 3029290A JP H03235675 A JPH03235675 A JP H03235675A
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- Prior art keywords
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- instantaneous
- conversion circuit
- load
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- 230000001172 regenerating effect Effects 0.000 title description 2
- 238000006243 chemical reaction Methods 0.000 claims description 57
- 230000008929 regeneration Effects 0.000 claims description 13
- 238000011069 regeneration method Methods 0.000 claims description 13
- 230000001629 suppression Effects 0.000 abstract description 11
- 238000001514 detection method Methods 0.000 abstract description 5
- 238000000034 method Methods 0.000 abstract 1
- 230000001105 regulatory effect Effects 0.000 abstract 1
- 239000003990 capacitor Substances 0.000 description 10
- 238000010586 diagram Methods 0.000 description 6
- 230000000694 effects Effects 0.000 description 2
- 230000007423 decrease Effects 0.000 description 1
- 230000002708 enhancing effect Effects 0.000 description 1
- 239000000284 extract Substances 0.000 description 1
- 230000006698 induction Effects 0.000 description 1
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Abstract
Description
【発明の詳細な説明】
Ａ、産業上の利用分野
本発明は、電源自生電圧形インバータに係り、特に誘導
機の可変速機能と電源力率を進みから遅れまで連続的に
調整可能とする調相機能とを合わせ持たせた電圧形イン
バータに関する。DETAILED DESCRIPTION OF THE INVENTION A. Field of Industrial Application The present invention relates to a self-generating voltage type inverter, and in particular to an adjustable speed function of an induction motor and an adjustment that allows continuous adjustment of the power factor from lead to lag. This invention relates to a voltage source inverter that also has a phase function.
Ｂ０発明の概要
本発明は、順変換回路に系統の高調波抑制機能を持たせ
た電源回生電圧形インバータにおいて、系統の高調波成
分を瞬時実電力で検出すると共に、相電圧から求めた瞬
時虚電力と基本波無効電力指令を加算して、逆変換回路
の直流電圧と電流から負荷への実電力を求めて瞬時実電
力に加算して順変換回路の電流指令を求めることにより
、高調波抑制効果を高めなからインバータ負荷にも安定
しｆ：、電力供給かできろと共に、力率を連続的に調整
できるようにしたものである。B0 Summary of the Invention The present invention provides a power regeneration voltage source inverter in which a forward conversion circuit has a system harmonic suppression function, which detects system harmonic components using instantaneous actual power and detects instantaneous harmonic components determined from phase voltages. Harmonics can be suppressed by adding the power and the fundamental wave reactive power command to determine the actual power to the load from the DC voltage and current of the inverse conversion circuit, and adding it to the instantaneous actual power to determine the current command of the forward conversion circuit. Because it is highly effective, it is stable even with inverter loads, and not only can it supply electric power, but it can also continuously adjust the power factor.
Ｃ１従来の技術
電圧形インバータは、順変換回路を自己消弧形デバイス
（トランジスタやＧＴ○）を用いたＰ ＷＮ１制御回路
に構成することで電源側への電力の回生を可能にする。C1 Conventional technology A voltage source inverter makes it possible to regenerate power to the power supply side by configuring the forward conversion circuit as a PWN1 control circuit using self-extinguishing devices (transistors and GT○).
第３図は電源回生電圧形インバータの回路図を示す。交
流電源１には電圧形インバータ２〜４が接続され、各イ
ンバータによって電動機５〜７を駆動する構成で示す。FIG. 3 shows a circuit diagram of a power regeneration voltage type inverter. Voltage type inverters 2 to 4 are connected to AC power source 1, and electric motors 5 to 7 are driven by each inverter.
インバータ２〜４はインバータ２に代表して示すように
、自己消弧形デバイスを主回路スイッチとする順変換回
路１１とコンデンサ１２と逆変換回路１３とを備え、交
流電源ｌとは交流リアクトル１４を通して電力授受を行
い、順変換回路１１はコンデンサ１２の直流電圧を一定
に保持するようＰＷＭ制御することで順逆両方向変換、
即ち電源回生も可能にする。搬送波除去フィルタ１５は
ＰＷＭ制御による搬送波成分の除去を行う。順変換回路
１１の制御回路１６はコンデンサ１２の直流電圧Ｅｄと
交流電源１の同期信号を検出して順変換回路１１のＰＷ
Ｍ制御を行う。As shown in the inverter 2 as a representative, the inverters 2 to 4 are equipped with a forward conversion circuit 11, a capacitor 12, and an inverse conversion circuit 13 each using a self-arc-extinguishing device as a main circuit switch, and the AC power source l is an AC reactor 14. The forward conversion circuit 11 performs forward and reverse conversion by performing PWM control to maintain the DC voltage of the capacitor 12 constant.
In other words, it also enables power regeneration. The carrier wave removal filter 15 removes the carrier wave component by PWM control. The control circuit 16 of the forward conversion circuit 11 detects the DC voltage Ed of the capacitor 12 and the synchronization signal of the AC power supply 1, and controls the PW of the forward conversion circuit 11.
Performs M control.
ここで、電圧形インバータ２に順変換回路１１が持つ電
源回生機能を利用して高調波抑制機能を持たせるには、
制御回路１６は交流電源ｌの電源ラインの負荷電流から
高調波成分を抽出し、この成分に応じた交流電流を電源
１側に供給する。Here, in order to provide the voltage source inverter 2 with a harmonic suppression function using the power regeneration function of the forward conversion circuit 11,
The control circuit 16 extracts a harmonic component from the load current of the power line of the AC power source 1, and supplies an AC current corresponding to this component to the power source 1 side.
Ｄ９発明が解決しようとする課題
従来の構成において、高調波電流を完全に補償しようと
すると、負荷の瞬時実電力の交流分によるエネルギーが
系統に接続される負荷と補償装置を往復してコンデンサ
１２の蓄積エネルギーが増減する。従って、コンデンサ
１２の電圧を一定に制御しようとすると高調波抑制効果
を低下させることになる。D9 Problems to be Solved by the Invention In the conventional configuration, when attempting to completely compensate for harmonic currents, the energy due to the alternating current portion of the instantaneous actual power of the load is transferred back and forth between the load connected to the grid and the compensator, and is transferred to the capacitor 12. The stored energy of increases or decreases. Therefore, if an attempt is made to control the voltage of the capacitor 12 to be constant, the harmonic suppression effect will be reduced.
逆に、高調波抑制効果を高めると、コンデンサの直流電
圧が大きく振動し、インバータ１３から負荷への安定し
に電力供給ができなくなる。On the other hand, if the harmonic suppression effect is increased, the DC voltage of the capacitor will greatly oscillate, making it impossible to stably supply power from the inverter 13 to the load.
また、電源電流は正弦波であっても、力率は負荷によっ
て変化し、必ずしも１００％にはならない。Further, even if the power supply current is a sine wave, the power factor changes depending on the load and is not necessarily 100%.
本発明の目的は、高調波抑制効果を高めながらインバー
タ負荷にも安定した電力供給ができると共に、力率を連
続的に調整可能な電圧形インバータを提供することにあ
る。SUMMARY OF THE INVENTION An object of the present invention is to provide a voltage source inverter that can stably supply power to an inverter load while enhancing harmonic suppression effects and that can continuously adjust the power factor.
８１課題を解決するための手段と作用
本発明は、前記目的を達成するため、自己消弧形デバイ
スを主回路スイッチとしてＰＷＭ制御により電源回生を
可能にした順変換回路と、この順変換回路から直流電力
が供給され負荷に交流電力を供給する逆変換回路と、前
記順変換回路をＰＷＭ制御する制御回路とを備えた電源
回生電圧形インバータにおいて、１ｉ７Ｊ記制御回路は
順変換回路の交流系統の負荷電流から瞬時実電力の高調
波成分を求める手段と、前記順変換回路の交流系統の相
電圧から虚電力を求めこの虚電力に基本波無効電力を加
算して力率を調整する手段と、前記逆変換回路の直流電
圧と直流電流から負荷の実電力を求める手段と、この負
荷の実電力を前記瞬時実電力の高調波成分に加算した実
電力と前記瞬時虚電力とから前記順変換回路の電流指令
を求める手段とを備え、順変換回路の交流系統の負荷電
流から瞬時実電力の高調波成分を求めて高調波抑制のた
めの検出信号とし、このうち瞬時実電力の高調波成分に
逆変換回路か負荷に供給する実電力を加算して順変換回
路の実電力制御信号とすることて瞬時電力による高調波
抑制制御に逆変換回路の負荷電力分を含ませると共に、
相電圧から求めた瞬時虚電力と基本波無効電力により力
率を調整できるＰ〜■Ｍ制御を行う。81 Means and Effects for Solving the Problems In order to achieve the above object, the present invention provides a forward conversion circuit that uses a self-arc extinguishing device as a main circuit switch to enable power regeneration through PWM control, and a forward conversion circuit that uses a self-extinguishing device as a main circuit switch to enable power regeneration through PWM control. In a power regeneration voltage type inverter that includes an inverse conversion circuit that is supplied with DC power and supplies AC power to a load, and a control circuit that performs PWM control on the forward conversion circuit, the control circuit 1i7J controls the AC system of the forward conversion circuit. means for determining harmonic components of instantaneous actual power from the load current; means for determining imaginary power from the phase voltage of the AC system of the forward conversion circuit; and adjusting the power factor by adding fundamental wave reactive power to the imaginary power; means for determining the actual power of the load from the DC voltage and DC current of the inverse conversion circuit; and the forward conversion circuit from the real power obtained by adding the real power of the load to the harmonic components of the instantaneous actual power and the instantaneous imaginary power. means for determining the current command of the instantaneous actual power from the load current of the AC system of the forward conversion circuit, and uses the harmonic component of the instantaneous actual power as a detection signal for harmonic suppression; By adding the actual power supplied from the inverse conversion circuit to the load and making it the real power control signal of the forward conversion circuit, the load power of the inverse conversion circuit is included in the harmonic suppression control using instantaneous power.
P~M control is performed that can adjust the power factor using the instantaneous imaginary power and fundamental wave reactive power obtained from the phase voltages.
Ｆ、実施例
以下に本発明の実施例を第１図〜第２図を参照しながら
説明する。F. EXAMPLE An example of the present invention will be described below with reference to FIGS. 1 and 2.
第２図は本発明の実施例による全体構成図を示し、第３
図のものと同−又は相当部分には同一符号が付されてい
る。第２図において、１６Ａは順変換部制御回路、１７
はヘースドライブ回路、１８は逆変換部制御回路である
。FIG. 2 shows an overall configuration diagram according to an embodiment of the present invention, and FIG.
The same or corresponding parts as those in the figures are given the same reference numerals. In FIG. 2, 16A is a forward conversion unit control circuit;
1 is a Hayes drive circuit, and 18 is an inverse conversion unit control circuit.
第１図は本発明の一実施例を示す制御回路図である。３
相／２相変換部２１は、系統の３相負荷電流ＩＬ：、Ｉ
５２．Ｉｗを直交α−β座標上の２１目電流■。、Ｉｓ
に変換する。FIG. 1 is a control circuit diagram showing one embodiment of the present invention. 3
The phase/two-phase converter 21 converts the three-phase load current IL:, I
52. Iw is the 21st current on the orthogonal α-β coordinate. ,Is
Convert to
同様に、３相／２相変換部２２は、系統の相電圧Ｅｕ、
Ｅｖ、 Ｅｗを直交α−β座標上の２相電圧Ｅ、、Ｅ
、に変換する。Similarly, the three-phase/two-phase converter 22 converts the system phase voltage Eu,
Ev, Ew are two-phase voltages E, , E on orthogonal α-β coordinates
, convert to
）
上述の２相電流１．、Ｉ、と２相電圧Ｅ、、Ｅ６とはα
−β座標軸上の瞬時ベクトルとして取り扱え、瞬時電力
はＥ、２．Ｉ−、Ｅｓ、Ｉｎのスカラ積で表される。従
って、瞬時電力演算部２３は２相電圧と電流のスカラ積
の和として瞬時実電力Ｐと瞬時虚電力ｑを求める。) The above two-phase current 1. , I, and the two-phase voltage E, , E6 are α
It can be treated as an instantaneous vector on the −β coordinate axis, and the instantaneous power is E, 2. It is expressed as a scalar product of I-, Es, and In. Therefore, the instantaneous power calculation unit 23 calculates the instantaneous real power P and the instantaneous imaginary power q as the sum of the scalar products of the two-phase voltage and current.
ところで、瞬時実電力Ｐ、虚電力Ｑを直流分と交流分に
分離すると、
−二
Ｑ＝Ｑ＋Ｑ
（４）式のＰ（交流分）とＱ（交流分）は高調波瞬時電
力を表しており、高調波補償対象となる。By the way, when instantaneous real power P and imaginary power Q are separated into DC and AC components, -2Q=Q+Q (4) P (AC component) and Q (AC component) represent harmonic instantaneous power. , subject to harmonic compensation.
交流分演算部２４はローパスフィルタと加算器によって
バイパスフィルタ機能を持ち、瞬時実電力Ｐから夫々の
交流分（高調波瞬時電力）Ｐｈを求める。The AC component calculation unit 24 has a bypass filter function using a low-pass filter and an adder, and calculates each AC component (harmonic instantaneous power) Ph from the instantaneous actual power P.
基本波無効電力をも補償して力率を調整するために、全
ての瞬時虚電力Ｑ（基本波に起因するもの十高調波に起
因するもの）と、瞬時実電力Ｐを補償対象とする。In order to adjust the power factor by also compensating for the fundamental wave reactive power, all instantaneous imaginary powers Q (attributable to the fundamental wave and those attributable to ten harmonics) and instantaneous real power P are subject to compensation.
従って、瞬時虚電力においては、ＱとＱを分離する必要
がなくなり、補償対象抽出のフィルタも不要になる。そ
れ故、第１図では瞬時実電力部分のみフィルタを用いた
構成となっている。Therefore, in the instantaneous imaginary power, there is no need to separate Q and Q, and a filter for extracting the compensation target is also no longer necessary. Therefore, in FIG. 1, a filter is used only for the instantaneous actual power portion.
すなわち、電流指令部２５においては、基本波成分の無
効電力指令Ｑ”（直流分）を補償対象に与えろことで、
任意の進み電流・遅れ電流指令か与えられる。That is, in the current command unit 25, by giving the reactive power command Q" (DC component) of the fundamental wave component to the compensation target,
An arbitrary lead current/lag current command can be given.
補償対象となる高調波に起因する瞬時実電力Ｐと、全て
の瞬時虚電力Ｑが求まったのて、電流措置演算部２６：
よ瞬時電力Ｐｈ、ｑｈと相電圧Ｅ１゜Ｅ １１から直交
α−β叱標」二の瞬時電流１９１．■。After the instantaneous real power P caused by the harmonics to be compensated and all the instantaneous imaginary powers Q are determined, the current measure calculation unit 26:
From the instantaneous power Ph, qh and the phase voltage E1゜E11 orthogonal α-β, the second instantaneous current 191. ■.
を求める。seek.
、＋、ｌ霞 Ｌ Ｅ ａ Ｅ ＩＩＪ Ｉ Ｑ ｈ
」２相／３相変換部２７は、２相隣時電ゐＩ。,+,l Kasumi L E a E IIJ I Q h
The 2-phase/3-phase converter 27 converts the 2-phase adjacent power I.
Ｉ〆を３相隣時電流１ ｃａ ＋ Ｉ ｔｂ ＋
Ｉ ＣＱ′に変換して３相隣時電流での補償電流指令値
を求める。I〆 is the current when three phases are adjacent 1 ca + I tb +
Convert to I CQ' to obtain the compensation current command value for the three-phase adjacent current.
ＰＷＭ制御ｇ！Ｉ２８は、３相隣時電流ＩｃａＴｃｂ［
ｃどと補償電流の検出信号ＩＲ，Ｉｓ、 ＩＴとを突
き合わせ、コンパ１ノータによる搬送波との比較方式で
ＰＷ：〜１波形のゲート信号を得、このケート信号によ
り順変換回路１１の自己消弧素子をスイッチング制御す
る、
上述までの構成により、系統負荷電流に含まれろ高調波
成分を順変換回路１１から補償する電流として交流電源
ｌ側に供給する。PWM control g! I28 is the three-phase adjacent current IcaTcb [
C and the compensation current detection signals IR, Is, and IT are compared with the carrier wave using a comparator 1 notator to obtain a PW:~1 waveform gate signal, and this gate signal causes the forward conversion circuit 11 to self-extinguish. With the above-described configuration that controls the switching of the elements, the forward conversion circuit 11 supplies the harmonic components included in the system load current to the AC power supply l side as a current that compensates for them.
ここで、瞬時実電力Ｐｈには逆変換回路１３が電動機５
に供給する実電力Ｐ１．を加算してＮ？Ｍ指令演算部２
６に供給する。この実電力ＰＬはコンデンサ１２の電圧
Ｅ、と逆変換回路１３の直流電流Ｉ、の夫々の検出信号
を乗算することで直流負荷を求め、必要に応じてフィル
タによる一次遅れを持って実電力演算部２９によって求
められる。Here, for the instantaneous actual power Ph, the inverse conversion circuit 13
Actual power supplied to P1. Add N? M command calculation section 2
Supply to 6. This actual power PL is obtained by multiplying the detection signals of the voltage E of the capacitor 12 and the DC current I of the inverse conversion circuit 13 to obtain the DC load, and if necessary, calculates the actual power with a first-order delay due to a filter. 29.
また、瞬時実電力Ｐｈには順変換回路１１のスイッチン
グロス等のロス分を補償するロス電力Ｐ（！を加算して
いる。このロス電力ＰＣはコンデンサ電圧Ｅ４の検出信
号とコンデンサ１２の直流電圧指令Ｅｄ″との突き合わ
せで電圧制御回路３０から求める。In addition, a loss power P (!) is added to the instantaneous actual power Ph to compensate for losses such as switching loss of the forward conversion circuit 11. This loss power PC is the detection signal of the capacitor voltage E4 and the DC voltage of the capacitor 12. It is obtained from the voltage control circuit 30 by comparing it with the command Ed''.
本実施例によれば、系統負荷電流から瞬時実電力Ｐと瞬
時虚電力ｑを求め、瞬時実電力Ｐから高調波瞬時実電力
Ｐｈを求めると共に、瞬時虚電力ｑに基本波無効電力指
令Ｑ４を加算することにより虚電力ｑｈを求める。この
うち実電力Ｐｈには逆変換回路１３が負荷（５）に供給
する実電力ＰＬ支び順変換回路１１の変換ロス分ＰＣを
加えて順変換回路１１の瞬時実電力Ｐの制御信号とし、
この実電力Ｐと瞬時虚電力ｑ７から電流指令に変換し、
さらに２相／３相変換と電流フィードバック制御によっ
てＰＷＭ制御信号を得る。According to this embodiment, instantaneous real power P and instantaneous imaginary power q are determined from the grid load current, harmonic instantaneous actual power Ph is determined from instantaneous actual power P, and fundamental wave reactive power command Q4 is applied to instantaneous imaginary power q. The imaginary power qh is obtained by adding. Of these, to the actual power Ph, the real power PL supplied by the inverse conversion circuit 13 to the load (5) and the conversion loss PC of the forward conversion circuit 11 are added to form a control signal for the instantaneous actual power P of the forward conversion circuit 11,
Convert this real power P and instantaneous imaginary power q7 into a current command,
Furthermore, a PWM control signal is obtained by 2-phase/3-phase conversion and current feedback control.
従って、高調波抑制のためには瞬時実電力と虚電力から
高調渡分を求めて順変換回路１１への電流指令を求め、
この電流指令に逆変換回路１３の負荷実電力を加えて順
変換回路１１への電流指令を求めるため、高調波抑制機
能を低下させることなく逆変換回路の負荷にも安定した
電力供給を行うことができる。また、逆変換回路１３の
負荷に供給するべき電力を直流電圧と直流電流のみから
求めるため実電力演算部２つを簡単化する。さらに、逆
変換回路１３の実電力を高調波抑制のにめの高調波実電
力Ｐｈに加算して、順変換回路１１の電力制御になるた
め、逆変換回路１３がら負荷に供給する電力は力率１に
なるし、同様に回生運転時も力率１に制御される。Therefore, in order to suppress harmonics, the harmonic component is determined from the instantaneous real power and the imaginary power, and the current command to the forward conversion circuit 11 is determined.
Since the current command to the forward conversion circuit 11 is obtained by adding the load actual power of the inverse conversion circuit 13 to this current command, stable power can be supplied to the load of the inverse conversion circuit without reducing the harmonic suppression function. I can do it. Furthermore, since the power to be supplied to the load of the inverse conversion circuit 13 is determined from only the DC voltage and DC current, the two actual power calculation units are simplified. Furthermore, since the power of the forward conversion circuit 11 is controlled by adding the actual power of the inverse conversion circuit 13 to the harmonic actual power Ph for harmonic suppression, the power supplied to the load from the inverse conversion circuit 13 is The power factor becomes 1, and the power factor is similarly controlled to 1 during regenerative operation.
また、高調波成分を補償する二とて電源電流は正弦波に
ζす、さろに基本波無効電流を補償することによって基
本波電流の位相を力率１に制御できる。Further, by compensating for harmonic components, the power supply current becomes a sine wave, and by compensating for the fundamental reactive current, the phase of the fundamental current can be controlled to a power factor of 1.
このように、全ての瞬時電力を補償対象とするので、フ
ィルタによって補償対象を抽出することなく、瞬時虚電
力成分に基本波無効電力指令（直流分）を加えることて
任意の基本波無効電流の補償ができ、結果として連続的
な力率の調整が可能である。In this way, since all instantaneous power is subject to compensation, any fundamental reactive current can be calculated by adding the fundamental wave reactive power command (DC component) to the instantaneous imaginary power component without extracting the compensation subject using a filter. compensation, resulting in continuous power factor adjustment.
Ｇ４発明の効果
以上のとおり、本発明によれば、電源回生機能を持つ順
変換回路のＰＷＭ制御に、系統負荷電流から求めた瞬時
電力の高調波成分に逆変換回路から負荷に供給する実電
力を瞬時実電力に加えておく几め、系統の高調波抑制効
果を高めながら逆変換回路の負荷にも安定かつ力率ｌに
しｆ：電力供給つ・できろ。また、逆変換回路の実電力
は直流電流と電圧から求めるため、回路構成を簡単化す
る。Effects of the G4 Invention As described above, according to the present invention, in PWM control of a forward conversion circuit having a power regeneration function, harmonic components of instantaneous power obtained from the grid load current are converted to actual power supplied to the load from an inverse conversion circuit. By adding this to the instantaneous actual power, it is possible to increase the harmonic suppression effect of the grid while maintaining stability and power factor l for the load of the inversion circuit. Furthermore, since the actual power of the inverse conversion circuit is determined from DC current and voltage, the circuit configuration is simplified.
まｆ二、可変速装置として機能する１こけてなく、電力
系統の電源力率を調整できるので力率調整用の進相コン
デンサ、位（目制御リアクトル等か不要こなり、回路構
成が簡単になると共に、負荷を運転していないときでも
、順変換部のみ動作させることで電源力率を連続的に調
整できるので、高性能にして信頼性が向上する。Second, it functions as a variable speed device, and since it can adjust the power factor of the power supply system, there is no need for phase advance capacitors, phase control reactors, etc. for power factor adjustment, and the circuit configuration is simple. In addition, even when the load is not operating, the power factor of the power source can be adjusted continuously by operating only the forward conversion section, resulting in high performance and improved reliability.
第１図は本発明の一実施例を示す制御回路図、第２図は
本発明の実施例による電源回生電圧形インバータの全体
構成図、第３図は従来の電源回生電圧形インバータの回
路図である。
ｌｌ 順変換回路、１３・・・逆変換回路、２３・・瞬
時電力演算部、２４ 交流分演算部、２５・電流指令部
、２６・・電流指令演算部、２９・・実電力演算部、３
０・・・電圧制御回路。Fig. 1 is a control circuit diagram showing an embodiment of the present invention, Fig. 2 is an overall configuration diagram of a power regeneration voltage type inverter according to an embodiment of the present invention, and Fig. 3 is a circuit diagram of a conventional power regeneration voltage type inverter. It is. ll Forward conversion circuit, 13... Inverse conversion circuit, 23... Instantaneous power calculation section, 24 AC component calculation section, 25. Current command section, 26. Current command calculation section, 29.. Actual power calculation section, 3
0...Voltage control circuit.
Claims (1)
Ｍ制御により電源回生を可能にした順変換回路と、この
順変換回路から直流電力が供給され負荷に交流電力を供
給する逆変換回路と、前記順変換回路をＰＷＭ制御する
制御回路とを備えた電源回生電圧形インバータにおいて
、前記制御回路は順変換回路の交流系統の負荷電流から
瞬時実電力の高調波成分を求める手段と、前記順変換回
路の交流系統の相電圧から虚電力を求めこの虚電力に基
本波無効電力を加算して力率を調整する手段と、前記逆
変換回路の直流電圧と直流電流から負荷の実電力を求め
る手段と、この負荷の実電力を前記瞬時実電力の高調波
成分に加算した実電力と前記瞬時虚電力とから前記順変
換回路の電流指令を求める手段とを備えたことを特徴と
する電源回生電圧形インバータ。(1) PW using a self-extinguishing device as the main circuit switch
A forward conversion circuit that enables power regeneration through M control, an inverse conversion circuit that receives DC power from the forward conversion circuit and supplies AC power to a load, and a control circuit that performs PWM control on the forward conversion circuit. In the power regeneration voltage type inverter, the control circuit includes means for determining harmonic components of instantaneous actual power from the load current of the AC system of the forward conversion circuit, and means for determining the imaginary power from the phase voltage of the AC system of the forward conversion circuit. means for adjusting the power factor by adding fundamental wave reactive power to the electric power; means for determining the actual power of the load from the DC voltage and DC current of the inverse conversion circuit; A power regeneration voltage type inverter comprising means for determining a current command for the forward conversion circuit from the real power added to the wave component and the instantaneous imaginary power.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2030292A JP2990723B2 (en) | 1990-02-09 | 1990-02-09 | Power regeneration voltage type inverter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2030292A JP2990723B2 (en) | 1990-02-09 | 1990-02-09 | Power regeneration voltage type inverter |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPH03235675A true JPH03235675A (en) | 1991-10-21 |
| JP2990723B2 JP2990723B2 (en) | 1999-12-13 |
Family
ID=12299656
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP2030292A Expired - Fee Related JP2990723B2 (en) | 1990-02-09 | 1990-02-09 | Power regeneration voltage type inverter |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JP2990723B2 (en) |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2005304156A (en) * | 2004-04-09 | 2005-10-27 | Toshiba Corp | Power converter |
| CN112136271A (en) * | 2018-04-19 | 2020-12-25 | Abb瑞士股份有限公司 | System and method for power conversion |
-
1990
- 1990-02-09 JP JP2030292A patent/JP2990723B2/en not_active Expired - Fee Related
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2005304156A (en) * | 2004-04-09 | 2005-10-27 | Toshiba Corp | Power converter |
| CN112136271A (en) * | 2018-04-19 | 2020-12-25 | Abb瑞士股份有限公司 | System and method for power conversion |
Also Published As
| Publication number | Publication date |
|---|---|
| JP2990723B2 (en) | 1999-12-13 |
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