JPH02211748A - Orthogonal modulation circuit - Google Patents
Orthogonal modulation circuitInfo
- Publication number
- JPH02211748A JPH02211748A JP1032154A JP3215489A JPH02211748A JP H02211748 A JPH02211748 A JP H02211748A JP 1032154 A JP1032154 A JP 1032154A JP 3215489 A JP3215489 A JP 3215489A JP H02211748 A JPH02211748 A JP H02211748A
- Authority
- JP
- Japan
- Prior art keywords
- phase
- modulation
- branching filter
- circuit
- phase shifter
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
- 230000010363 phase shift Effects 0.000 claims description 6
- 239000000969 carrier Substances 0.000 abstract description 6
- 238000006243 chemical reaction Methods 0.000 description 6
- 238000010586 diagram Methods 0.000 description 6
- 238000004891 communication Methods 0.000 description 1
- 238000005516 engineering process Methods 0.000 description 1
- 239000000284 extract Substances 0.000 description 1
- 238000000034 method Methods 0.000 description 1
Landscapes
- Amplitude Modulation (AREA)
- Digital Transmission Methods That Use Modulated Carrier Waves (AREA)
Abstract
Description
【発明の詳細な説明】
〔産業上の利用分野〕
本発明は直交変調回路に関し、特にディジタル通信用変
調器に用いられる直交変調回路に関する。DETAILED DESCRIPTION OF THE INVENTION [Field of Industrial Application] The present invention relates to a quadrature modulation circuit, and particularly to a quadrature modulation circuit used in a modulator for digital communication.
従来の直交変調回路の一つとして、第２図のブロック図
に示すようなダブルコンバージョン方式の変調回路があ
る。即ち、第１０−カル信号ｆ１を分波器６で分波し、
一方を第１ミキサ３でベースバンド第１入力１と混合す
る。また、他方はπ／２移相器９Ａで移相し、第２ミキ
サ４でベースバンド第２入力２と混合する。そして、各
ミキサ３．４の出力を合成器１２で合成し、これを第３
ミキサ１４により第２０−カルｆ２と混合し、帯域通過
フィルタ１５を通して直交変調信号１３を得ている。One of the conventional orthogonal modulation circuits is a double conversion type modulation circuit as shown in the block diagram of FIG. That is, the 10th-cal signal f1 is demultiplexed by the demultiplexer 6,
One is mixed with the baseband first input 1 by the first mixer 3. Further, the other signal is phase-shifted by the π/2 phase shifter 9A, and mixed with the baseband second input 2 by the second mixer 4. Then, the outputs of each mixer 3.4 are combined by a combiner 12, and this is combined by a third
It is mixed with the 20th-cal f2 by a mixer 14 and passed through a bandpass filter 15 to obtain an orthogonal modulation signal 13.
この回路では、第１０−カルｆ１で先ず直交変調を正確
に行い、その後第２０−カルｆ２により広帯域周波数変
換を行っている。In this circuit, the 10th cal f1 first performs orthogonal modulation accurately, and then the 20th cal f2 performs wideband frequency conversion.
また、第３図のブロック図に示すような直接変調方式変
調回路もある。即ち、第２図のπ／２移相界９Ａに代え
て、可変π／２移相器９を用い、これを記憶素子１６及
びＤ／Ａ変換器１７で制御させてキャリア５の一方の分
波の移相を行っている。また、直交変調信号１３は合成
器１２から得ている。There is also a direct modulation type modulation circuit as shown in the block diagram of FIG. That is, a variable π/2 phase shifter 9 is used in place of the π/2 phase shift field 9A in FIG. The phase of the wave is shifted. Further, the orthogonal modulation signal 13 is obtained from the combiner 12.
この回路では、互いにπ／２の位相差でなくてはならな
い変調信号Ｐ”、Ｑ“の広帯域位相誤差を予め測定して
おき、この位相誤差情報を記憶素子１６に記憶させ、任
意のキャリア周波数で任意の位相誤差情報をディジタル
信号で取り出し、このディジタル信号をＤ／Ａ変換器１
７でＤ／Ａ変換し、この変換された信号により可変π／
２移相器９を制御し正確な広帯域直交変調信号を得てい
る。In this circuit, the broadband phase error of the modulation signals P'' and Q'', which must have a phase difference of π/2 from each other, is measured in advance, this phase error information is stored in the storage element 16, and an arbitrary carrier frequency is stored. extracts arbitrary phase error information as a digital signal, and sends this digital signal to the D/A converter 1.
7 performs D/A conversion, and this converted signal allows variable π/
2 phase shifter 9 is controlled to obtain an accurate broadband orthogonal modulation signal.
（発明が解決しようとする課題〕
上述した従来の変調回路のうち、第２図のダブルコンバ
ージョン方式では、不要波を取り除くために帯域通過フ
ィルタ１５が必要であり、また第１及び第２０−カルを
２種類必要とし、回路構成が複雑化し、かつコスト高に
なるという問題がある。(Problems to be Solved by the Invention) Among the conventional modulation circuits described above, the double conversion method shown in FIG. 2 requires a bandpass filter 15 to remove unnecessary waves, and There are problems in that two types of circuits are required, which complicates the circuit configuration and increases costs.
また、第３図の変調回路では、広帯域位相誤差情報を予
め測定しておかなければならず、また位相誤差情報を記
憶素子１６に記憶させて使用するので、経時変化により
変調器の構成素子が変化した場合に正確に直交変調でき
なくなるという問題がある。Furthermore, in the modulation circuit shown in FIG. 3, broadband phase error information must be measured in advance, and the phase error information is stored in the storage element 16 for use, so the components of the modulator may deteriorate over time. There is a problem in that if there is a change, accurate orthogonal modulation cannot be performed.
本発明は上述した問題を同時に解消した直交変調回路を
提供することを目的とする。An object of the present invention is to provide a quadrature modulation circuit that simultaneously solves the above-mentioned problems.
本発明の直交変調回路は、２列のベースバンド入力によ
り直接変調を行う直接変調方式の変調回路において、第
１分波器によって２分された２列のキャリアを更に２分
波する第２及び第３の分波器と、これら分波器の各分波
を位相比較する位相比較器と、この位相比較器の出力を
増幅する直流増幅器とを備え、この直流増幅器の出力に
より可変π／２移相器の位相制御を行っている。The orthogonal modulation circuit of the present invention is a direct modulation type modulation circuit that performs direct modulation using two rows of baseband inputs, and the second and second rows of carriers, which are divided into two by a first branching filter, are further divided into two. It is equipped with a third branching filter, a phase comparator that compares the phases of each branched wave of these branching filters, and a DC amplifier that amplifies the output of this phase comparator. Performs phase control of the phase shifter.
上述した構成では、π／２移相器の位相を夫々分波され
た信号の位相比較結果に基づいて行っているので、キャ
リアが広帯域に変化しても正確な直交変調が実現できる
。In the above-described configuration, since the phase of the π/2 phase shifter is determined based on the phase comparison result of each demultiplexed signal, accurate orthogonal modulation can be realized even if the carrier changes over a wide band.
次に、本発明を図面を参照して説明する。 Next, the present invention will be explained with reference to the drawings.
第１図は本発明の一実施例のブロック図である。FIG. 1 is a block diagram of one embodiment of the present invention.
図において、キャリア５は第１分波器６においてａ、ｂ
の２つに分波される。一方の分波ａは第２分波器７によ
り更にｃ、ｄと２つに分波される。In the figure, the carrier 5 is a, b in the first branching filter 6.
It is split into two waves. One branched wave a is further branched into two, c and d, by the second branching filter 7.
また、他方の分波すは、外部の制御信号により移相補正
が可能な可変π／２移相器９を通過された後、第３分波
器８においてｅ、ｆの２つに分波される。The other demultiplexer passes through a variable π/2 phase shifter 9 whose phase can be corrected by an external control signal, and then is demultiplexed into two, e and f, by a third demultiplexer 8. be done.
前記第２分波器７の出力ｄと前記第３分波器８の出力ｆ
は共に位相比較器ＩＯに入力されて位相比較が行われる
。この位相比較器１０は正弦特性を有し、π／２からの
誤差に比例した誤差信号を発生し、この誤差信号は直流
増幅器１１に入力され、それが直流増幅されてπ／２可
変移相回路８の制御信号となり、π／２可変移相回路８
の移相量が正確にπ／２となるように自動制御が行われ
る。Output d of the second branching filter 7 and output f of the third branching filter 8
are both input to the phase comparator IO to perform phase comparison. This phase comparator 10 has a sine characteristic and generates an error signal proportional to the error from π/2, and this error signal is input to a DC amplifier 11, where it is DC amplified and a variable phase shift of π/2 is performed. It becomes a control signal for the circuit 8, and the π/2 variable phase shift circuit 8
Automatic control is performed so that the amount of phase shift is exactly π/2.
このとき、第２分波器７から第１ミキサ３までの信号路
長と第３分波器８から第２ミキサ４までの信号路長が等
しくなるように、また第２分波器７から位相比較器１０
までの信号路長と第３分波器８から位相比較器１０まで
の信号路長が等しくなるように回路設計を行えば、上述
した負帰還制御により可変π／２移相器９の経時変動は
自動的に補正される。At this time, the signal path length from the second splitter 7 to the first mixer 3 is made equal to the signal path length from the third splitter 8 to the second mixer 4. Phase comparator 10
If the circuit is designed so that the signal path length from the third branching filter 8 to the phase comparator 10 is equal to is automatically corrected.
一方、第２分波器５の出力Ｃは第１ミキサ３においてベ
ースバンド第１入力１で振幅変調され、第３分波器の出
力ｅは第２ミキサ４においてベースバンド第２入力２で
振幅変調される。そして、第１ミキサ３及び第２ミキサ
４の出力を合成器１２で合成することにより、合成器出
力に正確な直交変調信号１３を得ることができる。On the other hand, the output C of the second branching filter 5 is amplitude modulated by the baseband first input 1 in the first mixer 3, and the output e of the third branching filter is amplitude modulated by the baseband second input 2 in the second mixer 4. Modulated. Then, by combining the outputs of the first mixer 3 and the second mixer 4 in the combiner 12, an accurate orthogonal modulation signal 13 can be obtained as the combiner output.
したがって、この構成では第２図に示した従来のダブル
コンバージョン方式の回路に比較して第２０−カル、第
３ミキサ、帯域通過フィルタ等を不要にし、回路構成を
節単にして小型化を図り、かつ低コスト化が可能となる
。Therefore, compared to the conventional double-conversion circuit shown in Figure 2, this configuration eliminates the need for a 20th cal, a 3rd mixer, a bandpass filter, etc., making the circuit configuration simpler and more compact. , and enables cost reduction.
また、第３図に示した直接変調方式の回路に比較して、
変調信号の位相誤差を予め測定してこれを記憶素子に記
憶させておく必要がないとともに、経時変化等によって
変調器の構成素子が変化した場合でもその影響を受ける
ことなく正確な直交変調を行うことができる。Also, compared to the direct modulation circuit shown in Figure 3,
There is no need to measure the phase error of the modulation signal in advance and store it in a storage element, and even if the components of the modulator change due to changes over time, accurate quadrature modulation can be performed without being affected. be able to.
なお、本発明の直交変調はディジタル変調のみでなく、
ＡＣ３５Ｂ変調等のアナログ変調にも応用可能である。Note that the orthogonal modulation of the present invention is not limited to digital modulation.
It is also applicable to analog modulation such as AC35B modulation.
以上説明したように本発明は、２列のベースバンド入力
により直接変調を行う直接変調方式の変調回路に、２列
のキャリアから分波された信号を位相比較して可変π／
２移相器の位相制御を行なう回路を付設しているので、
キャリアが広帯域に変化しても正確な直交変調を行うこ
とができ、従来に比較して回路構成が簡単になり、回路
装置の小型化、及び低コスト化が実現できる。また、位
相誤差を予め測定する手間が不要であるとともに、経時
変化によっても正確な変調を安定して行うことができる
効果がある。As explained above, the present invention provides a direct modulation type modulation circuit that performs direct modulation using two columns of baseband inputs, and compares the phases of signals demultiplexed from two columns of carriers to provide a variable π/
Since it is equipped with a circuit to control the phase of the 2 phase shifter,
Accurate orthogonal modulation can be performed even when the carrier changes to a wide band, the circuit configuration is simpler than the conventional one, and the circuit device can be made smaller and lower in cost. Further, there is an effect that there is no need to take the trouble of measuring the phase error in advance, and that accurate modulation can be stably performed even with changes over time.
第１図は本発明の一実施例のブロック図、第２図は従来
のダブルコンバージョン方式の直交変調器のブロック図
、第３図は従来の直接変調方式直交変調器のブロック図
である。
１・・・ベースバンド第１入力、２・・・ベースバンド
第２入力、３・・・第１ミキサ、４・・・第２ミキサ、
５・・・キャリア、６・・・第１分波器、７・・・第２
分波器、８・・・第３分波器、９・・・可変π／２移相
器、９Ａ・・・π／２移相器、１０・・・移相比較器、
１１・・・直流増幅器、１２・・・合成器、１３・・・
直交変調信号、１４・・・第３ミキサ、１５・・・帯域
通過フィルタ、１６・・・記憶素子、１７・・・Ｄ／Ａ
変換器。FIG. 1 is a block diagram of an embodiment of the present invention, FIG. 2 is a block diagram of a conventional double conversion quadrature modulator, and FIG. 3 is a block diagram of a conventional direct modulation quadrature modulator. 1... Baseband first input, 2... Baseband second input, 3... First mixer, 4... Second mixer,
5...Carrier, 6...First branching filter, 7...Second
Branching filter, 8... Third branching filter, 9... Variable π/2 phase shifter, 9A... π/2 phase shifter, 10... Phase shift comparator,
11... DC amplifier, 12... Combiner, 13...
Quadrature modulation signal, 14...Third mixer, 15...Band pass filter, 16...Storage element, 17...D/A
converter.
Claims (1)
器の一方の分波を更に２分波する第２分波器と、前記第
１分波器の他方の分波を外部の制御信号により移相補正
する可変π／２移相器と、この移相器の出力を更に２分
波する第３分波器と、前記第２分波器の一方の分波をベ
ースバンド第１入力により振幅変調する第１ミキサと、
前記第３分波器の一方の分波をベースバンド第２入力に
より振幅変調する第２ミキサと、前記第１及び第２ミキ
サの各出力を合成する合成器と、前記第２分波器の他方
の分波と第３分波器の他方の分波の位相を比較する位相
比較器と、この位相比較器の出力を増幅して前記可変π
／２移相器に制御信号として出力する直流増幅器とを備
えることを特徴とする直交変調回路。1. A first branching filter that splits the carrier into two, a second branching filter that further splits one branch of this first branching filter into two, and the other branching of the first branching filter. a variable π/2 phase shifter that corrects the phase shift by an external control signal; a third branching filter that further splits the output of this phase shifter into two; and a third splitter that splits the output of the phase shifter into two parts; a first mixer that performs amplitude modulation using a first baseband input;
a second mixer that amplitude-modulates one branched wave of the third branching filter using a second baseband input; a synthesizer that synthesizes each output of the first and second mixers; and a synthesizer of the second branching filter. a phase comparator that compares the phase of the other branched wave with that of the other branched wave of the third branching filter;
1. A quadrature modulation circuit comprising: a DC amplifier that outputs a control signal to a /2 phase shifter.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP1032154A JPH02211748A (en) | 1989-02-10 | 1989-02-10 | Orthogonal modulation circuit |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP1032154A JPH02211748A (en) | 1989-02-10 | 1989-02-10 | Orthogonal modulation circuit |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| JPH02211748A true JPH02211748A (en) | 1990-08-23 |
Family
ID=12351002
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP1032154A Pending JPH02211748A (en) | 1989-02-10 | 1989-02-10 | Orthogonal modulation circuit |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPH02211748A (en) |
Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS5851602A (en) * | 1981-09-22 | 1983-03-26 | Fujitsu Ltd | Orthogonal modulation circuit |
| JPS6030654B2 (en) * | 1980-12-31 | 1985-07-17 | 株式会社林原生物化学研究所 | Method for producing human colony stimulating factor |
| JPS61238144A (en) * | 1985-04-15 | 1986-10-23 | Nippon Telegr & Teleph Corp <Ntt> | Phase adjustment circuit |
| JPS63121347A (en) * | 1986-11-10 | 1988-05-25 | Nec Corp | Four-phase quadrature modulator |
-
1989
- 1989-02-10 JP JP1032154A patent/JPH02211748A/en active Pending
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS6030654B2 (en) * | 1980-12-31 | 1985-07-17 | 株式会社林原生物化学研究所 | Method for producing human colony stimulating factor |
| JPS5851602A (en) * | 1981-09-22 | 1983-03-26 | Fujitsu Ltd | Orthogonal modulation circuit |
| JPS61238144A (en) * | 1985-04-15 | 1986-10-23 | Nippon Telegr & Teleph Corp <Ntt> | Phase adjustment circuit |
| JPS63121347A (en) * | 1986-11-10 | 1988-05-25 | Nec Corp | Four-phase quadrature modulator |
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