JPH0153836B2 - - Google Patents
Info
- Publication number
- JPH0153836B2 JPH0153836B2 JP3374683A JP3374683A JPH0153836B2 JP H0153836 B2 JPH0153836 B2 JP H0153836B2 JP 3374683 A JP3374683 A JP 3374683A JP 3374683 A JP3374683 A JP 3374683A JP H0153836 B2 JPH0153836 B2 JP H0153836B2
- Authority
- JP
- Japan
- Prior art keywords
- current
- terminal
- mirror circuit
- operational amplifier
- voltage conversion
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
Links
- 238000006243 chemical reaction Methods 0.000 claims description 28
- 238000010586 diagram Methods 0.000 description 2
- 238000004804 winding Methods 0.000 description 2
- 230000003321 amplification Effects 0.000 description 1
- 230000010354 integration Effects 0.000 description 1
- 238000003199 nucleic acid amplification method Methods 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04M—TELEPHONIC COMMUNICATION
- H04M19/00—Current supply arrangements for telephone systems
- H04M19/001—Current supply source at the exchanger providing current to substations
- H04M19/005—Feeding arrangements without the use of line transformers
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Signal Processing (AREA)
- Amplifiers (AREA)
- Devices For Supply Of Signal Current (AREA)
- Interface Circuits In Exchanges (AREA)
Description
【発明の詳細な説明】
（技術分野）
本発明は、加入者回路用給電回路に用いて、回
路のハード量を減らし、集積化に適する不平衡・
平衡回路に関するものである。Detailed Description of the Invention (Technical Field) The present invention provides an unbalanced and
It concerns a balanced circuit.
（従来技術）
従来の加入者回路は、第１図に示すように電磁
部品で構成されており、音声等の交流信号の不平
衡・平衡変換はトランスT1を介して行なわれ、
不平衡信号Vsは、２線側Ａ，Ｂに平衡信号とし
て、加入者端末TELに送出される。これと同時
に、給電電流は、直流抵抗Ra、トランス巻線La
を介して加入者端末TELに流れ、さらにトラン
ス巻線Lb、直流抵抗Rbのルートで電池Vbbに流れ
込み、加入者端末に給電を行なつていた。従つ
て、変換トランスT1には給電電流が重畳するた
め形状が大きく、加入者回路の小型経済化が不可
能であつた。(Prior Art) A conventional subscriber circuit is composed of electromagnetic parts as shown in Fig. 1, and unbalanced/balanced conversion of AC signals such as voice is performed via a transformer T1 .
The unbalanced signal V s is sent to the subscriber terminal TEL as a balanced signal on the two-line sides A and B. At the same time, the feeding current is connected to the DC resistance R a and the transformer winding L a
It flows to the subscriber terminal TEL via the transformer winding L b and direct current resistor R b to the battery V bb to supply power to the subscriber terminal. Therefore, since the power supply current is superimposed on the conversion transformer T1 , the shape is large, making it impossible to miniaturize the subscriber circuit economically.
（発明の目的）
本発明の目的は、小ハード量で集積化に適し、
不平衡・平衡変換が容易であり、加入者回路に用
いて良好な不平衡・平衡変換回路を提供すること
にある。(Object of the Invention) The object of the present invention is to provide a system that is suitable for integration with a small amount of hardware;
The object of the present invention is to provide an unbalanced/balanced conversion circuit that can easily perform unbalanced/balanced conversion and is suitable for use in subscriber circuits.
（発明の構成）
本発明の構成は、各々のコレクタを１対の各加
入者線に接続し、各々のエミツタは抵抗Rea，
Rebの各々を介して電池あるいは地気に接続する
とともに各演算増幅器の逆相入力に接続し、各ベ
ースは前記各演算増幅器の出力に接続した１対の
トランジスタを有し、かつ前記１対の演算増幅器
の正相入力を電流電圧変換抵抗Ra，Rbの各々を
介して電池あるいは地気に接続するとともに入出
力伝達係数Ｎのカレントミラー回路の基準端子あ
るいは出力端子に接続し、前記カレントミラー回
路の基準端子に接続する前記一方の電流電圧変換
抵抗Raが出力端子に接続する前記他方の電流電
圧変換抵抗Rbに定数Ｎ／（Ｎ＋１）を乗じた値
を持ち、かつ前記カレントミラー回路の入力端子
を加入者端末への不平衡信号入力端子とした事を
特徴とする不平衡・平衡変換回路である。(Configuration of the Invention) In the configuration of the present invention, each collector is connected to each subscriber line of a pair, and each emitter is connected to a resistor R ea ,
R eb is connected to the battery or the ground through each of the bases, and each base has a pair of transistors connected to the output of each operational amplifier, and each base has a pair of transistors connected to the output of each operational amplifier; The positive phase input of the operational amplifier is connected to the battery or the earth through current-voltage conversion resistors R a and R b , and also connected to the reference terminal or output terminal of a current mirror circuit with an input/output transfer coefficient N. The one current-voltage conversion resistance R a connected to the reference terminal of the current mirror circuit has a value obtained by multiplying the other current-voltage conversion resistance R b connected to the output terminal by a constant N/(N+1), and This is an unbalanced/balanced conversion circuit characterized in that the input terminal of the mirror circuit is used as an unbalanced signal input terminal to a subscriber terminal.
（実施例）
第２図は、本発明の実施例の回路図である。端
子Ａ，Ｂは加入者端末TELに接続する加入者端
子であり、トランジスタQa，Qbのコレクタに接
続されている。トランジスタQa，Qbのベースは
演算増幅器Aa，Abの出力にそれぞれ接続され、
トランジスタQaエミツタは抵抗Reaを介して電池
Vbbに接続されるとともに演算増幅器Aaの逆相入
力端子に接続する。一方、トランジスタQbのエ
ミツタは抵抗Rebを介して地気に接続されるとと
もに演算増幅器Abの逆相入力端子に接続する。
演算増幅器Abの正相入力端子はカレントミラー
回路CM0の出力に接続し、また電流電圧変換抵
抗Rbを介して地気に接続される。演算増幅器Aa
の正相入力端子はカレントミラーCMの基準側に
接続し、さらに電流電圧変換抵抗Raを介して電
池に接続される。ここで、カレントミラー回路
CM0の入出力伝達係数をＮとし、電流電圧変換
抵抗Raは電流電圧変換抵抗Rb×Ｎ／（１＋Ｎ）
の値をもつ。さらに、カレントミラー回路CM0
の入力端子Ｓは電圧・電流変換回路TRNの出力
に接続され、端子Ｓが不平衡・平衡変換回路の入
力となる。以下、本実施例の動作を説明する。(Embodiment) FIG. 2 is a circuit diagram of an embodiment of the present invention. Terminals A and B are subscriber terminals connected to the subscriber terminal TEL, and are connected to the collectors of transistors Q a and Q b . The bases of transistors Q a and Q b are connected to the outputs of operational amplifiers A a and A b , respectively,
Transistor Q a emitter connects to battery via resistor R ea
Connected to V bb and to the negative phase input terminal of operational amplifier A a . On the other hand, the emitter of transistor Q b is connected to the ground via resistor Re b and also to the negative phase input terminal of operational amplifier A b .
The positive phase input terminal of the operational amplifier A b is connected to the output of the current mirror circuit CM 0 and is also connected to the ground via the current-voltage conversion resistor R b . Operational amplifier A a
The positive phase input terminal of is connected to the reference side of the current mirror CM, and further connected to the battery via a current-voltage conversion resistor R a . Here, the current mirror circuit
Let the input/output transfer coefficient of CM 0 be N, and the current-voltage conversion resistance R a is the current-voltage conversion resistance R b ×N/(1+N)
has the value of Additionally, the current mirror circuit CM 0
The input terminal S of is connected to the output of the voltage/current conversion circuit TRN, and the terminal S becomes the input of the unbalanced/balanced conversion circuit. The operation of this embodiment will be explained below.
カレントミラー回路CM0の直流入力電流をIDC
（＝KI0）とし、カレントミラー回路CM0の入出
力伝達係数をＮとすると、カレントミラー回路
CM0の出力側には、Ｎ・IDCの電流が流れる。従
つてＢ線に流れる電流は、正相入力側に電流電圧
変換抵抗Rbが接続された演算増幅器Abの電流増
幅により、ILB＝Ｎ・IDC・Rb／Rebとなる。一方、
カレントミラー回路CM0の基準側には、（１＋
Ｎ）IDCの電流が流れるから、演算増幅器Aa側に
Ｎ・Rb／（１＋Ｎ）の値の電流電圧変換抵抗Ra
を接続することにより、Ａ線側にはILA＝（１＋
Ｎ）・IDC・Ｎ・Rb／Rea（１＋Ｎ）＝Ｎ・IDC・Rb／
Reaの電流が流れる。Rea＝Rebとすれば、ILA＝ILB
となり、電流源I0を適当な方法でコントロールす
ることにより、従来の加入者回路と同等に加入者
端末に直流給電ができる。 The DC input current of the current mirror circuit CM 0 is I DC
(=KI 0 ) and the input/output transfer coefficient of the current mirror circuit CM 0 is N, then the current mirror circuit
A current of N·I DC flows through the output side of CM 0 . Therefore, the current flowing through the B line becomes I LB =N·I DC ·R b /Re b due to the current amplification of the operational amplifier A b to which the current-voltage conversion resistor R b is connected to the positive phase input side. on the other hand,
The reference side of the current mirror circuit CM 0 has (1+
Since a current of N) I DC flows, a current-voltage conversion resistor R a with a value of N・R b /(1+N) is installed on the operational amplifier A a side.
By connecting I LA = (1+
N)・I DC・N・R b /R ea (1+N)=N・I DC・R b /
A current of R ea flows. If R ea = R eb , I LA = I LB
By controlling the current source I 0 in an appropriate manner, DC power can be supplied to the subscriber terminal in the same manner as in the conventional subscriber circuit.
また４線側からの不平衡信号Vsは、電圧電流
変換回路TRNで電流に変換され、電流信号i0で
カレントミラー回路CM0に入力する。直流給電
の場合と同様にカレントミラー回路CM0の出力
と基準側に電流電圧変換抵抗Rb・Ｎ・Rb／（１
＋Ｎ）をそれぞれ接続することにより、カレント
ミラー回路CM0は二つの演算増幅器Aa，Abを同
等に駆動し、Ａ，Ｂ線間に平衡信号を送出し、不
平衡・平衡変換が行なわれる。 Further, the unbalanced signal V s from the 4-wire side is converted into a current by the voltage-current conversion circuit TRN, and is input to the current mirror circuit CM 0 as a current signal i 0 . As in the case of DC power supply, a current-voltage conversion resistor R b・N・R b /(1
+N), the current mirror circuit CM 0 drives two operational amplifiers A a and A b equally, sends a balanced signal between the A and B lines, and unbalanced/balanced conversion is performed. .
第３図は、カレントミラー回路CM0の一構成
例を示す。 FIG. 3 shows an example of the configuration of the current mirror circuit CM0 .
本実施例では、電流電圧変換抵抗RaをＮ・
Rb／（１＋Ｎ）として演算増幅器Aaの正相入力
端子と、電池Vbbの間に接続したが、カレントミ
ラー回路CM0を第４図に示す如く、pnpトランジ
スタ構成とし、演算増幅器Abと地気間にＮ・
Ra／（１＋Ｎ）の値の電流電圧変換抵抗Rbを接
続し、演算増幅器Aaと電池間に電流電圧変換抵
抗Raを接続しても同様な動作が実現できる。 In this example, the current-voltage conversion resistance R a is set to N.
R b /(1+N) is connected between the positive phase input terminal of the operational amplifier A a and the battery V bb , but the current mirror circuit CM 0 is configured as a pnp transistor as shown in Fig. 4, and the operational amplifier A b And in the earth's atmosphere N・
A similar operation can be achieved by connecting a current-voltage converting resistor R b having a value of R a /(1+N) and connecting a current-voltage converting resistor R a between the operational amplifier A a and the battery.
（発明の効果）
本発明によれば、トランス等の電磁部品を用い
ずに電子部品だけで構成することができ、集積回
路化が可能である。また、カレントミラー回路の
段数が少なく、かつ２線側の演算増幅器を同等に
駆動することができ、回路動作の精度が向上す
る。(Effects of the Invention) According to the present invention, it is possible to configure only electronic components without using electromagnetic components such as transformers, and it is possible to form an integrated circuit. Further, the number of stages of the current mirror circuit is small, and the operational amplifiers on the two-line side can be equally driven, improving the accuracy of circuit operation.
第１図は従来の加入者回路、第２図は本発明の
一実施例の回路図、第３図、第４図はカレントミ
ラー回路の例である。
Ａ，Ｂ…加入者線端子、TEL…加入者端末、
Rea，Reb，Ra，Rb…抵抗、Qa，Qb…トランジス
タ、Aa，Ab…演算増幅器、Ｓ…入力端子、Vs…
不平衡信号源、TRN…電圧電流変換回路。
FIG. 1 is a conventional subscriber circuit, FIG. 2 is a circuit diagram of an embodiment of the present invention, and FIGS. 3 and 4 are examples of current mirror circuits. A, B...Subscriber line terminal, TEL...Subscriber terminal,
R ea , Re b , R a , R b ... Resistor, Q a , Q b ... Transistor, A a , A b ... Operational amplifier, S ... Input terminal, V s ...
Unbalanced signal source, TRN...voltage-current conversion circuit.
Claims (1)
するとともに第１の演算増幅器Aaの逆相入力端
子に接続し、 ベースは前記第１の演算増幅器の出力端子に接
続したNPN形の第１のトランジスタと、 コレクタを加入者線の他方の線に接続し、 エミツタは第２の抵抗Rebを介して地気に接続
するとともに第２の演算増幅器Abの逆相入力端
子に接続し、 ベースは前記第２の演算増幅器の出力端子に接
続したPNP形の第２のトランジスタを有し、 前記第１の演算増幅器の正相入力端子を第１の
電流電圧変換抵抗Raの一端および入出力伝達係
数Ｎのカレントミラー回路の基準端子または出力
端子のどちらか一方に接続するとともに前記第１
の電流電圧変換抵抗の他端を電池に接続し、 前記第２の演算増幅器の正相入力端子を第２の
電流電圧変換抵抗Rbの一端および前記入出力伝
達係数Ｎのカレントミラー回路の出力端子または
基準端子の他方に接続するとともに前記第２の電
流電圧変換抵抗の他端を地気に接続し、 前記カレントミラー回路の基準端子に接続され
る前記電流電圧変換抵抗の抵抗値がカレントミラ
ー回路の出力端子に接続される前記電流電圧変換
抵抗の抵抗値に定数Ｎ／（Ｎ＋１）を乗じた抵抗
値を持ち、 前記カレントミラー回路の入力端子を加入者端
末への不平衡信号入力端子とすることを特徴とす
る不平衡・平衡変換回路。[Claims] 1. The collector is connected to one line of the subscriber line, and the emitter is connected to the battery via the first resistor R ea and to the negative phase input terminal of the first operational amplifier A a . The base is connected to the output terminal of the first operational amplifier, the collector is connected to the other subscriber line, and the emitter is connected to ground via a second resistor Reb . a PNP-type second transistor whose base is connected to the output terminal of the second operational amplifier A b ; Connecting the positive phase input terminal of the operational amplifier to one end of the first current-voltage conversion resistor R a and either the reference terminal or the output terminal of a current mirror circuit with an input/output transfer coefficient N, and
The other end of the current-voltage conversion resistor is connected to the battery, and the positive phase input terminal of the second operational amplifier is connected to one end of the second current-voltage conversion resistor R b and the output of the current mirror circuit of the input-output transfer coefficient N. terminal or a reference terminal, and the other end of the second current-voltage conversion resistor is connected to the ground, and the resistance value of the current-voltage conversion resistor connected to the reference terminal of the current mirror circuit is a current mirror circuit. The current mirror circuit has a resistance value obtained by multiplying the resistance value of the current-voltage conversion resistor connected to the output terminal of the circuit by a constant N/(N+1), and the input terminal of the current mirror circuit is used as an unbalanced signal input terminal to the subscriber terminal. An unbalanced/balanced conversion circuit characterized by:
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP58033746A JPS59160394A (en) | 1983-03-03 | 1983-03-03 | Unbalance and balance converting circuit |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP58033746A JPS59160394A (en) | 1983-03-03 | 1983-03-03 | Unbalance and balance converting circuit |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS59160394A JPS59160394A (en) | 1984-09-11 |
| JPH0153836B2 true JPH0153836B2 (en) | 1989-11-15 |
Family
ID=12394975
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP58033746A Granted JPS59160394A (en) | 1983-03-03 | 1983-03-03 | Unbalance and balance converting circuit |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS59160394A (en) |
Families Citing this family (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CA1291836C (en) * | 1987-06-17 | 1991-11-05 | Kenji Takato | Battery feed circuit |
-
1983
- 1983-03-03 JP JP58033746A patent/JPS59160394A/en active Granted
Also Published As
| Publication number | Publication date |
|---|---|
| JPS59160394A (en) | 1984-09-11 |
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