JPH01170110A - Radio equipment - Google Patents

Abstract

PURPOSE:To eliminate the interference of an unnecessary signal and to eliminate the subradiation of an unnecessary wave by forming a digital signal processing unit of a 90 deg. phase shifter by means of the digital signal processing unit. CONSTITUTION:A signal captured by an antenna 14 is sufficiently amplified by a high frequency amplifier 15 and inputted to a balanced modulator 16. The component of a difference between a local oscillating frequency and the frequency of the received signal is made into a low frequency, A/D-converted and, thereafter, inputted to a digital signal processor 20. The processor 20 has a function as a phase shifter to obtain the phase difference of 90 deg.. Thus, the interference of the unnecessary signal can be eliminated, and the subradiation of the unnecessary wave can be eliminated.

Description

【発明の詳細な説明】 第１図は、典型的な従来の無線通信機の例である。この
例では単側波帯用無線通信機の例で単側帯波を得るには
２の平衡変調器の出力を非常に急峻な特性の帯域ろ波器
を通して単側帯波得ている。一方、受信時に於ける選択
度の向上のためかかるろ波器を共用するのが一般的であ
る。DETAILED DESCRIPTION OF THE INVENTION FIG. 1 is an example of a typical conventional wireless communication device. In this example, a single sideband radio communication device is used, and to obtain a single sideband, the output of two balanced modulators is passed through a bandpass filter with a very steep characteristic to obtain a single sideband. On the other hand, it is common to share such a filter in order to improve selectivity during reception.

この種の通信機では、周波数変換が一段のみというのは
、むしろ希であり二段から四段位が一般的である。周波
数変換の度に局部発振器が必要である。しかもそれぞれ
の局部発振器の周波数安定度は非常に高いことが要求さ
れる。In this type of communication equipment, it is rather rare that frequency conversion requires only one stage, and two to four stages are common. A local oscillator is required for each frequency conversion. Furthermore, each local oscillator is required to have extremely high frequency stability.

また、このように周波数変換することを必要とするシス
テムでは影像周波数を十分に抑圧しなければならない。Furthermore, in a system that requires frequency conversion in this manner, the image frequency must be sufficiently suppressed.

これが不十分だと、不要な信号に混信を受けたり不要な
電波の副射をしてしまう等設計には十分な考慮がはられ
れる。If this is insufficient, sufficient consideration must be taken in the design, as interference from unnecessary signals or unnecessary side radiation of radio waves may occur.

このようなシステムでは構造が非常に複雑化しやすい。Such a system tends to have a very complex structure.

また高価でもある。It's also expensive.

第２図は本考案の１例である。まず受信状態に於て、１
４の空中線によって捕捉した信号を１５の高周波増幅器
で十分増幅し１６の平衡変ｍ１ｌｌｉ！に入力される。FIG. 2 is an example of the present invention. First, in the receiving state, 1
The signal captured by 4 antennas is sufficiently amplified by 15 high frequency amplifiers, and 16 balanced changes m1lli! is input.

平衡度ｉｌｌ器の他の入力端子には局部発ｗｉ８２６の
出力が印加されている。The output of the local oscillator wi826 is applied to the other input terminal of the balance illumination device.

２つの局部発振器の出力は、互いに９０°の位相差がも
たせである。したがって２の出力間にハ常に９０°の位
相差が現れる。これら出力には局部発振周波数と受信信
号の周波数の和と差の成分が含まれる。和の成分は非常
に簡単な成域ろ波器８で除去できる。差の成分は低周波
となってＡＤ変換後ディジタル信号処理装置に入力され
る。２０の内部ではその演算機能により入力信号を更に
９０°の位相差を得る位移器としての機能をもつ。更に
その出力の和ないし差をとると影像周波数成分を除去で
きる。The outputs of the two local oscillators have a phase difference of 90° from each other. Therefore, a phase difference of 90° always appears between the two outputs. These outputs include the sum and difference components of the local oscillation frequency and the frequency of the received signal. The sum component can be removed with a very simple bandpass filter 8. The difference component becomes a low frequency and is input to a digital signal processing device after AD conversion. The inside of 20 has a function as a shifter which further obtains a phase difference of 90° from the input signal by its arithmetic function. Furthermore, by taking the sum or difference of the outputs, the image frequency component can be removed.

一方、送受切り換えリレー２６を図示しである状態とは
、反対にすることにより送信状態に移すことができる。On the other hand, the transmitting/receiving switching relay 26 can be moved to the transmitting state by changing it to the opposite state from the illustrated state.

２３のマイクから得られた音声信号等は２２で十分に増
幅され２０に入力される。２０は演算によって、この音
声信号を２つの９０’の位相差をもった出力を出す。こ
の信号は１９のＤＡ変換後１６の平衡変調器に入力され
る。次にこの２つの信号の和または差をとる。すると、
その操作に応じて上側帯波又は下側帯波がえられる。こ
れを１８の高周波増幅器により所望の電力まで増幅し１
４の空中線へと送り出す。The audio signal etc. obtained from the microphone 23 is sufficiently amplified at 22 and inputted to 20. 20 performs calculation to output two audio signals having a phase difference of 90'. This signal is input to 16 balanced modulators after 19 DA conversions. Next, the sum or difference of these two signals is taken. Then,
Depending on the operation, an upper sideband wave or a lower sideband wave can be obtained. This is amplified to the desired power using 18 high frequency amplifiers, and 1
Send it to the 4th antenna.

次に２０の本考案に於けるディジタル信号処理装置の動
作について説明する。この装置は高速演算装置であって
下記の動作と等価な演算を行なうものである。第３図は
２０の動作をブロック図化したものである。周知のよう
に帯域ろ波器等のろ波器は差分方程式で演算される。Next, the operation of the digital signal processing device according to No. 20 of the present invention will be explained. This device is a high-speed arithmetic device and performs arithmetic operations equivalent to the operations described below. FIG. 3 is a block diagram of 20 operations. As is well known, filters such as bandpass filters are operated using a difference equation.

まず受信状態では、どちらかがどらかよりも９０°位相
を進ませるか遅らせるかをしなければならない。２９の
帯域ろ波器と元の信号の差を図の比率でとると所謂オー
ルパス・フィルタと等価になる。これを２組み用意し、
それぞれのろ波器の中心周波数とＱを適当にえらぶと９
０°移相蕎が得られる。この２つの出力を和又は差をと
ると上側帯波のみ又は下側帯波のみの受信が可能となり
、影像周波数の影響を無（すことができる。First, in the receiving state, one of them must lead or lag the other by 90° in phase. If the difference between the bandpass filter No. 29 and the original signal is taken at the ratio shown in the figure, it becomes equivalent to a so-called all-pass filter. Prepare two sets of this,
By selecting the center frequency and Q of each filter appropriately, we get 9.
A 0° phase shift is obtained. By taking the sum or difference of these two outputs, it is possible to receive only the upper sideband or only the lower sideband, and the influence of the image frequency can be eliminated.

送信状態では上で説明した９０’移相藩が必要なだけで
ある。この様子を第４図に示す。２２で増幅された音声
信号をティジタル化したものを演算によって２つの９０
°位相差をもった信号に処理されこれを出力としている
。In the transmit state, only the 90' phase shift range described above is needed. This situation is shown in FIG. The digitized audio signal amplified by 22 is converted into two 90
The signal is processed into a signal with a phase difference of .degree. and this is output.

これでわかるように、２０の動作は、ソフトウェア的に
為きれるため、特性の変更が容易である。例えば受信状
態の場合では、９０°移相器を通して和又は差をとった
出力を帯域ろ波器を通過させる場合、この帯域ろ波器の
特性すなわち帯域幅や中心周波数を他の不要な信号から
逃れるために可変できる必要があり得る。このような場
合、周知のようにディジタル信号処理装置では非常に容
易である。従来のアナログ式ろ波器では非常に困難であ
る。その性能の高い高次のものであればある程、困難ざ
が増す。As can be seen, since the operation of 20 can be performed by software, it is easy to change the characteristics. For example, in the case of reception, when the output obtained by taking the sum or difference through a 90° phase shifter is passed through a bandpass filter, the characteristics of this bandpass filter, such as the bandwidth and center frequency, are separated from other unnecessary signals. You may need to be able to change in order to escape. As is well known, such a case is very easy to handle using a digital signal processing device. This is extremely difficult to achieve with conventional analog filters. The higher the level of performance, the more difficult it becomes.

尚、ここに示したれいｉ、１例であり９０’移相器と言
ってもその演算機能によって他の方法が考えられる。例
えば平衡変調器と帯域ろ波器とを組合せた物を２組み用
意したものでもよい。又、周波数変復調も可能である。Note that the slope i shown here is just one example, and although it is called a 90' phase shifter, other methods can be considered depending on its calculation function. For example, two sets of balanced modulators and bandpass filters may be prepared. Frequency modulation and demodulation is also possible.

【図面の簡単な説明】[Brief explanation of the drawing]

第１図は従来の単側波帯用無線通信機の例第２図は本考
案の一例、第３図は受信時のディジタル号処理装置の動
作の説明図、第４図は送信時のディジタル信号処理装置
の動作図１−ｍ−空中線、２−ｍ−高周波増幅器３−−
−平衡変調器、４−ｍ−中間周波増幅器５−−−送受切
り換えリレー ６一−−低周波増幅器、７−−−スピーカ８−−−第２
局部発信藩、９−ｍ−帯域ろ波器１０−ｍ−高周波電力
増幅器 １１−一一第１局部発信器 １２−一一音声増輻醪、１３−ｍ−マイク１４−−−空
中線、１５−ｍ−高周波増幅器１６−−−平衡変調響、
１７−−−ＡＤ変換器１８−ｍ−高周波電力増幅器 １９−−−ＤＡ変換器、２０−ｍ−ディジタル信号処理
装置、２１−ｍ−低周波増幅器２２−−−音声増輻諸、
２３．−−−マイク２４−一一スビーカ、２５−−−９
０°位相器２６−−−局部発信器、２７−−−和算器２
８−一一送受切り換えリレー ２９−ｍ−帯域ろ波器、３０−ｍ−積算器３１−−−和
算器、３２−−一和算器又は減算器Figure 1 is an example of a conventional single-sideband radio communication device. Figure 2 is an example of the present invention. Figure 3 is an explanatory diagram of the operation of a digital signal processing device during reception. Figure 4 is an illustration of a digital signal processing device during transmission. Operation diagram of signal processing device 1-m-antenna, 2-m-high frequency amplifier 3--
- Balanced modulator, 4m - Intermediate frequency amplifier 5 - Transmission/reception switching relay 6 - Low frequency amplifier, 7 - Speaker 8 - - Second
Local transmitter, 9-m-Band filter 10-m-High frequency power amplifier 11-11 First local oscillator 12-11 Audio amplification device, 13-m-Microphone 14--Antenna, 15- m-high frequency amplifier 16---balanced modulation acoustics;
17--AD converter 18-m-high frequency power amplifier 19--DA converter, 20-m-digital signal processing device, 21-m-low frequency amplifier 22--audio amplification,
23. ---Mike 24-11 Subika, 25--9
0° phase shifter 26 --- local oscillator, 27 --- adder 2
8-11 transmission/reception switching relay 29-m-band filter, 30-m-integrator 31--summer, 32--1 summator or subtractor

Claims (1)

【特許請求の範囲】[Claims] ディジタル信号処理装置でディジタル信号処理による９
０°移相器、帯域ろ波器、低域ろ波器、高域ろ波器、等
のディジタルフィルタを具備したことを特徴とする無線
通信機。9 by digital signal processing with digital signal processing equipment
A wireless communication device characterized by being equipped with digital filters such as a 0° phase shifter, a bandpass filter, a low-pass filter, and a high-pass filter.