JPH01126170A - Control system of polyphase and multiple voltage type inverter - Google Patents
Control system of polyphase and multiple voltage type inverterInfo
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- JPH01126170A JPH01126170A JP62284039A JP28403987A JPH01126170A JP H01126170 A JPH01126170 A JP H01126170A JP 62284039 A JP62284039 A JP 62284039A JP 28403987 A JP28403987 A JP 28403987A JP H01126170 A JPH01126170 A JP H01126170A
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- 238000010586 diagram Methods 0.000 description 12
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- 238000006243 chemical reaction Methods 0.000 description 1
- 239000002131 composite material Substances 0.000 description 1
- 238000007796 conventional method Methods 0.000 description 1
- 238000005516 engineering process Methods 0.000 description 1
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Abstract
Description
【発明の詳細な説明】
〔産業上の利用分野〕
この発明は、低出力周波数時における多重電圧形インバ
ータの出力電圧リップル或いは該インバータにて駆動さ
れるモータのトルクリップルを低減し、実用上十分な低
出力周波数域の運転特性を得るよう制御する多相多重電
圧形インバータの制御方式に関するものである。[Detailed Description of the Invention] [Field of Industrial Application] This invention reduces the output voltage ripple of a multi-voltage inverter or the torque ripple of a motor driven by the inverter at low output frequencies, and achieves a practically sufficient result. This invention relates to a control method for a multi-phase, multi-voltage inverter that is controlled to obtain operating characteristics in a low output frequency range.
第５図（ａ）、（ｂ）、（ｃ）は例えば電気学会１９８
７年３月３１日発刊「半導体電力変換回路ＪＰ、１００
に示された従来の１２相多重電圧形インバータを示す回
路図とベクトル図及び出力電圧波形図であり、図におい
て（１）はＰＡＭ制御によって調節される可変直流電圧
源、（２１、（３）は３相方形波インバータ、（４）、
（６）は多重変圧器−次巻線、（５）、（７）は該変圧
器二次巻線である。Figures 5(a), (b), and (c) are, for example, published by the Institute of Electrical Engineers of Japan 1988.
“Semiconductor Power Conversion Circuit JP, 100,” published on March 31, 2007.
2 are a circuit diagram, a vector diagram, and an output voltage waveform diagram showing the conventional 12-phase multiple voltage type inverter shown in FIG. is a three-phase square wave inverter, (4),
(6) is a multiplex transformer-secondary winding, and (5) and (7) are secondary windings of the transformer.
次に動作について説明する。３０”の基本波位相差を有
する各インバータ（２）、（３）によって多重変圧器の
各−次巻線（４）、（６）は３０゛位相差を有する方形
波電圧が印加され、該変圧器二次巻線（５）、（７）に
は、合成出力電圧としてＶｌＪ−ｖなる波形を発生する
。このＶＬＩ−Ｖは、多相多重変圧器の原理として周知
の様に、多重相数ｍに対し、（ｎｍ±１）次（ｎ＝１．
２，３．・・・）高調波成分が残され、第５図の場合、
１２相多重なので、ｍ＝１２で、５ 、７．１７，１９
，２９゜３１、・・・次調波は消され、（１２ｎ±１）
（ｎ” １，２．・・・）次の高調波成分を含有した
波形となる。Next, the operation will be explained. Each inverter (2), (3) with a fundamental phase difference of 30" applies a square wave voltage with a 30" phase difference to each secondary winding (4), (6) of the multiplex transformer; The secondary windings (5) and (7) of the transformer generate a waveform VlJ-v as a composite output voltage.This VLI-V is a multi-phase multiple transformer, as is well known as the principle of a multi-phase multiple transformer. For several m, (nm±1) order (n=1.
2,3. ...) The harmonic components are left, and in the case of Figure 5,
Since it is a 12-phase multiplex, m = 12, 5, 7.17, 19
,29゜31,... the harmonics are erased, (12n±1)
The waveform contains the following harmonic components (n" 1, 2...).
従来の多相多重電圧形インバータは以上のように構成さ
れているので、低出力周波数（基本波）時、ＧＴＯ素子
等を用いる場合、ＯＦＦ時のテイル時間が延びるため直
流電圧Ｅｄをある値以下に下げられず、Ｅｄ−一定条件
でＰＷＭによる出力電圧制御が不可欠となるが、ＰＷＨ
時の高調波に注意しないと負荷によっては多相多重変圧
器で除去し得ない高調波次数ｎｍ±１の高調波によって
、モータ負荷の場合該高調波によるトルクリップルが機
械系の共振周波数に一致し、運転に支障を来たしたりす
るため、不必要な多重相数の増加をまねき、装置の大形
化、価格の増加等を発生する可能性があり、また高出力
周波数域においてＰＷＭをｉ続すると、インバータのス
イッチングが増大し、スイッチングロスの増大及びサイ
リスタ、ＧＴＯ等の低スイッチング素子には向かない等
の欠点があった。Conventional multi-phase multi-voltage inverters are configured as described above, so when using GTO elements etc. at low output frequency (fundamental wave), the tail time when OFF is extended, so the DC voltage Ed must be kept below a certain value. Therefore, it is essential to control the output voltage by PWM under Ed- certain conditions, but PWH
Depending on the load, if you do not pay attention to the harmonics of the harmonic order nm±1, which cannot be removed by a multi-phase transformer, the torque ripple due to the harmonics in the case of a motor load may become equal to the resonant frequency of the mechanical system. This may lead to an unnecessary increase in the number of multiplexed phases, resulting in an increase in the size and cost of the equipment, and may cause problems with operation. This increases switching of the inverter, resulting in increased switching loss and disadvantages such as being unsuitable for low switching elements such as thyristors and GTOs.
この発明は上記のような問題点を解消するためになされ
たもので、低出力周波数域の出力電流リップル或いはモ
ータ負荷時のトルクリップルを実用上問題ないレベルに
低減でき、且つ高出力周波数域においてはインバータの
スイッチング数を従来に比べ増大させることなく、全運
転域においてバランスのとれた運転特性を得ることがで
きる多相多重電圧形インバータの制御方式を提供するこ
とを目的とする。This invention was made in order to solve the above-mentioned problems, and it is possible to reduce the output current ripple in the low output frequency range or the torque ripple at the time of motor load to a level that does not cause any practical problem, and also to reduce the output current ripple in the low output frequency range or the torque ripple at the time of motor load to a level that does not cause any problem in practical use. The object of the present invention is to provide a control method for a multi-phase, multi-voltage inverter that can obtain balanced operating characteristics over the entire operating range without increasing the number of switching operations of the inverter compared to conventional methods.
この発明に係る多相多重電圧形インバータの制御方式は
、多相多重変圧器に複数の多相インバータの出力を給電
する多相多重電圧形インバータにおいて、出力電圧制御
として低出力周波数或いは一定直流電圧におけるＰＷＭ
（パルス幅変調）制御と高出力周波数或いは方形波ＰＡ
Ｍ （パルス振幅変調）制御を運転周波数によって切り
換え、ＰＷＭ制御時、各インバータ出力電圧波形は多重
相数をｍとして多相多重変圧器で相殺されず出力される
出力電圧高調波の次数（ｎｍ±１） （ｎ＝１、２，３
，・・・）に対し、少なくとも最低次付近の（ｍ±１）
次高調波を含有しないよう制御するものである。A control method for a polyphase multiple voltage type inverter according to the present invention is a polyphase multiple voltage type inverter that feeds the outputs of a plurality of polyphase inverters to a polyphase multiple transformer. PWM at
(pulse width modulation) control and high output frequency or square wave PA
M (Pulse Amplitude Modulation) control is switched depending on the operating frequency, and during PWM control, each inverter output voltage waveform is determined by the order of output voltage harmonics (nm± 1) (n=1, 2, 3
,...), at least around the lowest order (m±1)
This is to control so as not to contain harmonics.
（作用〕
この発明における多相多重インバータの制御方式は、低
出力周波数域において、ＰＷＨにより出力電圧制御を行
なうと同時に多相多重変圧器で除去し得ないＶＶＶＦ
（可変電圧可変周波数変換器）システムにとって有害な
低次高調波をもＰＷＨの波形制御により実用上十分な程
度まで低減し、ＶＶＶＦシステムの低出力周波数域での
運転特性の向上が計れ、高出力周波数域においては方形
波のＰＡＭ制御に切り換えられ、スイッチング周波数の
増大を招くことなく運転される。(Function) The control method of the polyphase multiplex inverter in this invention performs output voltage control using PWH in the low output frequency range, and at the same time, VVVF which cannot be removed by the polyphase multiplex transformer.
(Variable Voltage Variable Frequency Converter) Low-order harmonics that are harmful to the system can be reduced to a practically sufficient level by controlling the PWH waveform, improving the operating characteristics of the VVVF system in the low output frequency range, and achieving high output. In the frequency range, it is switched to square wave PAM control and operated without increasing the switching frequency.
以下、この発明の一実施例を簡単化のため１２相多重時
の図について説明する。第１図（ａ）において、（１）
は可変直流電圧源、（２）、（３）は互いに３０°の基
本波位相差を有する出力電圧を発生する３相インバータ
、（４）、（６）は多相多重変圧器−次巻線、（５）、
（７）は該変圧器二次巻線であり、同図（ｂ）は変圧器
合成出力電圧のベクトル図である。Hereinafter, an embodiment of the present invention will be described with reference to a diagram for 12-phase multiplexing for the sake of simplicity. In Figure 1(a), (1)
is a variable DC voltage source, (2) and (3) are three-phase inverters that generate output voltages with a fundamental wave phase difference of 30 degrees from each other, and (4) and (6) are polyphase multiplex transformers - secondary windings. ,(5),
(7) is the secondary winding of the transformer, and (b) of the same figure is a vector diagram of the transformer combined output voltage.
第２図は各インバータ（２）、（３）の出力線間電圧波
形が１２０°方形波の時の基本波を基準とした場合の含
有高調波（次数を１とする）を示す。また第３図はＶ／
ｆ ＝一定制御時のこの発明の制御における出力基本波
周波数ｆと直流電圧源電圧Ｅｄ及び基本波出力ｖ１の関
係を示す。FIG. 2 shows the harmonics contained (assuming the order is 1) based on the fundamental wave when the output line voltage waveform of each inverter (2), (3) is a 120° square wave. Also, Figure 3 shows V/
The relationship between the output fundamental wave frequency f, the DC voltage source voltage Ed, and the fundamental wave output v1 in the control of the present invention when f = constant control is shown.
第１図は従来例の第５図と同様１２相多重インバータの
構成で、動作自体は同一であり、（１２ｎ±１）次高調
波（ｎ＝１．２，３．・・・）は変圧器で相殺されず出
力端Ｕ、 Ｖ、 Ｗ線間に高調波電圧として含有される
。第２図に示す様に３相インバータ（２）、（３）の出
力波形が方形波の場合は、単一インバータ出力電圧に含
有される電圧高調波Ｖ、工１．Ｖ１６：ｌ、・・・は相
殺され、Ｖ１２２１、■２４！Ｉ、・・・が出力に含有
されて残る。第３図にこの発明の特徴的なＰＷＭ−ＰＡ
Ｍ切換え状態を示すが、以上の様に方形波ＰＡＭ制御時
はＶ ｌ ２ ＬＩ 、Ｖ ２４ ＬＩ 、・・・は出
力電圧に含有されるが、基本波ｆが比較的高い領域で使
用されているため、以下の様に問題ない。出力電流リッ
プルは各高調波電流成分１ｔ、Ｑｉｕが
Ｉ ｆＡ＋＋＋ ／ ｒｌｎ ＝ （Ｖ＋／ｆ） ・（
ｆｎ／Ｖ＋ｎ） ４／％Ｘ・１／（ＩＬま１）２
・・・（１）但し、
Ｖ ｔＱ４ｎ ＝ ｖ＋／ （ｆＬ＋１）％Ｘ ＝Ｘｎ
（Ｌｎ／Ｖ＋ｎ）：負荷過渡インピーダンス（ｐ、ｕ、
）
ｘ（！ｌｑ目＝％Ｘ’ （ｖａｎ／ｒａｎ） ’ （ｌ
Ｌｉ１） （ｆ／ｆｎ）Ｉ （Ｑｚｎ ＝ Ｖ （ｊｌ
ｚｎ ／ Ｘ ｊ、ｇｊｌ＋また添字のｎは定格を表わ
す。Figure 1 shows the configuration of a 12-phase multiplex inverter similar to the conventional example in Figure 5, and the operation itself is the same. It is not canceled out by the output terminal and is contained as a harmonic voltage between the output terminals U, V, and W lines. As shown in FIG. 2, when the output waveforms of the three-phase inverters (2) and (3) are square waves, the voltage harmonics V contained in the single inverter output voltage, V16:l,... are canceled out, V1221, ■24! I, . . . remain contained in the output. Figure 3 shows the characteristic PWM-PA of this invention.
As shown above, during square wave PAM control, V l 2 LI , V 24 LI , . . . are included in the output voltage, but they are used in a region where the fundamental wave f is relatively high. Therefore, there is no problem as shown below. The output current ripple is each harmonic current component 1t, Qiu is I fA+++ / rln = (V+/f) ・(
fn/V+n) 4/%X・1/(ILma1)2
...(1) However, V tQ4n = v+/ (fL+1)%X = Xn
(Ln/V+n): Load transient impedance (p, u,
) x (!lqth = %X' (van/ran) ' (l
Li1) (f/fn)I (Qzn = V (jl
zn/X j, gjl+The subscript n represents the rating.
（１）式において、Ｖ／ｆ ＝一定を考えると、Ｉ ＋
ｊｌｑ＋１ ／ Ｉ Ｉｎ ＝ １／％Ｘ・１／（ｆ
ｌ、ｑｌ）’ ・（２）通常負荷として訪導電動機
（１，Ｍ、）を考えると、％Ｘ ＝０．１５が普通で、
ｆＬ−１２＋７）１２相時、Ｉｌｌ ？５．５ ％
１１３ ４３．９ ％１１１％Ｉ１３による
発生高調波トルクは１２次高調波トルクＴＩ２で約１．
９％である。In equation (1), considering V/f = constant, I +
jjlq+1 / I In = 1/%X・1/(f
l, ql)' (2) Considering the visiting motor (1, M,) as a normal load, %X = 0.15 is normal,
fL-12+7) At 12 phase, Ill? 5.5%
113 43.9%111%The harmonic torque generated by I13 is the 12th harmonic torque TI2, which is approximately 1.
It is 9%.
但し、この場合は基本波出力周波数が比較的高いため、
機械系の軸共振の心配はない。ところがこのままＰＡＭ
にて低周波域まで運転すると機械系の共振倍率Ｑ ＝
１００程度あるものに対しては定格トルクの約１．９倍
のトルク脈動を発生し危険であるし、ＧＴＯ素子使用時
には低周波域でのＰＷＭが不可欠であり、（ｔ２ｎｔｌ
）次の高調波による電流リップル、トリクリップル等不
具合を排除するためＰＷＭによる出力基本波周波数制御
と出力基本波電圧制御と同時に少なくともこの場合（１
２±１）次高調波ｖｌ□、Ｖ ｌ ３を除去あるいは実
用上十分なレベルまで低減する様なＰＷＭパターンが使
用される。However, in this case, since the fundamental wave output frequency is relatively high,
There is no need to worry about mechanical shaft resonance. However, as it is, PAM
When operating down to low frequency range, the mechanical system resonance magnification Q =
100, it is dangerous to generate torque pulsations approximately 1.9 times the rated torque, and PWM in the low frequency range is essential when using the GTO element.
) At least in this case (1
A PWM pattern is used that eliminates or reduces the 2±1) order harmonics vl□ and Vl3 to a practically sufficient level.
次にＰＷＭパターンについて説明する。第４図はインバ
ータ１相のスイッチング素子のスイッチングパターンで
、８１〜ａ、はスイッチング変化点の角度を示す。この
パターン使用時はａ、〜ａ３の自由度３となり、基本波
振幅、（Ｉｌｌ−１）次高調波、（ｍ十１）高直調波振
幅の制御が可能であり、各次調波は下式で求められる。Next, the PWM pattern will be explained. FIG. 4 shows the switching pattern of the switching elements of one phase of the inverter, and 81 to a indicate the angle of the switching change point. When using this pattern, there are 3 degrees of freedom for a, ~a3, and it is possible to control the fundamental wave amplitude, (Ill-1)th harmonic, and (m11) harmonic amplitude, and each harmonic is It can be obtained using the formula below.
線間基本波電圧
Ｖ＋ ＝−ｒＴ／π（２（ＣＯ５ａ、−ＣＯ５（ａ、＋
ａ２）＋ＣＯＳ （ａｔ”ａ２”ａ３））−１）
・・・（３）線間ｌ±１次高調高調波
電圧＠ ＋ １ ＝ ｆＴ／ ｒｔ （ｍ±１） （２
（ＣＯ５（（ｍ±１） ａｔ）−ＣＯ５（（ｍ±１）
（ａｔ”ａ２））”Ｃ０５（（ｍ±１） （ａ＋十ａ２
＋ａ３）））−１）・・・（４）
（３）、（４）式により所望のＶｌ、％＋１次のａ１〜
ａ、が求められる。またこの場合偶数調波と３の倍数調
波は出力として現われない。この様なＰＷＭによりｍ±
１次調波を除去或いは低減して低出力周波数域の高調波
不具合が抑えられる。Line fundamental wave voltage V+ = -rT/π(2(CO5a, -CO5(a, +
a2)+COS (at"a2"a3))-1)
...(3) Line-to-line l±1st harmonic voltage @ + 1 = fT/rt (m±1) (2
(CO5((m±1) at)-CO5((m±1)
(at”a2)”C05((m±1) (a+10a2
+a3)))-1)...(4) By formulas (3) and (4), the desired Vl,%+1 order a1~
a, is required. Also, in this case, even harmonics and harmonics multiples of 3 do not appear as output. With such PWM, m±
By removing or reducing the first harmonic, harmonic problems in the low output frequency range can be suppressed.
なお、上記実施例では１２相多重時について説明したが
、１８相、２４相時についても同様である。またＰＷＭ
は自由度３のパターン式ＰＷＭで説明したが、同様の効
果が得られるものなら何でも良い。In addition, although the above embodiment has been described for 12-phase multiplexing, the same applies to 18-phase and 24-phase multiplexing. Also PWM
Although the explanation has been made using pattern-type PWM with three degrees of freedom, any method may be used as long as the same effect can be obtained.
以上のように、この発明によれば、多相多重電圧形イン
バータの制御を、低出力周波域ではＰＷＭによる波形改
善と出力電圧制御、高串力周波域では方形波ＰＡＭとし
、全出力周波数域において高調波による不具合の除去と
スムーズな出力電圧出力周波数制御を可能にしたので、
運転性能の向上と装置の小形化に寄与できる効果がある
。As described above, according to the present invention, the control of a polyphase multiple voltage type inverter is performed using PWM waveform improvement and output voltage control in the low output frequency range, square wave PAM in the high force frequency range, and In this way, it is possible to eliminate problems caused by harmonics and to smoothly control the output voltage and output frequency.
This has the effect of contributing to improved operating performance and downsizing of equipment.
第１図（ａ）、（ｂ）はこの発明の一実施例による多相
多重インバータ装置を示す構成図と出力電圧のベクトル
図、第２図は方形波出力電圧時の高調波分布を示す特性
図、第３図はこの発明の制御実施時の各インバータ入力
直流電圧と出力基本波周波数との関係を示す説明図、第
４図はこの発明の一実施例で説明に使用したＰＷＭパタ
ーン図、第５図（ａ）、（ｂ）、（ｃ）は従来の１２相
多重電圧形インバータの構成図と出力電圧の波形図及び
ベクトル図である。
（１）は可変直流電圧源、（２）、（３）は３相インバ
ーク、（４）、 （６）は出力変圧器−次巻線、（５）
、（７）は出力変圧器二次巻線を示す。
なお、図中同一符号は同一、又は相当部分を示す。FIGS. 1(a) and (b) are block diagrams and output voltage vector diagrams showing a polyphase multiplex inverter device according to an embodiment of the present invention, and FIG. 2 is a characteristic showing harmonic distribution at square wave output voltage. 3 is an explanatory diagram showing the relationship between each inverter input DC voltage and the output fundamental wave frequency when controlling the present invention, and FIG. 4 is a PWM pattern diagram used for explanation in one embodiment of the present invention. FIGS. 5(a), 5(b), and 5(c) are a configuration diagram, an output voltage waveform diagram, and a vector diagram of a conventional 12-phase multiple voltage type inverter. (1) is a variable DC voltage source, (2) and (3) are 3-phase inverters, (4) and (6) are output transformer-secondary winding, (5)
, (7) indicates the output transformer secondary winding. Note that the same reference numerals in the figures indicate the same or equivalent parts.
Claims (2)
給電する多相多重電圧形インバータにおいて、出力電圧
制御として低出力周波数或いは一定直流電圧におけるＰ
ＷＭ（パルス幅変調）制御と高出力周波数或いは方形波
ＰＡＭ（パルス振幅変調）制御を運転周波数によって切
り換え、ＰＷＭ制御時、各インバータ出力電圧波形は多
重相数をｍとして多相多重変圧器で相殺されず出力され
る出力電圧高調波の次数（ｎｍ±１）（ｎ＝１、２、３
、・・・）に対し、少なくとも最低次付近の（ｍ±１）
次高調波を含有しないよう制御することを特徴とする多
相多重電圧形インバータの制御方式。(1) In a multi-phase multi-voltage inverter that supplies the output of multiple multi-phase inverters to a multi-phase multi-transformer, P at low output frequency or constant DC voltage is used as output voltage control.
WM (Pulse Width Modulation) control and high output frequency or square wave PAM (Pulse Amplitude Modulation) control can be switched depending on the operating frequency, and during PWM control, each inverter output voltage waveform is offset by a multiphase transformer with the number of multiphases being m. The order (nm±1) of the output voltage harmonics that are output without being output (n=1, 2, 3
,...), at least around the lowest order (m±1)
A control method for a multi-phase multi-voltage inverter characterized by controlling it so as not to contain harmonics.
生トルクのリップルが実用上差し支えないレベルまで、
少なくともｍ±１次の高調波を除去しないまでも低減さ
せることを特徴とする特許請求の範囲第１項記載の多相
多重電圧形インバータの制御方式。(2) The output current ripple or the ripple of the motor generated torque as a load is at a level that does not pose a practical problem.
2. A control method for a multi-phase multi-voltage inverter according to claim 1, characterized in that at least m±1-order harmonics are reduced, if not eliminated.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP62284039A JPH01126170A (en) | 1987-11-10 | 1987-11-10 | Control system of polyphase and multiple voltage type inverter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP62284039A JPH01126170A (en) | 1987-11-10 | 1987-11-10 | Control system of polyphase and multiple voltage type inverter |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| JPH01126170A true JPH01126170A (en) | 1989-05-18 |
Family
ID=17673507
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP62284039A Pending JPH01126170A (en) | 1987-11-10 | 1987-11-10 | Control system of polyphase and multiple voltage type inverter |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPH01126170A (en) |
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH03135323A (en) * | 1989-10-14 | 1991-06-10 | Mitsubishi Electric Corp | Multiple voltage type inverter apparatus |
| JP2003069351A (en) * | 2001-08-29 | 2003-03-07 | Yokogawa Analytical Systems Inc | High frequency amplifier circuit and drive method of the high frequency amplifier circuit |
| JP2008301704A (en) * | 2008-09-12 | 2008-12-11 | Hitachi Ltd | Power conversion apparatus |
Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS6285679A (en) * | 1985-10-07 | 1987-04-20 | Meidensha Electric Mfg Co Ltd | Gate signal generator for multiple inverter |
| JPS62193596A (en) * | 1986-02-18 | 1987-08-25 | Toshiba Corp | Inverter unit |
-
1987
- 1987-11-10 JP JP62284039A patent/JPH01126170A/en active Pending
Patent Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS6285679A (en) * | 1985-10-07 | 1987-04-20 | Meidensha Electric Mfg Co Ltd | Gate signal generator for multiple inverter |
| JPS62193596A (en) * | 1986-02-18 | 1987-08-25 | Toshiba Corp | Inverter unit |
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH03135323A (en) * | 1989-10-14 | 1991-06-10 | Mitsubishi Electric Corp | Multiple voltage type inverter apparatus |
| JP2003069351A (en) * | 2001-08-29 | 2003-03-07 | Yokogawa Analytical Systems Inc | High frequency amplifier circuit and drive method of the high frequency amplifier circuit |
| JP2008301704A (en) * | 2008-09-12 | 2008-12-11 | Hitachi Ltd | Power conversion apparatus |
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