JP6176663B2 - AC motor drive system - Google Patents

AC motor drive system Download PDF

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JP6176663B2
JP6176663B2 JP2013207887A JP2013207887A JP6176663B2 JP 6176663 B2 JP6176663 B2 JP 6176663B2 JP 2013207887 A JP2013207887 A JP 2013207887A JP 2013207887 A JP2013207887 A JP 2013207887A JP 6176663 B2 JP6176663 B2 JP 6176663B2
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大森　洋一
洋一 大森
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Toyo Electric Manufacturing Ltd
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本発明は、２台の３相電圧形ＰＷＭインバータで中性点が分離された巻線を有する交流電動機を駆動するシステムに関する。   The present invention relates to a system for driving an AC motor having a winding with a neutral point separated by two three-phase voltage type PWM inverters.

図２における従来技術について以下に説明する。交流電動機１は、中性点が分離した端子Ｕ１、Ｕ２のＵ相巻線と端子Ｖ１、Ｖ２のＶ相巻線と端子Ｗ１、Ｗ２のＷ相巻線が施されており、端子Ｕ１、Ｖ１、Ｗ１が３相ＰＷＭインバータ７の出力に接続されていて、端子Ｕ２、Ｖ２、Ｗ２が３相ＰＷＭインバータ８の出力に接続されている。３相ＰＷＭインバータ７には電圧Ｅ１の直流電圧源２から電力が供給されていて、３相ＰＷＭインバータ８には電圧Ｅ２のキャパシタ４から電力が供給されている。端子Ｕ１、Ｖ１、Ｗ１から端子Ｕ２、Ｖ２、Ｗ２へ流れる方向を正とする各相巻線ｉｕ、ｉｖ、ｉｗの電流は、電流検出器５により検出され、座標変換器１３で式１を用いて電流ベクトルＩの各成分ｉａ、ｉｂとなり、式２で静止座標のａ軸からの位相差θのｄ軸とそれに直交するｑ軸の成分に変換される。   The prior art in FIG. 2 will be described below. The AC motor 1 is provided with a U-phase winding of terminals U1 and U2, a terminal V1, a V-phase winding of V2, and a W-phase winding of terminals W1 and W2 separated from neutral points. , W1 are connected to the output of the three-phase PWM inverter 7, and the terminals U2, V2, W2 are connected to the output of the three-phase PWM inverter 8. The three-phase PWM inverter 7 is supplied with electric power from the DC voltage source 2 having the voltage E1, and the three-phase PWM inverter 8 is supplied with electric power from the capacitor 4 having the voltage E2. The current of each phase winding iu, iv, iw with the direction flowing from the terminals U1, V1, W1 to the terminals U2, V2, W2 as positive is detected by the current detector 5, and the coordinate converter 13 uses Equation 1 Thus, each component ia and ib of the current vector I is converted into a d-axis component of the phase difference θ from the a-axis of the stationary coordinates and a q-axis component orthogonal thereto by the equation (2).

Figure 0006176663
Figure 0006176663
Figure 0006176663
Figure 0006176663

電流指令演算器１１は、トルク指令Ｔｒと２次鎖交磁束の大きさ指令φ２ｒを入力し、交流電動機１の出力トルクＴと２次鎖交磁束ベクトルの大きさφ２がそれぞれ前記指令に一致するように、前記ｄ軸の電流の指令ｉｄｒとｑ軸の電流指令ｉｑｒを求めて出力する。キャパシタ４の電圧とその指令Ｅ２ｒとの差が減算器３８で求められ、比例積分増幅器２４で増幅されてキャパシタ電圧制御電流ｉｃが得られる。３相ＰＷＭインバータ７用のｄ軸電流指令ｉｄｒ１は、加算器２７でキャパシタ電圧制御電流ｉｃとｄ軸電流指令ｉｄｒとの和で得られる。３相ＰＷＭインバータ７用のｑ軸電流指令ｉｑｒ１は、減算器３７でｑ軸電流指令ｉｑｒからキャパシタ電圧制御電流ｉｃを引くことで得られる。また３相ＰＷＭインバータ８用のｄ軸電流指令ｉｄｒ２は、減算器３９でキャパシタ電圧制御電流ｉｃからｑ軸電流指令ｉｑｒを引くことで得られ、３相ＰＷＭインバータ８用のｑ軸電流指令ｉｑｒ２は、加算器３２でのキャパシタ電圧制御電流ｉｃとｄ軸電流指令ｉｄｒとの和で得られる。電流指令ｉｄｒ１、ｉｑｒ１と座標変換器１３出力のｉｄ、ｉｑとの偏差が減算器３５、３６で求められて、それぞれ比例積分増幅器２０、２１で増幅されて、非干渉制御器５５の出力との和を加算器２９、２８で求めることで３相ＰＷＭインバータ７用のｄ軸電圧指令ｖｄｒ１とｑ軸電圧指令ｖｑｒ１となる。同様に電流指令ｉｄｒ２、ｉｑｒ２と座標変換器１３出力のｉｄ、ｉｑとの偏差が減算器４１、４０で求められて、それぞれ比例積分増幅器２２、２３で増幅されて、非干渉制御器５６の出力との和を加算器３１、３０で求めることで３相ＰＷＭインバータ８用のｄ軸電圧指令ｖｄｒ２とｑ軸電圧指令ｖｑｒ２となる。ｖｄｒ１とｖｑｒ１は、座標変換器１２により、静止座標の電圧成分を持つ電圧指令ベクトルＶｉ１ｒに変換されて３相ＰＷＭインバータ７に出力される。３相ＰＷＭインバータ７は、入力した電圧指令ベクトル相当の電圧を出力する。ｖｄｒ２とｖｑｒ２は、座標変換器１４により、静止座標の電圧成分を持つ電圧指令ベクトルＶｉ２ｒに変換されて３相ＰＷＭインバータ８に出力される。３相ＰＷＭインバータ８は、入力した電圧指令ベクトル相当の電圧を出力する。座標演算器５７は、ｄ軸位相θを求めて座標変換器１２、１３、１４に出力する。   The current command calculator 11 receives the torque command Tr and the secondary linkage magnetic flux magnitude command φ2r, and the output torque T of the AC motor 1 and the secondary linkage flux vector magnitude φ2 respectively match the commands. Thus, the d-axis current command idr and the q-axis current command iqr are obtained and output. The difference between the voltage of the capacitor 4 and its command E2r is obtained by the subtractor 38 and amplified by the proportional-integral amplifier 24 to obtain the capacitor voltage control current ic. The d-axis current command idr1 for the three-phase PWM inverter 7 is obtained by the adder 27 as the sum of the capacitor voltage control current ic and the d-axis current command idr. The q-axis current command iqr1 for the three-phase PWM inverter 7 is obtained by subtracting the capacitor voltage control current ic from the q-axis current command iqr by the subtractor 37. The d-axis current command idr2 for the three-phase PWM inverter 8 is obtained by subtracting the q-axis current command iqr from the capacitor voltage control current ic by the subtractor 39, and the q-axis current command iqr2 for the three-phase PWM inverter 8 is The sum of the capacitor voltage control current ic and the d-axis current command idr in the adder 32 is obtained. Deviations between the current commands idr1 and iqr1 and the id and iq of the coordinate converter 13 are obtained by subtractors 35 and 36, amplified by proportional-integral amplifiers 20 and 21, respectively, and output from the non-interference controller 55. By obtaining the sum by the adders 29 and 28, the d-axis voltage command vdr1 and the q-axis voltage command vqr1 for the three-phase PWM inverter 7 are obtained. Similarly, deviations between the current commands idr2 and iqr2 and the id and iq of the coordinate converter 13 are obtained by the subtractors 41 and 40, amplified by the proportional-integral amplifiers 22 and 23, respectively, and output from the non-interference controller 56 Is obtained by the adders 31 and 30 to obtain the d-axis voltage command vdr2 and the q-axis voltage command vqr2 for the three-phase PWM inverter 8. The vdr1 and vqr1 are converted by the coordinate converter 12 into a voltage command vector Vi1r having a voltage component of stationary coordinates and output to the three-phase PWM inverter 7. The three-phase PWM inverter 7 outputs a voltage corresponding to the input voltage command vector. vdr2 and vqr2 are converted into a voltage command vector Vi2r having a voltage component of stationary coordinates by the coordinate converter 14 and output to the three-phase PWM inverter 8. The three-phase PWM inverter 8 outputs a voltage corresponding to the input voltage command vector. The coordinate calculator 57 calculates the d-axis phase θ and outputs it to the coordinate converters 12, 13, and 14.

このような構成にすることで、交流電動機１の出力トルクがトルク指令Ｔｒに追従するようになり、キャパシタ４の電圧Ｅ２はその指令Ｅ２ｒに一致するようになる。よって、交流電動機１が低い電圧しか必要としない低い回転数の時は、キャパシタ４の電圧を低い値に制御し、回転速度に応じてキャパシタ電圧を上げることで、交流電動機１の印加電圧の高調波成分を小さくすることができる。   With such a configuration, the output torque of the AC motor 1 follows the torque command Tr, and the voltage E2 of the capacitor 4 matches the command E2r. Therefore, when the AC motor 1 has a low rotational speed that requires only a low voltage, the voltage of the capacitor 4 is controlled to a low value, and the capacitor voltage is increased in accordance with the rotational speed, whereby the harmonic of the applied voltage of the AC motor 1 is increased. Wave components can be reduced.

町屋孟、芳賀仁、近藤正示著、「キャパシタ電圧と一定電圧源で駆動するオープン巻線誘導機の可変速制御法」、電気学会全国大会論文集第４分冊、２０１３年、ｐ．１８４Satoshi Machiya, Hitoshi Haga and Masami Kondo, “Variable Speed Control Method for Open Winding Induction Machines Driven by Capacitor Voltage and Constant Voltage Source”, Proceedings of the Annual Conference of the Institute of Electrical Engineers of Japan, 2013, p. 184

図２に示されている従来技術においては、キャパシタ４の電圧制御の為に、各軸の電流指令が補正されており、その電流指令に追従するように交流電動機１の電流を制御しているので、キャパシタ電圧制御によって電動機電流が変化し電動機制御特性が変化することとなる。つまり、電動機制御とキャパシタ電圧制御が分離されていないので、それぞれの制御が他方の制御に影響を及ぼすこととなり、比例積分増幅器２４の調整が困難となる。また、例えばｄ軸電流を制御するために２０と２２の２つの比例積分増幅器を使用していることから両者が干渉しあって制御が不安定になる可能性がある。   In the prior art shown in FIG. 2, the current command of each axis is corrected for voltage control of the capacitor 4, and the current of the AC motor 1 is controlled so as to follow the current command. Therefore, the motor current changes due to the capacitor voltage control, and the motor control characteristics change. That is, since the motor control and the capacitor voltage control are not separated, each control affects the other control, and adjustment of the proportional-integral amplifier 24 becomes difficult. Further, for example, since two proportional integration amplifiers 20 and 22 are used to control the d-axis current, both may interfere with each other and control may become unstable.

本発明は上記問題点を解決するためになされたものであり、両端にそれぞれＵ１Ｕ２とＶ１Ｖ２とＷ１Ｗ２の端子を有して互いに電気的に分離した３相対称巻線を有する交流電動機の前記Ｕ１、Ｖ１、Ｗ１端子から成る第１の端子群を第１の３相電圧形ＰＷＭインバータに接続すると共に、前記Ｕ２、Ｖ２、Ｗ２端子から成る第２の端子群を第２の３相電圧形ＰＷＭインバータに接続し、前記第１の３相電圧形ＰＷＭインバータの直流電圧源と前記第２の３相電圧形ＰＷＭインバータの直流電圧源とを分離した交流電動機ドライブシステムにおいて、前記Ｕ１、Ｖ１、Ｗ１端子から前記Ｕ２、Ｖ２、Ｗ２端子の方向を正として流れる前記交流電動機の各相の電流を検出して３相２相変換して電流ベクトルＩを出力する電流変換器と、前記Ｕ２、Ｖ２、Ｗ２端子からの前記Ｕ１、Ｖ１、Ｗ１端子の各電圧からなる前記交流電動機の各相電圧を３相２相変換した電圧ベクトルの電圧指令ベクトルＶｍｒを出力する電動機電圧指令生成器と、前記第２の３相電圧形ＰＷＭインバータの出力電力である電力指令Ｐ２を出力する電力指令器と、前記電流ベクトルＩと前記電圧指令ベクトルＶｍｒと前記電力指令Ｐ２とを入力して、第１の電圧指令ベクトルＶｉ１ｒと第２の電圧指令ベクトルＶｉ２ｒとの差を前記電圧指令ベクトルＶｍｒに一致させ、前記第２の電圧指令ベクトルＶｉ２ｒと前記電流ベクトルＩとの内積を前記電力指令Ｐ２の極性反転に一致させ、前記第２の電圧指令ベクトルＶｉ２ｒの大きさを前記第２の３相電圧形ＰＷＭインバータが出力可能な最大電圧ベクトルの大きさに制限した上で前記第１の電圧指令ベクトルＶｉ１ｒの大きさを最小とするような前記第１の電圧指令ベクトルＶｉ１ｒと前記第２の電圧指令ベクトルＶｉ２ｒとを出力するベクトル演算器とを具備し、前記第１の３相電圧形ＰＷＭインバータは前記第１の電圧指令ベクトルＶｉ１ｒを出力するように動作させ、前記第２の３相電圧形ＰＷＭインバータは前記第２の電圧指令ベクトルＶｉ２ｒを出力するように動作させることを特徴とする交流電動機ドライブシステム。 The present invention has been made in order to solve the above-mentioned problems, and the U1 of the AC motor having three-phase symmetrical windings having terminals U1U2, V1V2 and W1W2 at both ends and electrically separated from each other, A first terminal group consisting of V1 and W1 terminals is connected to a first three-phase voltage source PWM inverter, and a second terminal group consisting of U2, V2 and W2 terminals is connected to a second three-phase voltage source PWM inverter. In the AC motor drive system in which the DC voltage source of the first three-phase voltage source PWM inverter and the DC voltage source of the second three-phase voltage source PWM inverter are separated, the U1, V1, and W1 terminals A current converter for detecting a current of each phase of the AC motor flowing with the directions of the U2, V2, and W2 terminals being positive from each other and performing three-phase to two-phase conversion to output a current vector I; U2 A motor voltage command generator that outputs a voltage command vector Vmr of a voltage vector obtained by three-phase to two-phase conversion of each phase voltage of the AC motor consisting of voltages of the U1, V1, and W1 terminals from the V2 and W2 terminals; A power command device that outputs a power command P2 that is output power of the second three-phase voltage source PWM inverter, the current vector I, the voltage command vector Vmr, and the power command P2 are input, and the first voltage The difference between the command vector Vi1r and the second voltage command vector Vi2r is matched with the voltage command vector Vmr, and the inner product of the second voltage command vector Vi2r and the current vector I is matched with the polarity inversion of the power command P2. And the magnitude of the second voltage command vector Vi2r is the magnitude of the maximum voltage vector that can be output by the second three-phase voltage source PWM inverter. A vector calculator that outputs the first voltage command vector Vi1r and the second voltage command vector Vi2r so as to minimize the magnitude of the first voltage command vector Vi1r; The first three-phase voltage source PWM inverter is operated to output the first voltage command vector Vi1r, and the second three-phase voltage source PWM inverter is configured to output the second voltage command vector Vi2r. AC motor drive system characterized in that

本発明により、電圧指令生成器出力の電動機電圧指令ベクトルと第２の３相電圧形ＰＷＭインバータが出力する電力の指令から、ベクトル演算器により第１及び第２の３相電圧形ＰＷＭインバータの出力すべき電圧ベクトルを得ることができるので、電動機電圧制御とキャパシタ電圧制御を完全に切り離すことができ、電圧指令生成器に電動機制御機能を入れることで、電動機のトルク制御や電流制御からキャパシタ電圧制御を完全に切り離すことができる。   According to the present invention, from the motor voltage command vector output from the voltage command generator and the power command output from the second three-phase voltage source PWM inverter, the vector calculator outputs the first and second three-phase voltage source PWM inverters. Since the voltage vector to be obtained can be obtained, the motor voltage control and the capacitor voltage control can be completely separated, and by adding the motor control function to the voltage command generator, the capacitor voltage control from the torque control and current control of the motor Can be completely separated.

本発明の交流電動機ドライブシステムを示した説明図である。（実施例１）It is explanatory drawing which showed the alternating current motor drive system of this invention. Example 1 従来の交流電動機ドライブシステムを示した説明図である。It is explanatory drawing which showed the conventional alternating current motor drive system.

図１は、本発明の交流電動機ドライブシステムを示した説明図であり、この図に基づいて実施例１の説明を以下に示す。電圧指令生成器７０は、式３に示されるＶｍａ、Ｖｍｂを成分とする交流電動機１の電圧ベクトルＶｍの指令Ｖｍｒを出力する。電圧指令生成器７０において、例えばＶ／ｆ一定制御を行うのであればその結果としての電圧指令ベクトルを、または交流電動機１の出力トルク制御を行うのであればその為のベクトル制御演算結果としての電圧指令ベクトルを出力することとなる。電流検出器５で検出した交流電動機１の電流から電流ベクトル変換器６６は、式１の演算でｉａ、ｉｂを成分とする電流ベクトルＩを出力する。減算器４５でキャパシタ４の電圧Ｅ２とその指令Ｅ２ｒとの偏差を求め、比例積分増幅器２６で増幅して３相ＰＷＭインバータ８の出力電力の指令Ｐ２が得られる。つまり、３相ＰＷＭインバータ８の出力電力がＰ２に追従するならば、Ｐ２が正ならばキャパシタ４の電圧Ｅ２は減少し、Ｐ２が負ならばＥ２は増加することとなる。ベクトル演算器８０は、電流ベクトルＩと電圧指令ベクトルＶｍｒと３相ＰＷＭインバータ８出力電力指令Ｐ２とを入力して以下の手順で３相ＰＷＭインバータ７の出力電圧ベクトルの指令Ｖｉ１ｒと３相ＰＷＭインバータ８の出力電圧ベクトルの指令Ｖｉ２ｒを出力する。   FIG. 1 is an explanatory view showing an AC motor drive system of the present invention, and a description of the first embodiment will be given below based on this figure. The voltage command generator 70 outputs a command Vmr of the voltage vector Vm of the AC motor 1 having Vma and Vmb shown in Equation 3 as components. In the voltage command generator 70, for example, if the V / f constant control is performed, the resulting voltage command vector, or if the output torque control of the AC motor 1 is performed, the voltage as the vector control calculation result therefor A command vector is output. From the current of the AC motor 1 detected by the current detector 5, the current vector converter 66 outputs a current vector I having ia and ib as components in the calculation of Equation 1. The subtracter 45 obtains the deviation between the voltage E2 of the capacitor 4 and its command E2r, and amplifies it by the proportional-integral amplifier 26 to obtain the command P2 of the output power of the three-phase PWM inverter 8. That is, if the output power of the three-phase PWM inverter 8 follows P2, the voltage E2 of the capacitor 4 decreases if P2 is positive, and E2 increases if P2 is negative. The vector calculator 80 receives the current vector I, the voltage command vector Vmr, and the three-phase PWM inverter 8 output power command P2, and outputs the output voltage vector command Vi1r of the three-phase PWM inverter 7 and the three-phase PWM inverter in the following procedure. 8 output voltage vector command Vi2r is output.

Figure 0006176663
Figure 0006176663

ベクトル演算器８０において、電流ベクトルＩと電圧指令ベクトルＶｍｒとが原点Ｏを基準に描かれたベクトル図上で、電圧指令ベクトルＶｍｒの頂点Ａを通る電流ベクトルＩに平行な線ａを描き、該線ａ上で電流ベクトルＩの逆向きを正として頂点Ａからの距離を、電力指令Ｐ２を電流ベクトルＩの大きさで除した値とした点Ｂをとり、点Ｂから前記線ａに垂直な垂線ｂを描き、原点Ｏを通り電流ベクトルＩに平行な線ｃと垂線ｂとの交点をＣとし、３相電圧形ＰＷＭインバータ８が出力できる電圧ベクトルの最大の大きさＶｉ２ｘを半径として頂点Ａを中心とする円弧ｄと垂線ｂとの交点をＤとし、交点Ｃと交点Ｄのなかで頂点Ａからの距離が短い方を交点Ｅとし、頂点Ａから交点Ｅに向くベクトルを電圧指令ベクトルＶｉ２ｒとして出力し、原点Ｏから交点Ｅに向くベクトルを電圧指令ベクトルＶｉ１ｒとして出力する。   In the vector computing unit 80, a line a parallel to the current vector I passing through the vertex A of the voltage command vector Vmr is drawn on the vector diagram in which the current vector I and the voltage command vector Vmr are drawn with the origin O as a reference. On the line a, the point B is defined as the value obtained by dividing the power command P2 by the magnitude of the current vector I with the reverse direction of the current vector I being positive and the distance from the vertex A being perpendicular to the line a. A perpendicular line b is drawn, the intersection point of the line c and the perpendicular line b passing through the origin O and parallel to the current vector I is defined as C, and the maximum voltage vector Vi2x that can be output by the three-phase voltage source PWM inverter 8 is defined as the radius A. The intersection point of the arc d and the perpendicular line b centered at is D, the shortest distance from the vertex A among the intersection points C and D is the intersection point E, and the vector from the vertex A toward the intersection point E is the voltage command vector Vi2r. As out , And it outputs a vector directed from the origin O at the intersection E as a voltage vector Vi1r.

３相ＰＷＭインバータ７は、入力した電圧指令ベクトルＶｉ１ｒ通りの電圧を出力し、３相ＰＷＭインバータ８は、入力した電圧指令ベクトルＶｉ２ｒ通りの電圧を出力する。   The three-phase PWM inverter 7 outputs a voltage according to the input voltage command vector Vi1r, and the three-phase PWM inverter 8 outputs a voltage according to the input voltage command vector Vi2r.

以上の構成により、ベクトル演算器８０において、Ｖｉ１ｒ＝Ｖｍｒ＋Ｖｉ２ｒの関係があり、３相ＰＷＭインバータ７の出力電圧ベクトルＶｉ１と３相ＰＷＭインバータ８の出力電圧ベクトルＶｉ２と交流電動機１の電圧ベクトルＶｍにはＶｉ１＝Ｖｍ＋Ｖｉ２の関係があり、３相ＰＷＭインバータ７や３相ＰＷＭインバータ８はＶｉ１＝Ｖｉ１ｒ、Ｖｉ２＝Ｖｉ２ｒとするので、電圧指令ベクトルＶｍｒ通りの電圧が交流電動機１に印加されることとなる。また、ベクトル演算器８０において、電流ベクトルＩと電圧指令ベクトルＶｉ２ｒとの内積が（−Ｐ２）と一致するようにしているので、３相ＰＷＭインバータ８の出力電力をＰ２とすることができる。しかも、交流電動機１の印加電圧ベクトルと３相ＰＷＭインバータ８の出力電力をそれぞれ指令通りとした上で、３相ＰＷＭインバータ７が出力する電圧指令ベクトルＶｉ１の大きさを最小とすることができるため、３相ＰＷＭインバータ７の直流電圧源２の電圧Ｅ１を最小限にすることができる。   With the above configuration, the vector calculator 80 has a relationship of Vi1r = Vmr + Vi2r, and the output voltage vector Vi1 of the three-phase PWM inverter 7, the output voltage vector Vi2 of the three-phase PWM inverter 8, and the voltage vector Vm of the AC motor 1 are There is a relationship of Vi1 = Vm + Vi2, and the three-phase PWM inverter 7 and the three-phase PWM inverter 8 have Vi1 = Vi1r and Vi2 = Vi2r. Further, in the vector calculator 80, the inner product of the current vector I and the voltage command vector Vi2r is made to coincide with (−P2), so that the output power of the three-phase PWM inverter 8 can be P2. In addition, since the applied voltage vector of the AC motor 1 and the output power of the three-phase PWM inverter 8 are set as commanded, the magnitude of the voltage command vector Vi1 output from the three-phase PWM inverter 7 can be minimized. The voltage E1 of the DC voltage source 2 of the three-phase PWM inverter 7 can be minimized.

本発明により、電源が区別された２台の３相電圧形ＰＷＭインバータで中性点が分離された巻線を有する交流電動機を駆動するシステムにおいて、交流電動機制御とは無関係に片方の３相電圧形ＰＷＭインバータの出力電力制御が可能となる。これによって例えば片方の３相電圧形ＰＷＭインバータの電源を燃料電池とし、他方の３相電圧形ＰＷＭインバータの電源をキャパシタやバッテリとした電気自動車の交流電動機に適用した場合、交流電動機制御と独立してキャパシタやバッテリの充放電電力を制御できるようになるだけでなく、交流電動機には、燃料電池電圧とキャパシタやバッテリの電圧との和の電圧を印加できるようになり、交流電動機の高速運転が可能となる。   According to the present invention, in a system for driving an AC motor having windings with neutral points separated by two three-phase voltage type PWM inverters with different power sources, one of the three-phase voltages is independent of the AC motor control. The output power of the PWM inverter can be controlled. Thus, for example, when applied to an AC motor of an electric vehicle in which the power source of one of the three-phase voltage source PWM inverters is a fuel cell and the power source of the other three-phase voltage source PWM inverter is a capacitor or a battery, it is independent of the AC motor control. In addition to being able to control the charge / discharge power of the capacitor and battery, the AC motor can be applied with the sum of the fuel cell voltage and the voltage of the capacitor and battery, enabling high-speed operation of the AC motor. It becomes possible.

１ 交流電動機
２、３ 直流電圧源
４ キャパシタ
５ 電流検出器
７、８ ３相ＰＷＭインバータ
１１ 電流指令演算器
１２〜１４ 座標変換器
２０〜２４、２６ 比例積分増幅器
２７〜３２ 加算器
３５〜４１、４５ 減算器
５５、５６ 非干渉制御器
５７ 座標演算器
６６ 電流ベクトル変換器
７０ 電圧指令生成器
８０ ベクトル演算器 DESCRIPTION OF SYMBOLS 1 AC motor 2, 3 DC voltage source 4 Capacitor 5 Current detector 7, 8 Three-phase PWM inverter 11 Current command calculator 12-14 Coordinate converter 20-24, 26 Proportional integral amplifier 27-32 Adder 35-41, 45 Subtractor 55, 56 Non-interference controller 57 Coordinate calculator 66 Current vector converter 70 Voltage command generator 80 Vector calculator

Claims (1)

両端にそれぞれＵ１Ｕ２とＶ１Ｖ２とＷ１Ｗ２の端子を有して互いに電気的に分離した３相対称巻線を有する交流電動機の前記Ｕ１、Ｖ１、Ｗ１端子から成る第１の端子群を第１の３相電圧形ＰＷＭインバータに接続すると共に、前記Ｕ２、Ｖ２、Ｗ２端子から成る第２の端子群を第２の３相電圧形ＰＷＭインバータに接続し、前記第１の３相電圧形ＰＷＭインバータの直流電圧源と前記第２の３相電圧形ＰＷＭインバータの直流電圧源とを分離した交流電動機ドライブシステムにおいて、
前記Ｕ１、Ｖ１、Ｗ１端子から前記Ｕ２、Ｖ２、Ｗ２端子の方向を正として流れる前記交流電動機の各相の電流を検出して３相２相変換して電流ベクトルＩを出力する電流変換器と、前記Ｕ２、Ｖ２、Ｗ２端子からの前記Ｕ１、Ｖ１、Ｗ１端子の各電圧からなる前記交流電動機の各相電圧を３相２相変換した電圧ベクトルの電圧指令ベクトルＶｍｒを出力する電動機電圧指令生成器と、前記第２の３相電圧形ＰＷＭインバータの出力電力である電力指令Ｐ２を出力する電力指令器と、前記電流ベクトルＩと前記電圧指令ベクトルＶｍｒと前記電力指令Ｐ２とを入力して、第１の電圧指令ベクトルＶｉ１ｒと第２の電圧指令ベクトルＶｉ２ｒとの差を前記電圧指令ベクトルＶｍｒに一致させ、前記第２の電圧指令ベクトルＶｉ２ｒと前記電流ベクトルＩとの内積を前記電力指令Ｐ２の極性反転に一致させ、前記第２の電圧指令ベクトルＶｉ２ｒの大きさを前記第２の３相電圧形ＰＷＭインバータが出力可能な最大電圧ベクトルの大きさに制限した上で前記第１の電圧指令ベクトルＶｉ１ｒの大きさを最小とするような前記第１の電圧指令ベクトルＶｉ１ｒと前記第２の電圧指令ベクトルＶｉ２ｒとを出力するベクトル演算器とを具備し、前記第１の３相電圧形ＰＷＭインバータは前記第１の電圧指令ベクトルＶｉ１ｒを出力するように動作させ、前記第２の３相電圧形ＰＷＭインバータは前記第２の電圧指令ベクトルＶｉ２ｒを出力するように動作させることを特徴とする交流電動機ドライブシステム。

A first terminal group consisting of the U1, V1, and W1 terminals of an AC motor having three-phase symmetrical windings that have U1U2, V1V2, and W1W2 terminals at both ends and electrically separated from each other is defined as a first three-phase. A DC voltage of the first three-phase voltage source PWM inverter is connected to a voltage type PWM inverter and a second terminal group consisting of the U2, V2 and W2 terminals is connected to a second three-phase voltage source PWM inverter. AC motor drive system in which a power source and a DC voltage source of the second three-phase voltage source PWM inverter are separated,
A current converter for detecting a current of each phase of the AC motor flowing from the U1, V1, W1 terminals as positive in the direction of the U2, V2, W2 terminals, converting the current into three phases and two phases, and outputting a current vector I; Motor voltage command generation that outputs a voltage command vector Vmr of a voltage vector obtained by three-phase to two-phase conversion of each phase voltage of the AC motor composed of the voltages of the U1, V1, and W1 terminals from the U2, V2, and W2 terminals A power command device that outputs a power command P2 that is output power of the second three-phase voltage source PWM inverter, the current vector I, the voltage command vector Vmr, and the power command P2. The difference between the first voltage command vector Vi1r and the second voltage command vector Vi2r is made to coincide with the voltage command vector Vmr, and the second voltage command vector Vi2r and the current vector are matched. The inner product with the torque I coincides with the polarity inversion of the power command P2, and the magnitude of the second voltage command vector Vi2r is set to the magnitude of the maximum voltage vector that can be output by the second three-phase voltage source PWM inverter. A vector calculator that outputs the first voltage command vector Vi1r and the second voltage command vector Vi2r so as to minimize the magnitude of the first voltage command vector Vi1r; The first three-phase voltage source PWM inverter is operated to output the first voltage command vector Vi1r, and the second three-phase voltage source PWM inverter is configured to output the second voltage command vector Vi2r. AC motor drive system characterized in that

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