JP4626628B2 - Pulse width measuring device, pulse width measuring method, optical transmission line dispersion detection device, and optical transmission line dispersion detection method - Google Patents

Pulse width measuring device, pulse width measuring method, optical transmission line dispersion detection device, and optical transmission line dispersion detection method Download PDF

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JP4626628B2
JP4626628B2 JP2007112769A JP2007112769A JP4626628B2 JP 4626628 B2 JP4626628 B2 JP 4626628B2 JP 2007112769 A JP2007112769 A JP 2007112769A JP 2007112769 A JP2007112769 A JP 2007112769A JP 4626628 B2 JP4626628 B2 JP 4626628B2
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昌俊 賀川
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Oki Electric Industry Co Ltd
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本発明は、パルス幅測定装置及びパルス幅測定方法に関し、例えば、光パルスが間欠的に生じている光信号（光パルス列）における光パルス幅の測定に適用し得るものである。   The present invention relates to a pulse width measurement device and a pulse width measurement method, and can be applied to, for example, measurement of an optical pulse width in an optical signal (optical pulse train) in which optical pulses are intermittently generated.

また、他の本発明は、光伝送路分散検出装置及び光伝送路分散検出方法に関し、特に、光パルス幅の測定結果を利用して、光伝送路の分散変動を検出しようとしたものである。   Another aspect of the present invention relates to an optical transmission line dispersion detection device and an optical transmission line dispersion detection method, and in particular, attempts to detect dispersion fluctuations in an optical transmission line by using an optical pulse width measurement result. .

例えば、ＲＺ光信号は、光パルス（光短パルス）が時間軸上で間欠的に存在するもの（光短パルス列）である。このような光信号における光パルスのパルス幅を測定する方法として、従来、入力された光短パルス列（光信号）を２分岐し、分岐した一方の光短パルス列を遅延させた後、非線形光学結晶に入力し、分岐した他方の光短パルス列との相関波形（自己相関波形）を得、この相関波形の形状に基づいて、パルス幅を測定する方法が一般的である。しかしながら、自己相関波形の形状を測定する方法は、強度が揃った光短パルス列を入力する方法であり、信号伝送に用いる強度変調された信号には適用することができない。   For example, an RZ optical signal is an optical pulse (optical short pulse train) in which optical pulses (optical short pulses) exist intermittently on the time axis. As a method for measuring the pulse width of an optical pulse in such an optical signal, conventionally, an input optical short pulse train (optical signal) is bifurcated, one of the branched optical short pulse trains is delayed, and then a nonlinear optical crystal In general, a correlation waveform (autocorrelation waveform) with the other optical short pulse train branched from the other is obtained, and the pulse width is measured based on the shape of the correlation waveform. However, the method of measuring the shape of the autocorrelation waveform is a method of inputting an optical short pulse train with uniform intensity, and cannot be applied to an intensity-modulated signal used for signal transmission.

また、装置内部にサンプリング光パルスを有し、このサンプリング光パルスと入力光信号の強度相関光を得て、この強度を、計算機を用いて再配置することで入力光信号の波形を観測できる光波形測定法がある。このサンプリング光パルスを用いる方式は、入力する信号の偏光方向とサンプリング光パルスの偏光方向、及び、用いる非線形光学結晶の結晶軸方向を合わせることにより、測定に必要な感度が得られる。これらの調整は煩雑な作業を伴う。しかしながら、入力光を２つの偏光方向に分離し、それぞれの偏光方向で強度相関を得る偏波ダイバーシティ法や、特許文献１に記載の従来技術で示されるような、入力される光信号の偏光状態を制御する方法が考案されている。   In addition, there is a sampling light pulse inside the device, the intensity correlation light of this sampling light pulse and the input optical signal is obtained, and this intensity is rearranged using a computer, and the waveform of the input optical signal can be observed There is a waveform measurement method. In the method using the sampling light pulse, sensitivity required for measurement can be obtained by matching the polarization direction of the input signal with the polarization direction of the sampling light pulse and the crystal axis direction of the nonlinear optical crystal to be used. These adjustments involve complicated operations. However, the polarization state of the input optical signal as shown in the polarization diversity method in which the input light is separated into two polarization directions and intensity correlation is obtained in each polarization direction, or the prior art described in Patent Document 1. A method has been devised.

また、光伝送路の波長分散を検出する方法として、日本工業規格（非特許文献１参照）で定められているように、位相法、パルス法、微分位相法、干渉法などがある。
特開２００６−１９４８４２ ＪＩＳ Ｃ ６８２７ As a method for detecting chromatic dispersion in an optical transmission line, there are a phase method, a pulse method, a differential phase method, an interference method and the like as defined in Japanese Industrial Standard (see Non-Patent Document 1).
JP 2006-194842 A JIS C 6827

しかしながら、光パルス幅を測定する上述した光波形測定法は、偏光状態を制御した上での光波形を観測する手法であり、しかも、光波形からパルス幅を特定するためには、ソフトウェアによる解析手法が必要となっている。例えば、偏光状態を適切に制御し得ないで、ソフトウェアによる解析を行った場合には、そのソフトウェアによる解析が無駄になってしまう。   However, the optical waveform measurement method described above for measuring the optical pulse width is a method of observing the optical waveform with the polarization state controlled, and in addition, in order to identify the pulse width from the optical waveform, analysis by software A technique is needed. For example, when the analysis by software is performed without properly controlling the polarization state, the analysis by the software is wasted.

また、光伝送路の波長分散を検出する日本工業規格で規定されている波長分散測定法は、光ファイバなどの測定対象を測定装置に接続し、特別な信号を入力する方式であり、信号伝送に用いる送受信器を接続した状態で、波長分散を測定することができない。   In addition, the chromatic dispersion measurement method stipulated in the Japanese Industrial Standard for detecting chromatic dispersion in an optical transmission line is a method in which a measurement object such as an optical fiber is connected to a measurement device, and a special signal is input. It is impossible to measure chromatic dispersion in a state where the transmitter / receiver used in the above is connected.

そのため、被測定光の偏光状態の制御を必要とせず、実際に信号伝送に用いられる変調された信号に対しても、簡便にパルス幅を測定することができるパルス幅測定装置及びパルス幅測定方法が望まれている。   Therefore, it is not necessary to control the polarization state of the light to be measured, and a pulse width measuring device and a pulse width measuring method that can easily measure the pulse width even for a modulated signal actually used for signal transmission Is desired.

また、信号伝送に用いる送受信機を接続した状態でも、波長分散又はその変動を検出することができる光伝送路分散検出装置及び光伝送路分散検出方法が望まれている。   There is also a demand for an optical transmission line dispersion detection device and an optical transmission line dispersion detection method that can detect chromatic dispersion or variations thereof even when a transceiver used for signal transmission is connected.

第１の本発明は、パルス信号のパルス幅を測定するパルス幅測定装置において、（１）検出対象のパルス信号を２分岐する分岐手段と、（２）分岐された一方のパルス信号が入力され、そのパルス信号に対し、固定帯域の帯域制限を行ってパルス信号のパルス幅を伸長してピークタイミングを遅延させるフィルタ手段と、（３）分岐された他方のパルス信号と、上記フィルタ手段を介して遅延されたパルス信号との時間差を検出する時間差検出手段と、（４）検出された時間差をパルス幅に変換する時間差／パルス幅変換手段とを有し、（５）上記時間差検出手段は、第１及び第２の位相同期ループを有し、（５−１）第１の位相同期ループは、上記フィルタ手段を介することなく入力された周波数ｆの第１のパルス信号に対して、周波数Δｆの局部発振信号と周波数ｆの第１の位相同期後信号とが混合されて得られた所定周波数ｆ−Δｆの第１の参照信号を用いて変調し、第１のパルス信号と第１の参照信号との間での周波数Δｆの第１のビート信号を得ると共に、得られた第１のビート信号を、上記第１の参照信号に位相同期させ、かつ、検出対象の第１のパルス信号が意図している周波数ｆの上記第１の位相同期後信号に変換し、（５−２）第２の位相同期ループは、上記フィルタ手段を介して入力された周波数ｆの第２のパルス信号に対して、周波数Δｆの局部発振信号と周波数ｆの第２の位相同期後信号とが混合されて得られた所定周波数ｆ−Δｆの第２の参照信号を用いて変調し、第２のパルス信号と第２の参照信号との間での周波数Δｆの第２のビート信号を得ると共に、得られた第２のビート信号を、上記第２の参照信号に位相同期させ、かつ、検出対象の第２のパルス信号が意図している周波数ｆの上記第２の位相同期後信号に変換し、（５−３）これら第１及び第２の位相同期ループにおける第１及び第２の位相同期後信号の時間差を検出信号として出力することを特徴とする。 According to a first aspect of the present invention, in a pulse width measuring apparatus for measuring a pulse width of a pulse signal, (1) branching means for branching a pulse signal to be detected into two and (2) one of the branched pulse signals is inputted. A filter means for performing band limitation on the pulse signal to extend the pulse width of the pulse signal to delay the peak timing; (3) the other branched pulse signal; and the filter means and time difference detecting means for detecting a time difference between the delayed pulse signal Te, (4) the detected time difference have a time difference / pulse width conversion means for converting the pulse width, (5) the time difference detecting means, (5-1) The first phase-locked loop has a frequency Δ with respect to the first pulse signal having the frequency f inputted without passing through the filter means. The first pulse signal and the first reference are modulated by using the first reference signal having a predetermined frequency f−Δf obtained by mixing the local oscillation signal of the first frequency and the signal after the first phase synchronization of the frequency f. A first beat signal having a frequency Δf with respect to the signal is obtained, and the obtained first beat signal is phase-synchronized with the first reference signal, and the first pulse signal to be detected is The first phase-locked signal having the intended frequency f is converted into the signal after the first phase-locking, and (5-2) the second phase-locked loop is converted into the second pulse signal having the frequency f inputted through the filter means. On the other hand, the second pulse signal is modulated using a second reference signal having a predetermined frequency f−Δf obtained by mixing the local oscillation signal having the frequency Δf and the second phase-synchronized signal having the frequency f. And obtaining a second beat signal of frequency Δf between the first reference signal and the second reference signal The obtained second beat signal is phase-synchronized with the second reference signal and converted into the second phase-synchronized signal having the frequency f intended by the second pulse signal to be detected. (5-3) The time difference between the first and second phase-synchronized signals in the first and second phase-locked loops is output as a detection signal .

第２の本発明は、パルス信号のパルス幅を測定するパルス幅測定方法において、（１）分岐手段は、検出対象のパルス信号を２分岐し、（２）フィルタ手段は、入力された分岐された一方のパルス信号に対し、固定帯域の帯域制限を行ってパルス信号のパルス幅を伸長してピークタイミングを遅延させ、（３）時間差検出手段は、分岐された他方のパルス信号と、上記フィルタ手段を介して遅延されたパルス信号との時間差を検出し、（４）時間差／パルス幅変換手段は、検出された時間差をパルス幅に変換し、（５）上記時間差検出手段は、第１及び第２の位相同期ループを有し、（５−１）第１の位相同期ループは、上記フィルタ手段を介することなく入力された周波数ｆの第１のパルス信号に対して、周波数Δｆの局部発振信号と周波数ｆの第１の位相同期後信号とが混合されて得られた所定周波数ｆ−Δｆの第１の参照信号を用いて変調し、第１のパルス信号と第１の参照信号との間での周波数Δｆの第１のビート信号を得ると共に、得られた第１のビート信号を、上記第１の参照信号に位相同期させ、かつ、検出対象の第１のパルス信号が意図している周波数ｆの上記第１の位相同期後信号に変換し、（５−２）第２の位相同期ループは、上記フィルタ手段を介して入力された周波数ｆの第２のパルス信号に対して、周波数Δｆの局部発振信号と周波数ｆの第２の位相同期後信号とが混合されて得られた所定周波数ｆ−Δｆの第２の参照信号を用いて変調し、第２のパルス信号と第２の参照信号との間での周波数Δｆの第２のビート信号を得ると共に、得られた第２のビート信号を、上記第２の参照信号に位相同期させ、かつ、検出対象の第２のパルス信号が意図している周波数ｆの上記第２の位相同期後信号に変換し、（５−３）これら第１及び第２の位相同期ループにおける第１及び第２の位相同期後信号の時間差を検出信号として出力することを特徴とする。 According to a second aspect of the present invention, in the pulse width measuring method for measuring the pulse width of a pulse signal, (1) the branching means splits the pulse signal to be detected into two branches, and (2) the filter means splits the input branch. For one of the pulse signals, band limitation of a fixed band is performed to extend the pulse width of the pulse signal to delay the peak timing. (3) The time difference detecting means includes the other branched pulse signal and the filter Detecting a time difference with the pulse signal delayed through the means; (4) the time difference / pulse width conversion means converts the detected time difference into a pulse width ; and (5) the time difference detection means includes the first and (5-1) The first phase-locked loop has a local oscillation of frequency Δf with respect to the first pulse signal of frequency f input without passing through the filter means. Signal and frequency Modulation is performed using a first reference signal having a predetermined frequency f−Δf obtained by mixing the first phase-synchronized signal with f, and the first pulse signal and the first reference signal are modulated. A first beat signal having a frequency Δf is obtained, the obtained first beat signal is phase-synchronized with the first reference signal, and the frequency f intended by the first pulse signal to be detected is obtained. (5-2) The second phase-locked loop has a frequency Δf with respect to the second pulse signal of the frequency f input through the filter means. A second pulse signal and a second reference signal are modulated by using a second reference signal having a predetermined frequency f−Δf obtained by mixing the local oscillation signal and the second phase-synchronized signal having the frequency f. To obtain a second beat signal of frequency Δf between and Are phase-synchronized with the second reference signal, and converted into the second phase-synchronized signal having the frequency f intended by the second pulse signal to be detected, (5-3) The time difference between the first and second phase-synchronized signals in the first and second phase-locked loops is output as a detection signal .

第３の本発明は、光伝送路での波長分散を検出する光伝送路分散検出装置において、（１）上記光伝送路を介した後のパルス信号のパルス幅を測定する通過後光パルス幅測定装置と、（２）上記光伝送路を介する前のパルス信号のパルス幅について、上記光伝送路を介した後のパルス信号のパルス幅と上記光伝送路の波長分散値との関係情報を保持している変換用情報保持手段と、（３）上記通過後光パルス幅測定装置による測定パルス幅を、上記変換用情報保持手段が保持している情報に当て嵌めて、上記光伝送路の波長分散値を得る情報変換手段とを有している。通過後光パルス幅測定装置は、（４−１）入力されたパルス信号を２分岐する第１の分岐手段と、（４−２）分岐された一方のパルス信号が入力され、そのパルス信号に対し、固定帯域の帯域制限を行ってパルス信号のパルス幅を伸長してピークタイミングを遅延させる第１のフィルタ手段と、（４−３）分岐された他方のパルス信号と、上記第１のフィルタ手段を介して遅延されたパルス信号との時間差を検出する第１の時間差検出手段と、（４−４）検出された時間差をパルス幅に変換する第１の時間差／パルス幅変換手段とを有し、（５）上記第１の時間差検出手段は、第１及び第２の位相同期ループを有し、（５−１）第１の位相同期ループは、上記第１のフィルタ手段を介することなく入力された周波数ｆの第１のパルス信号に対して、周波数Δｆの局部発振信号と周波数ｆの第１の位相同期後信号とが混合されて得られた所定周波数ｆ−Δｆの第１の参照信号を用いて変調し、第１のパルス信号と第１の参照信号との間での周波数Δｆの第１のビート信号を得ると共に、得られた第１のビート信号を、上記第１の参照信号に位相同期させ、かつ、検出対象の第１のパルス信号が意図している周波数ｆの上記第１の位相同期後信号に変換し、（５−２）第２の位相同期ループは、上記第１のフィルタ手段を介して入力された周波数ｆの第２のパルス信号に対して、周波数Δｆの局部発振信号と周波数ｆの第２の位相同期後信号とが混合されて得られた所定周波数ｆ−Δｆの第２の参照信号を用いて変調し、第２のパルス信号と第２の参照信号との間での周波数Δｆの第２のビート信号を得ると共に、得られた第２のビート信号を、上記第２の参照信号に位相同期させ、かつ、検出対象の第２のパルス信号が意図している周波数ｆの上記第２の位相同期後信号に変換し、（５−３）これら第１及び第２の位相同期ループにおける第１及び第２の位相同期後信号の時間差を検出信号として出力する。
ここで、上記光伝送路を介する前のパルス信号のパルス幅を測定する通過前光パルス幅測定装置を有することが好ましく、通過前光パルス幅測定装置の構成として、（６−１）入力されたパルス信号を２分岐する第２の分岐手段と、（６−２）分岐された一方のパルス信号が入力され、そのパルス信号に対し、固定帯域の帯域制限を行ってパルス信号のパルス幅を伸長してピークタイミングを遅延させる第２のフィルタ手段と、（６−３）分岐された他方のパルス信号と、上記第２のフィルタ手段を介して遅延されたパルス信号との時間差を検出する第２の時間差検出手段と、（６−４）検出された時間差をパルス幅に変換する第２の時間差／パルス幅変換手段とを有し、（７）上記第２の時間差検出手段は、第３及び第４の位相同期ループを有し、（７−１）第３の位相同期ループは、上記第２のフィルタ手段を介することなく入力された周波数ｆの第３のパルス信号に対して、周波数Δｆの局部発振信号と周波数ｆの第３の位相同期後信号とが混合されて得られた所定周波数ｆ−Δｆの第３の参照信号を用いて変調し、第３のパルス信号と第３の参照信号との間での周波数Δｆの第３のビート信号を得ると共に、得られた第３のビート信号を、上記第３の参照信号に位相同期させ、かつ、検出対象の第３のパルス信号が意図している周波数ｆの上記第３の位相同期後信号に変換し、（７−２）第４の位相同期ループは、上記第２のフィルタ手段を介して入力された周波数ｆの第４のパルス信号に対して、周波数Δｆの局部発振信号と周波数ｆの第４の位相同期後信号とが混合されて得られた所定周波数ｆ−Δｆの第４の参照信号を用いて変調し、第４のパルス信号と第４の参照信号との間での周波数Δｆの第４のビート信号を得ると共に、得られた第４のビート信号を、上記第４の参照信号に位相同期させ、かつ、検出対象の第４のパルス信号が意図している周波数ｆの上記第４の位相同期後信号に変換し、（７−３）これら第３及び第４の位相同期ループにおける第３及び第４の位相同期後信号の時間差を検出信号として出力するものを適用できる。 According to a third aspect of the present invention, there is provided an optical transmission line dispersion detecting device for detecting chromatic dispersion in an optical transmission line. (1) A post-passage optical pulse width for measuring a pulse width of a pulse signal after passing through the optical transmission line. (2) With respect to the pulse width of the pulse signal before passing through the optical transmission path, (2) the relationship information between the pulse width of the pulse signal after passing through the optical transmission path and the chromatic dispersion value of the optical transmission path Holding the conversion information holding means, and (3) fitting the measured pulse width by the post-passage optical pulse width measuring device to the information held by the conversion information holding means, Information conversion means for obtaining a chromatic dispersion value. The post-passage optical pulse width measuring device includes: (4-1) a first branching unit that branches the input pulse signal into two; (4-2) one of the branched pulse signals is input, and the pulse signal is On the other hand, the first filter means for delaying the peak timing by extending the pulse width of the pulse signal by performing band limitation of the fixed band, (4-3) the other branched pulse signal, and the first filter A first time difference detecting means for detecting a time difference from the pulse signal delayed through the means; and (4-4) a first time difference / pulse width converting means for converting the detected time difference into a pulse width. (5) The first time difference detection means includes first and second phase locked loops, and (5-1) the first phase locked loop does not pass through the first filter means. To the input first pulse signal of frequency f On the other hand, the first pulse signal is modulated using the first reference signal having a predetermined frequency f−Δf obtained by mixing the local oscillation signal having the frequency Δf and the first phase-synchronized signal having the frequency f. A first beat signal having a frequency Δf between the first reference signal and the first reference signal is obtained, the obtained first beat signal is phase-synchronized with the first reference signal, and the first beat signal to be detected is detected. 1 pulse signal is converted to the first post-phase-locked signal of the intended frequency f, and (5-2) the second phase-locked loop is the frequency input via the first filter means Using a second reference signal having a predetermined frequency f−Δf obtained by mixing a local oscillation signal having a frequency Δf and a second phase-synchronized signal having a frequency f with respect to the second pulse signal having f. Modulating, a second of the frequency Δf between the second pulse signal and the second reference signal The second beat signal obtained is phase-synchronized with the second reference signal and the second pulse signal to be detected has the frequency f intended by the second pulse signal. (5-3) The time difference between the first and second phase-synchronized signals in the first and second phase-locked loops is output as a detection signal .
Here, it is preferable to have a pre-passage optical pulse width measurement device that measures the pulse width of the previous pulse signal through the optical transmission line, and the configuration of the pre-passage optical pulse width measurement device is (6-1) (6-2) One of the branched pulse signals is inputted, and a fixed band is limited to the pulse signal to reduce the pulse width of the pulse signal. A second filter means for extending and delaying the peak timing; (6-3) a first filter for detecting a time difference between the other branched pulse signal and the pulse signal delayed through the second filter means; and second time difference detecting means, (6-4) the detected time difference and have a second time difference / pulse width conversion means for converting the pulse width, (7) the second time difference detecting means, third And a fourth phase synchronization loop (7-1) The third phase-locked loop has a local oscillation signal having the frequency Δf and a third pulse signal having the frequency f inputted without passing through the second filter means. Modulation is performed using a third reference signal having a predetermined frequency f−Δf obtained by mixing the third phase-synchronized signal having the frequency f, and between the third pulse signal and the third reference signal. The third beat signal having the frequency Δf is obtained, the obtained third beat signal is phase-synchronized with the third reference signal, and the frequency to which the third pulse signal to be detected is intended f is converted into the third phase-locked signal, and (7-2) the fourth phase-locked loop is applied to the fourth pulse signal having the frequency f input through the second filter means. , The local oscillation signal of frequency Δf and the fourth phase-synchronized signal of frequency f are mixed And a fourth beat signal having a frequency Δf between the fourth pulse signal and the fourth reference signal is obtained and modulated. The fourth beat signal thus obtained is phase-synchronized with the fourth reference signal, and converted to the fourth phase-synchronized signal having the frequency f intended by the fourth pulse signal to be detected, (7-3) The one that outputs the time difference between the third and fourth phase-locked signals in the third and fourth phase-locked loops as the detection signal can be applied.

第４の本発明は、光伝送路での波長分散を検出する光伝送路分散検出方法において、（１）通過後光パルス幅測定装置は、上記光伝送路を介した後のパルス信号のパルス幅を測定し、（２）変換用情報保持手段は、上記光伝送路を介する前のパルス信号のパルス幅について、上記光伝送路を介した後のパルス信号のパルス幅と上記光伝送路の波長分散値との関係情報を保持しており、（３）情報変換手段は、上記通過後光パルス幅測定装置による測定パルス幅を、上記変換用情報保持手段が保持している情報に当て嵌めて、上記光伝送路の波長分散値を得るものである。ここで、通過後光パルス幅測定装置は、分岐手段、フィルタ手段、時間差検出手段及び時間差／パルス幅変換手段を有し、（４−１）上記分岐手段が、入力されたパルス信号を２分岐し、（４−２）上記フィルタ手段が、分岐された一方のパルス信号に対し、固定帯域の帯域制限を行ってパルス信号のパルス幅を伸長してピークタイミングを遅延させ、（４−３）上記時間差検出手段が、分岐された他方のパルス信号と、上記フィルタ手段を介して遅延されたパルス信号との時間差を検出し、（４−４）上記時間差／パルス幅変換手段が、検出された時間差をパルス幅に変換し、（５）上記時間差検出手段は、第１及び第２の位相同期ループを有し、（５−１）位相同期ループは、上記フィルタ手段を介することなく入力された周波数ｆの第１のパルス信号に対して、周波数Δｆの局部発振信号と周波数ｆの第１の位相同期後信号とが混合されて得られた所定周波数ｆ−Δｆの第１の参照信号を用いて変調し、第１のパルス信号と第１の参照信号との間での周波数Δｆの第１のビート信号を得ると共に、得られた第１のビート信号を、上記第１の参照信号に位相同期させ、かつ、検出対象の第１のパルス信号が意図している周波数ｆの上記第１の位相同期後信号に変換し、（５−２）第２の位相同期ループは、上記フィルタ手段を介して入力された周波数ｆの第２のパルス信号に対して、周波数Δｆの局部発振信号と周波数ｆの第２の位相同期後信号とが混合されて得られた所定周波数ｆ−Δｆの第２の参照信号を用いて変調し、第２のパルス信号と第２の参照信号との間での周波数Δｆの第２のビート信号を得ると共に、得られた第２のビート信号を、上記第２の参照信号に位相同期させ、かつ、検出対象の第２のパルス信号が意図している周波数ｆの上記第２の位相同期後信号に変換し、（５−３）これら第１及び第２の位相同期ループにおける第１及び第２の位相同期後信号の時間差を検出信号として出力する。 According to a fourth aspect of the present invention, there is provided an optical transmission line dispersion detection method for detecting chromatic dispersion in an optical transmission line. (2) the information holding means for conversion uses the pulse width of the pulse signal before passing through the optical transmission path, the pulse width of the pulse signal after passing through the optical transmission path, and the width of the optical transmission path. (3) the information conversion means applies the measurement pulse width measured by the post-passage optical pulse width measurement device to the information held by the conversion information holding means. Thus, the chromatic dispersion value of the optical transmission line is obtained. Here, the post-passage optical pulse width measuring device has branching means, filter means, time difference detection means, and time difference / pulse width conversion means. (4-1) The branching means splits the inputted pulse signal into two (4-2) The filter means performs band limitation of a fixed band on one of the branched pulse signals to extend the pulse width of the pulse signal to delay the peak timing. (4-3) The time difference detection means detects a time difference between the other branched pulse signal and the pulse signal delayed through the filter means. (4-4) The time difference / pulse width conversion means is detected. The time difference is converted into a pulse width . (5) The time difference detection means has first and second phase locked loops. (5-1) The phase locked loop is inputted without passing through the filter means. Of frequency f The first pulse signal is modulated using a first reference signal having a predetermined frequency f−Δf obtained by mixing a local oscillation signal having a frequency Δf and a first phase-synchronized signal having a frequency f. Obtaining a first beat signal having a frequency Δf between the first pulse signal and the first reference signal, and synchronizing the obtained first beat signal with the first reference signal, In addition, the first pulse signal to be detected is converted into the first phase-locked signal having the intended frequency f, and (5-2) the second phase-locked loop is input via the filter means. The second reference signal having a predetermined frequency f−Δf obtained by mixing the second pulse signal having the frequency f with the local oscillation signal having the frequency Δf and the second phase-synchronized signal having the frequency f. And the frequency between the second pulse signal and the second reference signal A second beat signal of Δf is obtained, the obtained second beat signal is phase-synchronized with the second reference signal, and the second pulse signal to be detected has the frequency f intended. The signal is converted into the second signal after phase synchronization, and (5-3) the time difference between the first and second signals after phase synchronization in the first and second phase locked loops is output as a detection signal .

第１及び第２の本発明によれば、被測定対象の偏光状態などの制御を必要とせず、実際に信号伝送に用いられる変調された信号に対しても、簡便にパルス幅を測定することができる。   According to the first and second aspects of the present invention, it is possible to easily measure the pulse width even for a modulated signal that is actually used for signal transmission, without requiring control of the polarization state of the object to be measured. Can do.

第３及び第４の本発明によれば、信号伝送に用いる送受信機を接続した状態でも、波長分散又はその変動を検出することができる。   According to the third and fourth aspects of the present invention, it is possible to detect chromatic dispersion or its variation even when a transceiver used for signal transmission is connected.

（Ａ）第１の実施形態
以下、本発明によるパルス幅測定装置及びパルス幅測定方法に係る第１の実施形態を、図面を参照しながら説明する。第１の実施形態は、光通信に供している光信号における光パルスのパルス幅を測定しようとしたものである。 (A) First Embodiment Hereinafter, a first embodiment according to a pulse width measuring apparatus and a pulse width measuring method according to the present invention will be described with reference to the drawings. The first embodiment is intended to measure the pulse width of an optical pulse in an optical signal used for optical communication.

（Ａ−１）第１の実施形態の構成
図１は、第１の実施形態に係る光パルス幅測定装置２００の詳細構成を示すブロック図である。 (A-1) Configuration of First Embodiment FIG. 1 is a block diagram showing a detailed configuration of an optical pulse width measuring apparatus 200 according to the first embodiment.

図１において、第１の実施形態の光パルス幅測定装置２００は、光信号系と電気信号系とで構成されおり、図１では、光信号に対する信号線を相対的な太線で示すと共に、電気信号に対する信号線を細線で示している。   In FIG. 1, an optical pulse width measuring apparatus 200 according to the first embodiment is composed of an optical signal system and an electrical signal system. In FIG. A signal line for the signal is indicated by a thin line.

光信号系は、光スプリッタ２０１、光バンドパスフィルタ（ＯＢＰＦ）２０２、第１及び第２のＥＡ変調器（ＥＡＭ）２０３及び２０４、第１及び第２のフォトダイオード（ＰＤ）２０５及び２０６を構成要素として含んでいる。なお、第１及び第２のＥＡ変調器２０３及び２０４、第１及び第２のフォトダイオード２０５及び２０６は、電気信号系の構成要素にもなっている。   The optical signal system includes an optical splitter 201, an optical bandpass filter (OBPF) 202, first and second EA modulators (EAM) 203 and 204, and first and second photodiodes (PD) 205 and 206. Contains as an element. Note that the first and second EA modulators 203 and 204 and the first and second photodiodes 205 and 206 are also constituent elements of the electric signal system.

電気信号系は、局部発振器２０７、第１及び第２の変調器ドライバ（Ｄｒｖ．）２０８及び２０９、第１及び第２のバイアスティー（Ｂｉａｓ−Ｔ）２１０及び２１１、バイアス駆動電圧源（Ｖｂ）２１２、第１及び第２のローパスフィルタ（ＬＰＦ）２１３及び２１４、第１及び第２の位相比較器２１５及び２１６、第３及び第４のローパスフィルタ（ＬＰＦ）２１７及び２１８、第１及び第２の電圧制御発振器２１９及び２２０、第３の位相比較器２２１、第１及び第２のミキサ（ｍｉｘｅｒ）２２２及び２２３を構成要素として含んでいる。   The electric signal system includes a local oscillator 207, first and second modulator drivers (Drv.) 208 and 209, first and second bias tees (Bias-T) 210 and 211, and a bias drive voltage source (Vb). 212, first and second low-pass filters (LPF) 213 and 214, first and second phase comparators 215 and 216, third and fourth low-pass filters (LPF) 217 and 218, first and second Voltage control oscillators 219 and 220, a third phase comparator 221, and first and second mixers 222 and 223 are included as constituent elements.

第１及び第２の位相比較器２１５及び２１６や、第３の位相比較器２２１も、いわゆるミキサ（ｍｉｘｅｒ）で構成されているが、混合される２個の入力信号の意図している周波数が等しいので、位相比較器として機能するものである。また、第３及び第４のローパスフィルタ２１７及び２１８はそれぞれ、後述するループ処理での追随速度を規定するループフィルタとして機能するものとなっている。   The first and second phase comparators 215 and 216 and the third phase comparator 221 are also constituted by so-called mixers, but the intended frequencies of the two input signals to be mixed are the same. Since they are equal, they function as a phase comparator. Further, the third and fourth low-pass filters 217 and 218 function as loop filters that regulate the following speed in loop processing to be described later.

上記各構成要素の光パルス幅測定装置２００における担当機能については、後述する動作説明で明らかにする。   The function in charge of the optical pulse width measuring apparatus 200 of each of the above components will be clarified in the operation description to be described later.

（Ａ−２）第１の実施形態の動作
次に、第１の実施形態に係る光パルス幅測定装置２００の動作（光パルス幅測定方法）を、図１に加え、図２をも参照しながら詳述する。 (A-2) Operation of the First Embodiment Next, the operation (optical pulse width measurement method) of the optical pulse width measuring apparatus 200 according to the first embodiment is added to FIG. It will be described in detail.

第１の実施形態に係る光パルス幅測定装置２００の入力端子には、例えば、ピットレートがｆ［ｂｐｓ］のＲＺ光信号が入力される。例えば、当該光パルス幅測定装置２００が光送信機側に設けられている場合であれば、送信しようとするＲＺ光信号を２分岐した一方の光信号が当該光パルス幅測定装置２００に入力される。また例えば、当該光パルス幅測定装置２００が光受信機側に設けられている場合であれば、受信したＲＺ光信号を２分岐した一方の光信号が当該光パルス幅測定装置２００に入力される。すなわち、この第１の実施形態では、光通信に供している光信号における光パルスそのものが、パルス幅を測定する対象となっている。   For example, an RZ optical signal having a pit rate of f [bps] is input to the input terminal of the optical pulse width measuring apparatus 200 according to the first embodiment. For example, if the optical pulse width measuring apparatus 200 is provided on the optical transmitter side, one optical signal obtained by bifurcating the RZ optical signal to be transmitted is input to the optical pulse width measuring apparatus 200. The Further, for example, if the optical pulse width measuring apparatus 200 is provided on the optical receiver side, one optical signal obtained by bifurcating the received RZ optical signal is input to the optical pulse width measuring apparatus 200. . That is, in the first embodiment, the optical pulse itself in the optical signal used for optical communication is a target for measuring the pulse width.

当該光パルス幅測定装置２００に入力されＲＺ光信号は、スプリッタ２０１において２分岐され、分岐された一方の光信号は、直接、第１のＥＡ変調器２０３に入力され、分岐された他方の光信号は、光バンドパスフィルタ２０２を通過した後、第２のＥＡ変調器２０４に入力される。光バンドパスフィルタ２０２は、通過帯域の中心周波数がｆ［Ｈｚ］であって、通過帯域幅は後述するΔｆ［Ｈｚ］より狭いものであり、例えば、５次バターワース型のバンドパスフィルタを適用できる。   The RZ optical signal input to the optical pulse width measuring apparatus 200 is branched into two by the splitter 201, and one branched optical signal is directly input to the first EA modulator 203 and the other branched light is input. The signal passes through the optical bandpass filter 202 and is then input to the second EA modulator 204. The optical bandpass filter 202 has a passband center frequency of f [Hz] and a passband width narrower than Δf [Hz], which will be described later. For example, a fifth order Butterworth type bandpass filter can be applied. .

第１及び第２のＥＡ変調器２０３及び２０４はそれぞれ、後述するようにして、入力され光信号と、バイアス入力端子に印加された信号とのビート成分を有する信号を得て、対応するフォトダイオード２０５、２０６に入力し、その信号がフォトダイオード２０５、２０６によって光電変換される。 Each of the first and second EA modulators 203 and 204 obtains a signal having a beat component of the input optical signal and the signal applied to the bias input terminal, as will be described later, and a corresponding photodiode. The signals are input to 205 and 206, and the signals are photoelectrically converted by the photodiodes 205 and 206.

ここで、第２のフォトダイオード２０６からの出力信号（電気信号）は、光バンドパスフィルタ２０２での帯域制限の影響を受けており、第１のフォトダイオード２０５からの出力信号（電気信号）は、当然に、光バンドパスフィルタ２０２での帯域制限の影響を受けていない。   Here, the output signal (electric signal) from the second photodiode 206 is affected by the band limitation in the optical bandpass filter 202, and the output signal (electric signal) from the first photodiode 205 is Of course, the optical bandpass filter 202 is not affected by the band limitation.

以下、図２を参照しながら、光バンドパスフィルタ２０２の入出力光の関係について説明する。   Hereinafter, the relationship between input and output light of the optical bandpass filter 202 will be described with reference to FIG.

当該装置に入力された光短パルス列のそれぞれの光短パルスは、光バンドパスフィルタ２０２の通過後には時間軸上で広がると共に、そのピークは時間遅延を受ける。図２は、このフィルタリングの様子を、光短パルスのパルス幅が狭い場合と（図２（ａ））、光短パルスのパルス幅が広い場合とについて示している。なお、この明細書では、パルス幅はパルス波形の半値全幅（ＦＷＨＭ）で規定している。光短パルスピークの時間遅延は、光短パルスのパルス幅によって異なっている。光短パルスのパルス幅が狭い（細い）場合における、入力光短パルスとフィルタリングの光パルスとの遅延時間τ１は、光短パルスのパルス幅が広い（太い）場合における、入力光短パルスとフィルタリングの光パルスとの遅延時間τ２より長くなっている。   Each optical short pulse of the optical short pulse train input to the apparatus spreads on the time axis after passing through the optical bandpass filter 202, and its peak undergoes a time delay. FIG. 2 shows the state of this filtering when the pulse width of the optical short pulse is narrow (FIG. 2A) and when the pulse width of the optical short pulse is wide. In this specification, the pulse width is defined by the full width at half maximum (FWHM) of the pulse waveform. The time delay of the optical short pulse peak differs depending on the pulse width of the optical short pulse. The delay time τ1 between the input optical short pulse and the filtering optical pulse when the pulse width of the optical short pulse is narrow (thin) is the input optical short pulse and filtering when the pulse width of the optical short pulse is wide (thick). It is longer than the delay time τ2 with respect to the optical pulse.

光短パルスは、そのパルス幅が狭いほど、立上りエッジや立下りエッジが急峻であって高周波数成分を多く含んでいる。そのため、光短パルスのパルス幅によって、フィルタによって除去される高周波数成分のエネルギーなどが異なり、その影響が遅延時間の相違になって現れるようになっている。   As the pulse width of the optical short pulse is narrower, the rising edge and the falling edge are steeper and contain more high frequency components. Therefore, the energy of the high frequency component removed by the filter differs depending on the pulse width of the optical short pulse, and the influence appears as a difference in delay time.

この第１の実施形態では、光バンドパスフィルタ２０２を介することによって、入力光短パルスのパルス幅を、遅延時間（というパラメータ）に変換し、この遅延時間を、光バンドパスフィルタ２０２を介在している第２のクロック再生ループと、光バンドパスフィルタ２０２を介在していない第１のクロック再生ループとの位相差として取り出そうとしたものである。なお、光バンドパスフィルタ２０２に代え、光ローパスフィルタを適用して、パルス幅を遅延時間に変換するようにしても良い。   In the first embodiment, the pulse width of the input optical short pulse is converted into a delay time (a parameter called) by passing through the optical bandpass filter 202, and this delay time is passed through the optical bandpass filter 202. The phase difference between the second clock recovery loop and the first clock recovery loop without the optical bandpass filter 202 is taken out. Instead of the optical bandpass filter 202, an optical lowpass filter may be applied to convert the pulse width into a delay time.

局部発振器２０７は、参照周波数Δｆ［Ｈｚ］の信号（電気信号；以下、参照信号と呼ぶ）を局部発振して生成するものであり、参照信号は、第１及び第２のクロック再生ループに導入される。すなわち、参照信号は、第１及び第２のミキサ２２２及び２２３、並びに、第１及び第２の位相比較器２１５及び２１６に与えられる。   The local oscillator 207 generates a signal (electric signal; hereinafter referred to as a reference signal) having a reference frequency Δf [Hz] by local oscillation, and the reference signal is introduced into the first and second clock recovery loops. Is done. That is, the reference signal is supplied to the first and second mixers 222 and 223 and the first and second phase comparators 215 and 216.

上述した第１及び第２のクロック再生ループは、光バンドパスフィルタ２０２を介在しているか否かを除けば同様な構成を有する。   The first and second clock recovery loops described above have the same configuration except that the optical bandpass filter 202 is interposed.

第１のクロック再生ループは、第１のミキサ２２２、第１の変調器ドライバ２０８、第１のバイアスティー２１０、第１のＥＡ変調器２０３、第１のフォトダイオード２０５、第１のローパスフィルタ２１３、第１の位相比較器２１５、第３のローパスフィルタ２１７及び第１の電圧制御発振器２１９を有する。   The first clock recovery loop includes a first mixer 222, a first modulator driver 208, a first bias tee 210, a first EA modulator 203, a first photodiode 205, and a first low-pass filter 213. , A first phase comparator 215, a third low-pass filter 217, and a first voltage-controlled oscillator 219.

第２のクロック再生ループは、第２のミキサ２２３、第２の変調器ドライバ２０９、第２のバイアスティー２１１、第２のＥＡ変調器２０４、第２のフォトダイオード２０６、第２のローパスフィルタ２１４、第２の位相比較器２１６、第４のローパスフィルタ２１８及び第２の電圧制御発振器２２０を有し、さらに、光バンドパスフィルタ２０２を有する。   The second clock recovery loop includes a second mixer 223, a second modulator driver 209, a second bias tee 211, a second EA modulator 204, a second photodiode 206, and a second low-pass filter 214. , A second phase comparator 216, a fourth low-pass filter 218, a second voltage-controlled oscillator 220, and an optical bandpass filter 202.

第１及び第２のクロック再生ループの動作はほぼ同様であるので、以下では、第１のクロック再生ループに着目してループ動作を説明する。   Since the operations of the first and second clock recovery loops are substantially the same, the loop operation will be described below with a focus on the first clock recovery loop.

周波数Δｆ［Ｈｚ］の参照信号が与えられる第１のミキサ２２２には、第１の電圧制御発振器２１９から出力された周波数ｆ［Ｈｚ］の発振信号も与えられ、第１のミキサ２２２からは、これら入力信号の周波数差を成分ｆ−ｎ×Δｆ［Ｈｚ］（ｎは自然数）に含むミキサ信号（差周波数成分信号）が出力される。 The first mixer 222 to which the reference signal of the frequency Δf [Hz] is given is also given the oscillation signal of the frequency f [Hz] outputted from the first voltage controlled oscillator 219, and the first mixer 222 gives A mixer signal (difference frequency component signal) including the frequency difference of these input signals in a component f−n × Δf [Hz] (n is a natural number) is output.

この周波数がｆ−Δｆ［Ｈｚ］の差周波数成分信号は、第１の変調器ドライバ２０８によって増幅され、また、第１のバイアスティー２１０によって負電界を付与され、このような処理が施された信号が第１のＥＡ変調器２０３の制御入力端子に入力される。第１のＥＡ変調器２０３にはｆ［ｂｐｓ］のＲＺ光信号が入力されているので、第１のＥＡ変調器２０３からは、周波数がｎ×Δｆ［Ｈｚ］のビート信号が出力される。ビート信号のうち、周波数がΔｆ［Ｈｚ］のビート信号が最大の強度を持つ。周波数がｎ×Δｆ［Ｈｚ］のビート信号は、第１のフォトダイオード２０５によって電気信号に変換された後、第１のローパスフィルタ２１３を通過し、Δｆ［Ｈｚ］成分だけが抽出され、第１の位相比較器２１５に与えられる。 The difference frequency component signal whose frequency is f−Δf [Hz] is amplified by the first modulator driver 208, and a negative electric field is applied by the first bias tee 210, and such processing is performed. A signal is input to the control input terminal of the first EA modulator 203. Since an RZ optical signal of f [bps] is input to the first EA modulator 203, a beat signal having a frequency of n × Δf [Hz] is output from the first EA modulator 203. Among beat signals, a beat signal having a frequency of Δf [Hz] has the maximum intensity. The beat signal having a frequency of n × Δf [Hz] is converted into an electric signal by the first photodiode 205, and then passes through the first low-pass filter 213, and only the Δf [Hz] component is extracted. To the phase comparator 215.

第１の位相比較器２１５には、局部発振器２０７から出力された周波数がΔｆ［Ｈｚ］の参照信号も与えられている。これにより、第１の位相比較器２１５によって、周波数がΔｆ［Ｈｚ］の第１のローパスフィルタ２１３の出力信号と、同じ周波数Δｆ［Ｈｚ］を有する参照信号との位相比較が行われ（位相差が抽出され）、得られた位相差信号がループフィルタとして機能する第３のローパスフィルタ２１７を介して直流化されて、第１の電圧制御発振器２１９に与えられ、第１の電圧制御発振器２１９は、自己からの中心周波数がｆ［Ｈｚ］の発振信号の位相を、抽出された位相差が０になる方向に移相させる（周波数を微小に増減させる）。第１の電圧制御発振器２１９の発振信号が、第１のミキサ２２２へ入力され、ループ動作が継続する。 The first phase comparator 215 is also provided with a reference signal having a frequency Δf [Hz] output from the local oscillator 207. Thus, the first phase comparator 215 performs phase comparison between the output signal of the first low-pass filter 213 having the frequency Δf [Hz] and the reference signal having the same frequency Δf [Hz] (phase difference). And the obtained phase difference signal is converted into a direct current through a third low-pass filter 217 functioning as a loop filter, and is supplied to the first voltage- controlled oscillator 219. The first voltage- controlled oscillator 219 The phase of the oscillation signal having a center frequency of f [Hz] from the self is shifted in a direction in which the extracted phase difference becomes 0 (the frequency is slightly increased or decreased). The oscillation signal of the first voltage controlled oscillator 219 is input to the first mixer 222 , and the loop operation continues.

ループ動作が継続することにより、第１のクロック再生ループにおいて、やがて、第１の電圧制御発振器２１９からの発振信号（クロック信号）の位相が安定する。この安定状態では、第１のクロック再生ループによって再生されたｆ［Ｈｚ］のクロック信号は、入力されたＲＺ光信号における光パルスの時間位置（位相）の平均値に同調している。 As the loop operation continues, the phase of the oscillation signal (clock signal) from the first voltage controlled oscillator 219 is eventually stabilized in the first clock recovery loop. In this stable state, the clock signal of f [Hz] regenerated by the first clock regenerating loop is tuned to the average value of the time positions (phases) of the optical pulses in the input RZ optical signal.

以上のように、第１のクロック再生ループは、参照信号の位相を基準にし、第１の電圧制御発振器２１９からの発振信号の位相を、入力されＲＺ光信号に同期させる位相同期ループになっており、第１の電圧制御発振器２１９からの発振信号の周波数がｆ［Ｈｚ］であるので、その発振信号をクロック信号と見ることができる。 As described above, the first clock recovery loop is a phase-locked loop that synchronizes the phase of the oscillation signal from the first voltage controlled oscillator 219 with the input RZ optical signal based on the phase of the reference signal. Since the frequency of the oscillation signal from the first voltage controlled oscillator 219 is f [Hz], the oscillation signal can be regarded as a clock signal.

第２のクロック再生ループもほぼ同様に動作する。第２のクロック再生ループの場合、第２のＥＡ変調器２０４へは、光バンドパスフィルタ２０２を介したＲＺ光信号が入力されるので、第２のクロック再生ループは、参照信号の位相を基準にし、第２の電圧制御発振器２２０からの発振信号（クロック）の位相を、光バンドパスフィルタ２０２から出力されたＲＺ光信号に同期させる位相同期ループになっている。 The second clock recovery loop operates in a similar manner. In the case of the second clock recovery loop, since the RZ optical signal that has passed through the optical bandpass filter 202 is input to the second EA modulator 204, the second clock recovery loop uses the phase of the reference signal as a reference. In this manner, the phase of the oscillation signal (clock) from the second voltage controlled oscillator 220 is synchronized with the RZ optical signal output from the optical bandpass filter 202.

第１及び第２のクロック再生ループの相違は光バンドパスフィルタ２０２の有無であるので、第１及び第２のクロック再生ループが共に安定した状態における、第１及び第２の電圧制御発振器２１９及び２２０からのクロック信号間の位相差は、第１及び第２のＥＡ変調器２０３及び２０４へ入力されるＲＺ光信号の光パルスの時間位置間（位相差）を反映したものとなっている。第１及び第２のＥＡ変調器２０３及び２０４へ入力されるＲＺ光信号は、光バンドパスフィルタ２０２を介したか否かが異なるので、第１及び第２の電圧制御発振器２１９及び２２０からのクロック信号間の位相差は、光バンドパスフィルタ２０２の入力信号及び出力信号の光パルスの時間位置間（位相差）を反映したものとなっていると言い換えることができる。   Since the difference between the first and second clock recovery loops is the presence or absence of the optical bandpass filter 202, the first and second voltage controlled oscillators 219 and 219 in the state where both the first and second clock recovery loops are stable. The phase difference between the clock signals from 220 reflects the time position (phase difference) of the optical pulse of the RZ optical signal input to the first and second EA modulators 203 and 204. Since the RZ optical signals input to the first and second EA modulators 203 and 204 differ depending on whether they pass through the optical bandpass filter 202, the clocks from the first and second voltage controlled oscillators 219 and 220 are different. In other words, the phase difference between the signals reflects the time position (phase difference) of the optical pulse of the input signal and output signal of the optical bandpass filter 202.

図２を用いて上述したように、光バンドパスフィルタ２０２の入力信号及び出力信号の光パルスの時間位置間（遅延時間）は、光パルスのパルス幅によって異なるものとなっている。   As described above with reference to FIG. 2, the time position (delay time) of the optical pulse of the input signal and output signal of the optical bandpass filter 202 differs depending on the pulse width of the optical pulse.

そのため、この第１の実施形態では、第１及び第２の電圧制御発振器２１９及び２２０からのクロック信号間の位相差を、第３の位相比較器２２１によって取り出すようにしている。第３の位相比較器２２１によって取り出される位相差は、光バンドパスフィルタ２０２を介することによる遅延時間と、ループでのフィルタの帯域とが主として反映されたものであるが、フィルタの帯域を既知にしておくことで、第３の位相比較器２２１によって取り出される位相差は、光バンドパスフィルタ２０２を介することによる遅延時間、言い換えると、光パルスのパルス幅の関数となる（後述する図３参照）。   Therefore, in the first embodiment, the third phase comparator 221 extracts the phase difference between the clock signals from the first and second voltage controlled oscillators 219 and 220. The phase difference extracted by the third phase comparator 221 mainly reflects the delay time caused by passing through the optical bandpass filter 202 and the filter band in the loop. Thus, the phase difference extracted by the third phase comparator 221 is a function of the delay time caused by passing through the optical bandpass filter 202, in other words, the pulse width of the optical pulse (see FIG. 3 described later). .

図１では省略しているが、第３の位相比較器２２１の出力段には、第３の位相比較器２２１によって取り出された位相差を、光パルスのパルス幅に変換する変換手段を設けておく。例えば、アナログ／デジタル変換手段によってデジタル信号に変換した後、ＣＰＵなどの処理によってパルス幅に変換するようにしても良く、また、デジタル値をアドレスとして変換テーブルをアクセスすることで、パルス幅の情報に変換するようにしても良い。
図３は、入力する光短パルス列のパルス幅を横軸にとり、５次バターワース型の光バンドパスフィルタ２０２を通過した場合の、フィルタ出力の時間遅延を縦軸にとった図である。図３は、フィルタ帯域が、４．０、５．２、６．４、７．６及び８．８［ＧＨｚ］の場合を示している。時間遅延は、パルス幅２［ｐｓ］の場合の値を０として規格化して示している。例えば、パルス幅が４［ｐｓ］のパルス列が入力し、フィルタの帯域が８．８［ＧＨｚ］であった場合、光バンドパスフィルタ２０２を通過させたときには、パルス幅が２［ｐｓ］の場合と比較して、−０．２［ｐｓ］の遅延差が生じる。光短パルス列の繰り返し周期が４０［ＧＨｚ］であれば、０．２［ｐｓ］は０．８％の差である。第３の位相比較器２２１（ミキサ）から＋５／−５［Ｖ］の出力が得られるとすると、８０［ｍＶ］の出力が検出される。 Although omitted in FIG. 1, the output stage of the third phase comparator 221 is provided with conversion means for converting the phase difference extracted by the third phase comparator 221 into the pulse width of the optical pulse. deep. For example, after converting into a digital signal by an analog / digital conversion means, it may be converted into a pulse width by processing of a CPU or the like, and information on pulse width is obtained by accessing a conversion table using a digital value as an address. You may make it convert into .
FIG. 3 is a diagram in which the horizontal axis represents the pulse width of the input optical short pulse train, and the vertical axis represents the time delay of the filter output when passing through the fifth-order Butterworth type optical bandpass filter 202. FIG. 3 shows a case where the filter band is 4.0, 5.2, 6.4, 7.6, and 8.8 [GHz]. The time delay is shown normalized by setting the value for a pulse width of 2 [ps] to 0. For example, when a pulse train with a pulse width of 4 [ps] is input and the filter band is 8.8 [GHz], when the optical bandpass filter 202 is passed, the pulse width is 2 [ps]. Compared to the above, a delay difference of −0.2 [ps] is generated. If the repetition period of the optical short pulse train is 40 [GHz], 0.2 [ps] is a difference of 0.8%. If an output of + 5 / −5 [V] is obtained from the third phase comparator 221 (mixer), an output of 80 [mV] is detected.

（Ａ−３）第１の実施形態の効果
第１の実施形態によれば、被測定光の偏光状態を制御することなく、光短パルス列のパルス幅を測定することができる。 (A-3) Effect of First Embodiment According to the first embodiment, the pulse width of an optical short pulse train can be measured without controlling the polarization state of the light to be measured.

また、第１の実施形態によれば、ＲＺ光信号のような実際に信号伝送に用いられる変調された光信号に対しても、光バンドパスフィルタ２０２の通過前後の光パルスの位相差を捉え、それを、１対１の変換手段によってパルス幅に変換するという方法で測定しているので、簡便に光パルス幅を測定することができる。   In addition, according to the first embodiment, the phase difference between the optical pulses before and after passing through the optical bandpass filter 202 is captured even for a modulated optical signal that is actually used for signal transmission, such as an RZ optical signal. Since it is measured by a method of converting it into a pulse width by a one-to-one conversion means, the optical pulse width can be easily measured.

なお、当該光パルス幅測定装置２００が光受信機側に設けられている場合であれば、第１又は第２のクロック再生ループによって再生されたクロック信号を、受信構成で用いるようにすることもでき、この場合、受信構成でのクロック再生構成を省略又は簡略化することができる。   If the optical pulse width measuring apparatus 200 is provided on the optical receiver side, the clock signal regenerated by the first or second clock regenerating loop may be used in the receiving configuration. In this case, the clock recovery configuration in the reception configuration can be omitted or simplified.

（Ｂ）第２の実施形態
次に、本発明によるパルス幅測定装置及びパルス幅測定方法に係る第２の実施形態を、図面を参照しながら説明する。第２の実施形態も、光通信に供している光信号における光パルスのパルス幅を測定しようとしたものである。 (B) Second Embodiment Next, a second embodiment of the pulse width measuring apparatus and the pulse width measuring method according to the present invention will be described with reference to the drawings. The second embodiment is also intended to measure the pulse width of an optical pulse in an optical signal used for optical communication.

上述した第１の実施形態では、光信号の状態でビート信号を生成し、ビート信号に基づいて、パルス幅を遅延時間に変換するフィルタを介した信号と、そのフィルタを介さない信号との位相比較を行う方法を示した。第２の実施形態は、入力する光信号における光短パルス列が、パルス幅が十分広い光短パルス列であれば、電気変換した後に、フィルタを用いて遅延時間に変換しても、十分に測定が可能なことに基づいてなされたものである。   In the first embodiment described above, a beat signal is generated in the state of an optical signal, and a phase between a signal that passes through a filter that converts a pulse width into a delay time based on the beat signal and a signal that does not pass through the filter. The method of comparison was shown. In the second embodiment, if the optical short pulse train in the input optical signal is an optical short pulse train having a sufficiently wide pulse width, sufficient measurement can be performed even if it is converted into a delay time using a filter after electrical conversion. It was made based on what was possible.

図４は、第２の実施形態に係る光パルス幅測定装置の詳細構成を示すブロック図である。図４において、第２の実施形態に係る光パルス幅測定装置１００は、光スプリッタ１０１、第１及び第２のフォトダイオード（ＰＤ）１０２及び１０３、ローパスフィルタ（ＬＰＦ）１０４、並びに、ミキサ等の位相比較器１０５を構成要素として含んでいる。なお、ローパスフィルタ１０４に代え、バンドパスフィルタを適用するようにしても良い。   FIG. 4 is a block diagram showing a detailed configuration of the optical pulse width measuring apparatus according to the second embodiment. In FIG. 4, an optical pulse width measuring apparatus 100 according to the second embodiment includes an optical splitter 101, first and second photodiodes (PD) 102 and 103, a low-pass filter (LPF) 104, a mixer, and the like. A phase comparator 105 is included as a component. Instead of the low pass filter 104, a band pass filter may be applied.

次に、第２の実施形態に係る光パルス幅測定装置１００の動作について説明する。   Next, the operation of the optical pulse width measuring apparatus 100 according to the second embodiment will be described.

光パルス幅測定装置１００の光入力端から入力された周波数ｆ［ＧＨｚ］の光短パルス列は、光分岐部１０１で２系統に分岐され、それぞれ、第１又は第２のフォトダイオード１０２又は１０３に与えられて電気信号に変換される。第１のフォトダイオード１０２からの出力信号は位相比較器１０５に直接与えられ、一方、第２のフォトダイオード１０３からの出力信号は、ローパスフィルタ１０４で帯域制限を受けた後、位相比較器１０５に与えられる。   An optical short pulse train having a frequency of f [GHz] input from the optical input terminal of the optical pulse width measuring apparatus 100 is branched into two systems by the optical branching unit 101, and is supplied to the first or second photodiode 102 or 103, respectively. Given and converted to an electrical signal. The output signal from the first photodiode 102 is directly applied to the phase comparator 105, while the output signal from the second photodiode 103 is subjected to band limitation by the low-pass filter 104 and then to the phase comparator 105. Given.

ローパスフィルタ１０４によって帯域制限を受けた、光電変換後の短パルス列のそれぞれの短パルスは、図２を用いて第１の実施形態について上述したと同様に、当該ローパスフィルタ１０４の通過後に時間軸上で広がると共に、そのピークは時間遅延を受ける。この遅延時間が、位相比較器１０５によって位相差として抽出される。位相比較器１０５の後段の構成によって、抽出された位相差が、第１の実施形態で説明したようにしてパルス幅に変換される。 Receiving the band-limited by the low-pass filter 104, each of the short pulse of short pulse string after photoelectric conversion, similar to that described above for the first embodiment with reference to FIG. 2, on the time after passing through the axis of the low-pass filter 104 The peak is subject to a time delay. This delay time is extracted as a phase difference by the phase comparator 105. With the configuration subsequent to the phase comparator 105, the extracted phase difference is converted into a pulse width as described in the first embodiment.

第２の実施形態によっても、被測定光の偏光状態の制御を必要とせず、実際に信号伝送に用いられる変調された信号に対して、簡便に光パルス幅を測定することができる。   Also according to the second embodiment, it is not necessary to control the polarization state of the light to be measured, and the optical pulse width can be easily measured for a modulated signal that is actually used for signal transmission.

（Ｃ）第３の実施形態
次に、本発明による光伝送路分散検出装置及び光伝送路分散検出方法に係る第１の実施形態を、図面を参照しながら説明する。第３の実施形態は、実験室などに設定した実験用の光伝送路ではなく（但し、このような光伝送路を検出対象とすることもできる）、光通信に供している光伝送路での分散値及び又は分散値変動を検出しようとしたものである。 (C) Third Embodiment Next, a first embodiment according to an optical transmission line dispersion detection apparatus and an optical transmission line dispersion detection method according to the present invention will be described with reference to the drawings. The third embodiment is not an optical transmission line for experiments set in a laboratory or the like (however, such an optical transmission line can also be set as a detection target), and is an optical transmission line used for optical communication. The dispersion value and / or variation of the dispersion value are to be detected.

図５は、第３の実施形態に係る光伝送路分散検出装置の構成を示すブロック図である。図５において、第３の実施形態に係る光伝送路分散検出装置６００は、光短パルス列発生器６０１、光スプリッタ６０２、第１のパルス幅測定装置６０３及び第２のパルス幅測定装置６０４を含んでいる。図示は省略しているが、第１のパルス幅測定装置６０３及び第２のパルス幅測定装置６０４が測定したパルス幅から、光伝送路での分散値及び又は分散値変動を求める、例えば、パソコンなどでなる解析手段も設けられている。   FIG. 5 is a block diagram illustrating a configuration of an optical transmission line dispersion detection apparatus according to the third embodiment. In FIG. 5, an optical transmission line dispersion detector 600 according to the third embodiment includes an optical short pulse train generator 601, an optical splitter 602, a first pulse width measuring device 603, and a second pulse width measuring device 604. It is out. Although not shown, the dispersion value and / or dispersion value fluctuation in the optical transmission line is obtained from the pulse width measured by the first pulse width measuring device 603 and the second pulse width measuring device 604, for example, a personal computer Analyzing means is also provided.

光短パルス列発生器６０１は、例えば、光送信機が該当し、ＲＺ光信号のような光短パルス列を発生するものである。発生された光短パルス列（ＲＺ光信号）は、光スプリッタ６０２によって２分岐され、一方の光短パルス列は、第１のパルス幅測定装置６０３に入力され、他方の光短パルス列は、検出対象の光伝送路（光ファイバ；ＤＵＴ）６０５を通過した後、第２のパルス幅測定装置６０４に入力される。   The optical short pulse train generator 601 corresponds to, for example, an optical transmitter and generates an optical short pulse train such as an RZ optical signal. The generated optical short pulse train (RZ optical signal) is branched into two by the optical splitter 602, one optical short pulse train is input to the first pulse width measuring device 603, and the other optical short pulse train is the detection target. After passing through an optical transmission line (optical fiber; DUT) 605, it is input to the second pulse width measuring device 604.

第１及び第２のパルス幅測定装置６０３及び６０４はそれぞれ、入力された光短パルス列の光パルスのパルス幅を測定するものである。ここで、第１のパルス幅測定装置６０３は、検出対象の光伝送路６０５に入力される光パルスのパルス幅を測定しており、第２のパルス幅測定装置６０４は、検出対象の光伝送路６０５から出力された光パルスのパルス幅を測定している。   The first and second pulse width measuring devices 603 and 604 measure the pulse widths of the input optical pulses of the optical short pulse train, respectively. Here, the first pulse width measuring device 603 measures the pulse width of the optical pulse input to the detection target optical transmission line 605, and the second pulse width measuring device 604 is the detection target optical transmission. The pulse width of the optical pulse output from the path 605 is measured.

なお、第１及び第２のパルス幅測定装置６０３及び６０４としては、パルス幅を測定できるものであれば、どのような測定装置であっても良いが、当該光伝送路分散検出装置６００が、実通信時の検出を意図しているような場合には、上述した第１又は第２の実施形態のパルス幅測定装置２００又は１００を適用すれば良い。 The first and second pulse width measuring devices 603 and 604 may be any measuring device as long as the pulse width can be measured. If detection is intended during actual communication, the pulse width measuring device 200 or 100 according to the first or second embodiment described above may be applied.

第１及び第２のパルス幅測定装置６０３及び６０４による測定結果は、図示しない解析手段に与えられる。   The measurement results by the first and second pulse width measuring devices 603 and 604 are given to analysis means (not shown).

図６は、光短パルス列発生器６０１から出力される光短パルス列のパルス幅が２［ｐｓ］とした場合に、光伝送路（伝送媒体）６０５の分散に対して、光伝送路（伝送媒体）６０５を通過した後の光短パルスの半値幅を示している。光伝送路６０５に４［ｐｓ／ｎｍ］の分散がある場合には、パルス幅は２［ｐｓ］から４［ｐｓ］に伸張される。このとき、第１のパルス幅測定装置６０３で測定されるパルス幅２［ｐｓ］であるが、第２のパルス幅検出装置６０４で検出されるパルス幅は４［ｐｓ］であるため、解析手段が、図６の特性情報を記憶して用意しておくことにより、光伝送路（伝送媒体）６０５の分散値が、４［ｐｓ／ｎｍ］であることを検出することができる。   FIG. 6 shows an optical transmission line (transmission medium) with respect to dispersion of the optical transmission line (transmission medium) 605 when the pulse width of the optical short pulse train output from the optical short pulse train generator 601 is 2 [ps]. ) The half-value width of the short optical pulse after passing through 605 is shown. When the optical transmission line 605 has a dispersion of 4 [ps / nm], the pulse width is expanded from 2 [ps] to 4 [ps]. At this time, the pulse width measured by the first pulse width measuring device 603 is 2 [ps], but the pulse width detected by the second pulse width detecting device 604 is 4 [ps]. However, by storing and preparing the characteristic information of FIG. 6, it can be detected that the dispersion value of the optical transmission line (transmission medium) 605 is 4 [ps / nm].

図６のような特性情報を、光短パルス列発生器６０１から出力される光短パルス列のパルス幅が２［ｐｓ］以外についても用意しておき（各パルス幅毎に用意しておき）、第１のパルス幅測定装置６０３で測定されたパルス幅に応じて、適用する特性情報を選択した上で、第２のパルス幅測定装置６０４で測定されたパルス幅を当て嵌めて、光伝送路（伝送媒体）６０５の分散値を検出する。   The characteristic information as shown in FIG. 6 is prepared even when the pulse width of the optical short pulse train output from the optical short pulse train generator 601 is other than 2 [ps] (prepared for each pulse width). After selecting the characteristic information to be applied in accordance with the pulse width measured by the first pulse width measuring device 603, the pulse width measured by the second pulse width measuring device 604 is applied and the optical transmission line ( The dispersion value of the transmission medium 605 is detected.

第３の実施形態によれば、光伝送路（伝送媒体）の前後で光短パルスのパルス幅を測定することで、分散値を検出することができ、その時間変動を捉えることにより分散変動を検出することができる。   According to the third embodiment, the dispersion value can be detected by measuring the pulse width of the optical short pulse before and after the optical transmission path (transmission medium), and the dispersion fluctuation can be detected by capturing the time fluctuation. Can be detected.

信号伝送に用いる送受信機を接続した状態で、パルス幅を検出できるパルス幅測定装置（第１や第２の実施形態の装置）を適用することにより、信号伝送に用いる送受信機を接続した状態で、光伝送路（伝送媒体）の波長分散やその変動を検出することができる。   In a state where a transceiver used for signal transmission is connected by applying a pulse width measuring device (device of the first or second embodiment) capable of detecting a pulse width in a state where the transceiver used for signal transmission is connected. In addition, it is possible to detect chromatic dispersion and fluctuations of the optical transmission line (transmission medium).

（Ｄ）他の実施形態
上記各実施形態は、例えば、２［ｐｓ］のパルス幅を持ち、繰り返し周波数が４０［ＧＨｚ］の光短パルス列を適用することを前提として説明したが、パルス幅とフィルタの帯域は検出を行う分散値によって設計を行うものであり、本発明を、他のパルス幅や帯域でも用いることができる。 (D) Other Embodiments Each of the above embodiments has been described on the assumption that, for example, an optical short pulse train having a pulse width of 2 [ps] and a repetition frequency of 40 [GHz] is applied. The band of the filter is designed based on the dispersion value for detection, and the present invention can be used with other pulse widths and bands.

上記第３の実施形態においては、光伝送路（伝送媒体）６０５の入力側にも（第１の）パルス幅測定装置６０３を設けたものを示したが、光短パルス列発生器６０１からの光短パルスのパルス幅が既知の場合には、第１のパルス幅測定装置６０３を省略し、第２のパルス幅測定装置６０４だけで分散値を検出するようにしても良い。   In the third embodiment, the (first) pulse width measuring device 603 is also provided on the input side of the optical transmission path (transmission medium) 605. However, the light from the optical short pulse train generator 601 is shown. When the pulse width of the short pulse is known, the first pulse width measuring device 603 may be omitted, and the dispersion value may be detected only by the second pulse width measuring device 604.

上記第１及び第２の実施形態では、光パルス幅を測定するものを示したが、電気的なパルス信号のパルス幅を測定する場合にも、フィルタを利用して遅延時間に変換して測定するという技術思想を適用することができる。   In the first and second embodiments, the optical pulse width is measured. However, when measuring the pulse width of an electrical pulse signal, it is converted into a delay time using a filter. The technical idea of doing can be applied.

第１の実施形態に係る光パルス幅測定装置の詳細構成を示すブロック図である。It is a block diagram which shows the detailed structure of the optical pulse width measuring apparatus which concerns on 1st Embodiment. 第１の実施形態が光バンドパスフィルタを利用した理由の説明図である。It is explanatory drawing of the reason which 1st Embodiment utilized the optical band pass filter. 第１の実施形態におけるパルス幅と光バンドパスフィルタを介することによる遅延時間との関係を示す特性図である。It is a characteristic view which shows the relationship between the pulse width in 1st Embodiment, and the delay time by passing through an optical band pass filter. 第２の実施形態に係る光パルス幅測定装置の詳細構成を示すブロック図である。It is a block diagram which shows the detailed structure of the optical pulse width measuring apparatus which concerns on 2nd Embodiment. 第３の実施形態に係る光パルス幅測定装置の詳細構成を示すブロック図である。It is a block diagram which shows the detailed structure of the optical pulse width measuring apparatus which concerns on 3rd Embodiment. 第３の実施形態における光伝送路への一定の入力パルス幅に関し、光伝送路の波長分散と光伝送路からの出力パルス幅との関係を示す特性図である。FIG. 10 is a characteristic diagram showing a relationship between wavelength dispersion of an optical transmission line and output pulse width from the optical transmission line with respect to a constant input pulse width to the optical transmission line in the third embodiment.

符号の説明Explanation of symbols

１００…光パルス幅測定装置、１０１…光スプリッタ、１０２、１０３…フォトダイオード（ＰＤ）、１０４…ローパスフィルタ（ＬＰＦ）、１０５…位相比較器、
２００…光パルス幅測定装置、２０１…光スプリッタ、２０２…光バンドパスフィルタ（ＯＢＰＦ）、２０３、２０４…ＥＡ変調器（ＥＡＭ）、２０５、２０６…フォトダイオード（ＰＤ）、２０７…局部発振器、２０８、２０９…変調器ドライバ、２１０、２１１…バイアスティー（Ｂｉａｓ−Ｔ）、２１２…バイアス駆動電圧源（Ｖｂ）、２１３、２１４、２１７、２１８…ローパスフィルタ（ＬＰＦ）、２１５、２１６、２２１…位相比較器、２１９、２２０…電圧制御発振器、２２２、２２３…ミキサ（ｍｉｘｅｒ）、
６００…光伝送路分散検出装置、６０１…光短パルス列発生器、６０２…光スプリッタ、６０３、６０４…パルス幅測定装置。 DESCRIPTION OF SYMBOLS 100 ... Optical pulse width measuring apparatus, 101 ... Optical splitter, 102, 103 ... Photodiode (PD), 104 ... Low pass filter (LPF), 105 ... Phase comparator,
DESCRIPTION OF SYMBOLS 200 ... Optical pulse width measuring apparatus, 201 ... Optical splitter, 202 ... Optical band pass filter (OBPF), 203, 204 ... EA modulator (EAM), 205, 206 ... Photodiode (PD), 207 ... Local oscillator, 208 209: Modulator driver 210, 211 ... Bias tee (Bias-T) 212 ... Bias drive voltage source (Vb), 213, 214, 217, 218 ... Low pass filter (LPF), 215, 216, 221 ... Phase Comparators, 219, 220 ... voltage controlled oscillators, 222, 223 ... mixers,
600 ... Optical transmission line dispersion detector, 601 ... Optical short pulse train generator, 602 ... Optical splitter, 603, 604 ... Pulse width measuring device.

Claims (6)

パルス信号のパルス幅を測定するパルス幅測定装置において、
検出対象のパルス信号を２分岐する分岐手段と、
分岐された一方のパルス信号が入力され、そのパルス信号に対し、固定帯域の帯域制限を行ってパルス信号のパルス幅を伸長してピークタイミングを遅延させるフィルタ手段と、
分岐された他方のパルス信号と、上記フィルタ手段を介して遅延されたパルス信号との時間差を検出する時間差検出手段と、
検出された時間差をパルス幅に変換する時間差／パルス幅変換手段とを有し、
上記時間差検出手段は、第１及び第２の位相同期ループを有し、
第１の位相同期ループは、上記フィルタ手段を介することなく入力された周波数ｆの第１のパルス信号に対して、周波数Δｆの局部発振信号と周波数ｆの第１の位相同期後信号とが混合されて得られた所定周波数ｆ−Δｆの第１の参照信号を用いて変調し、第１のパルス信号と第１の参照信号との間での周波数Δｆの第１のビート信号を得ると共に、得られた第１のビート信号を、上記第１の参照信号に位相同期させ、かつ、検出対象の第１のパルス信号が意図している周波数ｆの上記第１の位相同期後信号に変換し、
第２の位相同期ループは、上記フィルタ手段を介して入力された周波数ｆの第２のパルス信号に対して、周波数Δｆの局部発振信号と周波数ｆの第２の位相同期後信号とが混合されて得られた所定周波数ｆ−Δｆの第２の参照信号を用いて変調し、第２のパルス信号と第２の参照信号との間での周波数Δｆの第２のビート信号を得ると共に、得られた第２のビート信号を、上記第２の参照信号に位相同期させ、かつ、検出対象の第２のパルス信号が意図している周波数ｆの上記第２の位相同期後信号に変換し、
これら第１及び第２の位相同期ループにおける第１及び第２の位相同期後信号の時間差を検出信号として出力する
ことを特徴とするパルス幅測定装置。 In a pulse width measuring device that measures the pulse width of a pulse signal,
Branching means for branching the pulse signal to be detected into two;
One of the branched pulse signals is input, and filter means for delaying the peak timing by extending the pulse width of the pulse signal by performing band limitation of the fixed band for the pulse signal,
Time difference detection means for detecting a time difference between the other branched pulse signal and the pulse signal delayed through the filter means;
Have a time difference / pulse width conversion means for converting the detected time difference to the pulse width,
The time difference detection means has first and second phase locked loops,
In the first phase-locked loop, the local oscillation signal having the frequency Δf and the first phase-locked signal having the frequency f are mixed with the first pulse signal having the frequency f inputted without passing through the filter means. The first reference signal having the predetermined frequency f−Δf thus obtained is modulated to obtain the first beat signal having the frequency Δf between the first pulse signal and the first reference signal, and The obtained first beat signal is phase-synchronized with the first reference signal and converted into the first phase-synchronized signal having the frequency f intended by the first pulse signal to be detected. ,
In the second phase-locked loop, the local oscillation signal having the frequency Δf and the second post-phase-locked signal having the frequency f are mixed with the second pulse signal having the frequency f input through the filter unit. The second reference signal having the predetermined frequency f−Δf obtained in this way is modulated to obtain a second beat signal having the frequency Δf between the second pulse signal and the second reference signal. The second beat signal is phase-synchronized with the second reference signal, and converted to the second phase-synchronized signal having the frequency f intended by the second pulse signal to be detected,
A pulse width measuring device that outputs a time difference between first and second phase-synchronized signals in the first and second phase-locked loops as a detection signal . 検出対象のパルス信号が光パルス信号であることを特徴とする請求項１に記載のパルス幅測定装置。 The pulse width measuring device according to claim 1 , wherein the pulse signal to be detected is an optical pulse signal. パルス信号のパルス幅を測定するパルス幅測定方法において、
分岐手段は、検出対象のパルス信号を２分岐し、
フィルタ手段は、入力された分岐された一方のパルス信号に対し、固定帯域の帯域制限を行ってパルス信号のパルス幅を伸長してピークタイミングを遅延させ、
時間差検出手段は、分岐された他方のパルス信号と、上記フィルタ手段を介して遅延されたパルス信号との時間差を検出し、
時間差／パルス幅変換手段は、検出された時間差をパルス幅に変換し、
上記時間差検出手段は、第１及び第２の位相同期ループを有し、
第１の位相同期ループは、上記フィルタ手段を介することなく入力された周波数ｆの第１のパルス信号に対して、周波数Δｆの局部発振信号と周波数ｆの第１の位相同期後信号とが混合されて得られた所定周波数ｆ−Δｆの第１の参照信号を用いて変調し、第１のパルス信号と第１の参照信号との間での周波数Δｆの第１のビート信号を得ると共に、得られた第１のビート信号を、上記第１の参照信号に位相同期させ、かつ、検出対象の第１のパルス信号が意図している周波数ｆの上記第１の位相同期後信号に変換し、
第２の位相同期ループは、上記フィルタ手段を介して入力された周波数ｆの第２のパルス信号に対して、周波数Δｆの局部発振信号と周波数ｆの第２の位相同期後信号とが混合されて得られた所定周波数ｆ−Δｆの第２の参照信号を用いて変調し、第２のパルス信号と第２の参照信号との間での周波数Δｆの第２のビート信号を得ると共に、得られた第２のビート信号を、上記第２の参照信号に位相同期させ、かつ、検出対象の第２のパルス信号が意図している周波数ｆの上記第２の位相同期後信号に変換し、
これら第１及び第２の位相同期ループにおける第１及び第２の位相同期後信号の時間差を検出信号として出力する
ことを特徴とするパルス幅測定方法。 In a pulse width measurement method for measuring the pulse width of a pulse signal,
The branching means splits the pulse signal to be detected into two branches,
The filter means, for one of the input branched pulse signals, performs band limitation of a fixed band to extend the pulse width of the pulse signal to delay the peak timing,
The time difference detection means detects the time difference between the other branched pulse signal and the pulse signal delayed through the filter means,
The time difference / pulse width conversion means converts the detected time difference into a pulse width ,
The time difference detection means has first and second phase locked loops,
In the first phase-locked loop, the local oscillation signal having the frequency Δf and the first phase-locked signal having the frequency f are mixed with the first pulse signal having the frequency f inputted without passing through the filter means. The first reference signal having the predetermined frequency f−Δf thus obtained is modulated to obtain the first beat signal having the frequency Δf between the first pulse signal and the first reference signal, and The obtained first beat signal is phase-synchronized with the first reference signal and converted into the first phase-synchronized signal having the frequency f intended by the first pulse signal to be detected. ,
In the second phase-locked loop, the local oscillation signal having the frequency Δf and the second post-phase-locked signal having the frequency f are mixed with the second pulse signal having the frequency f input through the filter unit. The second reference signal having the predetermined frequency f−Δf obtained in this way is modulated to obtain a second beat signal having the frequency Δf between the second pulse signal and the second reference signal. The second beat signal is phase-synchronized with the second reference signal, and converted to the second phase-synchronized signal having the frequency f intended by the second pulse signal to be detected,
A pulse width measurement method characterized by outputting a time difference between first and second phase-synchronized signals in the first and second phase-locked loops as a detection signal . 光伝送路での波長分散を検出する光伝送路分散検出装置において、
上記光伝送路を介した後のパルス信号のパルス幅を測定する通過後光パルス幅測定装置と、
上記光伝送路を介する前のパルス信号のパルス幅について、上記光伝送路を介した後のパルス信号のパルス幅と上記光伝送路の波長分散値との関係情報を保持している変換用情報保持手段と、
上記通過後光パルス幅測定装置による測定パルス幅を、上記変換用情報保持手段が保持している情報に当て嵌めて、上記光伝送路の波長分散値を得る情報変換手段とを有し、
通過後光パルス幅測定装置は、入力されたパルス信号を２分岐する第１の分岐手段と、分岐された一方のパルス信号が入力され、そのパルス信号に対し、固定帯域の帯域制限を行ってパルス信号のパルス幅を伸長してピークタイミングを遅延させる第１のフィルタ手段と、分岐された他方のパルス信号と、上記第１のフィルタ手段を介して遅延されたパルス信号との時間差を検出する第１の時間差検出手段と、検出された時間差をパルス幅に変換する第１の時間差／パルス幅変換手段とを有し、
上記第１の時間差検出手段は、第１及び第２の位相同期ループを有し、
第１の位相同期ループは、上記第１のフィルタ手段を介することなく入力された周波数ｆの第１のパルス信号に対して、周波数Δｆの局部発振信号と周波数ｆの第１の位相同期後信号とが混合されて得られた所定周波数ｆ−Δｆの第１の参照信号を用いて変調し、第１のパルス信号と第１の参照信号との間での周波数Δｆの第１のビート信号を得ると共に、得られた第１のビート信号を、上記第１の参照信号に位相同期させ、かつ、検出対象の第１のパルス信号が意図している周波数ｆの上記第１の位相同期後信号に変換し、
第２の位相同期ループは、上記第１のフィルタ手段を介して入力された周波数ｆの第２のパルス信号に対して、周波数Δｆの局部発振信号と周波数ｆの第２の位相同期後信号とが混合されて得られた所定周波数ｆ−Δｆの第２の参照信号を用いて変調し、第２のパルス信号と第２の参照信号との間での周波数Δｆの第２のビート信号を得ると共に、得られた第２のビート信号を、上記第２の参照信号に位相同期させ、かつ、検出対象の第２のパルス信号が意図している周波数ｆの上記第２の位相同期後信号に変換し、
これら第１及び第２の位相同期ループにおける第１及び第２の位相同期後信号の時間差を検出信号として出力する
ことを特徴とする光伝送路分散検出装置。 In an optical transmission line dispersion detection device for detecting chromatic dispersion in an optical transmission line,
A post-passage optical pulse width measuring device for measuring the pulse width of the pulse signal after passing through the optical transmission line;
For the pulse width of the pulse signal before passing through the optical transmission path, information for conversion that holds the relationship information between the pulse width of the pulse signal after passing through the optical transmission path and the chromatic dispersion value of the optical transmission path Holding means;
Information conversion means for obtaining the chromatic dispersion value of the optical transmission line by fitting the measurement pulse width by the post-passage optical pulse width measurement device to the information held by the conversion information holding means;
The post-passage optical pulse width measuring device receives a first branching means for bifurcating an input pulse signal and one of the branched pulse signals, and performs a band limitation on a fixed band for the pulse signal. A time difference between the first filter means for extending the pulse width of the pulse signal to delay the peak timing, the other branched pulse signal, and the pulse signal delayed through the first filter means is detected. a first time difference detecting means, a first time difference / pulse width conversion means for converting the detected time difference to the pulse width possess,
The first time difference detection means has first and second phase locked loops,
The first phase-locked loop has a local oscillation signal of frequency Δf and a first post-phase-locked signal of frequency f with respect to the first pulse signal of frequency f input without passing through the first filter means. Is modulated using a first reference signal having a predetermined frequency f−Δf obtained by mixing and a first beat signal having a frequency Δf between the first pulse signal and the first reference signal. The first beat signal obtained is phase-synchronized with the first reference signal, and the first post-phase-synchronized signal of the frequency f intended by the first pulse signal to be detected is obtained. Converted to
The second phase-locked loop has a local oscillation signal of frequency Δf and a second post-phase-locked signal of frequency f with respect to the second pulse signal of frequency f input through the first filter means. Is modulated using a second reference signal having a predetermined frequency f−Δf obtained by mixing the signals to obtain a second beat signal having a frequency Δf between the second pulse signal and the second reference signal. In addition, the obtained second beat signal is phase-synchronized with the second reference signal, and the second post-phase-synchronized signal of the frequency f intended by the second pulse signal to be detected is used. Converted,
An optical transmission line dispersion detection apparatus that outputs a time difference between the first and second phase-synchronized signals in the first and second phase-locked loops as a detection signal . 上記光伝送路を介する前のパルス信号のパルス幅を測定する通過前光パルス幅測定装置を有し、
通過前光パルス幅測定装置は、入力されたパルス信号を２分岐する第２の分岐手段と、分岐された一方のパルス信号が入力され、そのパルス信号に対し、固定帯域の帯域制限を行ってパルス信号のパルス幅を伸長してピークタイミングを遅延させる第２のフィルタ手段と、分岐された他方のパルス信号と、上記第２のフィルタ手段を介して遅延されたパルス信号との時間差を検出する第２の時間差検出手段と、検出された時間差をパルス幅に変換する第２の時間差／パルス幅変換手段とを有し、
上記第２の時間差検出手段は、第３及び第４の位相同期ループを有し、
第３の位相同期ループは、上記第２のフィルタ手段を介することなく入力された周波数ｆの第３のパルス信号に対して、周波数Δｆの局部発振信号と周波数ｆの第３の位相同期後信号とが混合されて得られた所定周波数ｆ−Δｆの第３の参照信号を用いて変調し、第３のパルス信号と第３の参照信号との間での周波数Δｆの第３のビート信号を得ると共に、得られた第３のビート信号を、上記第３の参照信号に位相同期させ、かつ、検出対象の第３のパルス信号が意図している周波数ｆの上記第３の位相同期後信号に変換し、
第４の位相同期ループは、上記第２のフィルタ手段を介して入力された周波数ｆの第４のパルス信号に対して、周波数Δｆの局部発振信号と周波数ｆの第４の位相同期後信号とが混合されて得られた所定周波数ｆ−Δｆの第４の参照信号を用いて変調し、第４のパルス信号と第４の参照信号との間での周波数Δｆの第４のビート信号を得ると共に、得られた第４のビート信号を、上記第４の参照信号に位相同期させ、かつ、検出対象の第４のパルス信号が意図している周波数ｆの上記第４の位相同期後信号に変換し、
これら第３及び第４の位相同期ループにおける第３及び第４の位相同期後信号の時間差を検出信号として出力する
ことを特徴とする請求項４に記載の光伝送路分散検出装置。 Having a pre-passage optical pulse width measuring device for measuring the pulse width of the previous pulse signal through the optical transmission line;
The pre-passage optical pulse width measurement device is configured to perform a second band splitting unit that splits an input pulse signal in two, and one of the branched pulse signals is input, and performs band limitation of a fixed band on the pulse signal. A time difference between the second filter means for extending the pulse width of the pulse signal to delay the peak timing, the other branched pulse signal, and the pulse signal delayed through the second filter means is detected. a second time difference detecting means, and a second time difference / pulse width conversion means for converting the detected time difference to the pulse width possess,
The second time difference detection means includes third and fourth phase locked loops,
The third phase-locked loop has a local oscillation signal of frequency Δf and a third post-phase-locked signal of frequency f with respect to the third pulse signal of frequency f input without passing through the second filter means. Is modulated using a third reference signal having a predetermined frequency f−Δf obtained by mixing and a third beat signal having a frequency Δf between the third pulse signal and the third reference signal. The third beat signal obtained is phase-synchronized with the third reference signal, and the third post-phase-synchronized signal having the frequency f intended by the third pulse signal to be detected is obtained. Converted to
The fourth phase-locked loop has a local oscillation signal of frequency Δf and a fourth post-phase-locked signal of frequency f with respect to the fourth pulse signal of frequency f input via the second filter means. Is modulated using a fourth reference signal having a predetermined frequency f−Δf obtained by mixing the signals to obtain a fourth beat signal having a frequency Δf between the fourth pulse signal and the fourth reference signal. In addition, the obtained fourth beat signal is phase-synchronized with the fourth reference signal, and the fourth post-phase-synchronized signal having the frequency f intended by the fourth pulse signal to be detected is used. Converted,
5. The optical transmission line dispersion detection apparatus according to claim 4 , wherein a time difference between the third and fourth phase-synchronized signals in the third and fourth phase-locked loops is output as a detection signal . 光伝送路での波長分散を検出する光伝送路分散検出方法において、
通過後光パルス幅測定装置は、上記光伝送路を介した後のパルス信号のパルス幅を測定し、
変換用情報保持手段は、上記光伝送路を介する前のパルス信号のパルス幅について、上記光伝送路を介した後のパルス信号のパルス幅と上記光伝送路の波長分散値との関係情報を保持しており、
情報変換手段は、上記通過後光パルス幅測定装置による測定パルス幅を、上記変換用情報保持手段が保持している情報に当て嵌めて、上記光伝送路の波長分散値を得、
上記通過後光パルス幅測定装置は、分岐手段、フィルタ手段、時間差検出手段及び時間差／パルス幅変換手段を有し、
上記分岐手段は、入力されたパルス信号を２分岐し、
上記フィルタ手段は、分岐された一方のパルス信号に対し、固定帯域の帯域制限を行ってパルス信号のパルス幅を伸長してピークタイミングを遅延させ、
上記時間差検出手段は、分岐された他方のパルス信号と、上記フィルタ手段を介して遅延されたパルス信号との時間差を検出し、
上記時間差／パルス幅変換手段は、検出された時間差をパルス幅に変換し、
上記時間差検出手段は、第１及び第２の位相同期ループを有し、
第１の位相同期ループは、上記フィルタ手段を介することなく入力された周波数ｆの第１のパルス信号に対して、周波数Δｆの局部発振信号と周波数ｆの第１の位相同期後信号とが混合されて得られた所定周波数ｆ−Δｆの第１の参照信号を用いて変調し、第１のパルス信号と第１の参照信号との間での周波数Δｆの第１のビート信号を得ると共に、得られた第１のビート信号を、上記第１の参照信号に位相同期させ、かつ、検出対象の第１のパルス信号が意図している周波数ｆの上記第１の位相同期後信号に変換し、
第２の位相同期ループは、上記フィルタ手段を介して入力された周波数ｆの第２のパルス信号に対して、周波数Δｆの局部発振信号と周波数ｆの第２の位相同期後信号とが混合されて得られた所定周波数ｆ−Δｆの第２の参照信号を用いて変調し、第２のパルス信号と第２の参照信号との間での周波数Δｆの第２のビート信号を得ると共に、得られた第２のビート信号を、上記第２の参照信号に位相同期させ、かつ、検出対象の第２のパルス信号が意図している周波数ｆの上記第２の位相同期後信号に変換し、
これら第１及び第２の位相同期ループにおける第１及び第２の位相同期後信号の時間差を検出信号として出力する
ことを特徴とする光伝送路分散検出方法。 In an optical transmission line dispersion detection method for detecting chromatic dispersion in an optical transmission line,
The post-passage optical pulse width measuring device measures the pulse width of the pulse signal after passing through the optical transmission line,
The conversion information holding means obtains the relationship information between the pulse width of the pulse signal after passing through the optical transmission path and the wavelength dispersion value of the optical transmission path with respect to the pulse width of the pulse signal before passing through the optical transmission path. Hold
The information conversion means applies the measurement pulse width by the post-passage optical pulse width measurement device to the information held by the conversion information holding means to obtain the chromatic dispersion value of the optical transmission line,
The post-passage optical pulse width measuring device has branching means, filter means, time difference detection means, and time difference / pulse width conversion means,
The branching means branches the input pulse signal into two branches,
The above filter means delays the peak timing by extending the pulse width of the pulse signal by performing band limitation of a fixed band on one of the branched pulse signals,
The time difference detection means detects the time difference between the other branched pulse signal and the pulse signal delayed through the filter means,
The time difference / pulse width conversion means converts the detected time difference into a pulse width ,
The time difference detection means has first and second phase locked loops,
In the first phase-locked loop, the local oscillation signal having the frequency Δf and the first phase-locked signal having the frequency f are mixed with the first pulse signal having the frequency f inputted without passing through the filter means. The first reference signal having the predetermined frequency f−Δf thus obtained is modulated to obtain the first beat signal having the frequency Δf between the first pulse signal and the first reference signal, and The obtained first beat signal is phase-synchronized with the first reference signal and converted into the first phase-synchronized signal having the frequency f intended by the first pulse signal to be detected. ,
In the second phase-locked loop, the local oscillation signal having the frequency Δf and the second post-phase-locked signal having the frequency f are mixed with the second pulse signal having the frequency f input through the filter unit. The second reference signal having the predetermined frequency f−Δf obtained in this way is modulated to obtain a second beat signal having the frequency Δf between the second pulse signal and the second reference signal. The second beat signal is phase-synchronized with the second reference signal, and converted to the second phase-synchronized signal having the frequency f intended by the second pulse signal to be detected,
An optical transmission line dispersion detection method, characterized in that the time difference between the first and second phase-synchronized signals in the first and second phase-locked loops is output as a detection signal .
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JP2004173026A (en) * 2002-11-21 2004-06-17 Fujitsu Ltd Optical dispersion monitoring method and apparatus, and optical transmission system using the same
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JP2007036989A (en) * 2005-07-29 2007-02-08 Oki Electric Ind Co Ltd Multi-rate clock signal extracting method and device

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JP2004173026A (en) * 2002-11-21 2004-06-17 Fujitsu Ltd Optical dispersion monitoring method and apparatus, and optical transmission system using the same
JP2005315858A (en) * 2004-03-31 2005-11-10 Sun Tec Kk Optical pulse evaluation device and in-service optical pulse evaluation device
JP2007036989A (en) * 2005-07-29 2007-02-08 Oki Electric Ind Co Ltd Multi-rate clock signal extracting method and device

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