JP4450749B2 - Partial discharge position locator - Google Patents

Partial discharge position locator Download PDF

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JP4450749B2
JP4450749B2 JP2005070967A JP2005070967A JP4450749B2 JP 4450749 B2 JP4450749 B2 JP 4450749B2 JP 2005070967 A JP2005070967 A JP 2005070967A JP 2005070967 A JP2005070967 A JP 2005070967A JP 4450749 B2 JP4450749 B2 JP 4450749B2
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partial discharge
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洋 前川
茂雄 藤井
俊弘 星野
孝夫 熊澤
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Chubu Electric Power Co Inc
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この発明は、配電・送変電設備等から発生する部分放電源の位置を標定する部分放電位置標定装置に関するものである。   The present invention relates to a partial discharge position locating device for locating a partial discharge power source generated from a power distribution / transmission / transformation facility or the like.

電力機器の機能維持、故障の未然防止の観点から変電所設備機器の部分放電を非接触で検出する方法として、例えば、部分放電源から放射される電磁波を複数の検出用アンテナで受信し、電磁波空間位相差法を用いて部分放電信号の検出を行う方法が提案されている。その方法に示された位置標定実験装置の例では、７７ｋＶガス絶縁開閉装置（ＧＩＳ）を囲み５０ｍ４方に配置した４本の検出用アンテナにより放電信号を受信し、そのうちの例えば２つの検出用アンテナで受信したときの到達時間Ｔ１及びＴ２の時間差（ΔＴ＝Ｔ２−Ｔ１）を求め、双曲線法を用いて放電点の位置標定を行っている。位相差（時間差）を求める方法は、検出用アンテナにより受信された２つの信号をデジタルオシロスコープに取り込み、パソコンを用いて、時間平均、標準化した後、フーリエ変換により周波数領域に変換する。その後、相互関数を求め、適応フィルタを通したのち、逆フーリエ変換により時間領域に変換し、アンテナ間の到達時間差を求めている。２対ごとのアンテナの時間差を求めることより部分放電の位置を算出することができる（非特許文献１参照）。   As a method for detecting the partial discharge of substation equipment in a non-contact manner from the viewpoint of maintaining the function of power equipment and preventing breakdowns, for example, receiving electromagnetic waves radiated from partial discharge sources with multiple detection antennas, A method of detecting a partial discharge signal using a spatial phase difference method has been proposed. In the example of the positioning experiment apparatus shown in the method, a discharge signal is received by four detection antennas arranged in a direction of 50 m 4 surrounding a 77 kV gas insulated switchgear (GIS), for example, two detection antennas among them. The time difference (ΔT = T2−T1) between the arrival times T1 and T2 when received at 1 is obtained, and the location of the discharge point is determined using the hyperbola method. As a method for obtaining a phase difference (time difference), two signals received by a detection antenna are taken into a digital oscilloscope, time averaged and standardized using a personal computer, and then converted into a frequency domain by Fourier transformation. Thereafter, a mutual function is obtained, passed through an adaptive filter, and then converted into the time domain by inverse Fourier transform to obtain an arrival time difference between the antennas. The position of partial discharge can be calculated by obtaining the time difference between two pairs of antennas (see Non-Patent Document 1).

「電磁波空間位相差法を用いた非接触部分放電検出法」電気学会論文誌Ｂ、vol. 115-B、No. 10(1995)"Non-contact partial discharge detection method using electromagnetic phase difference method" IEEJ Transactions B, vol. 115-B, No. 10 (1995)

上記に示すような従来の部分放電の位置標定装置は、変電所設備機器のように部分放電が比較的狭い範囲で特定されており、検出用アンテナを広い間隔で設置できるような場所での測定では有効であるが、上記技術では、アンテナ信号を直接デジタルで取り込んでいるため、位置を精度よく標定するには高速のデジタルオシロスコープ、たとえば数ギガサンプリング／チャンネルが必要であり、このような装置は高価で、かつ形状，重量も大きいという問題点を有していた。
例えば、不特定場所の配電柱上の電力設備から発生する部分放電を検出するような場合の部分放電位置標定装置では、携帯性が要求されるため、アンテナの間隔を狭くし、かつ高精度にする必要がある。従ってこのような測定対象には、精度，携帯性，経済性の面から、上記のような従来技術をそのまま適用するのは困難であった。 The conventional partial discharge position locator as shown above is measured in a place where the partial discharge is specified in a relatively narrow range, such as substation equipment, and the detection antennas can be installed at wide intervals. Although effective, the above technique directly captures the antenna signal digitally, so a high-speed digital oscilloscope, such as several gigasamples / channel, is required to accurately locate the position. It was expensive and had the problem of large shape and weight.
For example, in the partial discharge position locating device in the case of detecting partial discharge generated from power equipment on a distribution pole in an unspecified location, portability is required, so the interval between antennas is narrowed and the accuracy is high. There is a need to. Therefore, it has been difficult to apply the above-described conventional technology as it is to such a measurement object in terms of accuracy, portability, and economy.

この発明は、上記のような問題点を解消するためになされたもので、高精度で部分放電を検出でき、かつ、小型軽量で安価な部分放電位置標定装置を得ることを目的とする。   The present invention has been made to solve the above problems, and an object of the present invention is to obtain a partial discharge position locating device that can detect a partial discharge with high accuracy, and is small, light, and inexpensive.

この発明に係わる部分放電位置標定装置は、配電・送変電設備から発生する部分放電による電磁波を少なくとも第１と第２の２つの受信アンテナで受信し、部分放電源と両受信アンテナ間との距離に応じた受信信号の位相差を求めて部分放電の位置を標定する部分放電位置標定装置において、第１の受信アンテナで受信した受信信号及び第２の受信アンテナで受信した受信信号から、それぞれ特定の周波数成分の信号を抽出するバンドパスフィルタと、位相角０とπ／２の２つの中間周波数を生成する局部発振器と、バンドパスフィルタにより抽出した両信号に中間周波数をミキシングして直交検波を行ったのち、低周波成分の信号を取り出す手段と、取り出した低周波成分の信号をＡ／Ｄ変換するＡ／Ｄ変換器と、Ａ／Ｄ変換後の低周波成分の信号の除算処理を行って両受信信号の位相差を算出する演算手段とを有するものである。 The partial discharge position locating device according to the present invention receives electromagnetic waves caused by partial discharge generated from distribution / transmission / transformation equipment by at least the first and second receiving antennas, and the distance between the partial discharge power source and the two receiving antennas. In the partial discharge position locating device that determines the position of the partial discharge by obtaining the phase difference of the received signal in accordance with the received signal, it is specified from the received signal received by the first receiving antenna and the received signal received by the second receiving antenna, respectively. The bandpass filter that extracts the signal of the frequency component, the local oscillator that generates two intermediate frequencies with phase angles 0 and π / 2, and the quadrature detection by mixing the intermediate frequency into both signals extracted by the bandpass filter after performed, and means to eject the signal of the low frequency components, an a / D converter to a low frequency signal to a / D conversion taken out, low frequency of the a / D converted formed And has a calculating means for calculating a phase difference between the signal division processing performed both received signals.

また、第１の受信アンテナで受信した受信信号及び第２の受信アンテナで受信した受信信号から、それぞれ特定の周波数成分の信号を抽出するバンドパスフィルタと、第２の受信アンテナ側からの抽出信号を位相を遅延させて第１の受信アンテナ側からの抽出信号と乗算したのち低周波成分の信号を取り出す手段と、第１の受信アンテナ側からの抽出信号を位相を遅延させて第２の受信アンテナ側からの抽出信号と乗算したのち低周波成分の信号を取り出す手段と、取り出した両低周波成分の信号をＡ／Ｄ変換するＡ／Ｄ変換器と、Ａ／Ｄ変換後の両低周波成分の信号の和と差を利用し除算処理を行って両受信信号の位相差を算出する演算手段とを有するものである。 In addition, a band-pass filter that extracts a signal of a specific frequency component from a reception signal received by the first reception antenna and a reception signal received by the second reception antenna, respectively , and an extraction signal from the second reception antenna side means to eject the signal of the low frequency component After multiplying the extracted signal from the first reception antenna side by delaying the phase of the, first by the extraction signal from the first reception antenna side delays the phase 2 means to eject the signal of the low frequency component after multiplying the extracted signal from the reception antenna side, an a / D converter the signals of both the low-frequency component to a / D conversion taken out, a / D converted And calculating means for calculating a phase difference between the two received signals by performing a division process using the sum and difference of the signals of both low frequency components.

この発明の部分放電位置標定装置によれば、第１の受信アンテナで受信した受信信号及び第２の受信アンテナで受信した受信信号から特定の周波数成分を抽出し、中間周波数をミキシングして直交検波を行ったのち、低周波成分を取り出しＡ／Ｄ変換して両受信信号の比から位相差を算出するようにしたので、部分放電電磁波信号の位相差を広い角度の範囲に亘り高精度で捉えることができる。また、高周波回路の演算にアナログ回路を用いることにより小型，軽量で安価な部分放電位置標定装置を得ることができる。   According to the partial discharge position locating apparatus of the present invention, a specific frequency component is extracted from the received signal received by the first receiving antenna and the received signal received by the second receiving antenna, and the intermediate frequency is mixed to perform quadrature detection. Since the low-frequency component is extracted and A / D converted to calculate the phase difference from the ratio of the two received signals, the phase difference of the partial discharge electromagnetic wave signal is captured with high accuracy over a wide angle range. be able to. Further, by using an analog circuit for the calculation of the high frequency circuit, a small, light and inexpensive partial discharge position locating device can be obtained.

また、第１の受信アンテナで受信した受信信号及び第２の受信アンテナで受信した受信信号から特定の周波数成分を抽出し、一方のアンテナ出力の原波形と他方のアンテナ出力の遅延させた波形とを互いに乗算したのち、低周波成分の信号を取り出してＡ／Ｄ変換し、両低周波成分の信号の和と差の比から両受信信号の位相差を算出するようにしたので、回路を対称に設計できるため温度ドリフトなどの誤差要素を除去して高精度で部分放電電磁波信号の位相差を検出できる。また、高周波回路の演算にアナログ回路を用いることにより小型，軽量で安価な部分放電位置標定装置を得ることができる。   In addition, a specific frequency component is extracted from the received signal received by the first receiving antenna and the received signal received by the second receiving antenna, and the original waveform of one antenna output and the delayed waveform of the other antenna output, After multiplying each other, the low frequency component signal is taken out and A / D converted, and the phase difference between both received signals is calculated from the ratio of the sum and difference of both low frequency component signals. Therefore, the phase difference of the partial discharge electromagnetic wave signal can be detected with high accuracy by removing error elements such as temperature drift. Further, by using an analog circuit for the calculation of the high frequency circuit, a small, light and inexpensive partial discharge position locating device can be obtained.

実施の形態１．
図１はこの発明の実施の形態１による部分放電位置標定装置の信号処理ブロック図である。以下、図に従ってブロック図の構成と信号処理手順を説明する。
例えば、配電・送変電設備等の電気設備機器の絶縁劣化等により部分放電が発生すると、部分放電源から電磁波が放射される。このような空気中での部分放電による電磁波信号は、例えば、ｎｓ（ナノ秒）オーダで急峻に立ち上がる単発パルス信号が断続して発生し、２０ＭＨｚ〜数百ＭＨｚの周波数範囲に亘ってスペクトルが連続分布するような波形である。 Embodiment 1 FIG.
1 is a signal processing block diagram of a partial discharge position locating apparatus according to Embodiment 1 of the present invention. The configuration of the block diagram and the signal processing procedure will be described below with reference to the drawings.
For example, when partial discharge occurs due to insulation deterioration of electrical equipment such as power distribution / transmission / transformation equipment, electromagnetic waves are radiated from the partial discharge source. Such an electromagnetic wave signal due to partial discharge in the air is generated, for example, by intermittent single pulse signals that rise sharply in the order of ns (nanoseconds), and the spectrum is continuous over a frequency range of 20 MHz to several hundred MHz. The waveform is distributed.

上記のような部分放電源からの電磁波信号を、所定の距離（例えば、数十ｃｍ以下）だけ離隔して設けた複数の受信アンテナ、本実施の形態では第１の受信アンテナ１Ａと第２の受信アンテナ１Ｂの２本の受信アンテナで受信する。受信したそれぞれの受信信号をバンドパスフィルタ（以下ＢＰＦと略す）２Ａ及び２Ｂを通過させて所定の周波数（例えば４００ＭＨｚ）成分の電磁波信号を抽出する。   A plurality of receiving antennas provided with the electromagnetic wave signals from the partial discharge sources as described above separated by a predetermined distance (for example, several tens of centimeters or less), in the present embodiment, the first receiving antenna 1A and the second receiving antenna Reception is performed by the two reception antennas of the reception antenna 1B. Each received signal is passed through bandpass filters (hereinafter abbreviated as BPF) 2A and 2B, and an electromagnetic wave signal having a predetermined frequency (for example, 400 MHz) component is extracted.

また、局部発振器３により、位相角０とπ／２の２つの中間周波数（例えば、３４０ＭＨｚの矩形波。但し、矩形波に限定せず、正弦波等でもよい）の信号を発振させておく。第１の受信アンテナ１ＡからＢＰＦ２Ａを通過した信号Ｓ１(t)と、局部発振器３からの位相角π／２の矩形波とを高周波掛算器４Ａにより乗算し、ローパスフィルタ（以下ＬＰＦと略す）５Ａを通過させてその低周波成分を抽出する。一方、第２の受信アンテナ１ＢからＢＰＦ２Ｂを通過した信号Ｓ２(t)と、局部発振器３からの位相角０の矩形波とを高周波掛算器４Ｂにより乗算し、ＬＰＦ５Ｂを通過させてその低周波成分を抽出する。更に、ＢＰＦ２Ａからの信号Ｓ１(t)と、局部発振器３からの位相角０の矩形波とを高周波掛算器４Ｃにより乗算し、ＬＰＦ５Ｃを通過させてその低周波成分を抽出する。 Further, the local oscillator 3 oscillates a signal having two intermediate frequencies (for example, a rectangular wave of 340 MHz, but not limited to the rectangular wave but may be a sine wave or the like) having a phase angle of 0 and π / 2. The signal S 1 (t) that has passed through the BPF 2A from the first receiving antenna 1A and the rectangular wave with the phase angle π / 2 from the local oscillator 3 are multiplied by the high frequency multiplier 4A, and a low-pass filter (hereinafter abbreviated as LPF). The low frequency component is extracted by passing 5A. On the other hand, the signal S 2 (t) that has passed through the BPF 2B from the second receiving antenna 1B and the rectangular wave having a phase angle of 0 from the local oscillator 3 are multiplied by the high frequency multiplier 4B, and the low frequency is passed through the LPF 5B. Extract ingredients. Further, the signal S 1 (t) from the BPF 2A and the rectangular wave having the phase angle 0 from the local oscillator 3 are multiplied by the high frequency multiplier 4C, and the low frequency component is extracted by passing through the LPF 5C.

次に、ＬＰＦ５Ａからの出力信号とＬＰＦ５Ｂからの出力信号を低周波掛算器６Ａで乗算し、ＬＰＦ７Ａで低周波成分を抽出してサンプルホールド８Ａによりサンプリングしたのち、Ａ／Ｄ変換器９によってアナログ信号をデジタル信号に変換し、マイクロプロセッサ１０へ入力する。同様に、ＬＰＦ５Ｂからの出力信号とＬＰＦ５Ｃからの出力信号を低周波掛算器６Ｂで乗算し、ＬＰＦ７Ｂで低周波成分を抽出してサンプルホールド８Ｂによりサンプリングしたのち、Ａ／Ｄ変換器９によってアナログ信号をデジタル信号に変換し、マイクロプロセッサ１０へ入力する。マイクロプロセッサ１０では、２つの信号データを後述の理論式により演算して部分放電電磁波信号の到達位相差を求める。   Next, the output signal from the LPF 5A and the output signal from the LPF 5B are multiplied by the low frequency multiplier 6A, the low frequency component is extracted by the LPF 7A, sampled by the sample hold 8A, and then the analog signal is output by the A / D converter 9. Is converted into a digital signal and input to the microprocessor 10. Similarly, the output signal from the LPF 5B and the output signal from the LPF 5C are multiplied by the low frequency multiplier 6B, the low frequency component is extracted by the LPF 7B, sampled by the sample hold 8B, and then the analog signal is output by the A / D converter 9. Is converted into a digital signal and input to the microprocessor 10. The microprocessor 10 calculates the arrival phase difference of the partial discharge electromagnetic wave signal by calculating two signal data according to a theoretical formula described later.

上記のように、本実施の形態の回路では、第１の受信アンテナ１Ａで受信した受信信号及び第２の受信アンテナ１Ｂで受信した受信信号から、それぞれバンドパスフィルタ２Ａ，２Ｂを通し特定の周波数成分の信号を抽出し、抽出した両信号に、π／２だけ位相をずらせた２つの中間周波数をミキシングして、振幅とアンテナへの到達位相差情報が保持されたまま、ＢＰＦ通過後の周波数と中間周波数の差に応じた周波数の信号を取り出し、直交検波を行ったのち、その低周波成分の信号を抽出してＡ／Ｄ変換し、デジタル演算を行って位相差を求めるものである。高周波回路部の演算にはアナログ回路を用いてアナログ処理を行っている。   As described above, in the circuit according to the present embodiment, a specific frequency is obtained from the received signal received by the first receiving antenna 1A and the received signal received by the second receiving antenna 1B through the bandpass filters 2A and 2B, respectively. The component signals are extracted, and the two intermediate frequencies shifted in phase by π / 2 are mixed into the extracted signals, and the frequency after passing through the BPF while the amplitude and the arrival phase difference information to the antenna are maintained. A signal having a frequency corresponding to the difference between the intermediate frequency and the intermediate frequency is taken out and subjected to quadrature detection. Then, the low frequency component signal is extracted and A / D converted, and a digital operation is performed to obtain a phase difference. Analog processing is performed using an analog circuit for the calculation of the high-frequency circuit section.

上記の装置において、受信アンテナは１Ａ，１Ｂには、例えば、ロッドアンテナを使用する。局部発振器３には、例えば、小型軽量でノイズ特性に優れた電圧制御発振器（ＶＣＯ）を使用する。また、ＢＰＦ２Ａ，２Ｂには、例えば、４００ＭＨｚの表面弾性波フィルタ（ＳＡＷ）を使用する。ＳＡＷは帯域幅が狭く要素間の値のばらつきが少ないので、単発パルス信号である部分放電信号から個体差（ばらつき）のない安定した２０サイクル程度の出力波形が得られることを確認している。   In the above apparatus, for example, rod antennas are used for the receiving antennas 1A and 1B. As the local oscillator 3, for example, a voltage controlled oscillator (VCO) that is small and light and has excellent noise characteristics is used. For the BPFs 2A and 2B, for example, surface acoustic wave filters (SAW) of 400 MHz are used. Since the SAW has a narrow bandwidth and little variation in values between elements, it has been confirmed that a stable output waveform of about 20 cycles with no individual difference (variation) can be obtained from a partial discharge signal which is a single pulse signal.

次に、数式を用いて、図１のブロック図の動作を説明する。
部分放電による単発パルス信号が第１の受信アンテナ１Ａ及び第２の受信アンテナ１Ｂで受信されたときの、ＢＰＦ２Ａ及び２Ｂを通過後の出力をそれぞれＳ１(t)及びＳ２(t)とすると、次のように表すことができる。
Ｓ１(t)＝Ｅ１(t)×sin(ωt)・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・（１）
Ｓ２(t)＝Ｅ２(t)×sin(ω(t−Δt))・・・・・・・・・・・・・・・・・・・・・・・・・・・・（２）
ここでＥ１(t)，Ｅ２(t)はエンベロープ関数、ωはＢＰＦの通過角周波数、Δtは電磁波信号の到達時間差である。 Next, the operation of the block diagram of FIG. 1 will be described using mathematical expressions.
When the single pulse signals due to partial discharge are received by the first receiving antenna 1A and the second receiving antenna 1B, the outputs after passing through the BPFs 2A and 2B are S 1 (t) and S 2 (t), respectively. Can be expressed as:
S 1 (t) = E 1 (t) × sin (ωt) ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・・ (1)
S 2 (t) = E 2 (t) × sin (ω (t−Δt)) 2)
Here, E 1 (t) and E 2 (t) are envelope functions, ω is the passing angular frequency of the BPF, and Δt is the arrival time difference of the electromagnetic wave signal.

また、局部発振器３から出力する位相がπ／２異なった２つの矩形波の、それぞれの基本波（ω０）成分をＶ１(t)及びＶ２(t)とすると次のように表すことができる。
Ｖ１(t)＝Ｖ０×sin(ω０t＋φ)・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・（３）
Ｖ２(t)＝Ｖ０×sin(ω０t＋φ＋π／２)・・・・・・・・・・・・・・・・・・・・・・・・・（４）
ここで、φは局部発振器３の位相角である。 In addition, when the fundamental wave (ω 0 ) components of two rectangular waves having a phase difference of π / 2 output from the local oscillator 3 are V 1 (t) and V 2 (t), they are expressed as follows. Can do.
V 1 (t) = V 0 × sin (ω 0 t + φ) (3) )
V 2 (t) = V 0 × sin (ω 0 t + φ + π / 2) (4)
Here, φ is the phase angle of the local oscillator 3.

Ｓ１(t)とＶ１(t)とを乗算して得られる出力をＶout１１(t)、Ｓ１(t)とＶ２(t)とを乗算して得られる出力をＶout１２(t)、また、Ｓ２(t)とＶ１(t)とを乗算して得られる信号をＶout２１(t)とおくと、
Ｖout11(t)＝Ｓ１(t)×Ｖ１(t)
＝Ｖ０×Ｅ１(t)×cos((ω−ω０)t−φ)／２
−Ｖ０×Ｅ１(t)×cos((ω＋ω０)t＋φ)／２・・・・・・・・・・・（５）
Ｖout12(t)＝Ｓ１(t)×Ｖ２(t)
＝Ｖ０×Ｅ１(t)×cos((ω−ω０)t−φ−π／２)／２
−Ｖ０×Ｅ１(t)×cos((ω＋ω０)t＋φ＋π／２)／２
＝Ｖ０×Ｅ１(t)×sin((ω−ω０)t−φ)／２
−Ｖ０×Ｅ１(t)×sin((ω＋ω０)t＋φ)／２・・・・・・・・・・（６）
Ｖout21(t)＝Ｓ２(t)×Ｖ１(t)
＝Ｖ０×Ｅ２(t)×cos((ω−ω０)t−ωΔt−φ)／２
−Ｖ０×Ｅ１(t)×cos((ω＋ω０)t−ωΔt＋φ)／２・・・（７）
となる。すなわち、アンテナの受信信号のＬＰＦ通過後の周波数と局部発振器３の周波数の和の周波数の信号成分と、差の信号成分が加算されて出力される。 The output obtained by multiplying S 1 (t) and V 1 (t) is Vout 11 (t), and the output obtained by multiplying S 1 (t) and V 2 (t) is Vout 12 (t ), And a signal obtained by multiplying S 2 (t) and V 1 (t) by Vout 21 (t),
Vout 11 (t) = S 1 (t) × V 1 (t)
= V 0 × E 1 (t) × cos ((ω−ω 0 ) t−φ) / 2
−V 0 × E 1 (t) × cos ((ω + ω 0 ) t + φ) / 2 (5)
Vout 12 (t) = S 1 (t) × V 2 (t)
= V 0 × E 1 (t) × cos ((ω−ω 0 ) t−φ−π / 2) / 2
−V 0 × E 1 (t) × cos ((ω + ω 0 ) t + φ + π / 2) / 2
= V 0 × E 1 (t) × sin ((ω−ω 0 ) t−φ) / 2
−V 0 × E 1 (t) × sin ((ω + ω 0 ) t + φ) / 2 (6)
Vout 21 (t) = S 2 (t) × V 1 (t)
= V 0 × E 2 (t) × cos ((ω−ω 0 ) t−ωΔt−φ) / 2
−V 0 × E 1 (t) × cos ((ω + ω 0 ) t−ωΔt + φ) / 2 (7)
It becomes. That is, the signal component of the sum of the frequency after the LPF of the reception signal of the antenna and the frequency of the local oscillator 3 and the signal component of the difference are added and output.

次に、ＬＰＦ５Ａ〜５Ｃによりこれらの信号から低周波成分を取り出し、その出力をＶ１１(t)，Ｖ１２(t)及びＶ２１(t)とおくと、
Ｖ11(t)＝Ｖ０×Ｅ１(t)×cos((ω−ω０)t−φ)／２・・・・・・・・・・・・・・（８）
Ｖ12(t)＝Ｖ０×Ｅ１(t)×sin((ω−ω０)t−φ)／２・・・・・・・・・・・・・・（９）
Ｖ21(t)＝Ｖ０×Ｅ２(t)×cos((ω−ω０)t−ωΔt−φ)／２・・・・・（１０）
となる。上記のように振幅と位相（電磁波信号の到達時間差）情報が保存されている。 Next, low-frequency components are extracted from these signals by the LPFs 5A to 5C, and their outputs are set to V 11 (t), V 12 (t), and V 21 (t).
V 11 (t) = V 0 × E 1 (t) × cos ((ω-ω 0) t-φ) / 2 ·············· (8)
V 12 (t) = V 0 × E 1 (t) × sin ((ω−ω 0 ) t−φ) / 2 (9)
V 21 (t) = V 0 × E 2 (t) × cos ((ω−ω 0 ) t−ωΔt−φ) / 2 (10)
It becomes. As described above, amplitude and phase (difference in arrival time of electromagnetic wave signal) information is stored.

次に、Ｖ１１(t)とＶ２１(t)、及びＶ２１(t)とＶ１２(t)をそれぞれ低周波掛算器６Ｂ，６Ａにより乗算して得られた直交検波出力を、Ｖ11・21(t)及びＶ12・21(t)とすると、
Ｖ11・21(t)＝Ｖ11(t)×Ｖ21(t)
＝(1/8)×Ｖ０ ２×Ｅ１(t)×Ｅ２(t)×cos(２(ω−ω０)t−ωΔt−２φ)
＋(1/8)×Ｖ０ ２×Ｅ１(t)×Ｅ２(t)×cos(ωΔt)・・・・・・・（１１）
Ｖ12・21(t)＝Ｖ12(t)×Ｖ21(t)
＝(1/8)×Ｖ０ ２×Ｅ１(t)×Ｅ２(t)×sin(２(ω−ω０)t−ωΔt−２φ)
＋(1/8)×Ｖ０ ２×Ｅ１(t)×Ｅ２(t)×sin(ωΔt)・・・・・・・（１２）
となる。 Next, the quadrature detection output obtained by multiplying V 11 (t) and V 21 (t) and V 21 (t) and V 12 (t) by the low frequency multipliers 6B and 6A, respectively, is obtained as V 11・ 21 (t) and V12 ・ 21 (t)
V 11 ・ 21 (t) ＝ V 11 (t) × V 21 (t)
= (1/8) × V 0 2 × E 1 (t) × E 2 (t) × cos (2 (ω−ω 0 ) t−ωΔt−2φ)
+ (1/8) × V 0 2 × E 1 (t) × E 2 (t) × cos (ωΔt) (11)
V 12 ・ 21 (t) ＝ V 12 (t) × V 21 (t)
= (1/8) × V 0 2 × E 1 (t) × E 2 (t) × sin (2 (ω−ω 0 ) t−ωΔt−2φ)
+ (1/8) × V 0 2 × E 1 (t) × E 2 (t) × sin (ωΔt) (12)
It becomes.

上記の式１１及び式１２からＬＰＦ７Ａ，７Ｂにより低周波成分を取り出すことにより直流分のみを取りだすことができる。ＬＰＦ７Ａからの出力をＶout１(t)、ＬＰＦ７Ｂからの出力をＶout２(t)とすると、
Ｖout１(t)＝(1/8)×Ｖ０ ２×Ｅ１(t)×Ｅ２(t)×cos(ωΔt)・・・・・・（１３）
Ｖout２(t)＝(1/8)×Ｖ０ ２×Ｅ１(t)×Ｅ２(t)×sin(ωΔt)・・・・・・（１４） Only the DC component can be extracted by extracting the low frequency component from the above equations 11 and 12 by the LPFs 7A and 7B. If the output from the LPF 7A is Vout 1 (t) and the output from the LPF 7B is Vout 2 (t),
Vout 1 (t) = (1/8) × V 0 2 × E 1 (t) × E 2 (t) × cos (ωΔt) (13)
Vout 2 (t) = (1/8) × V 0 2 × E 1 (t) × E 2 (t) × sin (ωΔt) (14)

上記の式１３及び式１４より、次の式１５が得られる。
tan(ωΔt)＝Ｖout２(t)／Ｖout１(t)・・・・・・・・・・・・・・・・・・・・・・・・・（１５）
これより、到達位相差θ（＝ωΔt）は、
θ＝tan−１(Ｖout２(t)／Ｖout１(t))・・・・・・・・・・・・・・・・・・・・・・・・・（１６）
として求めることができる。 From the above equations 13 and 14, the following equation 15 is obtained.
tan (ωΔt) = Vout 2 (t) / Vout 1 (t) (15)
From this, the arrival phase difference θ (= ωΔt) is
θ = tan −1 (Vout 2 (t) / Vout 1 (t)) (16)
Can be obtained as

以上の理論式が意味するところは、部分放電の電磁波の到達時間差はＢＰＦ２Ａ，２Ｂ通過後の包絡線波形Ｅ１(t)及びＥ２(t)の波形に依存せず求められるということである。例えば、ＢＰＦ２Ａ，２Ｂの周波数を４００ＭＨｚ，局部発振器３の周波数を３４０ＭＨｚとすると、上記式８〜１０部分のＶ１２(t)，Ｖ１１(t)及びＶ２１(t)の周波数は、その差分である６０ＭＨｚに低周波化され、さらに直交検波及びＬＰＦにより直流化される。
次に、この信号はサンプルホールド８Ａ，８Ｂを通過後Ａ／Ｄ変換器９でデジタル信号に変換され、マイクロプロセッサ１０内で式１６の演算を行って到達時間差を求める。 The above theoretical formula means that the arrival time difference of electromagnetic waves of partial discharge can be obtained without depending on the waveforms of the envelope waveforms E 1 (t) and E 2 (t) after passing through the BPF 2A and 2B. . For example, if the frequency of BPF 2A, 2B is 400 MHz and the frequency of local oscillator 3 is 340 MHz, the frequencies of V 12 (t), V 11 (t) and V 21 (t) in the above parts 8 to 10 are the difference between them. The frequency is lowered to 60 MHz, and further converted to direct current by quadrature detection and LPF.
Next, this signal passes through the sample-and-holds 8A and 8B and is converted into a digital signal by the A / D converter 9, and the calculation of Expression 16 is performed in the microprocessor 10 to obtain the arrival time difference.

最終的には、この時間差Δｔから、部分放電源とアンテナの角度Θを次式により算出することができる。
Θ＝sin−１(c×Δt／Ｄ)・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・（１７）
ここで、Ｄは受信アンテナ間距離、ｃは光速である。
角度が分かれば、複数箇所で測定するか、受信アンテナの数を増やして測定する等の方法で、部分放電発生源の位置を特定し標定することができる。
位置が標定できれば、例えば、パソコン等の画面上に測定地域の配電・送変電設備等の配置図（地図）を表示させ、上記で算出した電磁波発生源の位置をスーパーインポーズすることも可能である。 Finally, from this time difference Δt, the angle Θ between the partial discharge source and the antenna can be calculated by the following equation.
Θ = sin −1 (c × Δt / D) (17) )
Here, D is the distance between the receiving antennas, and c is the speed of light.
If the angle is known, the position of the partial discharge generation source can be specified and determined by measuring at a plurality of locations or by increasing the number of receiving antennas.
If the location can be determined, for example, it is possible to display the layout (map) of the distribution / transmission / transformation equipment in the measurement area on the screen of a personal computer etc. and superimpose the location of the electromagnetic wave source calculated above. is there.

上述の理論式の妥当性を検証するためにシミュレーションを行った。図２はそのシミュレーション波形である。（ａ）はＢＰＦ２Ｂ（４００ＭＨｚ）通過後の波形であり，振幅一定の定常波を模擬している。ただし，ＢＰＦ通過後における実際の部分放電磁波形とは異なる。（ｂ）は（ａ）の波形と局部発振器３（矩形波３４０ＭＨｚ）とを高周波掛算器４Ｂで乗算した後の波形で、７４０ＭＨｚと６０ＭＨｚの周波数成分が含まれている。また、（ｃ）はＬＰＦ５Ｂ通過後の波形であり，６０ＭＨｚの周波数成分が含まれている。他の部分の波形についてもシミュレーションを行い前述の理論式の妥当性を確認した。   A simulation was performed to verify the validity of the above theoretical formula. FIG. 2 shows the simulation waveform. (A) is a waveform after passing through BPF2B (400 MHz), and simulates a stationary wave having a constant amplitude. However, it differs from the actual partial discharge waveform after passing through the BPF. (B) is a waveform obtained by multiplying the waveform of (a) and the local oscillator 3 (rectangular wave 340 MHz) by the high frequency multiplier 4B, and includes frequency components of 740 MHz and 60 MHz. Further, (c) is a waveform after passing through the LPF 5B, and includes a frequency component of 60 MHz. Simulations were also performed on the waveforms of other parts, and the validity of the above theoretical formula was confirmed.

以上のように、本実施の形態の発明によれば、第１の受信アンテナで受信した受信信号及び第２の受信アンテナで受信した受信信号から特定の周波数成分を抽出し、中間周波数をミキシングして直交検波を行ったのち、低周波成分を取り出しＡ／Ｄ変換して両受信信号の比から位相差を算出するようにしたので、部分放電電磁波信号の位相差を広い角度の範囲に亘り高精度で捉えることができる。また、高周波回路の演算にアナログ回路を用いることにより小型，軽量で安価な部分放電位置標定装置を得ることができる。   As described above, according to the present embodiment, the specific frequency component is extracted from the received signal received by the first receiving antenna and the received signal received by the second receiving antenna, and the intermediate frequency is mixed. After performing quadrature detection, the low-frequency component is extracted and A / D converted to calculate the phase difference from the ratio of both received signals. Therefore, the phase difference of the partial discharge electromagnetic wave signal is increased over a wide angle range. Can be captured with accuracy. Further, by using an analog circuit for the calculation of the high frequency circuit, a small, light and inexpensive partial discharge position locating device can be obtained.

実施の形態２．
図３はこの発明の実施の形態２による部分放電位置標定装置の信号処理ブロック図である。図に従って説明すると、先ず、実施の形態１と同様に、部分放電源からの信号を、所定の距離を空けて設けられた複数の受信アンテナ、本実施の形態では第１の受信アンテナ１Ａと第２の受信アンテナ１Ｂの２本のアンテナで受信し、それぞれバンドパスフィルタ（ＢＰＦ）２Ａ，２Ｂにより所定の周波数（例えば４００ＭＨｚ）の信号を抽出する。
第１の受信アンテナ１Ａで受信しＢＰＦ２Ａを通過した信号Ｓ１(t)は、デバイダ１１Ａで線路反射の影響をなくして３つに分割し、位相器１２Ａ、高周波掛算器１３Ａ及びログアンプ１４へ出力する。一方、第２のアンテナ１Ｂで受信してＢＰＦ２Ｂを通過した信号Ｓ２(t)は、デバイダ１１Ｂで２つに分割し、位相器１２Ｂと高周波掛算器１３Ｂへ出力する。 Embodiment 2. FIG.
FIG. 3 is a signal processing block diagram of a partial discharge position locating apparatus according to Embodiment 2 of the present invention. Referring to the figure, first, as in the first embodiment, a signal from a partial discharge power source is sent to a plurality of reception antennas provided at a predetermined distance, in this embodiment, the first reception antenna 1A and the first reception antenna. The signals are received by two antennas of the two receiving antennas 1B, and signals of a predetermined frequency (for example, 400 MHz) are extracted by band-pass filters (BPF) 2A and 2B, respectively.
The signal S 1 (t) received by the first receiving antenna 1A and passed through the BPF 2A is divided into three by the divider 11A without the influence of the line reflection, and sent to the phase shifter 12A, the high frequency multiplier 13A and the log amplifier 14. Output. On the other hand, the signal S 2 (t) received by the second antenna 1B and passed through the BPF 2B is divided into two by the divider 11B and output to the phase shifter 12B and the high frequency multiplier 13B.

次に、Ｓ１(t)を位相器１２Ａで所定時間（例えば、π／４）だけ遅延させて得た信号Ｖfs１(t)とＳ２(t)とを高周波掛算器１３Ｂで乗算し、その結果をローパスフィルタ（ＬＰＦ）１５Ｂで処理し、高周波成分を除去する。同様に、Ｓ２(t)を位相器１２Ｂで所定時間だけ遅延させて得た信号Ｖfs２(t)とＳ１(t)とを高周波掛算器１３Ａで乗算し、その結果をＬＰＦ１５Ａで処理し、高周波成分を除去する。次に、それぞれサンプルホールド１６Ａ，１６Ｂでサンプリングした後、Ａ／Ｄ変換器１７Ａ，１７Ｂによってデジタル信号に変換し、マイクロプロセッサ１８に入力する。マイクロプロセッサ１８では、２つの信号データを後述の理論式により演算して到達位相差を求める。なお、ＢＰＦ２Ａ，２Ｂには、実施の形態１と同様に、例えば、４００ＭＨｚの表面弾性波フィルタ（ＳＡＷ）を使用する。高周波回路部の演算にはアナログ回路を用いてアナログ処理を行っている。 Next, the signal Vfs 1 (t) obtained by delaying S 1 (t) by a predetermined time (for example, π / 4) by the phase shifter 12A and S 2 (t) are multiplied by the high frequency multiplier 13B, and The result is processed by a low pass filter (LPF) 15B to remove high frequency components. Similarly, the signal Vfs 2 (t) obtained by delaying S 2 (t) by a predetermined time by the phase shifter 12B and S 1 (t) are multiplied by the high frequency multiplier 13A, and the result is processed by the LPF 15A. Remove high frequency components. Next, after sampling by the sample hold 16A and 16B, respectively, it is converted into a digital signal by the A / D converters 17A and 17B and input to the microprocessor 18. The microprocessor 18 calculates the arrival phase difference by calculating two signal data according to a theoretical formula described later. For the BPFs 2A and 2B, for example, a 400 MHz surface acoustic wave filter (SAW) is used as in the first embodiment. Analog processing is performed using an analog circuit for the calculation of the high-frequency circuit section.

次に、数式を用いて、このブロック図の動作を説明する。
部分放電発生源からの単発パルス信号が第１の受信アンテナ１Ａ及び第２の受信アンテナ１Ｂで受信されたときのＢＰＦ２Ａ，２Ｂの出力をそれぞれＳ１(t)及びＳ２(t)とすると、実施の形態１と同様に、以下のように表すことができる。 Next, the operation of this block diagram will be described using mathematical expressions.
When the single pulse signals from the partial discharge source are received by the first receiving antenna 1A and the second receiving antenna 1B, the outputs of the BPFs 2A and 2B are S 1 (t) and S 2 (t), respectively. Similar to the first embodiment, it can be expressed as follows.

Ｓ１(t)＝Ｅ１(t)×sin(ωt)・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・（１）
Ｓ２(t)＝Ｅ２(t)×sin(ω(t−Δt))・・・・・・・・・・・・・・・・・・・・・・・・・・（２）
ここでＥ１(t)，Ｅ２(t)はエンベロープ関数、ωはＢＰＦの通過角周波数、Δtは電磁波信号の到達時間差である。 S 1 (t) = E 1 (t) × sin (ωt) (・ ・ ・ ・ ・) 1)
S 2 (t) = E 2 (t) × sin (ω (t−Δt)) (2)
Here, E 1 (t) and E 2 (t) are envelope functions, ω is the passing angular frequency of the BPF, and Δt is the arrival time difference of the electromagnetic wave signal.

ＢＰＦ２Ａ，２Ｂの出力Ｓ１(t)及びＳ２(t)を、デバイダ１１Ａ，１１Ｂにより分割して位相器１２Ａ，１２Ｂにより遅延させて得られる出力信号をそれぞれＶfs１(t)，Ｖfs２(t)とし、位相器１２Ａ及び１２Ｂの遅延時間をそれぞれＴｄ１及びＴｄ２とすると、
Ｖfs１(t)＝Ｅ１(t)×sin(ω(t−Ｔd１))・・・・・・・・・・・・・・・・・・・・・・・（１８）
Ｖfs２(t)＝Ｅ２(t)×sin(ω(t−Δt−Ｔd２))・・・・・・・・・・・・・・・・・・（１９）
となる。 Output signals obtained by dividing the outputs S 1 (t) and S 2 (t) of the BPFs 2A and 2B by the dividers 11A and 11B and delayed by the phase shifters 12A and 12B are Vfs 1 (t) and Vfs 2 ( t), and the delay times of the phase shifters 12A and 12B are Td 1 and Td 2 , respectively.
Vfs 1 (t) = E 1 (t) × sin (ω (t−Td 1 )) (18)
Vfs 2 (t) = E 2 (t) × sin (ω (t−Δt−Td 2 )) (19)
It becomes.

次に、Ｓ１(t)とＶfs２(t)、Ｓ２(t)とＶfs１(t)を高周波掛算器１３Ａ，１３Ｂにより乗算して得られる出力をそれぞれＶdc１２(t)及びＶdc２１(t)とおくと、
Ｖdc12(t)＝Ｓ１(t)×Ｖfs２(t)
＝Ｅ１(t)×Ｅ２(t)×sin(ωt)×sinω(t−Δt−Ｔd２)
＝(−1/2)×Ｅ１(t)×Ｅ２(t)×{cosω(２t−Δt−Ｔd２)
−cosω(Δt＋Ｔd２)}・・・・・・・・・・・・・・・・・・・・・・・・・・・・・（２０）
Ｖdc21(t)＝Ｓ２(t)×Ｖfs１(t)
＝Ｅ１(t)×Ｅ２(t)×sinω(t−Δt)×sinω(t−Ｔd１)
＝(−1/2)×Ｅ１(t)×Ｅ２(t)×{cosω(２t−Δt−Ｔd１)
−cosω(Δt＋Ｔd１)}・・・・・・・・・・・・・・・・・・・・・・・・・・・・・（２１） Next, outputs obtained by multiplying S 1 (t) and Vfs 2 (t), S 2 (t) and Vfs 1 (t) by the high frequency multipliers 13A and 13B are respectively Vdc 12 (t) and Vdc 21. (t)
Vdc 12 (t) = S 1 (t) × Vfs 2 (t)
= E 1 (t) × E 2 (t) × sin (ωt) × sin ω (t−Δt−Td 2 )
= (− 1/2) × E 1 (t) × E 2 (t) × {cosω (2t−Δt−Td 2 )
-Cosω (Δt + Td 2 )} ... (20)
Vdc 21 (t) = S 2 (t) × Vfs 1 (t)
= E 1 (t) × E 2 (t) × sin ω (t−Δt) × sin ω (t−Td 1 )
= (− 1/2) × E 1 (t) × E 2 (t) × {cosω (2t−Δt−Td 1 )
−cosω (Δt + Td 1 )} (21)

次に、ＬＰＦ１５Ａ及び１５Ｂを用いて、これらの信号の高周波成分を除去して低周波成分を取り出し、それぞれＶfo１２(t)，Ｖfo２１(t)とすると、
Ｖfo１２(t)＝(1/2)×Ｅ１(t)×Ｅ２(t)×cosω(Δt＋Ｔd２)・・・・・・・（２２）
Ｖfo２１(t)＝(1/2)×Ｅ１(t)×Ｅ２(t)×cosω(Δt＋Ｔd１)・・・・・・・（２３）
ここでＴd１＝Ｔd２=Ｔdとしてこれらの和及び差をとると
Ｖfo１２(t)＋Ｖfo２１(t)＝(1/2)×Ｅ１(t)×Ｅ２(t)×{cosω(Δt＋Ｔｄ)
＋cosω(Δt＋Ｔｄ)}
＝Ｅ１(t)×Ｅ２(t)×cos(ωΔt)×cos(ωＴd)・・・・（２４）
Ｖfo１２(t)−Ｖfo２１(t)＝(1/2)×Ｅ１(t)×Ｅ２(t)×{cosω(Δt＋Ｔｄ)
−cosω(Δt＋Ｔｄ)}
＝Ｅ１(t)×Ｅ２(t)×sin(ωΔt)×sin(ωＴd)・・・・（２５）
となる。 Next, using the LPFs 15A and 15B, the high frequency components of these signals are removed and the low frequency components are taken out to be Vfo 12 (t) and Vfo 21 (t), respectively.
Vfo 12 (t) = (1/2) × E 1 (t) × E 2 (t) × cosω (Δt + Td 2 ) (22)
Vfo 21 (t) = (1/2) × E 1 (t) × E 2 (t) × cosω (Δt + Td 1 ) (23)
Here, when Td 1 = Td 2 = Td and these sums and differences are taken, Vfo 12 (t) + Vfo 21 (t) = (1/2) × E 1 (t) × E 2 (t) × {cosω ( Δt + Td)
+ Cosω (Δt + Td)}
= E 1 (t) × E 2 (t) × cos (ωΔt) × cos (ωTd) (24)
Vfo 12 (t) −Vfo 21 (t) = (1/2) × E 1 (t) × E 2 (t) × {cosω (Δt + Td)
−cosω (Δt + Td)}
= E 1 (t) × E 2 (t) × sin (ωΔt) × sin (ωTd) (25)
It becomes.

上記の式２４を式２５で割り算して商を求めると、次のようになる。
{Ｖfo１２(t)−Ｖfo２１(t)}／{Ｖfo１２(t)＋Ｖfo２１(t)}
＝(1/2)×tan(ωΔt)×tan(ωＴd)・・・・・・（２６）
式２６をＫとおき、tan(ωΔt)を求めると、
tan(ωΔt)＝Ｋ／{tan(ωＴd)}・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・（２７）
となる。
ここで、例えば、ωＴd＝π／４になるようにＴdを選べば、
tan(ωΔt)＝Ｋ・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・（２８）
となり到達位相差Θ(=ωΔt)は、
Θ＝tan−１Ｋ・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・・（２９）
から求めることができる。
位相差が分かれば部分放電発生源の位置を標定できるので、実施の形態１と同様に、例えば、パソコン等の画面上に測定地域の配電・送変電設備等の配置図を表示させ、上記で算出した電磁波発生源の位置をスーパーインポーズすることも可能である。 Dividing the above equation 24 by equation 25 to find the quotient gives the following.
{Vfo 12 (t) −Vfo 21 (t)} / {Vfo 12 (t) + Vfo 21 (t)}
= (1/2) × tan (ωΔt) × tan (ωTd) (26)
When Equation 26 is K and tan (ωΔt) is calculated,
tan (ωΔt) = K / {tan (ωTd)} ... (27)
It becomes.
Here, for example, if Td is selected so that ωTd = π / 4,
tan (ωΔt) ＝ K ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・・ (28)
And the arrival phase difference Θ (= ωΔt) is
Θ = tan −1 K ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・ ・... (29)
Can be obtained from
If the phase difference is known, the position of the partial discharge source can be determined. Therefore, as in the first embodiment, for example, the layout diagram of the distribution / transmission / transformation equipment in the measurement area is displayed on the screen of a personal computer, etc. It is also possible to superimpose the calculated position of the electromagnetic wave generation source.

図３のブロック図のログアンプ１４、コンパレータ１９は部分放電源からの電磁波強度の時間変化に対応するためのものである。ＢＰＦ２Ａを通過後の波形Ｓ１(t)の強度が時間変化する場合、この信号をログアンプ１４を通過させた後、コンパレータ１９によりトリガ基準信号と比較し、トリガ基準信号以上の信号入力時のみサンプルホールド１６Ａ，１６Ｂ及びＡ／Ｄ変換器１７Ａ，１７Ｂにトリガ信号を出すことにより、データの取り込みを開始する。Ｖfo１２及びＶfo２１の波形をサンプルホールド１６Ａ，１６Ｂで直流化した後、Ａ／Ｄ変換器１７Ａ，１７Ｂで取り込み、マイクロプロセッサ１８で式２６及び式２９を計算し部分放電電磁波の到達時間差を求める。 The log amplifier 14 and the comparator 19 in the block diagram of FIG. 3 are for dealing with the time change of the electromagnetic wave intensity from the partial discharge source. When the intensity of the waveform S 1 (t) after passing through the BPF 2A changes with time, this signal is passed through the log amplifier 14, and then compared with the trigger reference signal by the comparator 19, and only when a signal greater than or equal to the trigger reference signal is input. Data acquisition is started by outputting a trigger signal to the sample-holds 16A and 16B and the A / D converters 17A and 17B. The waveforms of Vfo 12 and Vfo 21 are converted into direct current by the sample-holds 16A and 16B, then taken in by the A / D converters 17A and 17B, and the microprocessor 18 calculates the equations 26 and 29 to obtain the difference in arrival time of the partial discharge electromagnetic waves. .

なお、上記のような、トリガタイミング発生回路は、実施の形態１で説明した図１の回路にも、同様に適用することができる。   The trigger timing generation circuit as described above can be similarly applied to the circuit of FIG. 1 described in the first embodiment.

以上のように、本実施の形態の発明によれば、第１及び第２の受信アンテナで受信した受信信号から特定の周波数成分を抽出し、一方のアンテナ出力の原波形と他方のアンテナ出力の遅延させた波形とを互いに乗算したのち、低周波成分の信号を取り出してＡ／Ｄ変換し、両低周波成分の信号の和と差から両受信信号の位相差を算出するようにしたので、回路を対象に設計できるため温度ドリフトなどの誤差要素を除去でき、部分放電電磁波信号の位相差を高精度で検出できる。また、高周波回路の演算にアナログ回路を用いることにより小型、軽量で安価な部分放電位置標定装置を得ることができる。   As described above, according to the invention of this embodiment, a specific frequency component is extracted from the received signals received by the first and second receiving antennas, and the original waveform of one antenna output and the other antenna output are extracted. After multiplying the delayed waveform with each other, the low frequency component signal was taken out and A / D converted, and the phase difference between both received signals was calculated from the sum and difference of both low frequency component signals. Since the circuit can be designed, error elements such as temperature drift can be removed, and the phase difference of the partial discharge electromagnetic wave signal can be detected with high accuracy. Further, by using an analog circuit for the calculation of the high frequency circuit, a small, light and inexpensive partial discharge position locating device can be obtained.

また、実施の形態１，２のいずれにおいても、バンドパスフィルタを表面弾性波フィルタにより構成した場合は、単発パルス信号である部分放電信号から個体差（ばらつき）のない安定した出力波形を取り出すことができる。
また、受信アンテナの受信信号が所定の強度に達したときに、Ａ／Ｄ変換のためのトリガ信号を出力するようにしたので、受信信号のノイズや装置を構成するデバイスのばらつき要素を排除し、信号の取り出し精度を向上させることができる。
更にまた、算出した位相差から求められた部分放電源の位置を、例えば、パソコン等に取り込み、配電・送変電設備の配置（地図）を表示させた表示画面上にスーパーインポーズした場合は、発生源を視覚的に容易に認識することができる。 In any of the first and second embodiments, when the band-pass filter is constituted by a surface acoustic wave filter, a stable output waveform without individual difference (variation) is extracted from a partial discharge signal that is a single pulse signal. Can do.
In addition, since the trigger signal for A / D conversion is output when the received signal of the receiving antenna reaches a predetermined intensity, the noise of the received signal and the variation elements of the devices constituting the apparatus are eliminated. The accuracy of signal extraction can be improved.
Furthermore, when the position of the partial discharge power source obtained from the calculated phase difference is taken into a personal computer, for example, and superimposed on the display screen displaying the distribution (transmission / transformation equipment arrangement) (map), The source can be easily recognized visually.

なお、受信アンテナは２本の場合について説明したが、更に本数を増やし、例えば３本の受信アンテナで同時に測定すれば、受信アンテナを回転させたり、移動させる等の動作が不要になり、測定精度の向上と測定時間の短縮を図ることができる。   In addition, although the case where the number of receiving antennas is two has been described, if the number of antennas is further increased and, for example, measurement is simultaneously performed with three receiving antennas, an operation such as rotating or moving the receiving antenna becomes unnecessary, and measurement accuracy is improved. Can be improved and measurement time can be shortened.

電気設備における絶縁物劣化で生じる部分放電や、環境中での不要な電磁波源を離れた場所から簡単に検出できる部分放電源の位置標定に広く適用できる。   It can be widely applied to the location of a partial discharge that can be easily detected from a remote location, such as a partial discharge caused by an insulator deterioration in an electrical facility, or an unnecessary electromagnetic wave source in the environment.

この発明の実施の形態１による部分放電位置標定装置の信号処理ブロック図である。It is a signal processing block diagram of the partial discharge position locating device according to Embodiment 1 of the present invention. 図１のブロック図におけるシミュレーション波形図である。FIG. 2 is a simulation waveform diagram in the block diagram of FIG. 1. この発明の実施の形態２による部分放電位置標定装置の信号処理ブロック図である。It is a signal processing block diagram of the partial discharge position locating device by Embodiment 2 of this invention.

符号の説明Explanation of symbols

１Ａ 第１の受信アンテナ
１Ｂ 第２の受信アンテナ
２Ａ，２Ｂ バンドパスフィルタ
３ 局部発振器
４Ａ，４Ｂ，４Ｃ，１３Ａ，１３Ｂ 高周波掛算器
５Ａ，５Ｂ，５Ｃ，７Ａ，７Ｂ，１５Ａ，１５Ｂ ローパスフィルタ
６Ａ，６Ｂ 低周波掛算器
９，１７Ａ，１７Ｂ Ａ／Ｄ変換器
１０，１８ マイクロプロセッサ
１２Ａ，１２Ｂ 位相器
１９ コンパレータ。 DESCRIPTION OF SYMBOLS 1A 1st receiving antenna 1B 2nd receiving antenna 2A, 2B Band pass filter 3 Local oscillator 4A, 4B, 4C, 13A, 13B High frequency multiplier 5A, 5B, 5C, 7A, 7B, 15A, 15B Low pass filter 6A, 6B Low frequency multiplier 9, 17A, 17B A / D converter 10, 18 Microprocessor 12A, 12B Phase shifter 19 Comparator.

Claims (5)

配電・送変電設備から発生する部分放電による電磁波を少なくとも第１と第２の２つの受信アンテナで受信し、部分放電源と上記両受信アンテナ間との距離に応じた受信信号の位相差を求めて部分放電の位置を標定する部分放電位置標定装置において、
上記第１の受信アンテナで受信した受信信号及び上記第２の受信アンテナで受信した受信信号から、それぞれ特定の周波数成分の信号を抽出するバンドパスフィルタと、
位相角０とπ／２の２つの中間周波数を生成する局部発振器と、
上記バンドパスフィルタにより抽出した両信号に上記中間周波数をミキシングして直交検波を行ったのち、低周波成分の信号を取り出す手段と、
取り出した上記低周波成分の信号をＡ／Ｄ変換するＡ／Ｄ変換器と、
Ａ／Ｄ変換後の上記低周波成分の信号の除算処理を行って上記両受信信号の位相差を算出する演算手段とを有することを特徴とする部分放電位置標定装置。 The electromagnetic waves generated by the partial discharge generated from the power distribution / transmission / transformation equipment are received by at least the first and second receiving antennas, and the phase difference of the received signal is determined according to the distance between the partial discharge source and the two receiving antennas. In the partial discharge position locating device for locating the partial discharge position,
A band-pass filter that extracts a signal of a specific frequency component from the reception signal received by the first reception antenna and the reception signal received by the second reception antenna ;
A local oscillator that generates two intermediate frequencies of phase angle 0 and π / 2;
After performing quadrature detection by mixing the intermediate frequency to both signal extracted by the band-pass filter, and it means to eject the signal of the low-frequency component,
An A / D converter for A / D converting the extracted low-frequency component signal;
A partial discharge position locating apparatus comprising: an arithmetic means for performing a division process on the low frequency component signal after A / D conversion and calculating a phase difference between the two received signals. 配電・送変電設備から発生する部分放電による電磁波を少なくとも第１と第２の２つの受信アンテナで受信し、部分放電源と上記両受信アンテナ間との距離に応じた受信信号の位相差を求めて部分放電の位置を標定する部分放電位置標定装置において、
上記第１の受信アンテナで受信した受信信号及び上記第２の受信アンテナで受信した受信信号から、それぞれ特定の周波数成分の信号を抽出するバンドパスフィルタと、
上記第２の受信アンテナ側からの抽出信号を位相を遅延させて上記第１の受信アンテナ側からの抽出信号と乗算したのち低周波成分の信号を取り出す手段と、
上記第１の受信アンテナ側からの抽出信号を位相を遅延させて上記第２の受信アンテナ側からの抽出信号と乗算したのち低周波成分の信号を取り出す手段と、
取り出した上記両低周波成分の信号をＡ／Ｄ変換するＡ／Ｄ変換器と、
Ａ／Ｄ変換後の上記両低周波成分の信号の和と差を利用し除算処理を行って上記両受信信号の位相差を算出する演算手段とを有することを特徴とする部分放電位置標定装置。 The electromagnetic waves generated by the partial discharge generated from the power distribution / transmission / transformation equipment are received by at least the first and second receiving antennas, and the phase difference of the received signal is determined according to the distance between the partial discharge source and the two receiving antennas. In the partial discharge position locating device for locating the partial discharge position,
A band-pass filter that extracts a signal of a specific frequency component from the reception signal received by the first reception antenna and the reception signal received by the second reception antenna ;
Means to eject the signal of the low frequency component After multiplying the extracted signal from the extracted signal by delaying the phase of the first reception antenna side from the second receiving antenna side,
Means to eject the signal of the low frequency component After multiplying the extracted signal from the extracted signal by delaying the phase the second receiving antenna side from the first receiving antenna side,
An A / D converter for A / D converting the extracted signals of both low frequency components;
A partial discharge position locating device comprising: an arithmetic means for calculating a phase difference between the two received signals by performing a division process using the sum and difference of the signals of the two low frequency components after A / D conversion. . 請求項１又は請求項２記載の部分放電位置標定装置において、上記バンドパスフィルタは表面弾性波フィルタにより構成されていることを特徴とする部分放電位置標定装置。   3. The partial discharge position locating apparatus according to claim 1 or 2, wherein the bandpass filter is a surface acoustic wave filter. 請求項１〜請求項３のいずれか１項に記載の部分放電位置標定装置において、上記受信信号が所定の強度に達したときに、上記Ａ／Ｄ変換のためのトリガ信号を出力することを特徴とする部分放電位置標定装置。   The partial discharge position locating device according to any one of claims 1 to 3, wherein when the received signal reaches a predetermined intensity, a trigger signal for the A / D conversion is output. A partial discharge position locating device. 請求項１〜請求項４のいずれか１項に記載の部分放電位置標定装置において、算出した位相差から求められた部分放電源の位置を、配電・送変電設備の配置を表示させた表示画面上にスーパーインポーズする機能を備えたことを特徴とする部分放電位置標定装置。   The partial discharge position locating device according to any one of claims 1 to 4, wherein the position of the partial discharge source obtained from the calculated phase difference is displayed on the display screen of the distribution / transmission / transformation facilities. A partial discharge position locator having a function of superimposing on top.
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