JP2617325B2 - Insulation resistance measurement method - Google Patents
Insulation resistance measurement methodInfo
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- JP2617325B2 JP2617325B2 JP30298487A JP30298487A JP2617325B2 JP 2617325 B2 JP2617325 B2 JP 2617325B2 JP 30298487 A JP30298487 A JP 30298487A JP 30298487 A JP30298487 A JP 30298487A JP 2617325 B2 JP2617325 B2 JP 2617325B2
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- transformer
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Description
【発明の詳細な説明】 （産業上の利用分野） 本発明は活線状態で電路の絶縁抵抗を測定する方法に
関する。Description: TECHNICAL FIELD The present invention relates to a method for measuring the insulation resistance of an electric circuit in a live state.
（従来技術） 従来，電路や負荷設備の絶縁劣化による漏電等の早期
発見の為には第４図に示す如き絶縁抵抗測定方法を用い
るのが一般的であった。(Prior Art) Conventionally, for early detection of electric leakage or the like due to insulation deterioration of an electric circuit or a load facility, an insulation resistance measuring method as shown in FIG. 4 has been generally used.
即ち,Zなる負荷を有する受電トランスＴの接地線LEを
周波数1なる測定用低周波電圧を発振する発振器OSCに
接続されたトランスOTのコアに貫通させるか，又は電路
L1，L2を上記トランスOTのコアに貫通させる等して電路
にVsinω1ｔ（ω1＝２π1）の電圧を印加し，前記接
地線もしくは前記電路L1，L2を貫通せしめた変流器ZCT
により電路（負荷機器も含む）と大地間に存在する絶縁
抵抗R0及び対地静電容量C0を介して前記接地線に帰還す
る漏洩電流を検出し，これを増幅器AMPで増幅した後，
フィルタFILに加え，周波数1の成分のみを選択してフ
ィルタの出力を整流器DETに加えて得られる出力を用い
て電路の絶縁抵抗を一括して測定するものであった。こ
のような被測定回路は第５図に示す如き等価回路で表示
することができる。即ち第５図においてR0は被測定電路
ならびに負荷機器と大地間の総合絶縁抵抗，C0は同じく
対地静電容量であって,rは接地線LEの接地抵抗である。That is, whether to penetrate the receiving transformer T core of the transformer OT connected to an oscillator OSC which oscillates a low-frequency voltage measurement frequency 1 comprising a ground line L E of having Z becomes load, or electrical path
L 1, the L 2 by applying a voltage of V sin ω 1 t (ω 1 = 2π 1) in path and the like to penetrate into the core of the transformer OT, through the ground line or the path L 1, L 2 Current transformer ZCT
By detecting the leakage current returning to the ground line via the insulation resistance R 0 and the ground capacitance C 0 existing between the electric circuit (including the load device) and the ground, and amplifying the leakage current with the amplifier AMP,
In addition to the filter FIL, only the component of frequency 1 was selected, and the output of the filter was applied to the rectifier DET to measure the insulation resistance of the electrical circuit at once. Such a circuit to be measured can be represented by an equivalent circuit as shown in FIG. That R 0 is overall insulation resistance between electrical path and a load device and the ground to be measured in FIG. 5, C 0 is also a capacitance to ground, r is a ground resistance of a ground line L E.
同図において電路に印加した周波数1の低周波電圧
をVsinω1ｔとすれば，接地線LEに帰還する周波数1の
漏洩電流J1は J1＝（Asinω1ｔ＋Bcosω1ｔ）Ｖ …… ここで となる。一般に絶縁抵抗R0は接地抵抗ｒより十分大であ
るからR0≫ｒ又 （ω0C0ｒ）2≪１ …… であるならば前記，式は Ｂω1C0 …… となり，漏洩電流I1の整流値 を実測することによって絶縁抵抗R0を推定していた。If a low-frequency voltage having a frequency 1 applied to the path in the figure and V sin ω 1 t, the leakage current J 1 frequency 1 which returns to the ground line L E is J 1 = (A sin ω 1 t + B cos ω 1 t) V ... where Becomes In general, the insulation resistance R 0 is sufficiently larger than the ground resistance r. Therefore, if R 0 ≫r or (ω 0 C 0 r) 2 ≪1... Bω 1 C 0 ……, the rectified value of the leakage current I 1 Was actually measured to estimate the insulation resistance R0 .
しかしながら、，式から明らかなように対地静電
容量C0が大きいとき，又周波数1が高くなると正確な
絶縁抵抗の推定が困難となり又，接地抵抗ｒが高い時も
同様に推定が困難であった。However, as is clear from the equation, when the ground capacitance C 0 is large, or when the frequency 1 is high, it is difficult to accurately estimate the insulation resistance. Similarly, when the ground resistance r is high, the estimation is also difficult. Was.
（本発明の目的） 本発明は従来の問題を解決するものであって，測定用
低周波電圧の周波数が若干高くても，又対地静電容量が
大きくても，又更に接地抵抗が高くても正しく絶縁抵抗
の測定することのできる方法を提供することを目的とす
る。(Object of the present invention) The present invention is to solve the conventional problems. Even if the frequency of the low-frequency voltage for measurement is slightly high, the capacitance to ground is large, and the ground resistance is high, Another object of the present invention is to provide a method capable of correctly measuring the insulation resistance.
（発明の概要） この目的を達成するために本発明に於いては被測定電
路又はその接地線に信号注入トランスと変流器とを電磁
誘導或は直接に挿入接続する手段等により結合すること
によって該電路に，前記注入トランスを介して1，2
なる互いに異なる周波数の低周波信号を印加すると共
に，前記注入トランスに巻線した信号線より又は前記信
号発生源から直接に得た前記低周波信号を90度移相した
うえでこれを前記変流器に前記電路とは逆相となる如く
貫通せしめた接続線に印加し，前記変流器中の前記低周
波信号成分が最小となる如く前記接続線に流れる電流を
調整したときの該電流値と前記変流器出力中の当該低周
波信号値とから絶縁抵抗を算出するよう構成する。(Summary of the Invention) In order to achieve this object, in the present invention, the signal injection transformer and the current transformer are connected to the electric circuit to be measured or the ground line thereof by means of electromagnetic induction or direct insertion and connection. 1 , 2 via the injection transformer
And applying a low-frequency signal of a different frequency to each other and shifting the phase of the low-frequency signal obtained from the signal line wound on the injection transformer or directly from the signal source by 90 degrees. The current value when the current flowing through the connection line is adjusted so that the low-frequency signal component in the current transformer is minimized by applying the current to the connection line penetrating the transformer so that the phase is opposite to the electric circuit. And calculating the insulation resistance from the low-frequency signal value in the current transformer output.
（実施例） 以下，図示した実施例に基づいて本発明を詳細に説明
するが，その前に本発明の原理について少しく詳細に説
明する。(Embodiment) Hereinafter, the present invention will be described in detail based on the illustrated embodiment, but before that, the principle of the present invention will be described in some detail.
即ち，前記，式を得るためには式の関係が必要
であるが，式は対地静電容量C0，接地抵抗r,低周波電
圧の周波数の関係に一定の条件を設ているからこの条件
からはずれる場合は，式は成立しない。That is, in order to obtain the above equation, the relation of the equation is necessary. However, since the equation sets a certain condition in the relation of the ground capacitance C 0 , the ground resistance r, and the frequency of the low frequency voltage, this condition is set. If not, the expression does not hold.
そこで式の制限をなくせば，，式のA,Bは となる。If we eliminate the restriction of the equation, A and B of the equation become Becomes
そこで第３図に示す如く，電路L1，L2を周波数1，
2を夫々発振する発振器OSC1，OSC2の出力を印加した
トランスOTのコアに貫通せしめることにより電路にVsin
ω1t,Vsinω2ｔの電圧（それぞれＶとするが，必ずしも
等しい必要はない）を印加し，かつ変流器ZCTを電路に
貫通させる。トランスOTのコアに巻線（１ターンであっ
てもよい）することにより得た電圧を90度移相器Ｃに印
加し，周波数1，2の電圧の位相を90度シフトし,90
度移相器Ｃの出力電圧ecosω1ｔ＋ecosω2ｔを接続線Lp
を介して例えば抵抗Ｒで終端すると共に，接続線を変流
器に逆相となる如く貫通させる。変流器ZCTの出力を増
幅器AMPで増幅すれば，その出力に得られる周波数1の
電流成分J1′は となる。ここでi1′cosω1ｔは抵抗Ｒに流れる周波数
1の電流である。電流I1′の整流値が最小となるように
抵抗Ｒもしくは電圧ｅの大きさを調整する。Therefore, as shown in Figure 3, frequency 1 path L 1, L 2,
Oscillator OSC 1 to 2 respectively oscillation, the path by which allowed to penetrate into the core of the transformer OT was applied to the output of OSC 2 V sin
A voltage of ω 1 t, V sin ω 2 t (each of which is V, but not necessarily equal) is applied, and the current transformer ZCT is passed through the electric circuit. The voltage obtained by winding (may be one turn) the core of the transformer OT is applied to a 90-degree phase shifter C, and the phases of the voltages 1 and 2 are shifted by 90 degrees.
The output voltage e cos ω 1 t + e cos ω 2 t of the phase shifter C is connected to the connection line Lp
, For example, is terminated by a resistor R, and the connection line is passed through the current transformer in opposite phase. When the output of the current transformer ZCT is amplified by the amplifier AMP, the current component J 1 ′ of frequency 1 obtained at the output becomes Becomes Where i 1 ′ cos ω 1 t is the frequency flowing through the resistor R
1 current. The magnitude of the resistor R or the voltage e is adjusted so that the rectified value of the current I 1 ′ is minimized.
上記整流値が最小となる抵抗Ｒを流れる電流をi1とす
れば， 式から となり，このときの最小値I1は となる。一方増幅器AMP出力中に含まれる周波数2の成
分J2′は となる。ここでi2′cosω2ｔは抵抗Ｒに流れる周波数
2の電流であるI2′の整流値が最小となるように抵抗Ｒ
もしくは電圧ｅの大きさを調整する。上記整流値が最小
となる抵抗Ｒを流れる電流をi2とすれば， となり，このときの最小値I2は となる。If the current flowing through the resistor R to the rectifier value is minimized and i 1, the formula And the minimum value I 1 at this time is Becomes On the other hand, the component J 2 ′ of frequency 2 contained in the output of the amplifier AMP is Becomes Where i 2 ′ cos ω 2 t is the frequency flowing through the resistor R
In order to minimize the rectified value of the current I 2 ′, the resistance R
Alternatively, the magnitude of the voltage e is adjusted. Assuming that the current flowing through the resistor R at which the rectified value is minimum is i 2 , And the minimum value I 2 at this time is Becomes
次に上記測定結果から絶縁抵抗を算出する。 Next, the insulation resistance is calculated from the measurement result.
式から 式から ，式の比をとると よって対地静電容量C0は となる。一方，式から 又，式から ，式より 式のC0を式に代入し，整理すれば となる。From the formula From the formula , The ratio of the equations Therefore, the ground capacitance C 0 is Becomes On the other hand, from the equation Also, from the formula From the formula Substituting C 0 in the expression into the expression Becomes
したがって接続線に流れる電流を調整するに当たりも
し，抵抗Ｒの値を調整する場合，式において 即ちこの場合 となる。ここで，R1，R2はそれぞれの式のJ1′，式
のJ2′の整流値が最小となる抵抗Ｒの値である。Therefore, when adjusting the value of the resistor R when adjusting the current flowing through the connection line, That is, in this case Becomes Here, R 1 and R 2 are the values of the resistor R at which the rectified value of J 1 ′ of each equation and J 2 ′ of the equation becomes minimum.
一方，抵抗Ｒを固定値とし電圧ｅを調整する場合式
において， 即ちこの場合 となる。ここでe1，e2はそれぞれ式のJ1′の整流値が
最小となる電圧ｅの大きさである。On the other hand, when the resistance R is fixed and the voltage e is adjusted, That is, in this case Becomes Here, e 1 and e 2 are the magnitudes of the voltage e at which the rectified value of J 1 ′ in the equation becomes minimum.
上記の如く測定結果i1，i2，I1，I2ならびに を用いて式にて絶縁抵抗値ならびに印加した低周波電
圧の周波数1，2の影響を受けずに正確に測定しうる
ことが分る。As described above, the measurement results i 1 , i 2 , I 1 , I 2 and It can be understood that the measurement can be performed accurately without being affected by the insulation resistance value and the frequencies 1 and 2 of the applied low-frequency voltage by using the equation.
又上記説明では電路に印加した周波数1，2の低周
波の電圧が共に等しくＶとしたが，夫々がV1，V2のとき
は，式のＶをV1，，式のＶをV2におきかえるこ
とにより大地静電容量C0は となり，絶縁抵抗R0は 式で与えられる。ここでi1，i2の関係はもしくは式
で与えられる。V1，V2は一定であるから式の演算処理
することにより，絶縁抵抗R0を測定しうることになる。
本願発明は上述した測定原理に基づいて電路の絶縁抵抗
を測定するものであり、以下、上記測定原理を用いた実
施例について説明する。In the above description, the low-frequency voltages of frequencies 1 and 2 applied to the electric circuit are both equal to V. However, when they are V 1 and V 2 , respectively, V in the equation is V 1 , and V in the equation is V 2 By replacing it with the earth capacitance C 0 And the insulation resistance R 0 is Given by the formula. Here, the relationship between i 1 and i 2 is given by the following equation. Since V 1 and V 2 are constant, the insulation resistance R 0 can be measured by performing the arithmetic processing of the equation.
The present invention measures the insulation resistance of an electric circuit based on the above-described measurement principle. Hereinafter, an embodiment using the above measurement principle will be described.
第１図は，本発明に於いて用いる装置の一実施例を示
す図である。第３図，第４図と同一の記号は同一の意味
をもつものとする。FIG. 1 is a view showing one embodiment of an apparatus used in the present invention. The same symbols as those in FIGS. 3 and 4 have the same meaning.
同図に於いて，電路へ周波数1，2の互いに等しい
大きさＶの低周波電圧を印加するために，周波数1，
2を発振する発振器OSC1，OSC2をトランスOTのコアの
巻線と接続する。トランスOTには第４図では接続線LEが
貫通しているが，電路L1，L2を共に貫通させても同様に
電路に低周波電圧の印加が可能である。電路L1，L2を貫
通する変流器ZCTの出力を増幅器AMPで増幅し，その出力
を周波数1成分のみを選択するフィルタFIL1，周波数
2成分のみを選択するフィルタFIL2とに入力し，各フ
ィルタの出力は夫々整流器DET1，DET2とに入力する。ト
ランスOTのコアに貫通もしくは巻線して得る出力導線Lc
を90度移相器PSに印加し，周波数1，2の両成分の電
圧の位相が電路への印加電圧より90度移相するようにす
る。またトランスOTの印加電圧と導線Lcの電圧間の移相
推移がない場合は，導線LcをトランスOTの一次側，即ち
発振器出力から得てもよい。移相器PSの出力を増幅器PA
MPに印加し，その出力を例えば可変抵抗器Ｒで終端す
る。かくして抵抗Ｒと増幅器PAMPの出力を接続する接続
線Lpには電路への印加電圧より90度移相した電流が流れ
る。In the figure, to apply a low-frequency voltage having a frequency 1, 2 mutually equal magnitude V to path, Frequency 1,
An oscillator OSC 1, OSC 2 for oscillating the 2 connected to the winding core of the transformer OT. The trans OT Although the Figure 4 extending through the connection line L E, it is possible to apply the path L 1, the low-frequency voltage to similarly path be together passed through the L 2. The output of the current transformer ZCT passing through the electric circuits L 1 and L 2 is amplified by the amplifier AMP, and the output is filtered by the filter FIL 1 that selects only one frequency component,
2 only enter into the filter FIL 2 to select the components, the output of each filter is input to a respective rectifier DET 1, DET 2. Output conductor Lc obtained by penetrating or winding through the core of transformer OT
Is applied to the 90-degree phase shifter PS so that the phase of the voltage of both the frequency components 1 and 2 is shifted by 90 degrees from the voltage applied to the electric circuit. If there is no phase shift between the applied voltage of the transformer OT and the voltage of the conductor Lc, the conductor Lc may be obtained from the primary side of the transformer OT, that is, from the oscillator output. Output of phase shifter PS to amplifier PA
It is applied to MP and its output is terminated, for example, by a variable resistor R. Thus, a current flowing through the connection line Lp connecting the resistor R and the output of the amplifier PAMP is shifted by 90 degrees from the voltage applied to the electric circuit.
この接続線を変流器ZCTに貫通させ，変流器の一次電
流として印加する。このとき接続線に流れる電流が丁
度，電路の大地静電容量を介して流れる漏洩電流と逆相
となるごとく貫通させる。This connection line is passed through the current transformer ZCT and applied as the primary current of the current transformer. At this time, the current is passed through the connection line so that the current has a phase opposite to the leakage current flowing through the ground capacitance of the electric circuit.
先ず整流器DET1の出力OUT1が最小値を示すように抵抗
Ｒを調整し，そのときの抵抗Ｒの値をR1，またこのとき
の整流器の出力I1をコンデンサCMに記憶させるため，ス
イッチSWをオン→オフすることによりコンデンサCMに出
力I1が記憶される。次に整流器DET2の出力OUT2が最小値
を示すように抵抗Ｒを調整し，そのときの抵抗Ｒの値を
R2，またそのときの整流器DET2の出力をI2とする。Since the first output OUT 1 of the rectifier DET 1 adjusts the resistor R as the minimum value, R 1 the value of the resistor R at the time, also stores the output I 1 of the rectifier in this case the capacitor CM, the switch output I 1 is stored in the capacitor CM by turning on → off SW. Then the output OUT 2 of the rectifier DET 2 adjusts the resistor R as the minimum value, the value of the resistor R at the time
R 2 and the output of the rectifier DET 2 at that time are I 2 .
上記測定値R1，R2の比R2/R1を求めることにより式
のi1/i2を知ることができる。したがってR2/R1の値と定
数値 の積をとることにより が得られ，この値を係数回路CF1に設定する。コンデン
サCMの出力を引算器SUB1の一方の入力に加える。又係数
回路CF1の出力は となるから，これを引算器SUB1の他の一方の入力に印加
すると引算器SUB1の出力は となる。これは式の分子に相当する。又直流電圧Ｅを
引算器SUB2の一方の入力に印加する。次に直流電圧Ｅを
係数回路CF1と同一の値の設定された係数回路CF2に印加
すると係数回路CF2の出力は となる。これを引算器CUB2の他の一方の入力に印加する
と，引算器SUB2の出力は となる。By obtaining the ratio R 2 / R 1 of the measured values R 1 and R 2 , i 1 / i 2 of the equation can be known. Thus R 2 / R 1 value and the constant value By taking the product of Is obtained, this value is set to the coefficient circuits CF 1. The output of capacitor CM is applied to one input of subtractor SUB1. The output of the coefficient circuit CF 1 is Since the, which the output of the subtractor SUB 1 and applied to the other one input of the subtracter SUB 1 is Becomes This corresponds to the numerator of the formula. The application of a DC voltage E to one input of the subtractor SUB 2. Then the output of the coefficient circuit CF 2 is applied to the coefficient circuits CF 2 which are set in the same value as the coefficient circuit CF 1 a DC voltage E is Becomes When this is applied to the other input of the subtractor CUB 2 , the output of the subtractor SUB 2 becomes Becomes
引算器SUB1の出力を割算器DIVの一方の入力へ，又引
算器SUB2の出力を割算器DIVの他の入力端に印加する
と，割算器DIVの出力は となる。直流電圧Ｅは一定値であるから，上記出力は
式に相当し，絶縁抵抗R0を測定しうることになる。When the output of the subtracter SUB 1 is applied to one input of the divider DIV and the output of the subtracter SUB 2 is applied to the other input of the divider DIV, the output of the divider DIV becomes Becomes Since the DC voltage E is a constant value, the output corresponds to the equation, and the insulation resistance R0 can be measured.
第２図は本発明の他の実施例であり，接続線Lpに流れ
る電流を調整する別の方法を示している。即ち,90℃移
相器PSの出力を利得可変回路ATTに印加し，その出力を
増幅器PAMPに加え，増幅器PAMPの出力を固定抵抗Ｒで終
端とする。接続線Lpによる機能は第１図の場合と同様で
ある。可変利得回路を調整することにより増幅器PAMPの
出力電圧ｅが変わるため式の関係で接続線に電流i1，
i2を流すことができる。FIG. 2 shows another embodiment of the present invention, which shows another method for adjusting the current flowing through the connection line Lp. That is, the output of the 90 ° C. phase shifter PS is applied to the variable gain circuit ATT, the output is applied to the amplifier PAMP, and the output of the amplifier PAMP is terminated with a fixed resistor R. The function by the connection line Lp is the same as in the case of FIG. Since the output voltage e of the amplifier PAMP changes by adjusting the variable gain circuit, the current i 1 ,
i 2 can flow.
尚本発明の実施例においては，説明を簡単にするた
め，単相２線式電路の場合を示したが，本発明は何らこ
れに限定されるものでなく，一端接地型の単相３線式電
路,3相３線式電路の場合においても有効であることは説
明を要しないであろう。In the embodiment of the present invention, the case of a single-phase two-wire circuit is shown for simplicity of explanation, but the present invention is not limited to this, and the single-phase three-wire one-end grounded type is used. It will not be necessary to explain that the present invention is also effective in the case of a three-phase three-wire circuit.
上記説明では周波数1，2における，式のA,B
を得るために，印加電圧より90度移相したBVcosω1ｔ又
はBVcosω2ｔの電流成分を先ず打消すことにより得た
が，，式の電流J1′，J2′を夫々周波数1，2の
印加低周波電圧ならびに印加低周波電圧より90度移相し
た電圧で夫々同期検波することにより周波数1，2に
おけるA,Bを夫々測定可能であるから，これを用いて絶
縁抵抗R0を測定することも可能である。In the above explanation, A and B in the equations at frequencies 1 and 2
Was obtained by first canceling out the current component of BV cos ω 1 t or BV cos ω 2 t shifted by 90 degrees from the applied voltage, and the currents J 1 ′ and J 2 ′ in the equation were respectively obtained. A and B at frequencies 1 and 2 can be measured by synchronous detection with the applied low-frequency voltage at frequencies 1 and 2 and a voltage shifted by 90 degrees from the applied low-frequency voltage, respectively. It is also possible to measure R 0 .
（発明の効果） 本発明の方法によれば，接地抵抗が大きくても，正確
に絶縁抵抗の測定が可能である。また印加電圧の周波数
を高くすることが可能なため印加トランスOTの小型化が
可能となり可搬型の測定器を提供することができる。(Effect of the Invention) According to the method of the present invention, it is possible to accurately measure the insulation resistance even if the ground resistance is large. Further, since the frequency of the applied voltage can be increased, the size of the applied transformer OT can be reduced, and a portable measuring instrument can be provided.
第１図は本発明の一実施例を示す図，第２図は本発明の
他の実施例を示す図，第３図は本発明の説明に用いる
図，第４図は従来の測定方法を示す図，第５図は被測定
電路の等価回路を示す図である。 Ｔ……受電トランス，OSC1,2……発振器,OT……トラン
ス,ZCT……変流器,AMP,PAMP……増幅器，FIL1,2……フ
ィルタ，DET1,2……整流器，CF1,2……係数回路，SUB
1,2……引算器,DIV……割算器,ATT……可変利得回路。1 is a diagram showing one embodiment of the present invention, FIG. 2 is a diagram showing another embodiment of the present invention, FIG. 3 is a diagram used for explaining the present invention, and FIG. FIG. 5 is a diagram showing an equivalent circuit of the electric circuit to be measured. T: Power receiving transformer, OSC 1,2 ... Oscillator, OT ... Transformer, ZCT ... Current transformer, AMP, PAMP ... Amplifier, FIL 1,2 ... Filter, DET 1,2 ... Rectifier, CF 1,2 …… coefficient circuit, SUB
1,2 ... subtracter, DIV ... divider, ATT ... variable gain circuit.
Claims (4)
ンスと変流器とを結合し、該注入トランスを介して前記
電路に周波数f1とf2の低周波電圧を印加すると共に前記
変流器出力中の前記低周波電圧成分を検出することによ
って電路の絶縁抵抗を測定する方法において、 前記変流器には接続線を貫通せしめ、かつ該接続線を抵
抗で終端すると共に、該接続線に前記低周波信号電流を
90度移相しかつ前記電路に印加されている低周波信号と
は逆相になる如く電流を印加し、 前記変流器出力中の前記周波数f1の信号成分が最小とな
るときの前記変流器出力中の低周波電圧成分及び前記接
続線に流れる低周波信号電流値と、 前記変流器出力中の前記周波数f2の信号成分が最小とな
るときの前記変流器出力中の低周波電圧成分及び前記接
続線に流れる低周波信号電流値とから当該電路の絶縁抵
抗を測定したことを特徴とする絶縁抵抗測定方法。An injection transformer and a current transformer are coupled to a circuit to be measured or a ground wire of the circuit, and low-frequency voltages of frequencies f1 and f2 are applied to the circuit via the injection transformer, and the current transformer is connected to the circuit. A method for measuring the insulation resistance of an electric circuit by detecting the low-frequency voltage component in the output of a transformer, wherein the current transformer is passed through a connection line, and the connection line is terminated with a resistor, and the connection line The low-frequency signal current
A current is applied so that the phase is shifted by 90 degrees and the phase is opposite to the low-frequency signal applied to the electric circuit, and the current transformer when the signal component of the frequency f1 in the output of the current transformer is minimized. A low-frequency voltage component in the output of the current transformer and a low-frequency signal current value flowing in the connection line; and a low-frequency voltage in the output of the current transformer when the signal component of the frequency f2 in the output of the current transformer is minimized. A method for measuring insulation resistance, comprising measuring insulation resistance of the electric circuit from a component and a low-frequency signal current value flowing through the connection line.
ランスに貫通せしめた信号線によって得ると共に、該信
号線に流れる電流を90度移相器を介して導出したことを
特徴とする特許請求の範囲第１項記載の絶縁抵抗測定方
法。2. A patent wherein a low-frequency signal applied to the connection line is obtained by a signal line penetrating an injection transformer, and a current flowing through the signal line is derived through a 90-degree phase shifter. The method for measuring insulation resistance according to claim 1.
り、前記90度移相した電圧の大きさを調整したことを特
徴とする特許請求の範囲第１項又は第２項記載の絶縁抵
抗測定方法。3. The insulation resistance measurement according to claim 1, wherein the magnitude of the voltage shifted by 90 degrees is adjusted when adjusting the current flowing through the connection line. Method.
り、該接続線に直列に挿入した抵抗素子の値を調整した
ことを特徴とする特許請求の範囲第１項乃至３項記載の
絶縁抵抗測定方法。4. The insulation resistance according to claim 1, wherein a value of a resistance element inserted in series with the connection line is adjusted in adjusting a current flowing through the connection line. Measuring method.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP30298487A JP2617325B2 (en) | 1987-11-30 | 1987-11-30 | Insulation resistance measurement method |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP30298487A JP2617325B2 (en) | 1987-11-30 | 1987-11-30 | Insulation resistance measurement method |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPH01143972A JPH01143972A (en) | 1989-06-06 |
| JP2617325B2 true JP2617325B2 (en) | 1997-06-04 |
Family
ID=17915532
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP30298487A Expired - Lifetime JP2617325B2 (en) | 1987-11-30 | 1987-11-30 | Insulation resistance measurement method |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JP2617325B2 (en) |
-
1987
- 1987-11-30 JP JP30298487A patent/JP2617325B2/en not_active Expired - Lifetime
Also Published As
| Publication number | Publication date |
|---|---|
| JPH01143972A (en) | 1989-06-06 |
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