JP2010280235A - Noncontact current collector - Google Patents

Noncontact current collector Download PDF

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JP2010280235A
JP2010280235A JP2009132789A JP2009132789A JP2010280235A JP 2010280235 A JP2010280235 A JP 2010280235A JP 2009132789 A JP2009132789 A JP 2009132789A JP 2009132789 A JP2009132789 A JP 2009132789A JP 2010280235 A JP2010280235 A JP 2010280235A
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capacitor
coil
pwm converter
current collector
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Takeshi Shioda
剛 塩田
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Toyo Electric Manufacturing Ltd
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Abstract

<P>PROBLEM TO BE SOLVED: To solve such a problem that a device which connects a serial capacitor with second coil output, and controls a PWM converter in noncontact current collection for taking out electric power from alternating current power with large internal inductance with a power factor of 1, needs to install the serial capacitor at a traveling vehicle side, and thus traveling vehicle becomes heavy. <P>SOLUTION: In the noncontact current collector, the PWM converter changes alternating current output inducted by a second coil to direct current output. In the noncontact current collector, a first side capacitor is serially connected to an input side of a first coil, the PWM converter is controlled to become an equivalent series circuit of a resistor and the capacitor by PWM modulation, and a total serial reactance in which the first side capacitor, leakage inductance of the first coil, leakage inductance of a second coil, and an equivalent capacitor of the PWM converter are expressed at the second coil side is made zero. <P>COPYRIGHT: (C)2011,JPO&INPIT

Description

本発明は、電気車両に非接触によって集電する装置に関するものである。   The present invention relates to an apparatus for collecting electricity in a non-contact manner on an electric vehicle.

本出願人は先に、大きな内部インピーダンスを有する交流電源に接続されるＰＷＭコンバータの効率を上昇させ、スイッチング素子の小容量化を図るために、容量性インピーダンスを直列接続したＰＷＭコンバータについて提案している（特許文献１参照）。   The present applicant has previously proposed a PWM converter in which capacitive impedances are connected in series in order to increase the efficiency of a PWM converter connected to an AC power supply having a large internal impedance and to reduce the capacity of a switching element. (See Patent Document 1).

かかる先願技術を、図５の先願の非接触集電装置の主回路と電源系統を示す図、図４の先願の非接触集電装置の主回路と電源系統の単相等価回路を示す図、および図３の先願の非接触集電装置に用いるＰＷＭコンバータの制御回路図を参照して詳述する。
図５において、４はＰＷＭ変換器、５は負荷としての直流電源、７は交流電源、８は内部抵抗、９は内部インダクタンス、１０はＰＷＭコンバータ部、３３は直列コンデンサである。
図４において、１は１次コイル、２は２次コイルを表す。
図３において、２１は演算回路、２２はＦ/Ｖ変換回路、２３は容量指令発生器、２４は割算器、２５は比較器、２６は三角波発生器、２７はゲート発生回路を表す。 FIG. 5 shows the main circuit and power supply system of the non-contact current collector of the prior application shown in FIG. 5, and the single-phase equivalent circuit of the main circuit and power system of the non-contact current collector of FIG. This will be described in detail with reference to the drawings and the control circuit diagram of the PWM converter used in the non-contact current collector of the prior application of FIG.
In FIG. 5, 4 is a PWM converter, 5 is a DC power supply as a load, 7 is an AC power supply, 8 is an internal resistance, 9 is an internal inductance, 10 is a PWM converter unit, and 33 is a series capacitor.
In FIG. 4, 1 represents a primary coil and 2 represents a secondary coil.
In FIG. 3, 21 is an arithmetic circuit, 22 is an F / V conversion circuit, 23 is a capacity command generator, 24 is a divider, 25 is a comparator, 26 is a triangular wave generator, and 27 is a gate generation circuit.

図５において、３相の交流電源７に直列に内部抵抗８、内部インダクタンス９、および直列コンデンサ３３が直列に接続されて、さらに直列に接続されたＰＷＭ変換器４および負荷としての直流電源５において交流出力が直流出力に変換される。
先願技術は、リニア新幹線の補助電源を対象とする非接触集電であり、車両走行速度によって商用周波数程度からその数倍程度の周波数を有する交流電源７は、図４の１次コイル１に供給する電源を示す。図４と図５の交流電源７は、同一品を表す。２次コイル２、直列コンデンサ３３およびＰＷＭコンバータ部１０が図示しない走行車両上に搭載される。 In FIG. 5, an internal resistance 8, an internal inductance 9, and a series capacitor 33 are connected in series to a three-phase AC power supply 7, and further in a PWM converter 4 connected in series and a DC power supply 5 as a load. AC output is converted to DC output.
The prior application technology is a non-contact current collector for an auxiliary power source of a linear bullet train, and an AC power source 7 having a frequency that is about several times the commercial frequency depending on the vehicle traveling speed is connected to the primary coil 1 of FIG. Indicates the power to be supplied. 4 and 5 represent the same product. Secondary coil 2, series capacitor 33 and PWM converter unit 10 are mounted on a traveling vehicle (not shown).

図４において、１次コイル１は１次抵抗Ｒ１、１次漏れインダクタンスＬ１、主磁束によるインダクタンスＬ０１で表される。また、２次コイル２は２次抵抗Ｒ２、２次漏れインダクタンスＬ２、主磁束によるインダクタンスＬ０２で表される。この１次コイル１と２次コイル２の間には磁気結合による相互インダクタンスＭが存在し、Ｍ２＝Ｌ０１×Ｌ０２の関係がある。１次コイル１と２次コイル２は非接触で集電するために、磁気ギャップが大きくなり、相互インダクタンスＭは通常のトランスよりは小さく、両方のコイルの漏れインダクタンスは大きくなる。 In FIG. 4, the primary coil 1 is represented by a primary resistance R 1 , a primary leakage inductance L 1 , and an inductance L 01 due to the main magnetic flux. The secondary coil 2 is represented by a secondary resistance R 2 , a secondary leakage inductance L 2 , and an inductance L 02 due to the main magnetic flux. A mutual inductance M due to magnetic coupling exists between the primary coil 1 and the secondary coil 2, and there is a relationship of M 2 = L 01 × L 02 . Since the primary coil 1 and the secondary coil 2 collect current in a non-contact manner, the magnetic gap is increased, the mutual inductance M is smaller than that of a normal transformer, and the leakage inductance of both coils is increased.

１次コイル１と２次コイル２の巻数をＮ１,Ｎ２とすれば、巻数比ａはａ＝Ｎ１／Ｎ２で表される。従って、図４の相互インダクタンスＭを無視すると、図４と図５における抵抗とインダクタンスの関係は次のようになる。
図５の内部抵抗８の値ＲＳは１次抵抗Ｒ１を２次コイル２側に換算し、２次抵抗Ｒ２および巻数比ａを用いてＲＳ＝Ｒ１／ａ２＋Ｒ２で表される。同様に、内部インダクタンス９の値ＬＳは１次漏れインダクタンスＬ１を２次コイル２側に換算し、２次漏れインダクタンスＬ２および巻数比ａを用いてＬＳ＝Ｌ１／ａ２＋Ｌ２で表される。 If the number of turns of the primary coil 1 and the secondary coil 2 is N 1 and N 2 , the turn ratio a is expressed as a = N 1 / N 2 . Therefore, when the mutual inductance M in FIG. 4 is ignored, the relationship between the resistance and the inductance in FIGS. 4 and 5 is as follows.
The value R S of the internal resistance 8 in FIG. 5 is expressed as R S = R 1 / a 2 + R 2 by converting the primary resistance R 1 to the secondary coil 2 side and using the secondary resistance R 2 and the turn ratio a. Is done. Similarly, the value L S of the internal inductance 9 is obtained by converting the primary leakage inductance L 1 to the secondary coil 2 side, and using the secondary leakage inductance L 2 and the turn ratio a, L S = L 1 / a 2 + L 2 It is represented by

図４に示すように、従来技術においてＰＷＭ変換器４を力率＝１となるように制御した場合に、ＰＷＭコンバータ部１０は、等価容量Ｃｂと負荷抵抗Ｒｂの直列回路で表される。   As shown in FIG. 4, when the PWM converter 4 is controlled so that the power factor = 1 in the prior art, the PWM converter unit 10 is represented by a series circuit of an equivalent capacitor Cb and a load resistor Rb.

このように構成される先願の非接触集電主回路において、力率＝１でＰＷＭ変換器４を制御する方法を説明する。
交流電源７から力率＝１で電力を取り出すためには、１次コイル１と２次コイル２と負荷系統の全体のリアクタンスが零であることが必要である。すなわち、図６において内部インダクタンス９と直列コンデンサ３３およびＰＷＭコンバータ部１０の直列回路のリアクタンスが零である必要がある。
すなわち、直列コンデンサ３３およびＰＷＭコンバータ部１０の直列回路の合計容量をＣとすれば、内部インダクタンス９の値ＬＳとの間に式（１）の条件が成立すればリアクタンスが零となる。
しかしながら、容量ＣＣを有する直列コンデンサ３３が予め接続されているので、ＰＷＭコンバータ部１０の等価容量Ｃｂが式（２）を満たせば、式（１）を満たすことになる。
したがって、図５に示すＰＷＭ変換器４の３相入力端子電圧Ｅu ，Ｅv ，Ｅw が、次の式（３）〜（５）となれば、ＰＷＭコンバータ部１０は等価的に図４と等しくなる。ここで（１／ｊ）は位相を９０°遅らせる演算子である。 A method of controlling the PWM converter 4 with a power factor = 1 in the non-contact current collecting main circuit of the prior application configured as above will be described.
In order to extract electric power from the AC power source 7 with a power factor = 1, it is necessary that reactances of the primary coil 1, the secondary coil 2, and the load system as a whole are zero. That is, in FIG. 6, the reactance of the series circuit of the internal inductance 9, the series capacitor 33, and the PWM converter unit 10 needs to be zero.
That is, if the total capacity of the series circuit of the series capacitor 33 and the PWM converter unit 10 is C, the reactance becomes zero if the condition of the expression (1) is established between the value L S of the internal inductance 9.
However, since the series capacitor 33 having a capacitance C C is previously connected, the equivalent capacitance Cb of the PWM converter section 10 satisfies the equation (2) will satisfy the equation (1).
Therefore, if the three-phase input terminal voltages Eu, Ev, and Ew of the PWM converter 4 shown in FIG. 5 are expressed by the following equations (3) to (5), the PWM converter unit 10 is equivalently equivalent to FIG. . Here, (1 / j) is an operator that delays the phase by 90 °.

Figure 2010280235
Figure 2010280235

図３は、このための従来のＰＷＭコンバータの制御回路例を示すもので、２１は検出された電流Ｉu ，Ｉv から入力端子電圧の指令値Ｅu
*, Ｅv * ,Ｅw *を算出する演算回路、２４は割算器、２５は比較器、２７はゲート発生回路、２６は三角波発生器、２２はＦ／Ｖ変換器、２３は容量指令発生器である。演算回路２１は前記式（３）〜（５）の演算を行う。ここで、Ｉw
は（−Ｉu −Ｉv ）と等しいことと、Ｉu とＩv が１２０°位相差を持つことを利用して、入力端子電圧指令値Ｅu * ，Ｅv
* ，Ｅw * は次の式（６）〜（８）の如く算出される。 FIG. 3 shows an example of a control circuit of a conventional PWM converter for this purpose. Reference numeral 21 denotes an input terminal voltage command value Eu from detected currents Iu and Iv.
* , Ev * , Ew * calculation circuit, 24 is a divider, 25 is a comparator, 27 is a gate generation circuit, 26 is a triangular wave generator, 22 is an F / V converter, and 23 is a capacity command generator It is. The arithmetic circuit 21 performs the calculations of the above formulas (3) to (5). Where Iw
Is equal to (−Iu−Iv), and Iu and Iv have a 120 ° phase difference, and input terminal voltage command values Eu * and Ev.
* And Ew * are calculated as in the following equations (6) to (8).

Figure 2010280235
Ｆ/Ｖ変換器２２は電流検出値Ｉｕから２次コイルの電源角周波数ωを算出する。容量指令発生器２３は、電源内部インダクタンスＬｓとＦ/Ｖ変換器２２により算出されたωと外部容量Ｃｃの値より前記式（２）により等価容量Ｃｂの値を算出し、上記演算回路２１に出力する。
この外部容量Ｃｃの値は、例えば定格電源角周波数ωの時に式（１）で求められる値Ｃに近い値のコンデンサが接続される。
Figure 2010280235
 The F / V converter 22 calculates the power supply angular frequency ω of the secondary coil from the current detection value Iu. The capacity command generator 23 calculates the value of the equivalent capacity Cb from the power supply internal inductance Ls, the value of ω calculated by the F / V converter 22 and the value of the external capacity Cc by the above equation (2), and Output.
As the value of the external capacitance Cc, for example, a capacitor having a value close to the value C obtained by Expression (1) at the rated power supply angular frequency ω is connected.

このように構成されるＰＷＭコンバータ部１０は、例えばω＝２π×２５０Ｈz，Ｃ＝Ｃｃ＝１０００μＦ、Ｒ＝０.１Ωとすると、図４のＰＷＭコンバータ部１０の相インピーダンスの絶対値｜Ｚｂ｜、および直列コンデンサ３３とＰＷＭコンバータ部１０の合計相インピーダンス｜Ｚａ｜は、それぞれ｜Ｚｂ｜＝０．１Ω,
｜Ｚａ｜＝０．６４Ωとなり、｜Ｚａ｜／｜Ｚｂ｜＝６．４である。
すなわち、Ｃｃ ＝Ｃとすると、図４において直列コンデンサ３３とＰＷＭコンバータ部１０に印加される電圧Ｖｄは、ＰＷＭコンバータ部１０の負荷抵抗Ｒｂおよび等価容量Ｃｂの直列回路に印加される電圧の約６．４倍となる。逆に言うと、ＰＷＭコンバータ部１０の負荷抵抗Ｒｂおよび等価容量Ｃｂの直列回路に印加される電圧は小さくすることができる。 For example, when the PWM converter unit 10 configured as described above has ω = 2π × 250 Hz, C = Cc = 1000 μF, and R = 0.1Ω, the absolute value | Zb | of the phase impedance of the PWM converter unit 10 in FIG. The total phase impedance | Za | of the series capacitor 33 and the PWM converter unit 10 is | Zb | = 0.1Ω,
| Za | = 0.64Ω, and | Za | / | Zb | = 6.4.
That is, when Cc = C, the voltage Vd applied to the series capacitor 33 and the PWM converter unit 10 in FIG. 4 is about 6 of the voltage applied to the series circuit of the load resistor Rb and the equivalent capacitance Cb of the PWM converter unit 10. .4 times. In other words, the voltage applied to the series circuit of the load resistor Rb and the equivalent capacitor Cb of the PWM converter unit 10 can be reduced.

特開２０００−８３３７９号公報JP 2000-83379 A

上記した交流電源７を商用周波数程度からその数倍程度の周波数を有する３相交流電源７で構成し、ＰＷＭ変換器４に直列コンデンサ３３を直列に接続する方法では、内部インダクタンスＬＳの大きい交流電源から力率＝１で電力を取り出すことができる。しかし、直列コンデンサ３３を走行車両側に設置しなければならず、走行車両が重くなるという問題がある。
本発明は上記事情に鑑みなされたものであって、その目的とするところは、軽い走行車両を構成できる非接触集電装置を提供することである。 In the method in which the AC power source 7 described above is constituted by a three-phase AC power source 7 having a frequency of about several times the commercial frequency, and a series capacitor 33 is connected in series to the PWM converter 4, an AC having a large internal inductance L S is obtained. Electric power can be extracted from the power source at a power factor = 1. However, there is a problem that the series capacitor 33 must be installed on the traveling vehicle side and the traveling vehicle becomes heavy.
The present invention has been made in view of the above circumstances, and an object of the present invention is to provide a non-contact current collector capable of constituting a light traveling vehicle.

請求項１の発明によれば、地上の１次コイルから走行車両の２次コイルに誘導される交流出力をＰＷＭコンバータにより直流出力にする非接触集電装置において、該１次コイルの入力側に１次側コンデンサを直列に接続し、該ＰＷＭコンバータをＰＷＭ変調により等価的に抵抗とコンデンサの直列回路となるように制御し、該１次側コンデンサと前記１次コイルの漏れインダクタンスと該２次コイルの漏れインダクタンスと前記ＰＷＭコンバータの等価容量を全て２次コイル側で表した合計直列リアクタンスが零となることを特徴とする非接触集電装置である。   According to the first aspect of the present invention, in the non-contact current collector that converts the AC output induced from the primary coil on the ground to the secondary coil of the traveling vehicle to the DC output by the PWM converter, on the input side of the primary coil A primary side capacitor is connected in series, and the PWM converter is controlled to be equivalently a series circuit of a resistor and a capacitor by PWM modulation, and the leakage inductance of the primary side capacitor and the primary coil and the secondary side are controlled. The non-contact current collector is characterized in that the total series reactance in which the leakage inductance of the coil and the equivalent capacity of the PWM converter are all expressed on the secondary coil side is zero.

非接触集電装置において、電源系統側の１次コイルに直列コンデンサを接続して、走行車両側の２次コイルに接続されるＰＷＭコンバータにより力率＝１を達成することができるので、ＰＷＭコンバータを小さく構成できるので走行車両を軽くすることができる。   In the non-contact current collector, the power factor = 1 can be achieved by connecting a series capacitor to the primary coil on the power system side and the PWM converter connected to the secondary coil on the traveling vehicle side. Since the vehicle can be made small, the traveling vehicle can be lightened.

本発明の実施例に係る非接触集電装置の主回路構成を説明するための図である。It is a figure for demonstrating the main circuit structure of the non-contact collector which concerns on the Example of this invention. 本発明の実施例に係る非接触集電装置の単相等価回路で表した図である。It is the figure represented with the single phase equivalent circuit of the non-contact collector which concerns on the Example of this invention. 本発明の実施例および先願に係る非接触集電装置に用いるＰＷＭコンバータの制御回路を説明した図である。It is the figure explaining the control circuit of the PWM converter used for the non-contact current collecting apparatus which concerns on the Example of this invention, and a prior application. 従来の実施例に係る２次コイルに直列コンデンサを接続した非接触集電装置を単相等価回路で表した図である。It is the figure showing the non-contact current collecting device which connected the series capacitor to the secondary coil concerning the conventional example with the single phase equivalent circuit. 従来の実施例に係る２次コイルに直列コンデンサを接続した非接触集電装置の主回路構成を説明するための図である。It is a figure for demonstrating the main circuit structure of the non-contact collector which connected the series capacitor to the secondary coil which concerns on the conventional Example.

地上側１次コイルにコンデンサを直列接続して、２次コイル側のＰＭＷコンバータにより力率＝１を達成する。   A capacitor is connected in series to the ground side primary coil, and a power factor = 1 is achieved by the PMW converter on the secondary coil side.

以下、本発明の実施の形態について、詳細に説明する。
図1は、本発明が適用された電源系統に直列にコンデンサを接続した非接触集電装置の主回路結線図である。
図２は、電源系統に直列にコンデンサを接続した非接触集電装置の単相等価回路である。
３４は電源系統に接続した１次側コンデンサである。
同図において、図５、図４と同一番号は類似した同一構成部品を表す。
以下、図１および図２について、図３を参照して説明する。 Hereinafter, embodiments of the present invention will be described in detail.
FIG. 1 is a main circuit connection diagram of a non-contact current collector in which a capacitor is connected in series to a power supply system to which the present invention is applied.
FIG. 2 is a single-phase equivalent circuit of a non-contact current collector in which a capacitor is connected in series with the power supply system.
Reference numeral 34 denotes a primary side capacitor connected to the power supply system.
In the figure, the same reference numerals as those in FIGS. 5 and 4 denote similar components.
Hereinafter, FIG. 1 and FIG. 2 will be described with reference to FIG.

図２において、１次コイル１および２次コイル２の抵抗およびインダクタンスの関係は、図４と同様に表される。ここで、１次コイル１と２次コイル２の巻数をＮ１,Ｎ２とすれば、巻数比ａはａ＝Ｎ１／Ｎ２で表される。従って、図２の相互インダクタンスＭを無視すると、図１と図２における抵抗とインダクタンスの関係は、ＲＳ＝Ｒ１／ａ２＋Ｒ２およびＬＳ＝Ｌ１／ａ２＋Ｌ２で表される。
また、図２の交流電源７に接続される１次側コンデンサ３４の容量ＣＣ１は、２次コイル２側に換算すると、ＣＣ＝ａ２×ＣＣ１となる。従って、実際に接続される１次側コンデンサ３４の容量ＣＣ１は巻数比ａを用いてＣＣ１＝ＣＣ／ａ２から求められる。 In FIG. 2, the relationship between the resistance and inductance of the primary coil 1 and the secondary coil 2 is expressed in the same manner as in FIG. Here, if the number of turns of the primary coil 1 and the secondary coil 2 is N 1 and N 2 , the turn ratio a is expressed as a = N 1 / N 2 . Therefore, if the mutual inductance M in FIG. 2 is ignored, the relationship between the resistance and the inductance in FIGS. 1 and 2 is expressed as R S = R 1 / a 2 + R 2 and L S = L 1 / a 2 + L 2. .
Further, the capacitance C C1 of the primary side capacitor 34 connected to the AC power source 7 in FIG. 2 is C C = a 2 × C C1 when converted to the secondary coil 2 side. Therefore, the capacitance C C1 of the primary capacitor 34 that is actually connected is obtained from C C1 = C C / a 2 using the turns ratio a.

従って、非接触集電装置に用いられるＰＷＭコンバータ４の容量指令発生器２３は、１次側コンデンサ３４の容量ＣＣ１と巻数比ａを用いてＣＣ＝ａ２×ＣＣ１を求め、式（２）に基づいてＣｂを演算する。このＣｂを用いて、ＰＷＭコンバータ４は図３の制御回路により図５と同様に制御される。その結果、１次側コンデンサ３４と１次コイルの漏れインダクタンスＬ１と前記２次コイルの漏れインダクタンスＬ２と前記ＰＷＭコンバータの等価容量Ｃｂを全て２次コイル側で表した合計直列リアクタンスが零となり、力率＝１で運転される。 Therefore, the capacity command generator 23 of the PWM converter 4 used in the non-contact current collector obtains C C = a 2 × C C1 using the capacity C C1 of the primary capacitor 34 and the turn ratio a, and the formula ( Cb is calculated based on 2). Using this Cb, the PWM converter 4 is controlled in the same manner as in FIG. 5 by the control circuit in FIG. As a result, the total series reactance becomes zero representing the leakage inductance L 2 and the equivalent capacitance Cb of the PWM converter of the primary side capacitor 34 and the leakage inductance L 1 of the primary coil and the secondary coil at all secondary coil , Operated with power factor = 1.

ここで、電源角周波数ωの値によって、式（２）の分母が零になることがないように、分母の演算結果にヒステリシスを設ける必要がある。また、式（２）の演算結果が負になることがあるが、そのような場合には等価容量Ｃｂはインダクタンスとして動作し、結果として力率＝１は保たれる。   Here, it is necessary to provide hysteresis in the calculation result of the denominator so that the denominator of Expression (2) does not become zero depending on the value of the power supply angular frequency ω. In addition, the calculation result of Expression (2) may be negative. In such a case, the equivalent capacitance Cb operates as an inductance, and as a result, power factor = 1 is maintained.

非接触集電装置は、供給側のコイルと集電側のコイルの間隔が大きいために、コイルの漏れインダクタンスが大きくなり、力率が悪いために大きな出力が取れないという問題があった。本発明は、非接触集電装置の１次コイル側に１次側コンデンサを接続し、２次コイル側にＰＷＭコンバータを接続したものである。
この１次側コンデンサとＰＷＭコンバータは、１次コイルおよび２次コイルの漏れインダクタンスによる誘導性リアクタンスを打ち消すように、容量性リアクタンスとして動作する。
予め接続する１次側コンデンサのために、ＰＷＭコンバータが発生するリアクタンス分の電圧ドロップは少なくなり、ＰＷＭコンバータの容量を小さくできる。従って、走行車両の集電装置を小さくできるので、走行車両を軽くできるので産業利用上非常に有用である。 The non-contact current collector has a problem that since the gap between the supply-side coil and the current-collection coil is large, the leakage inductance of the coil is large, and the power factor is low, so that a large output cannot be obtained. In the present invention, a primary capacitor is connected to the primary coil side of the non-contact current collector, and a PWM converter is connected to the secondary coil side.
The primary capacitor and the PWM converter operate as capacitive reactance so as to cancel out inductive reactance due to leakage inductance of the primary coil and the secondary coil.
Because of the primary capacitor connected in advance, the voltage drop corresponding to the reactance generated by the PWM converter is reduced, and the capacitance of the PWM converter can be reduced. Therefore, since the current collector of the traveling vehicle can be reduced, the traveling vehicle can be lightened, which is very useful for industrial use.

１ １次コイル
２ ２次コイル
４ ＰＷＭ変換器
５ 直流電源
７ 交流電源
８ 内部抵抗
９ 内部インダクタンス
１０ ＰＷＭコンバータ部
２１ 演算回路
２２ Ｆ/Ｖ変換器
２３ 容量指令発生器
２４ 割算器
２５ 比較器
２６ 三角波発生器
２７ ゲート発生回路
３３ 直列コンデンサ
３４ １次側コンデンサ DESCRIPTION OF SYMBOLS 1 Primary coil 2 Secondary coil 4 PWM converter 5 DC power supply 7 AC power supply 8 Internal resistance 9 Internal inductance 10 PWM converter part 21 Calculation circuit 22 F / V converter 23 Capacity command generator 24 Divider 25 Comparator 26 Triangular wave generator 27 Gate generation circuit 33 Series capacitor 34 Primary side capacitor

Claims (1)

地上の１次コイルから走行車両の２次コイルに誘導される交流出力をＰＷＭコンバータにより直流出力にする非接触集電装置において、該１次コイルの入力側に１次側コンデンサを直列に接続し、該ＰＷＭコンバータをＰＷＭ変調により等価的に抵抗とコンデンサの直列回路となるように制御し、該１次側コンデンサと前記１次コイルの漏れインダクタンスと該２次コイルの漏れインダクタンスと前記ＰＷＭコンバータの等価容量を全て２次コイル側で表した合計直列リアクタンスが零となることを特徴とする非接触集電装置。 In a non-contact current collector that converts an AC output induced from a primary coil on the ground to a secondary coil of a traveling vehicle into a DC output by a PWM converter, a primary side capacitor is connected in series to the input side of the primary coil. The PWM converter is controlled by PWM modulation to be equivalently a series circuit of a resistor and a capacitor, and the primary capacitor, the leakage inductance of the primary coil, the leakage inductance of the secondary coil, and the PWM converter A non-contact current collector characterized in that the total series reactance in which all equivalent capacitances are expressed on the secondary coil side is zero.
JP2009132789A 2009-06-02 2009-06-02 Noncontact current collector Pending JP2010280235A (en)

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Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2012143106A (en) * 2011-01-05 2012-07-26 Showa Aircraft Ind Co Ltd Non-contact power feeding device of magnetic field resonance type
JP2012253924A (en) * 2011-06-03 2012-12-20 Toyo Electric Mfg Co Ltd Direct current output circuit of generator for distributed power source
JP2016025677A (en) * 2014-07-16 2016-02-08 学校法人東京理科大学 Power transmission device and electric apparatus

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2012143106A (en) * 2011-01-05 2012-07-26 Showa Aircraft Ind Co Ltd Non-contact power feeding device of magnetic field resonance type
JP2012253924A (en) * 2011-06-03 2012-12-20 Toyo Electric Mfg Co Ltd Direct current output circuit of generator for distributed power source
JP2016025677A (en) * 2014-07-16 2016-02-08 学校法人東京理科大学 Power transmission device and electric apparatus

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