JP2002353813A - Digital communication unit and communication unit for distribution line carrier using it - Google Patents
Digital communication unit and communication unit for distribution line carrier using itInfo
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- JP2002353813A JP2002353813A JP2001153641A JP2001153641A JP2002353813A JP 2002353813 A JP2002353813 A JP 2002353813A JP 2001153641 A JP2001153641 A JP 2001153641A JP 2001153641 A JP2001153641 A JP 2001153641A JP 2002353813 A JP2002353813 A JP 2002353813A
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- signal
- amplification
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- control circuit
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Abstract
Description
【０００１】[0001]
【発明の属する技術分野】この発明は、特に、配電線を
伝送路とし、複数の周波数の配電線搬送信号を送受信す
る通信装置に関する。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a communication apparatus for transmitting and receiving distribution line carrier signals of a plurality of frequencies, using a distribution line as a transmission line.
【０００２】[0002]
【従来の技術】従来のディジタル通信装置として、広帯
域ディジタル受信機（以下ディジタル受信機という）が
あり、例えば特開２０００−２３６２７６号公報に示さ
れている。図８は、上記公報に示された従来のディジタ
ル受信機の構成を示す構成概要図である。なお、ここで
言う広帯域ディジタル受信機とは、受信した広帯域信号
を高周波信号のままＲＦ帯あるいはＩＦ帯においてＡ／
Ｄ変換し、チャネル分離以降の処理をディジタル回路で
行う受信機である。このようなデイジタル受信機を開示
した公報としては特願昭６１−５０４７９１号公報“デ
ィジタル無線周波受信機”があるが、既によく知られて
いると考えられるので、同公報の説明は省略する。2. Description of the Related Art As a conventional digital communication apparatus, there is a wideband digital receiver (hereinafter referred to as a digital receiver), which is disclosed in, for example, Japanese Patent Application Laid-Open No. 2000-236276. FIG. 8 is a schematic diagram showing the configuration of a conventional digital receiver disclosed in the above publication. Note that the broadband digital receiver referred to here means that a received wideband signal is converted to an A / A signal in an RF band or an IF band as a high frequency signal.
It is a receiver that performs D-conversion and processes after channel separation by digital circuits. Japanese Patent Application No. 61-504791 entitled "Digital Radio Frequency Receiver" discloses such a digital receiver. However, since it is considered that the digital receiver is well known, the description of the publication is omitted.
【０００３】図８に示すように、ディジタル受信機は、
無線電波（ＲＦ信号）を受信するアンテナ３１と、帯域
制限を行うＲＦバンドパスフィルタ（ＲＦＢＰＦ）３２
と、前記ＲＦ信号をＩＦ信号に周波数変換するローカル
信号発振器３４とミキサ３３、このＩＦ信号に帯域制限
を施すためのとＩＦバンドパスフィルタ（ＩＦＢＰＦ）
３６と、ＩＦ信号増幅用のＡＧＣアンプ（増幅率可制御
アンプ）３７と、増幅されたＩＦ信号（アナログ受信信
号）をディジタルに変換するＡ／Ｄ変換器３８と、所望
のチャネル帯域を分離するチャネル分離器（ＣＨ分離）
３９と、該チャネル分離器３９の出力信号からデータ信
号を復調する復調器４１とで構成される。[0003] As shown in FIG. 8, a digital receiver comprises:
An antenna 31 for receiving a radio wave (RF signal), and an RF bandpass filter (RFBPF) 32 for band limitation
A local signal oscillator 34 and a mixer 33 for frequency-converting the RF signal into an IF signal, and an IF band-pass filter (IFBPF) for band-limiting the IF signal.
36, an AGC amplifier (amplifier controllable amplifier) 37 for amplifying an IF signal, an A / D converter 38 for converting the amplified IF signal (analog received signal) into a digital signal, and separating a desired channel band. Channel separator (CH separation)
39, and a demodulator 41 for demodulating a data signal from the output signal of the channel separator 39.
【０００４】図８において、アンテナ３１で受信した受
信信号は、ＲＦバンドパスフィルタ３２に入力されて必
要な帯域制限を受ける。ここで言う必要な帯域とは、本
広帯域ディジタル受信機が受信可能なバンド幅であり、
通常使用されるシステムのサービスバンド帯域に一致す
るよう設定される。例えば、ＰＤＣ８００ＭＨｚ方式携
帯電話システムでは１６ＭＨｚの帯域幅となる。ＲＦバ
ンドパスフィルタ３２のこの通過帯域幅をＷとする。[0004] In FIG. 8, a received signal received by an antenna 31 is input to an RF bandpass filter 32 and subjected to necessary band limitation. The necessary band here is a bandwidth that the wideband digital receiver can receive,
It is set to match the service band of the system normally used. For example, a PDC 800 MHz mobile phone system has a bandwidth of 16 MHz. This pass band width of the RF band-pass filter 32 is defined as W.
【０００５】次に、ＲＦバンドパスフィルタ３２で帯域
制限を受けた受信信号は、ミキサ３３、ローカル発振器
３４及びＩＦバンドパスフィルタ３５により周波数変換
及び帯域制限を施されてＩＦ信号となる。ＩＦバンドパ
スフィルタ３５の帯域幅即ちＩＦ信号の帯域幅は、ＲＦ
バンドパスフィルタ３２のそれと同じＷである。次に、
ＩＦ信号はＡＧＣアンプ３７で増幅された後、Ａ／Ｄ変
換器３８で広帯域ディジタル信号に変換される。ＡＧＣ
アンプ３７の増幅率は、Ａ／Ｄ変換器３８への入力信号
がＡ／Ｄ変換器３８の最大許容入力レベルを越えない範
囲で最大になるようにフィードバック制御される。[0005] Next, the received signal subjected to the band limitation by the RF bandpass filter 32 is subjected to frequency conversion and band limitation by the mixer 33, the local oscillator 34 and the IF bandpass filter 35 to become an IF signal. The bandwidth of the IF bandpass filter 35, that is, the bandwidth of the IF signal is RF
W is the same as that of the bandpass filter 32. next,
The IF signal is amplified by an AGC amplifier 37 and then converted to a wideband digital signal by an A / D converter 38. AGC
The amplification factor of the amplifier 37 is feedback-controlled so that the input signal to the A / D converter 38 becomes maximum within a range not exceeding the maximum allowable input level of the A / D converter 38.
【０００６】第一の課題として、この構成では、例えば
Ａ／Ｄ変換器３８の入力信号にレベルの高いノイズが重
畳されていると、ＡＧＣアンプの増幅率が低下させら
れ、Ａ／Ｄ変換器３８への入力信号レベルが減少し、復
調器４１において復調されたデータ信号のうち伝送に使
用された周波数信号成分のレベルがこれらの信号処理回
路のダイナミツクレンジに対して相対的に小さくなり、
送信信号の正常な再生が困難になる。Ａ／Ｄ変換器３８
から出力された広帯域ディジタル信号はチャネル分離器
３９に入力され、所望の狭帯域（チャネル帯域）ディジ
タル信号に分離される。ここで言う狭帯域（チャネル帯
域）とは、例えばＰＤＣ８００ＭＨｚ方式携帯電話シス
テムでは２５ｋＨｚである。チャネル分離された狭帯域
（チャネル帯域）ディジタル信号は、復調器４１におい
てシステムの変調方式（ＰＤＣ８００ＭＨｚ方式携帯電
話ではπ／４ＱＰＳＫ）に応じて復調されデータ信号と
なる。As a first problem, in this configuration, for example, when high-level noise is superimposed on the input signal of the A / D converter 38, the amplification factor of the AGC amplifier is reduced, and the A / D converter 38, the level of the frequency signal component used for transmission among the data signals demodulated by the demodulator 41 becomes relatively small with respect to the dynamic range of these signal processing circuits.
Normal reproduction of the transmission signal becomes difficult. A / D converter 38
Is input to the channel separator 39 and is separated into a desired narrow-band (channel band) digital signal. The narrow band (channel band) referred to here is, for example, 25 kHz in a PDC 800 MHz system portable telephone system. The narrow-band (channel band) digital signal separated from the channel is demodulated in the demodulator 41 in accordance with the system modulation system (π / 4QPSK in a PDC 800 MHz mobile phone) to become a data signal.
【０００７】また、近年、上記のようなデイジタル通信
装置がコスト削減などの理由から既存の電力線（配電
線）を利用して通信を行なう電力線モデムなどの技術と
して利用されはじめている。この技術に関しては例えば
特開２００１−１１１５１８号公報に開示されたものが
ある。この公報では、様々な家電機器の電源回路等から
漏えいするノイズへの耐ノイズ性を高めるという観点か
ら、複数の周波数帯域に同一のデータを載せ、ノイズの
影響の大きい周波数帯域を避けノイズの影響の少ない周
波数帯域を利用した通信が可能なマルチキャリア通信方
式が提案されている。第２の課題として、このようなマ
ルチキャリア通信方式の場合には、単一の周波数帯域を
利用したシングルキャリア通信方式に比較し、データの
処理時間が長いので、前述のＡＧＣのフィードバック制
御の安定時間が加われば、ますます長くなり、実用上、
フィードバック制御の応答速度が遅過ぎるという課題が
あった。In recent years, the above-mentioned digital communication device has begun to be used as a technology such as a power line modem for performing communication using an existing power line (distribution line) for reasons such as cost reduction. This technique is disclosed, for example, in Japanese Patent Application Laid-Open No. 2001-111518. In this gazette, from the viewpoint of improving the noise resistance against noise leaking from the power supply circuit of various home appliances, the same data is placed in a plurality of frequency bands, and the influence of noise is avoided by avoiding frequency bands where noise is greatly affected. A multi-carrier communication system capable of performing communication using a frequency band with few frequencies has been proposed. As a second problem, in the case of such a multi-carrier communication system, the data processing time is longer than that of the single-carrier communication system using a single frequency band. With time, it gets longer and longer,
There is a problem that the response speed of the feedback control is too slow.
【０００８】[0008]
【発明が解決しようとする課題】従来の広帯域ディジタ
ル受信機は、Ａ／Ｄ変換器への入力信号がその最大許容
入力レベルを越えない範囲で最大になるように、ＡＧＣ
アンプの増幅率がフィードバック制御されているので、
例えばＡ／Ｄ変換器の入力信号にレベルの高いノイズが
混入すると、相対的にＡ／Ｄ変換器への入力信号レベル
が減少し、復調器で復調されたデータ信号のうち伝送に
使用された周波数信号成分のレベルが信号処理回路のダ
イナミツクレンジに対して小さくなってしまうので、送
信信号の正常な再生が困難になるという課題があった。The conventional wideband digital receiver uses an AGC so that the input signal to the A / D converter is maximized without exceeding its maximum allowable input level.
Since the amplification rate of the amplifier is feedback controlled,
For example, when high-level noise is mixed in the input signal of the A / D converter, the input signal level to the A / D converter relatively decreases, and the data signal demodulated by the demodulator is used for transmission. Since the level of the frequency signal component becomes smaller than the dynamic range of the signal processing circuit, there is a problem that it is difficult to normally reproduce the transmission signal.
【０００９】また、以上のようなディジタル通信装置を
配電線搬送用通信装置として使用するためには、様々な
家電機器の電源回路等から漏えいするノイズが不特定か
つ時間的に変化するため、ＡＧＣアンプ７の増幅率の決
定をより短時間でもっと細かく行うことが求められてい
た。さらに、複数の周波数帯域に同一のデータを載せ、
ノイズの影響の少ない周波数帯域を利用した通信が可能
なマルチキャリア通信方式の場合には、単一の周波数帯
域を利用したシングルキャリア通信方式に比較し、デー
タの処理時間が長くなるため、ＡＧＣ処理時間をより短
することが望ましい。In order to use the above digital communication device as a communication device for transporting distribution lines, noise leaking from a power supply circuit of various home electric appliances and the like varies unspecified and changes over time. It has been required to determine the amplification factor of the amplifier 7 in a shorter time and in more detail. Furthermore, the same data is placed on multiple frequency bands,
In the case of a multi-carrier communication system capable of performing communication using a frequency band less affected by noise, the data processing time is longer than that of a single carrier communication system using a single frequency band. Shorter times are desirable.
【００１０】この発明は、かかる問題点を解決するため
になされたものであり、短時間で増幅回路の増幅率を決
定でき、マルチキャリア通信方式の配電線搬送用通信装
置にも使用可能で、かつ受信感度の高いディジタル通信
装置及びこれを用いた配電線搬送用通信装置を得ること
を目的としている。The present invention has been made in order to solve such a problem, and can determine the amplification factor of an amplifier circuit in a short time, and can be used for a communication device for carrying distribution lines of a multicarrier communication system. Another object of the present invention is to provide a digital communication device having high reception sensitivity and a communication device for distribution line transport using the digital communication device.
【００１１】[0011]
【課題を解決するための手段】この発明のディジタル通
信装置は、外部から所定の搬送周波数で入力されたアナ
ログ信号を増幅する増幅回路、前記増幅回路の出力側に
接続されたＡ／Ｄコンバータ、前記増幅回路から前記Ａ
／Ｄコンバータに入力される信号の大きさが、前記Ａ／
Ｄコンバータのダイナミックレンジに対してあらかじめ
定めた所定の値になるように前記増幅回路の増幅率を制
御する第一の制御回路、前記Ａ／Ｄコンバータの出力信
号から、前記搬送周波数の周波数成分の信号を抽出し、
この抽出した信号のレベルをあらかじめ定めた所定のレ
ベルと比較し、その結果にもとづき前記増幅回路の増幅
率を制御する第二の制御回路を備えたものである。According to the present invention, there is provided a digital communication apparatus comprising: an amplifier circuit for amplifying an analog signal input from an external device at a predetermined carrier frequency; an A / D converter connected to an output side of the amplifier circuit; From the amplifying circuit to the A
The magnitude of the signal input to the / D converter is A / D
A first control circuit for controlling an amplification factor of the amplifying circuit so as to have a predetermined value predetermined with respect to a dynamic range of the D converter, and a frequency component of the carrier frequency from an output signal of the A / D converter. Extract the signal,
A second control circuit is provided for comparing the level of the extracted signal with a predetermined level and controlling the amplification factor of the amplifier circuit based on the result.
【００１２】また、前記増幅回路の増幅率は段階的に変
化する不連続な値を持ち、前記第一の制御回路は前記増
幅回路が設定可能な全ての増幅率の段階の中から選択し
た互いに隣接しない複数の増幅率の段階により前記増幅
回路を制御し、前記第二の制御回路は前記全ての増幅率
の中から選択した増幅率で制御するものである。The amplification factor of the amplification circuit has a discontinuous value that changes stepwise, and the first control circuit selects one of all amplification factor stages that can be set by the amplification circuit. The amplifier circuit is controlled by a plurality of stages of amplification factors that are not adjacent to each other, and the second control circuit is controlled by an amplification factor selected from all the amplification factors.
【００１３】また、前記第一の制御回路は、前記増幅回
路の増幅率を制御する際、増幅率の大きい方から開始し
て前記Ａ／Ｄコンバータの出力の飽和程度を観測し、そ
の観測結果にもとづいて、制御する増幅率を順次低い方
へ移行するものである。When controlling the amplification factor of the amplifier circuit, the first control circuit observes the degree of saturation of the output of the A / D converter, starting from the one with the largest amplification factor, and observes the observation result. Based on this, the amplification factor to be controlled is sequentially shifted to a lower one.
【００１４】また、前記第二の制御回路は、前記Ａ／Ｄ
コンバータから出力されたディジタル信号をフーリエ変
換するＦＦＴ回路によりフーリエ変換された信号中から
搬送波周波数の成分の信号を抽出し、この信号の大きさ
を予め定めた所定のレベルと比較した結果にもとづい
て、前記増幅回路の増幅率を制御するように構成したも
のである。Further, the second control circuit is provided with the A / D
A signal of the component of the carrier frequency is extracted from the Fourier-transformed signal by the FFT circuit that performs a Fourier transform on the digital signal output from the converter, and the magnitude of this signal is compared with a predetermined level based on the result. , And is configured to control the amplification factor of the amplifier circuit.
【００１５】この発明にかかる配電線搬送用通信装置
は、配電線に接続する結合回路、前記結合回路から所定
の搬送周波数で入力されたアナログ信号を増幅する増幅
回路、前記増幅回路の出力側に接続されたＡ／Ｄコンバ
ータ、前記増幅回路から前記Ａ／Ｄコンバータに入力さ
れる信号の大きさが、前記Ａ／Ｄコンバータのダイナミ
ックレンジに対してあらかじめ定めた所定の値になるよ
うに前記増幅回路の増幅率を制御する第一の制御回路、
前記Ａ／Ｄコンバータの出力信号から、前記搬送周波数
の周波数成分の信号を抽出し、この抽出した信号のレベ
ルをあらかじめ定めた所定のレベルと比較し、その結果
にもとづき前記増幅回路の増幅率を制御する第二の制御
回路を備えたディジタル通信装置を用いたものである。According to the present invention, there is provided a communication device for conveying a distribution line, comprising: a coupling circuit connected to a distribution line; an amplification circuit for amplifying an analog signal input at a predetermined carrier frequency from the coupling circuit; The amplification is performed so that the magnitude of a signal input from the connected A / D converter and the amplification circuit to the A / D converter becomes a predetermined value predetermined with respect to a dynamic range of the A / D converter. A first control circuit for controlling the amplification of the circuit,
A signal of the frequency component of the carrier frequency is extracted from the output signal of the A / D converter, the level of the extracted signal is compared with a predetermined level, and the amplification factor of the amplifier circuit is determined based on the result. This uses a digital communication device provided with a second control circuit for controlling.
【００１６】また、配電線に配送される前記アナログ信
号の周波数は複数としたものである。Further, the analog signal delivered to the distribution line has a plurality of frequencies.
【００１７】[0017]
【発明の実施の形態】実施の形態１．図１はこの発明の
実施の形態１に係るデイジタル通信装置の構成図で、例
として複数周波数を搬送波として用いて通信を行なう配
電線搬送用の通信装置を示している。図１において、９
０は送信すべき送信データであり図示しないデータ処理
装置などから入力される。１はフレーミング回路で送信
データ９０に対して図２に示すようなフレーミング処理
を行ない、これを一次変調器２へ出力する。２は予め定
めた方式（例えばＤＢＰＳＫなど）で変調を行なう一次
変調器、３は制御回路１０の指令にもとづいて特定（複
数も可）のトーンの信号を抽出するトーン選択器、４は
逆高速フーリエ変換回路（ＩＦＦＴ：Inverse Fast Fou
rier Transform）で抽出されたトーン信号の周波数軸デ
ータを時間軸データに変換する。５はパラレル／シリア
ル変換回路（Ｐ／Ｓ）、６はディジタル／アナログ変換
回路（Ｄ／Ａ）、７は無線出力回路を配電線に接続する
ための結合回路、８は伝送路（配電線）、１０は制御回
路（詳細後述）であり、内部に第一の制御回路１０ａと
第二の制御回路１０ｂとを有している。フレーミング回
路１、一次変調器２、トーン選択器３、ＩＦＦＴ４、Ｐ
／Ｓ５、Ｄ／Ａ６、結合回路７で送信系１１０を構成し
ている。DESCRIPTION OF THE PREFERRED EMBODIMENTS Embodiment 1 FIG. 1 is a configuration diagram of a digital communication device according to a first embodiment of the present invention. As an example, a communication device for distribution line transport that performs communication using a plurality of frequencies as carrier waves is shown. In FIG. 1, 9
0 is transmission data to be transmitted, and is input from a data processing device (not shown) or the like. Reference numeral 1 denotes a framing circuit which performs a framing process as shown in FIG. 2 on the transmission data 90, and outputs this to the primary modulator 2. Reference numeral 2 denotes a primary modulator for performing modulation by a predetermined method (for example, DBPSK). Reference numeral 3 denotes a tone selector for extracting a signal of a specific (multiple) tone based on a command from the control circuit 10; Fourier transform circuit (IFFT: Inverse Fast Fou
The frequency domain data of the tone signal extracted by the carrier transform is converted into time domain data. 5 is a parallel / serial conversion circuit (P / S), 6 is a digital / analog conversion circuit (D / A), 7 is a coupling circuit for connecting a wireless output circuit to a distribution line, and 8 is a transmission line (distribution line). Reference numeral 10 denotes a control circuit (to be described in detail later), which internally includes a first control circuit 10a and a second control circuit 10b. Framing circuit 1, primary modulator 2, tone selector 3, IFFT4, P
/ S5, D / A6, and the coupling circuit 7 constitute the transmission system 110.
【００１８】１２０は受信系で、１７は結合回路７から
受信された高周波信号を制御回路１０の制御に基づく増
幅率（段階的に変化する不連続な増幅率の値を持つ）で
増幅するＡＧＣ増幅回路（Auto Gain Control ）、１６
はアナログ／ディジタル変換回路（Ａ／Ｄ変換器）、１
５はシリアル／パラレル変換回路（Ｓ／Ｐ）、１４は高
速フーリエ変換回路（ＦＦＴ：Fast Fourier Transfor
m）、１３はトーン選択器、１２は一次復調器、１１は
デフレーミング回路で、図２に示したフレーミングの信
号から受信データ９１を出力する。これらは送信系１１
０を構成する対応部分と逆の動作を行なうものであるの
で、個々についての詳細な説明は省略する。そして、結
合回路７、ＡＧＣ回路１７、Ａ／Ｄ１６、Ｓ／Ｐ１５、
ＦＦＴ１４、トーン選択器１３、一次復調器１２、デフ
レーミング回路１１で受信系１２０を構成する。結合回
路７は送信系１１０にも、受信系１２０にも属してい
る。Reference numeral 120 denotes a reception system. Reference numeral 17 denotes an AGC which amplifies the high-frequency signal received from the coupling circuit 7 at an amplification factor (having a stepwise varying discontinuous amplification factor) under the control of the control circuit 10. Amplifier circuit (Auto Gain Control), 16
Is an analog / digital converter (A / D converter), 1
5 is a serial / parallel conversion circuit (S / P), 14 is a fast Fourier transform circuit (FFT).
m) and 13 are tone selectors, 12 is a primary demodulator, and 11 is a deframing circuit, which outputs received data 91 from the framing signal shown in FIG. These are the transmission system 11
Since the operation is the reverse of that of the corresponding part constituting 0, detailed description of each is omitted. Then, the coupling circuit 7, the AGC circuit 17, the A / D16, the S / P15,
The FFT 14, the tone selector 13, the primary demodulator 12, and the deframing circuit 11 constitute a receiving system 120. The coupling circuit 7 belongs to both the transmission system 110 and the reception system 120.
【００１９】結合回路７は、例えばトランスとハイパス
フィルターにより構成され、通信装置の送受信部（図示
省略しているが例えばＤ／Ａ変換器６の出力側に接続さ
れた電力増幅回路など）を伝送路８である配電線に接続
し、商用周波数の流入を阻止しつつ配電線搬送信号を通
過させる役割を持つ。ＡＧＣ回路１７は、結合回路７を
通過した高周波ノイズを含む配電線搬送信号レベルの大
小に関わらず、Ａ／Ｄ変換器１６に許容の範囲でできる
限り大きい信号電圧を入力し、信号成分の抽出を容易に
するためのものであり、例えば複数のオペアンプにより
構成されており、制御回路１０の指示により増幅に使用
するオペアンプの組を選択するなどしてＡＧＣ回路ゲイ
ンを設定する。理解を助けるため、図３に例えば、４個
のオペアンプＡ，Ｂ，Ｃ，Ｄの組み合わせにより増幅回
路を構成する場合を示す。図３（ｂ）図はその回路で、
スイッチＳＡ，ＳＢ，ＳＣ，ＳＤをそれぞれアンプ側に
切り換えればアンプを使用し、バイパス回路側に切り換
えればアンプを使用しないことを示す。この場合、図３
（ａ）に示すように、２の４乗通り即ち１６通りの増幅
率の組合わせが得られる。ここでどのアンプも使用しな
い組み合わせもゲイン１として１組に数えている。The coupling circuit 7 is composed of, for example, a transformer and a high-pass filter, and transmits and receives a transmitting / receiving section (not shown, for example, a power amplifier circuit connected to the output side of the D / A converter 6) of the communication device. It is connected to the distribution line, which is the path 8, and has a role of passing the distribution line carrier signal while preventing the inflow of the commercial frequency. The AGC circuit 17 inputs a signal voltage as large as possible within the allowable range to the A / D converter 16 irrespective of the level of the distribution line carrier signal including high-frequency noise that has passed through the coupling circuit 7, and extracts a signal component. The AGC circuit is configured by, for example, a plurality of operational amplifiers, and sets the AGC circuit gain by selecting a set of operational amplifiers used for amplification in accordance with an instruction from the control circuit 10. For ease of understanding, FIG. 3 shows a case where an amplifier circuit is formed by combining, for example, four operational amplifiers A, B, C, and D. FIG. 3B shows the circuit.
Switching the switches SA, SB, SC, and SD to the amplifier side respectively indicates that the amplifier is used, and switching to the bypass circuit side indicates that the amplifier is not used. In this case, FIG.
As shown in (a), 2 4 power combinations, that is, 16 combinations of amplification factors are obtained. Here, a combination that does not use any amplifier is counted as one set as gain 1.
【００２０】図４は図１の回路のＡＧＣ制御動作を説明
する図であり、（ａ）はＡＧＣ回路１７の入力信号で、
説明上、異なる振幅レベルの５つの入力信号がある場合
を示している。ＡＧＣ回路１７通過後の信号は（ｂ）に
示したように振幅レベルが、あらかじめ定めたほぼ一定
の範囲（上下限とも）に押さえられるように、小さい信
号は大きく増幅され、大きい信号は縮小されている。こ
のように、ＡＧＣ回路１７通過後の信号を、大きさが一
定の範囲の信号としてＡ／Ｄコンバータ１６に入力させ
ることにより、Ａ／Ｄコンバータ１６のダイナミックレ
ンジを有効に使用することができる。FIGS. 4A and 4B are diagrams for explaining the AGC control operation of the circuit of FIG. 1. FIG.
For explanation, a case where there are five input signals of different amplitude levels is shown. As shown in (b), the signal after passing through the AGC circuit 17 has a small signal greatly amplified and a large signal reduced so that the amplitude level is kept within a predetermined substantially constant range (both upper and lower limits). ing. In this way, by inputting the signal after passing through the AGC circuit 17 to the A / D converter 16 as a signal having a fixed range, the dynamic range of the A / D converter 16 can be used effectively.
【００２１】トーン選択器１３は、制御回路１０からの
指示により、ある個別周波数成分（複数も可）のトーン
データを選択する。図２は、上記フレーミング回路１に
よるフレーミング処理で生成されるフレームの構成と、
そのフレームにおけるＰＯＣフィールド（Power Line C
ommunication Overhead Control Field ）の構成を示す
図である。図２に示すフレームは、 １）キャリア検出用の信号の領域であるプリアンブル
（１）フィールドと、 ２）シンボル同期用の信号の領域であるプリアンブル
（２）フィールドと、 ３）予め定められた固定コードの領域である同期コード
フィールドと、 ４）データフィールドの長さを示す信号の領域であるＦ
ｒａｍｅＴｙｐｅ（ＦＴ）フィールドと、 ５）住宅識別用コードの領域であるＨｏｕｓｅＣｏｄｅ
（ＨＣ）フィールドと、 ６）物理層で使用する制御コマンドの領域であるＰＯＣ
フィールドと、 ７）ＦＴ，ＨＣ，ＰＯＣに対する誤り訂正符号の領域で
あるＲ−Ｓ符号フィールドと、 ８）データフィールド から構成され、このフレームがフレーミング回路１にて
生成され、前述の処理で変調後、伝送路８に出力され
る。なお、実施の形態１においては、たとえば、上記プ
リアンブル（１）を１６シンボル区間にわたる同一デー
タの繰り返しパターンとし、上記プリアンブル（２）を
１６シンボル区間にわたる反転データの繰り返しパター
ン（シンボル単位にデータを反転させるパターン）とす
る。The tone selector 13 selects tone data of a certain individual frequency component (a plurality of individual frequency components) according to an instruction from the control circuit 10. FIG. 2 shows a configuration of a frame generated by the framing process by the framing circuit 1;
POC field in the frame (Power Line C
It is a figure showing the composition of ommunication Overhead Control Field). The frame shown in FIG. 2 includes: 1) a preamble (1) field which is an area of a signal for carrier detection; 2) a preamble (2) field which is an area of a signal for symbol synchronization; and 3) a predetermined fixed number. A sync code field which is a code area; and 4) an F area which is a signal area indicating the length of the data field.
5) a HouseType which is an area for a house identification code.
(HC) field and 6) POC which is an area of a control command used in the physical layer
And 7) an RS code field which is an area of an error correction code for FT, HC, and POC; and 8) a data field. This frame is generated by the framing circuit 1 and is modulated by the processing described above. Are output to the transmission line 8. In the first embodiment, for example, the preamble (1) is a repetition pattern of the same data over 16 symbol sections, and the preamble (2) is a repetition pattern of inversion data over 16 symbol sections (data is inverted in symbol units). Pattern).
【００２２】また、伝送路８（配電線）上のフレーム
は、伝送路８に接続されたすべての通信装置（図示しな
い）で受け取られ、制御回路１０では、ＲＳ（リードソ
ロモン）符号を利用してエラーチェックを行い、ＨＣの
識別を行った上で自家のＨＣと一致した場合、伝送路上
に送信されているデータが自分宛てであると判断し、Ｒ
Ｓ（リードソロモン）符号を利用してエラーチェック／
訂正を行い、その内容を理解する。自家のＨＣと一致し
ない場合は、動作を行わない。The frame on the transmission line 8 (distribution line) is received by all communication devices (not shown) connected to the transmission line 8, and the control circuit 10 uses an RS (Reed-Solomon) code. Error check is performed to identify the HC, and if the HC matches the own HC, it is determined that the data transmitted on the transmission path is addressed to itself, and R
Error check using S (Reed-Solomon) code /
Make corrections and understand their content. If it does not match the own HC, no operation is performed.
【００２３】一方、ＰＯＣは、通信の速度（たとえば、
低速モード、高速モード等）を設定する２ビットの通信
モードフィールドと、選択可能な変調方式（たとえば、
ＤＱＰＳＫ，ＤＢＰＳＫ，ＤＢＰＳＫ＋時間ダイバーシ
チ等）を示す２ビットの変調方式フィールドと、制御コ
マンド（通常動作、変更動作）を示す１ビットのコマン
ドフィールドと、制御コマンドの機能を示す２ビットの
サブコマンドと、各機能の設定情報（トーングループ、
セットポジション）を示す８ビットのコマンド引数と、
１ビットの拡張ビットから構成され、たとえば、トーン
の移動および一次変調方式の変更等の処理を行うために
使用される。On the other hand, the POC indicates the communication speed (for example,
A 2-bit communication mode field for setting a low-speed mode, a high-speed mode, and the like, and a selectable modulation method (for example,
A 2-bit modulation method field indicating DQPSK, DBPSK, DBPSK + time diversity, etc., a 1-bit command field indicating a control command (normal operation, change operation), a 2-bit subcommand indicating a function of the control command, Setting information of each function (tone group,
An 8-bit command argument indicating the set position)
It is composed of one extended bit, and is used, for example, for performing processing such as movement of a tone and change of a primary modulation method.
【００２４】次に、動作について説明する。 （送信動作）送信データ９０がフレーミング回路１に入
力されると制御回路１０からの制御で変調されるデータ
に変換され一次変調器２に入力される。一次変調器２
は、制御回路１０からの制御によりデータを一次変調
し、トーン選択器３へ出力する。トーン選択器３は、制
御回路１０からの制御でトーンごとにデータを生成し、
ＩＦＦＴ４に出力する。ＩＦＦＴ４は、入力されたデー
タを逆フーリエ変換して複数トーン分の合成されたデー
タとして生成する。５はシリアルパラレル変換回路であ
り、入力されたシリアルデータをパラレルデータに変換
し、Ｄ／Ａコンバータ入力する。Ｄ／Ａコンバータ６は
入力されたデータを変換し、結合回路７を経由して伝送
路８に出力する。Next, the operation will be described. (Transmission Operation) When transmission data 90 is input to the framing circuit 1, it is converted into data to be modulated under the control of the control circuit 10 and input to the primary modulator 2. Primary modulator 2
Performs primary modulation of data under the control of the control circuit 10 and outputs the data to the tone selector 3. The tone selector 3 generates data for each tone under the control of the control circuit 10,
Output to IFFT4. The IFFT 4 performs inverse Fourier transform of the input data to generate data that is synthesized for a plurality of tones. Reference numeral 5 denotes a serial / parallel conversion circuit which converts input serial data into parallel data and inputs the data to a D / A converter. The D / A converter 6 converts the input data and outputs the converted data to the transmission line 8 via the coupling circuit 7.
【００２５】（受信動作）配電線搬送信号が到来すると
伝送路８に接続された結合回路７の伝送路側に商用周波
数電圧に重畳された複数トーンの配電線搬送信号の信号
電圧が誘起する。配電線搬送信号は商用周波数より十分
に高い周波数であるため、商用周波数を阻止する結合回
路７を通過する。この時、他の家電機器等の電源回路か
ら伝送路８に漏えいしている高周波ノイズも同時に結合
回路７を通過する。結合回路７を通過した高周波ノイズ
を含む配電線搬送信号はＡＧＣ回路１７、Ａ／Ｄコンバ
ータ１６により、入力電圧の時系列ディジタルデータに
変換される。このディジタルデータを一定時間分記憶し
た後、ＦＦＴ信号処理１４により周波数分析を行い、ト
ーン選択器１３で伝送に使用している周波数データのみ
を一次復調器１２に導いている。(Reception operation) When a distribution line carrier signal arrives, a signal voltage of a multi-tone distribution line carrier signal superimposed on the commercial frequency voltage is induced on the transmission line side of the coupling circuit 7 connected to the transmission line 8. Since the distribution line carrier signal has a frequency sufficiently higher than the commercial frequency, it passes through the coupling circuit 7 that blocks the commercial frequency. At this time, high-frequency noise leaking from the power supply circuit of another home electric appliance or the like to the transmission line 8 also passes through the coupling circuit 7 at the same time. The distribution line carrier signal containing high frequency noise that has passed through the coupling circuit 7 is converted into time-series digital data of the input voltage by the AGC circuit 17 and the A / D converter 16. After storing the digital data for a predetermined time, the frequency analysis is performed by the FFT signal processing 14, and only the frequency data used for transmission by the tone selector 13 is led to the primary demodulator 12.
【００２６】図５はこの発明のＡＧＣ制御動作のフロー
チャートである。制御回路１０の内部の第一の制御回路
１０ａによる初期制御で、ＡＧＣ回路１７は、最初は、
最大増幅度（即ち図３のレベルＸ１６）に設定（ステッ
プＳ３１）し、次に、Ａ／Ｄコンバータ１６のディジタ
ル変換値を第一の制御回路１０ａが読み取る（ステップ
Ｓ３２）。第一の制御回路１０ａはＡ／Ｄコンバータ１
６の出力値により飽和判定（飽和判定の説明は後述）を
行い（ステップＳ３３）、非飽和ならばその値で次処理
のＦＦＴ回路１４によるＦＦＴ解析を実行する。飽和な
らば、第一の制御回路１０ａは図３に示すＡＧＣテーブ
ルの第一の制御回路が選択する増幅率の一段下の増幅率
（即ち図３のレベルＸ１４）をＡＧＣ回路１７に設定変
更し（ステップＳ３４）、再度Ａ／Ｄコンバータ１６の
ディジタル変換値を第一の制御回路１０ａが読み取り
（ステップＳ３５）、飽和判定（ステップＳ３７）を行
う。FIG. 5 is a flowchart of the AGC control operation of the present invention. In the initial control by the first control circuit 10a inside the control circuit 10, the AGC circuit 17
The maximum amplification degree (that is, the level X16 in FIG. 3) is set (step S31), and the digital conversion value of the A / D converter 16 is read by the first control circuit 10a (step S32). The first control circuit 10a is an A / D converter 1
Saturation determination (the saturation determination will be described later) is performed using the output value of No. 6 (step S33). If it is saturated, the first control circuit 10a changes the setting of the gain below the gain selected by the first control circuit in the AGC table shown in FIG. 3 (that is, the level X14 in FIG. 3) to the AGC circuit 17. (Step S34), the first control circuit 10a reads the digital conversion value of the A / D converter 16 again (Step S35), and performs the saturation determination (Step S37).
【００２７】ここで、飽和とは、図６に示すように、Ａ
／Ｄ変換された全データに占めるＡ／Ｄコンバータ１６
のダイナミックレンジの最大値、或いは最小値のデータ
の割合が、所定の割合を超えたときを意味する。図６に
おいて実線はＡ／Ｄコンバータ１６のダイナミックレン
ジの最大値（ＭＡＸ）及び最小値（ＭＩＮ）、破線はＡ
／Ｄコンバータ１６への入力信号、丸印はＡ／Ｄコンバ
ータ１６からの出力データである。第一の制御回路１０
ａは、出力データをその大きさ毎に集計し、所定の周期
（時間）内にＭＡＸ或いはＭＩＮとなったデータが所定
の個数を超えると飽和と判断する。Here, the saturation means A as shown in FIG.
A / D converter 16 occupying all the data converted into / D
Means that the ratio of the data of the maximum value or the minimum value of the dynamic range exceeds a predetermined ratio. In FIG. 6, the solid line is the maximum value (MAX) and the minimum value (MIN) of the dynamic range of the A / D converter 16, and the broken line is A
An input signal to the / D converter 16 and a circle represent output data from the A / D converter 16. First control circuit 10
As for a, the output data is totaled for each size, and if the data that has become MAX or MIN within a predetermined cycle (time) exceeds a predetermined number, it is determined that the data is saturated.
【００２８】再び、図５のフローチャートの説明に戻
り、第一の制御回路１０ａによるＡＧＣ処理は第一の制
御回路が選択するＡＧＣテーブルを最後まで使用するか
（ステップＳ３６）、飽和判定の結果が非飽和になる
（ステップＳ３７）まで、一連のＡＧＣ制御（ステップ
Ｓ３４〜３７）を行い、ＡＧＣの仮決定を行う（ステッ
プＳ６１）。ここで、図３の第一の制御回路が選択する
増幅率の欄に示すように、例えば、ＡＧＣ回路１７が４
個のオペアンプにより構成され、第一の制御回路１０ａ
が１６通りの増幅率の組から８組（８段階Ｘ１６，Ｘ１
４，Ｘ１２，Ｘ１０，Ｘ８，Ｘ６，Ｘ４，Ｘ２）の増幅
率を選択した使用テーブルによって制御する例について
説明する。使用テーブルは、図３に示す例に限らず予め
ユーザやシステムの開発者によって任意に決めることが
できる。一例として、ＡＧＣ使用テーブルが（Ｘ１６，
Ｘ１４，Ｘ１２，Ｘ１０，Ｘ８，Ｘ６，Ｘ４，Ｘ２ここ
で数字は単なる識別符号であり増幅率を意味するもので
はない）の８段階の場合、増幅率の大きい方から順に最
大７回のＡＧＣ制御が行なわれることとなる。このよう
に第一の制御回路１０ａにより、大雑把な飛び飛びの増
幅率によりＡＧＣ制御を行なうので、Ａ／Ｄコンバータ
１６のディジタル出力値を飽和に近い大きい値に選定す
ることができる。Returning to the description of the flowchart of FIG. 5 again, the AGC processing by the first control circuit 10a uses the AGC table selected by the first control circuit to the end (step S36), A series of AGC controls (steps S34 to S37) are performed until a non-saturation is reached (step S37), and the AGC is provisionally determined (step S61). Here, as shown in the column of the amplification factor selected by the first control circuit in FIG.
And a first control circuit 10a
Are 8 sets out of 16 sets of amplification factors (8 steps X16, X1
4, X12, X10, X8, X6, X4, X2) will be described by way of an example in which the amplification factor is controlled by a selected use table. The use table is not limited to the example shown in FIG. 3 and can be arbitrarily determined in advance by a user or a system developer. As an example, the AGC usage table is (X16,
X14, X12, X10, X8, X6, X4, X2, where the numbers are merely identification codes and do not mean the amplification rate), in the case of eight stages, the AGC control is performed up to seven times in ascending order of the amplification rate. Will be performed. As described above, since the AGC control is performed by the first control circuit 10a with a rough step-by-step amplification factor, the digital output value of the A / D converter 16 can be selected to a large value close to saturation.
【００２９】（ステップＳ６１）によるＡＧＣのゲイン
の仮決定後、Ａ／Ｄコンバータ１６の出力したディジタ
ルデータを一定時間分記憶した後、ＦＦＴ信号処理１４
により周波数分析を行い、トーン選択器１３で伝送に使
用している周波数データを抽出する。そして抽出した複
数の周波数成分毎にベクトル長を演算する（ステップＳ
６２）。この演算により得られたベクトル長は、信号周
波数以外の周波数ノイズが除去された信号成分となる。
その理由は配電線に重畳されているノイズは広い周波数
帯にわたって比較的均等にエネルギーが分布するいわゆ
るホワイトノイズと称されるノイズが多く、これはＦＥ
Ｔ信号処理１４による周波数分析により消去できるから
である。（図７（ａ），（ｂ）に示す信号レベルを参
照）。After the AGC gain is provisionally determined in step S61, the digital data output from the A / D converter 16 is stored for a certain period of time, and then the FFT signal processing 14 is performed.
And frequency data used for transmission is extracted by the tone selector 13. Then, a vector length is calculated for each of the plurality of extracted frequency components (step S
62). The vector length obtained by this operation is a signal component from which frequency noise other than the signal frequency has been removed.
The reason is that the noise superimposed on the distribution line is often called so-called white noise in which energy is distributed relatively uniformly over a wide frequency band.
This is because it can be eliminated by frequency analysis by the T signal processing 14. (Refer to the signal levels shown in FIGS. 7A and 7B).
【００３０】第二の制御回路１０ｂは、演算により得ら
れたベクトル長を判定基準値と比較する（ステップＳ６
３）。判定基準値は予め設定された値であり、例えばＡ
／Ｄコンバータ１６におけるダイナミックレンジの９０
％のレンジ（信号レベル）とする。ステップＳ６３での
比較結果により、そのベクトル長が判定基準値より大き
ければＡＧＣ仮決定値をＡＧＣ決定値として採用する
（ステップＳ６４）。他方、ベクトル長が判定基準値よ
り小さければ、第二の制御回路１０ｂはＡＧＣ使用テー
ブルの第二の制御回路が選択可能な増幅率の欄の中で、
ＡＧＣ仮決定値より１段階高い値（増幅率）を選択する
（ステップＳ６５）。例えば、第一の制御回路１０ａに
よるＡＧＣ使用テーブルが（Ｘ１６，Ｘ１４，Ｘ１２，
Ｘ１０，Ｘ８，Ｘ６，Ｘ４，Ｘ２）の８段階の場合にお
いて、ＡＧＣ仮決定値がＸ１０であるとき、演算により
得られたベクトル長が判定基準値より大きい場合ＡＧＣ
決定値はＸ１０、他方小さい場合ＡＧＣ決定値はＸ１１
となる。The second control circuit 10b compares the vector length obtained by the calculation with a determination reference value (step S6).
3). The criterion value is a preset value, for example, A
90 of the dynamic range in the / D converter 16
% Range (signal level). As a result of the comparison in step S63, if the vector length is larger than the determination reference value, the AGC provisionally determined value is adopted as the AGC determined value (step S64). On the other hand, if the vector length is smaller than the criterion value, the second control circuit 10b sets the amplification factor selectable by the second control circuit in the AGC use table.
A value (amplification factor) one step higher than the AGC provisionally determined value is selected (step S65). For example, the AGC use table by the first control circuit 10a is (X16, X14, X12,
X10, X8, X6, X4, X2), when the AGC provisionally determined value is X10, and when the vector length obtained by the operation is larger than the determination reference value, AGC
The determined value is X10, while the AGC determined value is X11 when smaller.
Becomes
【００３１】つまり、図７（ａ）に示すように、Ａ／Ｄ
コンバータ１６の入力にノイズが多く含まれているため
に、実信号成分が小さいときには、第一の制御回路１０
ａによるＡＧＣ仮決定値からプラス１段階され、他方、
図７（ｂ）に示すようにＡ/Ｄコンバータ１６の入力に
ノイズが少なく、実信号成分が十分大きいときには、第
一の制御回路１０ａによるＡＧＣ仮決定値が最終的に採
用され、それぞれの場合において信号レベルに合った増
幅がなされることとなる。That is, as shown in FIG.
When the actual signal component is small because the input of the converter 16 contains much noise, the first control circuit 10
a plus one step from the AGC tentatively determined value by a,
As shown in FIG. 7B, when there is little noise at the input of the A / D converter 16 and the real signal component is sufficiently large, the AGC provisionally determined value by the first control circuit 10a is finally adopted, and in each case, In this case, amplification that matches the signal level is performed.
【００３２】以上のように、第一の制御回路１０ａによ
り大雑把なＡＧＣを仮決定した後、第二の制御回路１０
ｂにより複数の信号周波数について信号のベクトル長を
判定基準値と比較し、その判定結果によりＡＧＣの仮決
定値を変更するという２段階の制御を行なうようにした
ので、ＡＧＣ使用テーブルの段数が多いにもかかわら
ず、素早く最適な増幅率に到達することができることと
なり、ＡＧＣ選択ケースを増加させ、伝送に使用してい
る信号成分の抽出を容易に、最高受信感度を向上させる
配電線搬送通信装置を得ることができる。As described above, after the rough AGC is provisionally determined by the first control circuit 10a, the second control circuit 10a
b, a two-stage control of comparing the vector length of the signal with the determination reference value for a plurality of signal frequencies and changing the provisional determination value of AGC based on the determination result is performed, so that the number of stages in the AGC use table is large. Nevertheless, it is possible to quickly reach the optimum amplification factor, increase the number of AGC selection cases, easily extract the signal components used for transmission, and improve the maximum receiving sensitivity of the distribution line carrier communication device. Can be obtained.
【００３３】また、制御回路１０は、仮決定までは、第
一の制御回路１０ａによりＡ/ Ｄコンバータ１６の出力
データのカウントにより飽和を検出してＡＧＣ増幅率を
大雑派に仮決定し、その後、第二の制御回路１０ｂによ
りＡ/ Ｄコンバータ１６で変換されたデータから伝送に
使用している周波数データのみを抽出しＦＦＴ変換によ
り信号のベクトル長を演算するようにしたので、ＡＧＣ
調整が短時間で最適な増幅率に設定が可能となり、アッ
ク電文（応答電文）や制御電文等の比較的フレームのヘ
ッダー部分が大きい（ヘッダー部分とデータ部分がほぼ
同じ長さの）フレームが頻繁に行き交う配電線搬送通信
装置に特に有効である。Further, the control circuit 10 detects the saturation by counting the output data of the A / D converter 16 by the first control circuit 10a and provisionally determines the AGC amplification factor roughly until the provisional determination. After that, the second control circuit 10b extracts only the frequency data used for transmission from the data converted by the A / D converter 16 and calculates the signal vector length by FFT conversion.
Adjustment can be set to the optimum amplification rate in a short period of time, and relatively large frames (such as headers and data portions of almost the same length) such as acknowledgment messages (response messages) and control messages are frequently used. This is particularly effective for a distribution line carrier communication device that travels to and from a location.
【００３４】また、第一の制御回路１０ａによるＡＧＣ
使用テーブルを（図３に示すようなＸ１６，Ｘ１４，Ｘ
１２，Ｘ１０，Ｘ８，Ｘ６，Ｘ４，Ｘ２）と、連続した
増幅率の中から大雑把に、飛び飛びの増幅率から選択す
るようにしているので、短時間で目標値の間近までＡＧ
Ｃ調整をすることができる。また、第一の制御回路によ
るＡＧＣの仮決定の後、第二の制御回路１０ｂにより信
号のベクトル長を判定して仮決定値を変更するようにし
たので、最終選択レベルが細かく設定されていても素早
く目標値に到達することができる。そして伝送に使用し
ている信号成分の抽出を容易に、最高受信感度を向上さ
せる配電線搬送通信装置を得ることができる。AGC by the first control circuit 10a
The use table is defined as (X16, X14, X
12, X10, X8, X6, X4, X2) and successive gains are roughly selected from discrete gains.
C adjustment can be performed. After the provisional determination of AGC by the first control circuit, the second control circuit 10b determines the vector length of the signal and changes the provisionally determined value, so that the final selection level is set finely. Can quickly reach the target value. Further, it is possible to easily obtain the signal component used for the transmission and to obtain the distribution line carrier communication device that improves the maximum reception sensitivity.
【００３５】実施の形態２．以上の説明では、信号のベ
クトル長が小さい（大きい）ときＡＧＣ増幅率を１段増
加させるようにしたが、勿論１段でなければならぬとい
うことはない。例えば、第一の制御回路１０ａが選択す
る増幅率を３段ごとに設定し、ＡＧＣ使用テーブルの隣
接する増幅率の組に２段以上の間隔があるときベクトル
長によって、その間の値の大きいほう、または小さいほ
うを選択仕分けるようにすると受信感度を更に細かくで
きる。Embodiment 2 In the above description, when the vector length of the signal is small (large), the AGC amplification factor is increased by one stage. However, it is needless to say that one stage is required. For example, the amplification factor selected by the first control circuit 10a is set for every three stages, and when there is an interval of two or more stages in the pair of adjacent amplification factors in the AGC use table, the larger the value between the two depending on the vector length, Alternatively, if the smaller one is selected and sorted, the reception sensitivity can be further reduced.
【００３６】また、ＡＧＣ使用テーブルを１０段階（Ｘ
１６，Ｘ１５，Ｘ１４，Ｘ１３，Ｘ１２，Ｘ１０，Ｘ
８，Ｘ６，Ｘ４，Ｘ２）とし、増幅率が一部（あるいは
１６段階全部）連続するようにしても良い。この場合に
は、連続する増幅率（例えばＸ１３）が第一の制御回路
１０ａにより仮決定され、第二の制御回路１０ｂにより
増幅率を１段増加させるときには、最終的に選択される
増幅率は仮決定された増幅率より１段大きい増幅率（例
えばＸ１４）となる。このように、増幅率の大きい領域
が密となったＡＧＣ使用テーブルを用いることで、搬送
信号の減衰が大きく受信信号のレベルがホワイトノイズ
に対して相対的に小さくなる条件、例えば、直下に負荷
が接続されている条件とか、搬送距離が長い条件などの
場合において、信号を受信できることとなる。また、上
記説明では、複数の信号周波数について信号レベル判定
のための演算は、抽出した複数の信号周波数についてベ
クトル長を演算しているが、最大値演算結果、重み付け
による演算結果など、配電線搬送用通信装置の各信号周
波数の重みによりレベル判定演算を変更できることは言
うまでもない。The AGC use table is stored in 10 stages (X
16, X15, X14, X13, X12, X10, X
8, X6, X4, X2), and the amplification factor may be partially (or all 16 steps) continuous. In this case, a continuous amplification factor (for example, X13) is provisionally determined by the first control circuit 10a, and when the amplification factor is increased by one stage by the second control circuit 10b, the amplification factor finally selected is The gain becomes one step larger than the provisionally determined gain (for example, X14). As described above, by using the AGC use table in which the region with the large amplification factor is dense, the condition that the attenuation of the carrier signal is large and the level of the received signal is relatively small with respect to the white noise, for example, the load is directly below. Signal can be received under conditions such as the condition where is connected or the condition where the transport distance is long. In the above description, the operation for determining the signal level for a plurality of signal frequencies is performed by calculating the vector length for the extracted plurality of signal frequencies. Needless to say, the level determination calculation can be changed by the weight of each signal frequency of the communication device for communication.
【００３７】また、ＡＧＣ回路１７から入力されるアナ
ログ信号がＡ／Ｄコンバータ１６のダイナミックレンジ
内で飽和せずに最大となるようにＡＧＣ回路１７の増幅
率を仮決定する例について説明したが、Ａ／Ｄコンバー
タ１６のダイナミックレンジの所定割合以上を占めるよ
うに、即ち図４における実線のハッチングで示す領域に
飽和せずに入力信号のピークが現れるようにしてもよ
い。また、電送路７は商用電源線であると説明したが、
専用の通信線であってもよいことは言うまでもない。Also, an example has been described in which the amplification factor of the AGC circuit 17 is provisionally determined such that the analog signal input from the AGC circuit 17 does not saturate within the dynamic range of the A / D converter 16 and becomes maximum. The peak of the input signal may be set so as to occupy a predetermined ratio or more of the dynamic range of the A / D converter 16, that is, without saturating the region indicated by the solid-line hatching in FIG. Also, it has been described that the transmission path 7 is a commercial power line,
It goes without saying that a dedicated communication line may be used.
【００３８】[0038]
【発明の効果】この発明に係る通信装置は、Ａ／Ｄコン
バータからのディジタル信号に基づいて、増幅回路から
入力されるアナログ信号が上記Ａ／Ｄコンバータのダイ
ナミックレンジの所定割合以上を占めるように増幅率を
大雑把に仮決定する第一の制御回路と、Ａ／Ｄコンバー
タから入力されたディジタル信号より伝送に使用してい
る周波数成分の信号レベルをＦＦＴ解析によって抽出
し、このレベルを所定のレベルと比較した結果に基づい
て、増幅回路の増幅率を細かく変更する第二の制御回路
とを備えたので、増幅率の制御が細かいにもかかわら
ず、短時間で増幅回路の増幅率を目標値に決定でき、か
つ受信感度の高いディジタル通信装置を得ることができ
る。According to the communication apparatus of the present invention, based on the digital signal from the A / D converter, the analog signal input from the amplifier circuit occupies a predetermined ratio or more of the dynamic range of the A / D converter. A first control circuit for roughly tentatively determining an amplification factor; and extracting a signal level of a frequency component used for transmission from a digital signal input from an A / D converter by FFT analysis, and setting this level to a predetermined level. And a second control circuit for finely changing the amplification factor of the amplification circuit based on the result of the comparison, so that the amplification factor of the amplification circuit can be set to the target value in a short time despite the fine control of the amplification factor. And a digital communication device with high reception sensitivity can be obtained.
【００３９】また、第一の制御回路は、得られる全ての
増幅率の値から、少なくとも増幅率の大きさが連続しな
い飛び飛びの増幅率を選択し、第二の制御回路は前記全
ての増幅率を選択可能なように構成したので、短時間で
目標増幅率に近い値に到達し、また、最終的には極めて
細かい増幅率の値の制御ができる。The first control circuit selects, from all the obtained gain values, at least discrete gains at which the magnitudes of the gains are not continuous, and the second control circuit selects all the gains. Can be selected, so that a value close to the target amplification factor can be reached in a short time, and finally, the value of the amplification factor can be very finely controlled.
【００４０】また、第一の制御回路は、増幅回路の増幅
率を大きい方から順に小さい増幅率へ移行させる指令を
出力する（制御する）ので、短時間で増幅回路の増幅率
を決定できる。Further, the first control circuit outputs (controls) the command to shift the amplification factor of the amplifier circuit from the larger one to the smaller one, so that the amplification factor of the amplifier circuit can be determined in a short time.
【００４１】また、Ａ／Ｄコンバータから出力されたデ
ィジタル信号をフーリエ変換するＦＦＴ回路を有し、 第
一の制御回路は、上記ＦＦＴ回路によりフーリエ変換さ
れる前のディジタル信号により増幅率を仮決定し、第二
の制御回路はＦＦＴ回路によりフーリエ変換された信号
により増幅率の変更を行なうように構成したので、短時
間で増幅回路の増幅率を細かく決定でき、かつ受信感度
を高くできる。Further, there is provided an FFT circuit for performing a Fourier transform of the digital signal output from the A / D converter, and the first control circuit tentatively determines the amplification factor based on the digital signal before the Fourier transform is performed by the FFT circuit. However, since the second control circuit is configured to change the amplification factor based on the signal subjected to the Fourier transform by the FFT circuit, the amplification factor of the amplification circuit can be finely determined in a short time, and the reception sensitivity can be increased.
【００４２】この発明の配電線搬送用の通信装置は、以
上のディジタル通信装置を用い、商用電源ラインを伝送
路として用いているので、家電電機機器の制御などに使
用できる。Since the communication apparatus for conveying distribution lines of the present invention uses the above-described digital communication apparatus and uses a commercial power supply line as a transmission line, it can be used for controlling home electric appliances and the like.
【００４３】また、配電線を拝送される信号の周波数は
複数としたので、安定した通信が可能となる。Further, since the frequency of the signal transmitted through the distribution line is plural, stable communication is possible.
【図１】 この発明の実施の形態１のディジタル通信装
置で配電線搬送用に複数周波数で通信するものの構成を
示すブロック図である。FIG. 1 is a block diagram showing a configuration of a digital communication device according to a first embodiment of the present invention which communicates at a plurality of frequencies for distribution line conveyance.
【図２】 図１の通信装置のフレームの構成を説明する
図である。FIG. 2 is a diagram illustrating a configuration of a frame of the communication device in FIG. 1;
【図３】 ＡＧＣ増幅回路の増幅率の選択組み合わせを
説明する図である。FIG. 3 is a diagram illustrating a selective combination of amplification factors of an AGC amplifier circuit.
【図４】 図１の通信装置のＡＧＣ制御動作の例を示す
図である。FIG. 4 is a diagram illustrating an example of an AGC control operation of the communication device in FIG. 1;
【図５】 図１の通信装置のＡＧＣ制御動作のフローチ
ャートである。FIG. 5 is a flowchart of an AGC control operation of the communication device of FIG. 1;
【図６】 図５のＡＧＣ制御動作における飽和判定動作
を説明するための図である。6 is a diagram for explaining a saturation determination operation in the AGC control operation of FIG.
【図７】 図１の通信装置のノイズの大小と信号レベル
との関連を示す図である。7 is a diagram showing the relationship between the magnitude of noise and the signal level of the communication device of FIG. 1;
【図８】 従来の広帯域ディジタル受信機の構成を示す
構成概要図である。FIG. 8 is a schematic configuration diagram showing a configuration of a conventional wideband digital receiver.
１ フレーミング回路、 ２ 一次変調回路、 ３ トー
ン選択器、４ ＩＦＦＴ処理、 ５ パラレル／シリア
ル変換回路、６ Ｄ／Ａコンバータ、 ７ 結合回路、
８ 配電線伝送路、１０ 制御回路、 １０ａ第一の
制御回路、 １０ｂ 第二の制御回路、１１ デフレー
ミング回路、 １２ 一次復調回路、１３ トーン選
択器、 １４ ＦＦＴ処理、１５ シリアル／パラレル
変換回路、 １６ Ａ/ Ｄ変換器、１７ ＡＧＣ回路。1 framing circuit, 2 primary modulation circuit, 3 tone selector, 4 IFFT processing, 5 parallel / serial conversion circuit, 6 D / A converter, 7 coupling circuit,
8 distribution line transmission line, 10 control circuit, 10a first control circuit, 10b second control circuit, 11 deframing circuit, 12 primary demodulation circuit, 13 tone selector, 14 FFT processing, 15 serial / parallel conversion circuit, 16 A / D converter, 17 AGC circuit.
───────────────────────────────────────────────────── フロントページの続き Ｆターム(参考） 5J022 AA01 BA02 BA08 BA10 CC01 CC04 CD02 CF02 5K046 AA03 BA06 BB05 CC06 DD13 DD15 DD25 ──────────────────────────────────────────────────続 き Continued on the front page F term (reference) 5J022 AA01 BA02 BA08 BA10 CC01 CC04 CD02 CF02 5K046 AA03 BA06 BB05 CC06 DD13 DD15 DD25
Claims (6)
アナログ信号を増幅する増幅回路、 前記増幅回路の出力側に接続されたＡ／Ｄコンバータ、 前記増幅回路から前記Ａ／Ｄコンバータに入力される信
号の大きさが、前記Ａ／Ｄコンバータのダイナミックレ
ンジに対してあらかじめ定めた所定の値になるように前
記増幅回路の増幅率を制御する第一の制御回路、 前記Ａ／Ｄコンバータの出力信号から、前記搬送周波数
の周波数成分の信号を抽出し、この抽出した信号のレベ
ルをあらかじめ定めた所定のレベルと比較し、その結果
にもとづき前記増幅回路の増幅率を制御する第二の制御
回路を備えたことを特徴とするディジタル通信装置。Amplifying circuit for amplifying an analog signal inputted from the outside at a predetermined carrier frequency, an A / D converter connected to an output side of the amplifying circuit, and input from the amplifying circuit to the A / D converter. A first control circuit for controlling an amplification factor of the amplifying circuit so that a magnitude of the signal becomes a predetermined value predetermined with respect to a dynamic range of the A / D converter; A second control circuit that extracts a signal of the frequency component of the carrier frequency from the signal, compares the level of the extracted signal with a predetermined level, and controls the amplification factor of the amplifier circuit based on the result. A digital communication device comprising:
な増幅率を持ち、前記第一の制御回路は前記増幅回路が
設定可能な全ての増幅率の段階の中から選択した互いに
隣接しない複数の増幅率の値により前記増幅回路を制御
し、前記第二の制御回路は前記全ての増幅率の中から選
択した増幅率の値で制御することを特徴とする請求項１
に記載のディジタル通信装置。2. The amplifying circuit has a discontinuous gain that varies stepwise, and the first control circuit is not adjacent to each other selected from all gain stages that can be set by the amplifying circuit. 2. The amplification circuit according to claim 1, wherein the amplification circuit is controlled by a plurality of amplification factors, and the second control circuit is controlled by an amplification factor selected from all the amplification factors.
A digital communication device according to claim 1.
増幅率を制御する際、増幅率の大きい方から開始して前
記Ａ／Ｄコンバータの出力の飽和程度を観測し、その観
測結果にもとづいて、制御する増幅率を順次低い方へ移
行することを特徴とする請求項１に記載のディジタル通
信装置。3. The first control circuit, when controlling the amplification factor of the amplifier circuit, starts from the one with the larger amplification factor and observes the degree of saturation of the output of the A / D converter. 2. The digital communication device according to claim 1, wherein the amplification factor to be controlled is sequentially shifted to a lower one based on the control signal.
バータから出力されたディジタル信号をフーリエ変換す
るＦＦＴ回路によりフーリエ変換された信号中から搬送
波周波数の成分の信号を抽出し、この信号の大きさを予
め定めた所定のレベルと比較した結果にもとづいて、前
記増幅回路の増幅率を制御するように構成したことを特
徴とする請求項１〜３のいずれか一項に記載の通信装
置。4. The second control circuit extracts a carrier frequency component signal from a signal Fourier-transformed by an FFT circuit that Fourier-transforms the digital signal output from the A / D converter. The communication according to any one of claims 1 to 3, wherein an amplification factor of the amplification circuit is controlled based on a result of comparing a magnitude of the amplification with a predetermined level. apparatus.
路から所定の搬送周波数で入力されたアナログ信号を増
幅する増幅回路、 前記増幅回路の出力側に接続されたＡ／Ｄコンバータ、 前記増幅回路から前記Ａ／Ｄコンバータに入力される信
号の大きさが、前記Ａ／Ｄコンバータのダイナミックレ
ンジに対してあらかじめ定めた所定の値になるように前
記増幅回路の増幅率を制御する第一の制御回路、 前記Ａ／Ｄコンバータの出力信号から、前記搬送周波数
の周波数成分の信号を抽出し、この抽出した信号のレベ
ルをあらかじめ定めた所定のレベルと比較し、その結果
にもとづき前記増幅回路の増幅率を制御する第二の制御
回路を備えたディジタル通信装置を用いた配電線搬送用
の通信装置。5. A coupling circuit connected to a distribution line, an amplification circuit for amplifying an analog signal input from the coupling circuit at a predetermined carrier frequency, an A / D converter connected to an output side of the amplification circuit, the amplification A first method of controlling an amplification factor of the amplifier circuit so that a signal input from the circuit to the A / D converter has a predetermined value predetermined with respect to a dynamic range of the A / D converter. A control circuit, extracting a signal of the frequency component of the carrier frequency from an output signal of the A / D converter, comparing the level of the extracted signal with a predetermined level, and based on the result, determining whether the amplification circuit A communication device for transporting distribution lines using a digital communication device having a second control circuit for controlling an amplification factor.
周波数は複数であることを特徴とする請求項５に記載の
配電線搬送用の通信装置。6. The communication device according to claim 5, wherein the analog signal delivered to the distribution line has a plurality of frequencies.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2001153641A JP2002353813A (en) | 2001-05-23 | 2001-05-23 | Digital communication unit and communication unit for distribution line carrier using it |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2001153641A JP2002353813A (en) | 2001-05-23 | 2001-05-23 | Digital communication unit and communication unit for distribution line carrier using it |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| JP2002353813A true JP2002353813A (en) | 2002-12-06 |
Family
ID=18998130
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP2001153641A Pending JP2002353813A (en) | 2001-05-23 | 2001-05-23 | Digital communication unit and communication unit for distribution line carrier using it |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JP2002353813A (en) |
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