JP2002095259A - Power factor improvement circuit - Google Patents
Power factor improvement circuitInfo
- Publication number
- JP2002095259A JP2002095259A JP2001109994A JP2001109994A JP2002095259A JP 2002095259 A JP2002095259 A JP 2002095259A JP 2001109994 A JP2001109994 A JP 2001109994A JP 2001109994 A JP2001109994 A JP 2001109994A JP 2002095259 A JP2002095259 A JP 2002095259A
- Authority
- JP
- Japan
- Prior art keywords
- diode
- power supply
- transformer
- capacitor
- power
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
Classifications
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02P—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN THE PRODUCTION OR PROCESSING OF GOODS
- Y02P80/00—Climate change mitigation technologies for sector-wide applications
- Y02P80/10—Efficient use of energy, e.g. using compressed air or pressurized fluid as energy carrier
Landscapes
- Rectifiers (AREA)
Abstract
Description
【０００１】[0001]
【発明の属する技術分野】この発明は、インバータ装置
等のスイッチング素子を含む電力変換装置におけるノイ
ズ低減のための力率改善回路に関する。The present invention relates to a power factor improving circuit for reducing noise in a power conversion device including a switching element such as an inverter device.
【０００２】[0002]
【従来の技術】商用の交流電源からダイオード整流器に
入力する高調波電流は、他の電力変換装置を誤動作させ
たり、電源の進相コンデンサを焼損させるなどの問題を
発生する。このため、電力変換装置には、ダイオード整
流器に代えて、入力電流高調波を低減するための入力力
率改善回路が必要になる。2. Description of the Related Art Harmonic current input from a commercial AC power supply to a diode rectifier causes problems such as malfunctioning of other power converters and burning of a phase advance capacitor of the power supply. Therefore, the power converter requires an input power factor improvement circuit for reducing input current harmonics, instead of the diode rectifier.
【０００３】図５に力率改善回路の従来例を示す。FIG. 5 shows a conventional example of a power factor improving circuit.
【０００４】これは、交流電源１に３相リアクトル２を
介してＩＧＢＴ（絶縁ゲートバイポーラトランジスタ）
とダイオードを逆並列接続したスイッチ１１〜１６で構
成されるコンバータ３を接続し、その出力は直流電源と
してのコンデンサ４に、交流電源１の各端子にはコンデ
ンサ５〜７がそれぞれ接続される。[0004] The IGBT (insulated gate bipolar transistor) is connected to an AC power supply 1 via a three-phase reactor 2.
And a converter 3 composed of switches 11 to 16 in which diodes are connected in anti-parallel. An output of the converter 3 is connected to a capacitor 4 as a DC power supply, and capacitors 5 to 7 are connected to terminals of the AC power supply 1, respectively.
【０００５】また、コンデンサ４の電圧が指令値Ｖ*に
等しくなるように、調節器Ｒ１１には電圧指令値Ｖ*と
電圧検出値Ｖｏが入力され、掛算器Ｍ１，Ｍ２で調節器
Ｒ１１の出力に交流電圧ＶｕとＶｗを掛け合わせて相電
流指令値ｉｕ*，ｉｗ*が形成される。さらに、相電流指
令値ｉｕ*，ｉｗ*と相電流検出値ｉｕ，ｉｗを調節器Ｒ
１２，Ｒ１３に入力し、その調節演算出力をパルス幅変
調回路（ＰＷＭ）に入力し、ここでＰＷＭ信号に変換し
ドライバーＤＲを介して各スイッチ１１〜１６のゲート
に与えることにより、所望の直流電圧を得ることができ
る。Further, as the voltage of the capacitor 4 becomes equal to the command value V *, the voltage command value V * and the voltage detection value Vo is input to the regulator R11, the output of the regulator R11 in multipliers M1, M2 Are multiplied by AC voltages Vu and Vw to form phase current command values iu * and iw * . Further, the phase current command values iu * , iw * and the phase current detection values iu, iw are adjusted by the controller R
12 and R13, the output of the adjustment operation is input to a pulse width modulation circuit (PWM), where it is converted into a PWM signal, which is applied to the gates of switches 11 to 16 via a driver DR to obtain a desired direct current. Voltage can be obtained.
【０００６】図５の動作について説明する。The operation of FIG. 5 will be described.
【０００７】スイッチ１１〜１６は、電流指令値ｉ
ｕ*，ｉｗ*となるようにオン，オフ制御される。例え
ば、電流ｉｕを図の向きに増加させる場合には、スイッ
チ１４→スイッチ１５（またはスイッチ１６）、または
スイッチ１１→スイッチ１２（またはスイッチ１３）を
介して交流電源１を短絡しリアクトル２の電流を増加さ
せる。また、電流ｉｕを減少させる場合は、コンデンサ
４の電圧は交流電源電圧より大きいので、スイッチ１１
→コンデンサ４→スイッチ１５（またはスイッチ１６）
を介してリアクトル２の電流を減少させる。The switches 11 to 16 are provided with a current command value i
On / off control is performed so that u * and iw * are obtained. For example, when increasing the current iu in the direction shown in the figure, the AC power supply 1 is short-circuited via the switch 14 → the switch 15 (or the switch 16) or the switch 11 → the switch 12 (or the switch 13), and the current of the reactor 2 is changed. Increase. When the current iu is decreased, the voltage of the capacitor 4 is higher than the AC power supply voltage.
→ capacitor 4 → switch 15 (or switch 16)
Reduce the current of the reactor 2 via
【０００８】この動作を繰り返すことにより、電流ｉｕ
を正弦波状に制御できる。また、電流ｉｗも同様に動作
させることにより、正弦波状に制御できる。このとき、
電流ｉｕと電流ｉｗを１２０°ずらすことにより、電流
ｉｖは、三相電流の和がゼロになることから、電流ｉｕ
と電流ｉｗから１２０°ずれた電流となる。この結果、
電流ｉｕ，ｉｖ，ｉｗは力率１の三相入力電流とするこ
とができる。By repeating this operation, the current iu
Can be controlled in a sine wave form. In addition, the current iw can be controlled in a sine wave shape by operating in the same manner. At this time,
By shifting the current iu and the current iw by 120 °, the current iv becomes zero because the sum of the three-phase currents becomes zero.
And a current 120 ° shifted from the current iw. As a result,
The currents iu, iv, iw can be three-phase input currents with unity power factor.
【０００９】また、コンデンサ４の電圧は、電流指令値
ｉｕ*，ｉｗ*の振幅値を調節器１で調整することによ
り、制御できる。例えば、コンデンサ４の電圧を大きく
したい場合には、電流指令値ｉｕ*，ｉｗ*を大きくする
ことでコンデンサ４に充電される電流も大きくなり、コ
ンデンサ４の電圧が増加する。これに対し減少させたい
場合は、電流指令値ｉｕ*，ｉｗ*を小さくすることで、
コンデンサ４に充電される電流も小さくなり、コンデン
サ４の電圧は減少する。The voltage of the capacitor 4 can be controlled by adjusting the amplitude of the current command values iu * and iw * by the controller 1. For example, when it is desired to increase the voltage of the capacitor 4, the current charged in the capacitor 4 increases by increasing the current command values iu * and iw *, and the voltage of the capacitor 4 increases. On the other hand, if it is desired to decrease the current command values iu * and iw * ,
The current charged in the capacitor 4 also decreases, and the voltage of the capacitor 4 decreases.
【００１０】[0010]
【発明が解決しようとする課題】しかしながら、図５の
ような従来例では、制御しなければならないスイッチが
６個も必要となる。通常、ＩＧＢＴなどの半導体スイッ
チはダイオードに比べて高価であり、装置が高価格化す
るという問題を生じる。However, in the conventional example as shown in FIG. 5, as many as six switches need to be controlled. Usually, a semiconductor switch such as an IGBT is more expensive than a diode, which causes a problem that the device becomes expensive.
【００１１】また、制御のための検出回路も電流検出器
が２個（ＣＴ１，ＣＴ２）、交流電圧検出器が２個（Ｐ
Ｔ１，ＰＴ２）、直流電圧（Ｖｏ）検出器が１個、の計
５個の検出回路が必要となり、部品点数の増大により装
置の大型化と高価格化を招くことになる。Also, the control circuit includes two current detectors (CT1 and CT2) and two AC voltage detectors (P
T1, PT2) and one DC voltage (Vo) detector, a total of five detection circuits are required, and an increase in the number of parts leads to an increase in the size and cost of the device.
【００１２】したがって、この発明の課題は、力率改善
回路の構成を簡略化し、低コスト化を図ることにある。SUMMARY OF THE INVENTION Accordingly, an object of the present invention is to simplify the configuration of the power factor correction circuit and reduce the cost.
【００１３】[0013]
【課題を解決するための手段】このような課題を解決す
るため、請求項１の発明では、三相交流電源からの交流
電力を直流電力に変換する電力変換装置において、前記
三相交流電源の第１の交流端子を第１のダイオードと第
２のダイオードとの直列回路の接続点に、この直列回路
に対し第１のトランス１次巻線と第１の半導体スイッチ
と第１のトランス２次巻線との直列回路を並列に、前記
三相交流電源の第２の交流端子を第３のダイオードと第
４のダイオードとの直列回路の接続点に、この直列回路
に対し第２のトランス１次巻線と第２の半導体スイッチ
と第２のトランス２次巻線との直列回路を並列に、前記
三相交流電源の第３の交流端子を第５のダイオードと第
６のダイオードとの直列回路の接続点に、この直列回路
に対し第３のトランス１次巻線と第３の半導体スイッチ
と第３のトランス２次巻線との直列回路を並列にそれぞ
れ接続し、前記第１から第３のトランスの各１次巻線の
一方をそれぞれ第７から第９のダイオードを介して直流
電源の一方の端子に、前記第１から第３のトランスの１
次巻線の各他方をそれぞれ共通に接続して直流電源の他
方に接続したことを特徴とする。According to the first aspect of the present invention, there is provided a power converter for converting AC power from a three-phase AC power supply into DC power. A first AC terminal is connected to a connection point of a series circuit of a first diode and a second diode, and a first transformer primary winding, a first semiconductor switch, and a first transformer secondary are connected to the series circuit. A series circuit with a winding is connected in parallel, a second AC terminal of the three-phase AC power supply is connected to a connection point of a series circuit of a third diode and a fourth diode, and a second transformer 1 is connected to the series circuit. A series circuit of a secondary winding, a second semiconductor switch, and a secondary transformer secondary winding is connected in parallel, and a third AC terminal of the three-phase AC power supply is connected in series with a fifth diode and a sixth diode. At the connection point of the circuit, a third transformer is connected to this series circuit. A series circuit of a primary winding, a third semiconductor switch, and a third transformer secondary winding is connected in parallel to each other, and one of the primary windings of the first to third transformers is connected to the first winding, respectively. One terminal of the first to third transformers is connected to one terminal of the DC power supply via the seventh to ninth diodes.
The other side of the next winding is connected in common and connected to the other side of the DC power supply.
【００１４】上記第１から第３の半導体スイッチに代え
て共通の半導体スイッチを用いることができる（請求項
２の発明）。これら請求項１または２の発明において
は、前記第１から第３のトランスの１次巻線の各他方と
前記直流電源の他方との間に、各トランスの３次巻線と
第１０から第１２のダイオードとの直列接続回路を挿入
することができる（請求項３の発明）。また、これら請
求項１ないし３のいずれかの発明においては、前記直流
電源の電圧が一定となるように、前記半導体スイッチを
一定のオン，オフ比をもって駆動することができ（請求
項４の発明）、または、前記第１から第３の半導体スイ
ッチまたは共通の半導体スイッチと前記第１から第３の
トランス１次巻線との接続点を第１から第３のコンデン
サまたはこれらに共通のコンデンサの一方に、この第１
から第３のコンデンサまたはこれらに共通のコンデンサ
の他方を前記第７から第９のダイオードと直流電源との
接続点に接続することができる（請求項５の発明）。A common semiconductor switch can be used in place of the first to third semiconductor switches (claim 2). In the first or second aspect of the present invention, the tertiary winding of each transformer and the tenth to third transformers are provided between each other of the primary windings of the first to third transformers and the other of the DC power supply. A series connection circuit with twelve diodes can be inserted (the invention of claim 3). Further, in any one of the first to third aspects of the present invention, the semiconductor switch can be driven with a constant on / off ratio so that the voltage of the DC power supply is constant (the invention of the fourth aspect). Or a connection point between the first to third semiconductor switches or a common semiconductor switch and the first to third transformer primary windings is connected to a first to third capacitor or a capacitor common to these. On the other hand, this first
The third to third capacitors or the other of the common capacitors can be connected to the connection point between the seventh to ninth diodes and the DC power supply (the invention of claim 5).
【００１５】[0015]
【発明の実施の形態】図１はこの発明の実施の形態を示
すシステム構成図である。FIG. 1 is a system configuration diagram showing an embodiment of the present invention.
【００１６】三相交流端子ｕにはダイオード２０とダイ
オード２１との接続点が、ダイオード２０とダイオード
２１の他方の端子間にはトランス１７の１次巻線，ＩＧ
ＢＴ２６およびトランス１７の２次巻線が並列に、三相
交流端子ｖにはダイオード２２とダイオード２３との接
続点が、ダイオード２２とダイオード２３の他方の端子
間にはトランス１８の１次巻線，ＩＧＢＴ２６およびト
ランス１８の２次巻線が並列に、三相交流端子ｗにはダ
イオード２４とダイオード２５との接続点が、ダイオー
ド２４とダイオード２５の他方の端子間にはトランス１
９の１次巻線，ＩＧＢＴ２６およびトランス１９の２次
巻線が並列にそれぞれ接続される。トランス１７〜１９
の１次巻線の各一方は各々ダイオード２７〜２９を介し
てコンデンサ４の一方の端子に、トランス１７〜１９の
１次巻線の各他方は短絡されてコンデンサ４の他方の端
子に接続され、交流入力端子ｕ，ｖ，ｗにはコンデンサ
８，９，１０がそれぞれ接続される。また、コンデンサ
４の電圧が指令値Ｖ*となるように、調節器Ｒ１４には
電圧指令値Ｖ*と電圧検出値Ｖｏが入力され、調節器Ｒ
１４の出力はＰＷＭ信号に変換され、ドライバーＤＲを
介してＩＧＢＴ２６のゲートに入力される。A connection point between the diode 20 and the diode 21 is connected to the three-phase AC terminal u, and a primary winding of the transformer 17 and the IG are connected between the other terminals of the diode 20 and the diode 21.
The BT 26 and the secondary winding of the transformer 17 are connected in parallel, the connection point of the diode 22 and the diode 23 is connected to the three-phase AC terminal v, and the primary winding of the transformer 18 is connected between the diode 22 and the other terminal of the diode 23. , IGBT 26 and the secondary winding of the transformer 18 are connected in parallel, the connection point of the diode 24 and the diode 25 is connected to the three-phase AC terminal w, and the transformer 1 is connected between the other terminal of the diode 24 and the diode 25.
9 are connected in parallel with the IGBT 26 and the secondary winding of the transformer 19, respectively. Transformers 17-19
Is connected to one terminal of the capacitor 4 via diodes 27 to 29, and the other of the primary windings of the transformers 17 to 19 is short-circuited and connected to the other terminal of the capacitor 4. , AC input terminals u, v, w are connected to capacitors 8, 9, 10 respectively. Further, as the voltage of the capacitor 4 becomes the command value V *, the voltage command value V * and the voltage detection value Vo is input to the regulator R14, regulator R
The output of 14 is converted into a PWM signal and input to the gate of the IGBT 26 via the driver DR.
【００１７】図２に図１の動作波形を示す。FIG. 2 shows the operation waveforms of FIG.
【００１８】いま、例えば時刻Ｔ１でＩＧＢＴ２６がオ
ンすると、交流電源ｕ端子→ダイオード２０→トランス
１７の１次巻線→ＩＧＢＴ２６→トランス１８の２次巻
線→ダイオード２３→交流電源ｖ端子の経路と、交流電
源ｕ端子→ダイオード２０→トランス１７の１次巻線→
ＩＧＢＴ２６→トランス１９の２次巻線→ダイオード２
５→交流電源ｗ端子の経路に電流を流す。このとき、各
相電流値ｉｕ，ｉｖ，ｉｗとすると、相電流は三相電流
であるため、以下の関係が成立する。Now, for example, when the IGBT 26 is turned on at time T1, the path of the AC power supply u terminal → the diode 20 → the primary winding of the transformer 17 → the IGBT 26 → the secondary winding of the transformer 18 → the diode 23 → the AC power supply v terminal , AC power supply u terminal → diode 20 → primary winding of transformer 17 →
IGBT 26 → secondary winding of transformer 19 → diode 2
5 → Current flows through the path of the AC power supply w terminal. At this time, if each phase current value is iu, iv, iw, the following relationship is established because the phase current is a three-phase current.
【００１９】 ｉｕ＋ｉｖ＋ｉｗ＝０ ……（１） また、トランス１７〜１９の励磁インダクタンスの値を
同じ値とすることにより、ｉｖとｉｗの電流値は相電圧
ｖｖとｖｗに比例する電流に分流される。つまり、ｉ
ｕ，ｉｖ，ｉｗは相電圧にｖｕ，ｖｖ，ｖｗに比例した
電流となる。Iu + iv + iw = 0 (1) By setting the values of the exciting inductances of the transformers 17 to 19 to the same value, the current values of iv and iw are divided into currents proportional to the phase voltages vv and vw. . That is, i
u, iv, and iw are currents proportional to the phase voltages vu, vv, and vw.
【００２０】次に、時刻Ｔ２でＩＧＢＴ２６がオフする
とリアクトル電流は、トランス１７の１次巻線→コンデ
ンサ４→ダイオード２７→トランス１７の１次巻線と、
トランス１８の１次巻線→コンデンサ４→ダイオード２
７→トランス１８の１次巻線と、トランス１９の１次巻
線→コンデンサ４→ダイオード２７→トランス１９の１
次巻線との経路でコンデンサ４を充電し、電流が減少す
る。このとき、トランス１８，１９の２次巻線に流れて
いた電流は１次巻線に移されて、コンデンサ４を充電す
る。Next, when the IGBT 26 is turned off at time T2, the reactor current is changed from the primary winding of the transformer 17, the capacitor 4, the diode 27, and the primary winding of the transformer 17,
Primary winding of transformer 18 → capacitor 4 → diode 2
7 → primary winding of transformer 18 and primary winding of transformer 19 → capacitor 4 → diode 27 → transformer 1
The capacitor 4 is charged in the path to the next winding, and the current decreases. At this time, the current flowing in the secondary windings of the transformers 18 and 19 is transferred to the primary winding, and charges the capacitor 4.
【００２１】また、交流電圧にｖｕ，ｖｖ，ｖｗの極性
が反対の場合は、ＩＧＢＴがオンのとき１次巻線に流し
ていた電流が２次に、２次巻線に流していた電流が１次
側にと入れ替わるだけで、同じ動作となる。したがっ
て、この動作を繰り返すことにより、交流電源を流れる
電流は正弦波状になる。When the polarity of vu, vv, vw is opposite to the AC voltage, the current flowing in the primary winding when the IGBT is on is secondarily, and the current flowing in the secondary winding is second. The same operation is performed simply by switching to the primary side. Therefore, by repeating this operation, the current flowing through the AC power supply becomes sinusoidal.
【００２２】電流値は入力電圧値によって大きさが制御
されるため、ＩＧＢＴはコンデンサ４の電圧を制御する
一定のオン，オフ比で駆動すれば良い。つまり、各相電
流を個別に制御することが不要である。具体的には、調
節器Ｒ１４に電圧指令値ｖ*と電圧検出値ｖｏを入力
し、その出力をＰＷＭ回路で一定のオン，オフ比に変換
し、その出力によりドライバーＤＲを介してＩＧＢＴ２
６のゲートを駆動すれば良いわけである。さらに、図２
の動作波形はオフ時に電流が零になるときの波形を示し
たが、零にならなくても電流の増加分は入力電圧に比例
するため正弦波状になり、入力高調波規格を満足させる
ことができる。Since the magnitude of the current value is controlled by the input voltage value, the IGBT may be driven at a constant on / off ratio for controlling the voltage of the capacitor 4. That is, it is not necessary to control each phase current individually. Specifically, the voltage command value v * and the voltage detection value vo are input to the controller R14, and the output is converted to a constant on / off ratio by a PWM circuit, and the output is used to output the IGBT2 via the driver DR.
That is, it is only necessary to drive the sixth gate. Further, FIG.
The operation waveform of the above shows the waveform when the current becomes zero when off, but even if it does not become zero, the increase in the current is proportional to the input voltage and becomes a sine wave, which can satisfy the input harmonic specification. it can.
【００２３】図３に、この発明の第２の実施の形態を示
す。図１との相違点は、各トランス１７〜１９の１次巻
線と直列に３次巻線およびダイオード３０〜３２を接続
した点である。FIG. 3 shows a second embodiment of the present invention. The difference from FIG. 1 is that a tertiary winding and diodes 30 to 32 are connected in series with the primary windings of the transformers 17 to 19.
【００２４】このような構成で、ＩＧＢＴ２６がオンし
ているときの動作は、図１の場合と同じである。ＩＧＢ
Ｔ２６がオフしているときは、各トランスの１次巻線→
３次巻線→ダイオード３０（または３１，３２）→コン
デンサ４→ダイオード２７（または２８，２９）の経路
で、コンデンサ４を充電する。このとき、各巻線の電圧
はコンデンサ電圧を１次巻線と３次巻線で分圧した電圧
となる。In such a configuration, the operation when the IGBT 26 is on is the same as that in FIG. IGB
When T26 is off, primary winding of each transformer →
The capacitor 4 is charged through the route of the tertiary winding → the diode 30 (or 31, 32) → the capacitor 4 → the diode 27 (or 28, 29). At this time, the voltage of each winding is a voltage obtained by dividing the capacitor voltage by the primary winding and the tertiary winding.
【００２５】１次巻線と２次巻線は、励磁インダクタン
スを同じにするため同じ巻数であり、１次巻線と同じ電
圧が発生する。ＩＧＢＴ２６に印加される電圧は、１次
巻線電圧，２次巻線電圧および三相線間電圧ｖｌを加え
た値となる。したがって、図１の回路では、１次巻線と
２次巻線にはコンデンサ４の電圧ｖｃが発生しているた
め、次の（２）式のような電圧が印加されるが、図３の
回路では、３次巻線で分圧された次の（３）式のような
電圧になる。The primary winding and the secondary winding have the same number of turns to make the same excitation inductance, and generate the same voltage as the primary winding. The voltage applied to the IGBT 26 has a value obtained by adding the primary winding voltage, the secondary winding voltage, and the three-phase line voltage vl. Therefore, in the circuit of FIG. 1, since the voltage vc of the capacitor 4 is generated in the primary winding and the secondary winding, a voltage as shown in the following equation (2) is applied. In the circuit, the voltage obtained by the voltage dividing by the tertiary winding is expressed by the following equation (3).
【００２６】 ｖｃ×（１＋１）＋ｖｌ→ＩＧＢＴ２６の印加電圧 ……（２） ｖｃ×（１＋１）×[１次巻線数／（１次巻線数＋３次巻線数）]＋ｖｌ →ＩＧＢＴ２６の印加電圧 ……（３） 図４に、この発明の第３の実施の形態を示す。図３との
相違点は、ＩＧＢＴ２６とコンデンサ４との間にコンデ
ンサ３４を接続した点にある。なお、図４には、回路中
に寄生するトランスの漏れインダクタンスおよび配線イ
ンダクタンス３３が、模式的に書き加えられている。Vc × (1 + 1) + v1 → applied voltage of IGBT 26 (2) vc × (1 + 1) × [number of primary windings / (number of primary windings + number of tertiary windings)] + vl → application of IGBT 26 Voltage (3) FIG. 4 shows a third embodiment of the present invention. The difference from FIG. 3 is that a capacitor 34 is connected between the IGBT 26 and the capacitor 4. In FIG. 4, the leakage inductance of the transformer and the wiring inductance 33 which are parasitic in the circuit are schematically added.
【００２７】このような構成で、ＩＧＢＴ２６がオンし
ているときの動作は図３と同じである。ただし、図示し
たトランスの漏れインダクタンスおよび配線インダクタ
ンス３３にもエネルギーが蓄積される。ＩＧＢＴ２６が
オフしているときの動作も図３と同じであるが、ＩＧＢ
Ｔ２６がオフした際、漏れインダクタンスおよび配線イ
ンダクタンス３３に蓄積されたエネルギーは、漏れイン
ダクタンスおよび配線インダクタンス３３→コンデンサ
３４→ダイオード２７（または２８，２９）の経路で蓄
積される。With such a configuration, the operation when the IGBT 26 is on is the same as that of FIG. However, energy is also stored in the leakage inductance and the wiring inductance 33 of the illustrated transformer. The operation when the IGBT 26 is off is the same as that in FIG.
When T26 is turned off, the energy stored in the leakage inductance and the wiring inductance 33 is stored in the path of the leakage inductance and the wiring inductance 33 → the capacitor 34 → the diode 27 (or 28, 29).
【００２８】また、蓄積されたエネルギーは、コンデン
サ３４→トランス１７（または１８，１９）の３次巻線
→ダイオード３０（または３１，３２）→コンデンサ４
の経路で出力側に放出される。The stored energy is transferred from the capacitor 34 → the tertiary winding of the transformer 17 (or 18, 19) → the diode 30 (or 31, 32) → the capacitor 4
It is released to the output side by the path.
【００２９】すなわち、図３のようにコンデンサ３４が
無い場合には、ＩＧＢＴ２６がオフした際にトランスの
漏れインダクタンスおよび配線インダクタンス３３に蓄
積されたエネルギーの行き場が無いことから、ＩＧＢＴ
２６にスパイク電圧が発生して素子破壊に至るおそれが
あるが、図４のようにコンデンサ３４を接続すること
で、素子破壊を防止することが可能となる。That is, when there is no capacitor 34 as shown in FIG. 3, since the leakage inductance of the transformer and the energy stored in the wiring inductance 33 when the IGBT 26 is turned off, there is no place to go.
Although there is a possibility that a spike voltage is generated at 26 and the element is destroyed, by connecting the capacitor 34 as shown in FIG. 4, it is possible to prevent the element from being destroyed.
【００３０】なお、図1，図３，図４ではＩＧＢＴ２６
を共通に設けたが、トランス１７の１次巻線，２次巻線
間には第1のＩＧＢＴ、トランス１８の１次巻線，２次
巻線間には第２のＩＧＢＴ、トランス１９の１次巻線，
２次巻線間には第３のＩＧＢＴのように、個別に設ける
ことも可能である。このとき、図４のコンデンサ３４も
共通とせずに、各ＩＧＢＴ対応に設けることができる。In FIGS. 1, 3 and 4, the IGBT 26 is used.
The first IGBT is provided between the primary and secondary windings of the transformer 17, the second IGBT and the second IGBT are provided between the primary and secondary windings of the transformer 18. Primary winding,
It is also possible to separately provide between the secondary windings, like the third IGBT. At this time, the capacitor 34 in FIG. 4 can be provided for each IGBT without being shared.
【００３１】[0031]
【発明の効果】この発明によれば、ＩＧＢＴを最終的に
は１個で構成できるため、回路が簡単になり安価とな
る。制御のための検出回路も交流電圧検出器が不要とな
るため、部品点数が減少し、小型化と低価格化を実現で
きる。また、制御回路も電流指令を出力するための掛算
器が２個不要となる。一般に、掛算器は高価なため、装
置の高価格化を招くが、本発明では制御回路の低価格化
も達成される。According to the present invention, since the IGBT can be finally constituted by one, the circuit is simplified and the cost is reduced. Since the AC voltage detector is not required for the control detection circuit, the number of components is reduced, and the size and cost can be reduced. Also, the control circuit does not need two multipliers for outputting the current command. In general, the multiplier is expensive, which results in an increase in the price of the device. However, the present invention also achieves a reduction in the cost of the control circuit.
【００３２】さらに、請求項３に係る発明によれば、請
求項１，２に係る発明のＩＧＢＴに比べて低耐圧のもの
で済む。一般に、ＩＧＢＴは高耐圧品ほど損失が大きく
高価であるため、装置を高効率，低価格化することがで
きる。Further, according to the third aspect of the present invention, the IGBT according to the first and second aspects of the present invention can have a lower breakdown voltage. In general, the higher the breakdown voltage of the IGBT, the greater the loss and the higher the cost, so that the device can be made more efficient and lower in price.
【００３３】加えて、請求項５に係る発明によれば、Ｉ
ＧＢＴのオフ時に発生するスパイク電圧を抑制でき、素
子破壊を防止することが可能となる。In addition, according to the invention of claim 5, I
Spike voltage generated when the GBT is turned off can be suppressed, and element destruction can be prevented.
【図１】この発明の第１の実施の形態を示す回路図であ
る。FIG. 1 is a circuit diagram showing a first embodiment of the present invention.
【図２】図1の動作を説明するための波形図である。FIG. 2 is a waveform chart for explaining the operation of FIG.
【図３】この発明の第２の実施の形態を示す回路図であ
る。FIG. 3 is a circuit diagram showing a second embodiment of the present invention.
【図４】この発明の第３の実施の形態を示す回路図であ
る。FIG. 4 is a circuit diagram showing a third embodiment of the present invention.
【図５】従来例を示す回路図である。FIG. 5 is a circuit diagram showing a conventional example.
１…三相交流電源、２…リアクトル、３…コンバータ回
路、４〜１０，３４…コンデンサ、１１〜１６…半導体
スイッチ、１７〜１９…トランス、２０〜２５，２７〜
３０…ダイオード、２６…ＩＧＢＴ（絶縁ゲートバイポ
ーラトランジスタ）、３３…トランスの漏れインダクタ
ンスおよび配線インダクタンス。DESCRIPTION OF SYMBOLS 1 ... Three-phase AC power supply, 2 ... Reactor, 3 ... Converter circuit, 4-10, 34 ... Capacitor, 11-16 ... Semiconductor switch, 17-19 ... Transformer, 20-25, 27-
Reference numeral 30 denotes a diode, 26 denotes an IGBT (insulated gate bipolar transistor), and 33 denotes a leakage inductance and a wiring inductance of a transformer.
Claims (5)
に変換する電力変換装置において、 前記三相交流電源の第１の交流端子を第１のダイオード
と第２のダイオードとの直列回路の接続点に、この直列
回路に対し第１のトランス１次巻線と第１の半導体スイ
ッチと第１のトランス２次巻線との直列回路を並列に、
前記三相交流電源の第２の交流端子を第３のダイオード
と第４のダイオードとの直列回路の接続点に、この直列
回路に対し第２のトランス１次巻線と第２の半導体スイ
ッチと第２のトランス２次巻線との直列回路を並列に、
前記三相交流電源の第３の交流端子を第５のダイオード
と第６のダイオードとの直列回路の接続点に、この直列
回路に対し第３のトランス１次巻線と第３の半導体スイ
ッチと第３のトランス２次巻線との直列回路を並列にそ
れぞれ接続し、前記第１から第３のトランスの各１次巻
線の一方をそれぞれ第７から第９のダイオードを介して
直流電源の一方の端子に、前記第１から第３のトランス
の１次巻線の各他方をそれぞれ共通に接続して直流電源
の他方に接続したことを特徴とする力率改善回路。1. A power converter for converting AC power from a three-phase AC power supply to DC power, wherein a first AC terminal of the three-phase AC power supply is a series circuit of a first diode and a second diode. At a connection point, a series circuit of a first transformer primary winding, a first semiconductor switch, and a first transformer secondary winding is connected in parallel to this series circuit.
A second AC terminal of the three-phase AC power supply is connected to a connection point of a series circuit of a third diode and a fourth diode, and a second transformer primary winding and a second semiconductor switch are connected to the series circuit. A series circuit with the second transformer secondary winding is connected in parallel,
A third AC terminal of the three-phase AC power supply is connected to a connection point of a series circuit of a fifth diode and a sixth diode, and a third transformer primary winding and a third semiconductor switch are connected to the series circuit. A series circuit with a third transformer secondary winding is respectively connected in parallel, and one of the primary windings of the first to third transformers is connected to a DC power supply via seventh to ninth diodes, respectively. A power factor improving circuit, wherein one of the primary windings of the first to third transformers is commonly connected to one of the terminals and connected to the other of the DC power supplies.
えて共通の半導体スイッチを用いることを特徴とする請
求項１に記載の力率改善回路。2. The power factor improving circuit according to claim 1, wherein a common semiconductor switch is used in place of said first to third semiconductor switches.
の各他方と前記直流電源の他方との間に、各トランスの
３次巻線と第１０から第１２のダイオードとの直列接続
回路を挿入したことを特徴とする請求項１または２のい
ずれかに記載の力率改善回路。3. A series connection of a tertiary winding of each transformer and a tenth to twelfth diode between each other of the primary windings of the first to third transformers and the other of the DC power supply. 3. The power factor improving circuit according to claim 1, wherein a connecting circuit is inserted.
に、前記半導体スイッチを一定のオン，オフ比をもって
駆動することを特徴とする請求項１ないし３のいずれか
に記載の力率改善回路。4. The power factor improving circuit according to claim 1, wherein the semiconductor switch is driven with a constant on / off ratio so that the voltage of the DC power supply is constant. .
は共通の半導体スイッチと前記第１から第３のトランス
１次巻線との接続点を第１から第３のコンデンサまたは
これらに共通のコンデンサの一方に、この第１から第３
のコンデンサまたはこれらに共通のコンデンサの他方を
前記第７から第９のダイオードと直流電源との接続点に
接続することを特徴とする請求項１ないし３のいずれか
に記載の力率改善回路。5. A connection point between the first to third semiconductor switches or a common semiconductor switch and the first to third transformer primary windings is connected to a first to third capacitor or a capacitor common thereto. One of these is the first to third
4. The power factor correction circuit according to claim 1, wherein the other of the capacitors or the common capacitor is connected to a connection point between the seventh to ninth diodes and a DC power supply.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2001109994A JP2002095259A (en) | 2000-07-12 | 2001-04-09 | Power factor improvement circuit |
Applications Claiming Priority (3)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2000-210795 | 2000-07-12 | ||
| JP2000210795 | 2000-07-12 | ||
| JP2001109994A JP2002095259A (en) | 2000-07-12 | 2001-04-09 | Power factor improvement circuit |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| JP2002095259A true JP2002095259A (en) | 2002-03-29 |
Family
ID=26595852
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP2001109994A Pending JP2002095259A (en) | 2000-07-12 | 2001-04-09 | Power factor improvement circuit |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JP2002095259A (en) |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| KR100440393B1 (en) * | 2002-05-27 | 2004-07-14 | 한국전기연구원 | 3 Phase Step Down AC Regulator |
Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS62160515A (en) * | 1986-01-09 | 1987-07-16 | Yutaka Denshi Kogyo:Kk | Method and device for detecting making phase of phase advance capacitor in 3-phase ac circuit |
| JPH07250471A (en) * | 1994-03-09 | 1995-09-26 | Isao Takahashi | Three-phase sine-wave input switching power circuit |
| JPH1141938A (en) * | 1997-07-23 | 1999-02-12 | Daihen Corp | Dc power supply equipment |
-
2001
- 2001-04-09 JP JP2001109994A patent/JP2002095259A/en active Pending
Patent Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS62160515A (en) * | 1986-01-09 | 1987-07-16 | Yutaka Denshi Kogyo:Kk | Method and device for detecting making phase of phase advance capacitor in 3-phase ac circuit |
| JPH07250471A (en) * | 1994-03-09 | 1995-09-26 | Isao Takahashi | Three-phase sine-wave input switching power circuit |
| JPH1141938A (en) * | 1997-07-23 | 1999-02-12 | Daihen Corp | Dc power supply equipment |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| KR100440393B1 (en) * | 2002-05-27 | 2004-07-14 | 한국전기연구원 | 3 Phase Step Down AC Regulator |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| US6072707A (en) | High voltage modular inverter | |
| US9712070B2 (en) | Power conversion device | |
| Kolar et al. | VIENNA rectifier II-a novel single-stage high-frequency isolated three-phase PWM rectifier system | |
| JP5457449B2 (en) | Power converter | |
| Welchko et al. | A three-level MOSFET inverter for low-power drives | |
| JP6206502B2 (en) | Power conversion device and power conversion method | |
| JP2539538B2 (en) | DC / AC power converter | |
| US20090040800A1 (en) | Three phase rectifier and rectification method | |
| WO2011033698A1 (en) | Power converter | |
| US20040004852A1 (en) | Utilizing zero-sequence switchings for reversible converters | |
| US20150016167A1 (en) | Multilevel Converter | |
| JP3478700B2 (en) | Three-phase power factor improving converter | |
| JP3584686B2 (en) | Voltage source power conversion circuit | |
| JP4765006B2 (en) | Power conversion system | |
| JP4178331B2 (en) | Serial multiple pulse width modulation cycloconverter device and control method thereof | |
| WO2002063755A1 (en) | A waveform converting method and apparatus | |
| US11152870B2 (en) | Power conversion device | |
| JP2002095259A (en) | Power factor improvement circuit | |
| JPH04334977A (en) | Power converter | |
| JPS63268470A (en) | Power convertor | |
| JP2001314086A (en) | Ac-dc converter | |
| JP2014054152A (en) | Power conversion device and power control device | |
| WO2022254746A1 (en) | Power conversion device | |
| JPH0746847A (en) | Three-phase rectifier | |
| JP4448294B2 (en) | Power converter |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| A621 | Written request for application examination |
Free format text: JAPANESE INTERMEDIATE CODE: A621 Effective date: 20061017 |
|
| A977 | Report on retrieval |
Free format text: JAPANESE INTERMEDIATE CODE: A971007 Effective date: 20091105 |
|
| A131 | Notification of reasons for refusal |
Free format text: JAPANESE INTERMEDIATE CODE: A131 Effective date: 20091110 |
|
| A02 | Decision of refusal |
Free format text: JAPANESE INTERMEDIATE CODE: A02 Effective date: 20100316 |