EP3718165B1 - Hochfrequenzselektivitätsfilter für mikrowellensignale - Google Patents

Hochfrequenzselektivitätsfilter für mikrowellensignale Download PDF

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Publication number
EP3718165B1
EP3718165B1 EP18826107.7A EP18826107A EP3718165B1 EP 3718165 B1 EP3718165 B1 EP 3718165B1 EP 18826107 A EP18826107 A EP 18826107A EP 3718165 B1 EP3718165 B1 EP 3718165B1
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rectangular waveguide
transversal
plane
coupling
folded
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French (fr)
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EP3718165A1 (de
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Walter STEFFE'
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Thales Alenia Space Italia SpA
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Thales Alenia Space Italia SpA
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/207—Hollow waveguide filters
    • H01P1/208—Cascaded cavities; Cascaded resonators inside a hollow waveguide structure

Definitions

  • the present invention relates, in general, to a microwave filter and, more particularly, to a high frequency selectivity filter for microwave signals, such as those used in uplink and downlink satellite transmissions.
  • downlink channels need to be efficiently combined (multiplexed) into a high-power composite output microwave signal, which is then fed into a satellite antenna system for downlink transmission.
  • Multiplexers and demultiplexers currently used in satellite transponders typically include waveguide filters, which may be coupled in different ways depending on specific requirements.
  • Each waveguide filter is generally dedicated to separation of signal frequencies associated with a respective uplink/downlink channel.
  • the bandwidth of a typical transponder channel is a small percentage of the central operating frequency and is in close proximity with the adjacent channels.
  • the filters must meet stringent requirements in terms of frequency selectivity in order to avoid adjacent channel interference.
  • the filter design must exploit a circuit topology that permits the allocation of transmission zeros in the proximity of the lower and the upper edges of the pass-band.
  • the filter topology and the number of resonators are determined to ensure the compliance with given requirements.
  • the first design step typically includes defining an ideal circuit that comprises ideal resonators coupled by impedance inverters.
  • FIG. 1 schematically illustrates an example of ideal symmetric folded circuit of order six (in Figure 1 denoted as a whole by 1 and hereinafter referred to as "symmetric folded circuit 1").
  • the symmetric folded circuit 1 includes:
  • Each first ideal resonator 11 is transversally coupled to a respective second ideal resonator 12 by means of a respective transversal coupling (in particular, a respective impedance inverter represented in Figure 1 as a respective dotted-line segment).
  • the symmetric folded circuit 1 allows the allocation of four transmission zeros that are symmetrically placed below and above the pass-band.
  • the impedance inverters are characterized by transversal coupling values/coefficients that can be positive or negative.
  • the frequency response of the symmetric folded circuit 1 is uniquely defined by the values of all the coupling coefficients (i.e., line and transversal coupling coefficients) and by the values of the resonance frequencies associated with all the resonators 11 and 12. With proper values of these design parameters, the symmetric folded circuit 1 can provide the selective frequency response shown in Figure 2 (which is centered at 41 GHz).
  • ideal symmetric folded circuits of lower/higher orders can be defined by reducing/extending the structure of order six shown in Figure 1 .
  • the second step of the modern filter design includes the definition and the optimization of a waveguide structure such that to approximate the electrical response of the ideal circuit.
  • This second design step is rendered hard by the fact that a waveguide structure is made up of distributed elements, which behave differently than the lumped elements used in an ideal circuit. Nevertheless, with a proper selection of the waveguide structure, the two responses can be very close over a wide frequency range that covers the pass-band of interest.
  • the most common filters used in multiplexers/demultiplexers of satellite payloads are those based on dual-mode cavities in circular waveguide (in this connection, reference can be made, for example, to A. E. Atia, A. E. Williams, "Dual-Mode Canonical Waveguide Filters", IEEE Transactions on Microwave Theory and Techniques, Volume 25, Issue 12, pages 1021-1026, December 1977 ).
  • the dual-mode configuration is characterized by a compact size, a high unloaded quality factor, and a high flexibility in the realization of transversal couplings with positive and negative signs.
  • hybrid folded rectangular waveguide filter is provided in US 2016/240905 A1 , which discloses a group of rectangular waveguide resonators including first and second resonators that are arranged so that first lateral walls of the first resonator extend in parallel to second lateral walls of the second resonator.
  • the first lateral walls correspond to broad sides of a first cross section of the first resonator perpendicular to a guide direction of the first resonator.
  • the second lateral walls correspond to broad sides of a second cross section of the second resonator perpendicular to a guide direction of the second resonator.
  • the first and second resonators are further arranged so that one of the first lateral walls at least partially faces one of the second lateral walls, and the first resonator is electromagnetically coupled to the second resonator through a first aperture in the one of the first lateral walls and a second aperture in the one of the second lateral walls.
  • the single-mode filters in rectangular waveguide may present some advantages in term of a lower manufacturing complexity and a reduced number of mechanical parts.
  • the coupling coefficients with different signs are obtained using inductive and capacitive couplings in the form of irises/windows. Inductive windows are easy to manufacture and can provide a wide range of couplings.
  • capacitive irises provide really strong couplings with small gaps, since the iris itself is a section of the propagation rectangular waveguide.
  • capacitive irises do not represent the best solution for the implementation of small couplings coefficients because the corresponding slot would be difficult to make due to its small size. This problem is exacerbated at high frequencies and for filters characterized by a narrow pass-band, because the amplitudes of the transversal coupling coefficients become smaller as the bandwidth decreases.
  • an object of the present invention is that of providing a microwave filter with enhanced frequency selectivity capabilities and with a more compact structure with respect to those of the currently known solutions.
  • the first and second folded circuits are designed for operating with a TE10N resonant mode and are transversally coupled on a coupling plane that is perpendicular to a transversal plane crossing all the first and second rectangular waveguide resonators.
  • Each first rectangular waveguide resonator is:
  • each of the first and second rectangular waveguide resonators transversally coupled by means of the respective single slot is crossed by the transversal plane at a respective resonator section where magnetic field component coupled by said respective single slot is maximum.
  • each of the first and second rectangular waveguide resonators transversally coupled by means of the respective pair of slots is crossed by the transversal plane at a respective resonator section where magnetic field component coupled by said respective pair of slots is null.
  • the first and second folded circuits are symmetrical with respect to a rotation of 180 degrees around a symmetry axis defined by an intersection of the transversal and coupling planes (and, hence, lying on both said transversal and coupling planes).
  • microwave filter The following are preferred features of the microwave filter:
  • the first and second curved rectangular waveguide lines have smaller height than the first and second rectangular waveguide resonant cavities, whereby said first and second curved rectangular waveguide lines have smaller characteristic impedance than said first and second rectangular waveguide resonant cavities.
  • the microwave filter is split up, at the first and second planes of symmetry, into three parts that comprise:
  • Figure 3 shows a single-mode filter (denoted as a whole by 2) in rectangular waveguide technology according to a preferred, non-limiting embodiment of the present invention.
  • the single-mode filter 2 represents a preferred mode for carrying out the ideal symmetric folded circuit 1 of order six (with four transmission zeros allocated in the proximity of the pass-band edges) shown in Figure 1 and previously described.
  • the single-mode filter 2 includes:
  • first and second folded circuits 21 and 22 are shown spaced apart from each other only for the sake of a better understanding of their structures (conveniently, their S-shaped structures). Nevertheless, actually, said first and second folded circuits 21 and 22 are transversally coupled to each other on a coupling plane P C that is parallel to, and equidistant from, the first and second planes of symmetry P S1 and P S2 .
  • the first and second folded circuits 21 and 22 are designed for operating with a TE10N resonant mode.
  • the first folded circuit 21 comprises:
  • the first, second and third rectangular waveguide resonators 211, 212 and 213 are connected in cascade by means of first line couplings in rectangular waveguide technology, in particular:
  • the second folded circuit 22 comprises a fourth rectangular waveguide resonator (or resonant cavity) 221, a fifth rectangular waveguide resonator (or resonant cavity) 222 and a sixth rectangular waveguide resonator (or resonant cavity) 223.
  • the fourth rectangular waveguide resonator 221 is crossed (orthogonally to second folded circuit's path) by the transversal plane P T at a respective transversal waveguide section where (i.e., at which) the longitudinal magnetic field component is maximum (condition for positive transversal couplings).
  • the fifth rectangular waveguide resonator 222 is crossed (orthogonally to the second folded circuit's path) by the transversal plane P T at a respective transversal waveguide section where (i.e., at which) the longitudinal magnetic field component is null (condition for negative transversal couplings).
  • the sixth rectangular waveguide resonator 223 is crossed (orthogonally to the second folded circuit's path) by the transversal plane P T at a respective transversal waveguide section where (i.e., at which) the longitudinal magnetic field component is maximum (condition for positive transversal couplings).
  • the fourth, fifth and sixth rectangular waveguide resonators 221, 222 and 223 are connected in cascade by means of second line couplings in rectangular waveguide technology, in particular:
  • the first, second, third and fourth rectangular waveguide lines 214, 215, 224 and 225 have a first height that is smaller than a second height of the first, second, third, fourth, fifth and sixth rectangular waveguide resonant cavities 211, 212, 213, 221, 222 and 223, thereby resulting in a first characteristic impedance associated with the rectangular waveguide lines 214, 215, 224 and 225 that is smaller than a second characteristic impedance associated with the rectangular waveguide resonant cavities 211, 212, 213, 221, 222 and 223.
  • the values of the line coupling coefficients may be conveniently controlled by properly tuning the characteristic impedances (waveguide heights) associated with the line coupling waveguides with respect to those of the resonant waveguides.
  • the lengths of the line coupling waveguides may be advantageously optimized to minimize the frequency spreading (i.e., the variations in frequency domain) of the line coupling coefficients over the operating frequency band.
  • the first and second folded circuits 21 and 22 include also, each, a respective rectangular waveguide input/output port 216,226 connected to, respectively, the first/fourth rectangular waveguide resonator 211,221.
  • the first and second folded circuits 21 and 22 are symmetrical with respect to a rotation of 180 degrees around a symmetry axis A S defined by the intersection of the transversal and coupling planes P T and P C and, hence, lying on both said transversal and coupling planes P T and Pc.
  • Said first and second folded circuits 21 and 22 are transversally coupled by means of transversal coupling slots (or apertures) lying on the coupling plane P C , in particular:
  • transversal coupling slots 23, 24 and 25 can be conveniently made in the form of apertures on the metallic wall(s) separating, respectively, the first 211 and fourth 221, the second 212 and fifth 222, and the third 213 and sixth 223 rectangular waveguide resonators.
  • the alternating signs of the transversal coupling coefficients are due to the geometrical arrangement of the two folded circuits 21 and 22 and to the special symmetry of the overall structure, which is invariant after a rotation of 180 degrees around the symmetry axis As.
  • This structure makes it possible the realization of different coupling signs using only one kind of iris, which can be advantageously selected for the best manufacturability and for the best agreement of its frequency response with the ideal coupling.
  • the aspect ratio of the transversal coupling slots 23, 24 and 25 may be advantageously selected for the best manufacturability and for a minimum frequency spreading of the transversal coupling coefficients.
  • the values of the transversal coupling coefficients may be conveniently controlled by properly tuning the size of the transversal coupling slots 23, 24 and 25.
  • the path lengths of the first and second folded circuits 21 and 22 are such that to achieve alignment of resonators fields with respect to the transversal plane P T .
  • the longitudinal magnetic field component of the resonant mode TE10N (i.e., the magnetic field component coupled by the transversal coupling slots 23, 24 and 25) is:
  • Figures 4 and 5 show examples of magnetic field lines in, respectively.
  • the longitudinal magnetic field component is null on said transversal plane P T .
  • the coupled magnetic field component (i.e., the longitudinal one) oscillates with a sinusoidal shape along the longitudinal direction (i.e., along the waveguide path represented by z axis in Figure 4 ).
  • the coupled magnetic field component achieves a couple of maximum absolute values, with opposite signs, at the centers of the two second transversal coupling slots 24, which, as previously said, are spaced apart from the transversal plane P T by a quarter of the guide wavelength (i.e., ⁇ g /4) along the longitudinal direction (i.e., along the z axis).
  • the longitudinal magnetic field component is maximum on said transversal plane P T and, hence, at the centers of said first and third transversal coupling slots 23 and 25.
  • the resonant field associated with each rectangular waveguide resonant cavity 211,212,213,221,222,223 is the TE10N mode.
  • the first index of "TE10N" i.e., 1 is related to a direction (y axis in Figures 3-5 ) that is orthogonal to the coupling plane P C and is associated with waveguide width.
  • the second index i.e., 0 is related to a direction (x axis in Figures 3-5 ) that is parallel to the coupling plane P C and is associated with waveguide height.
  • the last index i.e., N
  • N is related to the longitudinal direction ( z axis in Figures 3-5 ) parallel to (i.e.
  • the first, second and third transversal coupling slots 23, 24 and 25 located on the coupling plane P C establish a coupling between the longitudinal magnetic field components of the TE10N modes associated with adjacent resonators.
  • the longitudinal component is the only magnetic field component that is non-null on the coupling plane P C and, hence, is the magnetic field component coupled by the transversal coupling slots 23, 24 and 25.
  • the present invention might be conveniently carried out also with other technologies based on TEM mode (such as stripline or coaxial technology).
  • the transversal coupling slots would couple the transversal magnetic field component, which would be the only non-null magnetic field component on the coupling plane P C . Therefore, in this case, the transversal magnetic field component would be:
  • the magnetic field component coupled by the transversal coupling slots (e.g., the longitudinal one for TE10N-based solutions, or the transversal one for TEM-base solutions) is:
  • the electrical response of the single-mode filter 2 is in a very good agreement with the ideal response over a wide frequency region, as it is demonstrated by a comparison between a simulated frequency response of the single-mode filter 2 shown in Figure 6 and the corresponding ideal one shown in Figure 2 .
  • the configuration of the single-mode filter 2 is compatible with a clam-shell-like (or, equivalently, sandwich-like) realization (conveniently, by using a manufacturing process based on milling machines), wherein the single mode-filter 2 is split up into three parts at the first and second planes of symmetry P S1 and P S2 .
  • the single mode-filter 2 may be conveniently split up into:
  • This kind of splitting introduces a negligible degradation of the insertion loss because the electric currents associated with the TE10N resonant mode of a rectangular waveguide are null across the first and second planes of symmetry P S1 and P S2 .
  • the symmetry of the first and second folded circuits 21 and 22 is only approximate because of the presence of the transversal coupling slots 23, 24 and 25.
  • said transversal coupling slots 23, 24 and 25 are quite small in comparison with the waveguide size and, in use, generate a small perturbation of the field distribution in proximity of the first and second planes of symmetry P S1 and P S2 .
  • the electric currents across said first and second planes of symmetry P S1 and P S2 are, thence, not exactly null (as it would be in case of a perfect symmetry), but are anyway small.
  • Each of the three parts 201,202,203 is substantially a planar structure and does not present any discontinuity in the normal (out of plane) direction, except for the transversal coupling slots 23, 24 and 25. This kind of structure can be easily manufactured using a milling machine.
  • the clam-shell (or, equivalently, sandwich-like) realization as an assembly of three parts and the use of milling machines permits a substantial cost reduction with respect to a canonical dual-mode filter configuration, which must be manufactured as an assembly of a higher number of parts (typically, at least one part for each resonant cavity). This advantage becomes more evident with the increasing of the filter order and of the number of resonant cavities.
  • first and second folded circuits 21 and 22 might be conveniently based on technologies different than the rectangular waveguide one, by maintaining the same symmetry features and the same geometrical features taught by the present invention about the overall filter structure and the transversal couplings.
  • first and second folded circuits 21 and 22 might be conveniently based also on square coaxial technology, microstrip technology, stripline technology, etc.
  • the first and second folded circuits may be conveniently based on rectangular waveguide technology, or also on a different technology (such as square coaxial, microstrip or stripline technology), wherein each resonator is :
  • the first and second folded circuits might have a non-prefect symmetry with respect to a rotation of 180 degrees around the symmetry axis A S , or even not have any symmetry with respect to said axis.
  • the present invention allows to design microwave filters operating at high frequencies with a narrow pass-band, a high frequency selectivity, the allocation of multiple transmission zeros, and a good agreement of filters' electrical response with respect to the ideal one.
  • the present invention can be advantageously exploited in satellite multiplexers/demultiplexers and, more in general, for the design of microwave filters characterized by a high frequency selectivity.
  • the present invention allows to achieve the aforesaid technical advantages by means of single-mode microwave filters of the symmetric folded resonator circuit type characterized by a simple, symmetry-driven mechanism for the implementation of transversal-couplings with mixed signs.
  • the present invention provides a new technique for the realization of the transversal couplings with alternating signs.
  • different transversal coupling signs are obtained by a exploiting the symmetry of the structure and a special arrangement of the waveguide layouts. It is then possible to use inductive windows for all the transversal couplings allowing an easier manufacturability than previous designs of single-mode filters in rectangular waveguide.
  • the single-mode filter according to the present invention is well suited for a clam-shell-like (or sandwich-like) realization and can be manufactured by means of milling machines in a smaller number of parts and with a cost saving with respect to the canonical dual-mode filter configuration.

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Claims (7)

  1. Mikrowellenfilter (2), umfassend:
    • eine erste gefaltete Schaltung (21) mit einer Mehrzahl von ersten Rechteckwellenleiter-Resonatoren (211, 212, 213), die mittels erster Leitungskopplungen (214, 215) in Rechteckwellenleiter-Technik in Kaskade geschaltet sind; und
    • eine zweite gefaltete Schaltung (22) mit einer Mehrzahl von zweiten Rechteckwellenleiter-Resonatoren (221, 222, 223), die mittels zweiter Leitungskopplungen (224, 225) in Rechteckwellenleiter-Technik in Kaskade geschaltet sind;
    dadurch gekennzeichnet, dass die erste und die zweite gefaltete Schaltung (21, 22) zum Betrieb mit einer TE10N-Resonanzmode ausgestaltet sind und auf einer Kopplungsebene (Pc) transversal gekoppelt sind, die senkrecht zu einer transversalen Ebene (PT) liegt, die alle ersten und zweiten Rechteckwellenleiter-Resonatoren (211, 212, 213, 221, 222, 223) schneidet;
    wobei jeder erste Rechteckwellenleiter-Resonator (211, 212, 213):
    • von einem jeweiligen zweiten Rechteckwellenleiter-Resonator (221, 222, 223) durch eine jeweilige metallische oder metallisierte Wand getrennt ist, die auf der Kopplungsebene (Pc) liegt; und
    • transversal mit dem jeweiligen zweiten Rechteckwellenleiter-Resonator (221, 222, 223) gekoppelt ist, und zwar mittels
    - einer jeweiligen positiven transversalen Kopplung, die einen jeweiligen einzelnen Schlitz (23, 25) enthält, der durch die jeweilige metallische/metallisierte Wand hindurchgeht und in Bezug auf die transversale Ebene (PT) zentriert ist, oder
    - eine jeweilige negative transversale Kopplung, die ein jeweiliges Paar von Schlitzen (24) enthält, die durch die jeweilige metallische/metallisierte Wand hindurchgehen und symmetrisch von der transversalen Ebene (PT) um einen vordefinierten Abstand beabstandet sind;
    wobei für jede positive transversale Kopplung jedes der ersten (211, 213) und der zweiten (221, 223) Rechteckwellenleiter-Resonatoren, die mittels des jeweiligen einzelnen Schlitzes (23, 25) transversal gekoppelt sind, von der transversalen Ebene (PT) an einem jeweiligen Resonatorabschnitt geschnitten wird, an dem eine Magnetfeldkomponente, die durch den jeweiligen einzelnen Schlitz (23, 25) gekoppelt ist, maximal ist;
    und wobei für jede negative transversale Kopplung jedes der ersten (212) und der zweiten (222) Rechteckwellenleiter-Resonatoren, die mittels des jeweiligen Paars von Schlitzen (24) transversal gekoppelt sind, von der transversalen Ebene (PT) an einem jeweiligen Resonatorabschnitt geschnitten wird, an dem eine Magnetfeldkomponente, die durch das jeweilige Paar von Schlitzen (24) gekoppelt ist, Null ist.
  2. Mikrowellenfilter nach Anspruch 1, wobei die erste und die zweite gefaltete Schaltung (21, 22) symmetrisch sind in Bezug auf eine Drehung von 180 Grad um eine Symmetrieachse (As), die durch einen Schnittpunkt der transversalen Ebene und der Kopplungsebene (PT, PC) definiert ist.
  3. Mikrowellenfilter nach Anspruch 1 oder 2, wobei:
    • die erste gefaltete Schaltung (21) symmetrisch in Bezug auf eine erste Symmetrieebene (PS1) parallel zur Kopplungsebene (Pc) ist;
    • die zweite gefaltete Schaltung (22) symmetrisch in Bezug auf eine zweite Symmetrieebene (Ps2) parallel zur ersten Symmetrieebene (PS1) und zur Kopplungsebene (Pc) ist;
    • die Kopplungsebene (Pc) gleich weit von der ersten (PS1) und der zweiten (Ps2) Symmetrieebene entfernt ist;
    • jeder erste Rechteckwellenleiter-Resonator einen entsprechenden Rechteckwellenleiter-Resonanzhohlraum (211, 212, 213) enthält;
    • jeder zweite Rechteckwellenleiter-Resonator einen entsprechenden zweiten Rechteckwellenleiter-Resonanzhohlraum (221, 222, 223) enthält;
    • die ersten Leitungskopplungen erste gekrümmte Rechteckwellenleiter-Leitungen (214, 215) umfassen, die die ersten Rechteckwellenleiter-Resonanzhohlräume (211, 212, 213) in Kaskade verbinden; und
    • die zweiten Leitungskopplungen zweite gekrümmte Rechteckwellenleiter-Leitungen (224, 225) umfassen, die die zweiten Rechteckwellenleiter-Resonanzhohlräume (221, 222, 223) in Kaskade verbinden.
  4. Mikrowellenfilter nach Anspruch 3, wobei die ersten und die zweiten gekrümmten Rechteckwellenleiter-Leitungen (214, 215, 224, 225) eine geringere Höhe als die ersten und die zweiten Rechteckwellenleiter-Resonanzhohlräume (211, 212, 213, 221, 222, 223) aufweisen, wodurch die ersten und die zweiten gekrümmten Rechteckwellenleiter-Leitungen (214, 215, 224, 225) eine kleinere charakteristische Impedanz als die ersten und die zweiten Rechteckwellenleiter-Resonanzhohlräume (211, 212, 213, 221, 222, 223) aufweisen.
  5. Mikrowellenfilter nach Anspruch 3 oder 4, der an der ersten und der zweiten Symmetrieebene (PS1, PS2) in drei Teile aufgeteilt ist, die umfassen:
    • einen ersten Teil (201) mit einer ersten Symmetriehälfte der ersten gefalteten Schaltung (21);
    • einen zweiten Teil (202) mit einer zweiten Symmetriehälfte der ersten gefalteten Schaltung (21) und einer ersten Symmetriehälfte der zweiten gefalteten Schaltung (22); und
    • einen dritten Teil (203) mit einer zweiten Symmetriehälfte der zweiten gefalteten Schaltung (22) enthält;
    wobei der erste, zweite und dritte Teil (201, 202, 203) so ausgestaltet sind, dass sie aufeinander gestapelt sein können, um das Mikrowellenfilter (2) zu bilden.
  6. Vorrichtung, die für Satellitenübertragungen ausgestaltet ist und das Mikrowellenfilter (2) nach einem der vorhergehenden Ansprüche enthält.
  7. Satellit mit dem Mikrowellenfilter (2) nach einem der Ansprüche 1-5.
EP18826107.7A 2017-11-29 2018-11-29 Hochfrequenzselektivitätsfilter für mikrowellensignale Active EP3718165B1 (de)

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CN114279478B (zh) * 2021-12-24 2024-05-24 杭州电子科技大学 一种基于非厄米刻槽结构的微波传感器
CN115051133B (zh) * 2022-07-19 2023-11-17 北京星英联微波科技有限责任公司 波导宽边宽带耦合电桥

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WO2015058809A1 (en) 2013-10-25 2015-04-30 Esa European Space Agency Hybrid folded rectangular waveguide filter

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