EP1618766B1 - Starter circuit having regulated starting voltage - Google Patents

Starter circuit having regulated starting voltage Download PDF

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Publication number
EP1618766B1
EP1618766B1 EP04727829A EP04727829A EP1618766B1 EP 1618766 B1 EP1618766 B1 EP 1618766B1 EP 04727829 A EP04727829 A EP 04727829A EP 04727829 A EP04727829 A EP 04727829A EP 1618766 B1 EP1618766 B1 EP 1618766B1
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EP
European Patent Office
Prior art keywords
switch
lamp
ignition
starting
pulse transformer
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Expired - Lifetime
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EP04727829A
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German (de)
French (fr)
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EP1618766A1 (en
Inventor
Kai Arbinger
Roman Ploner
Hendrik Hein
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Tridonic GmbH and Co KG
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Tridonic GmbH and Co KG
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Publication of EP1618766A1 publication Critical patent/EP1618766A1/en
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    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/02—Details
    • H05B41/04—Starting switches
    • H05B41/042—Starting switches using semiconductor devices
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
    • Y10S—TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10S315/00—Electric lamp and discharge devices: systems
    • Y10S315/05—Starting and operating circuit for fluorescent lamp

Definitions

  • the present invention relates to circuits for generating ignition pulses for a lamp, such as a high-pressure gas discharge lamp, and to methods for generating ignition pulses for a lamp. Finally, the invention also relates to lamp ballasts having such ignition circuits.
  • Fig. 6 shown ignition circuit From the WO 97/08921 is the in Fig. 6 shown ignition circuit known.
  • Fig. 6 schematically shown ignition circuit has a magnetic ballast serving as a throttle 3, a pulse transformer 5, the secondary winding 6 is connected in series with the throttle 3 and the high-pressure gas discharge lamp 4, and the primary winding 8 is connected in series with a switching element 9, and a surge capacitor 7, wherein the surge capacitor 7 on the one hand and the series circuit of the primary winding 8 and the switching element 9 on the other hand form a parallel circuit, which in turn is connected in series with a charging resistor 13 to a controllable switch 10.
  • the controllable switch 10 is, for example, a bipolar transistor or field effect transistor driven in a rectifier bridge.
  • a Zündangeskondensator 11 and a control circuit 12 which serves to control the controllable switch 10.
  • the control circuit 12 controls the controllable switch 10 as a function of the occurrence of an ignition pulse for the high-pressure gas discharge lamp 4, wherein an ignition pulse is detected by a Zündimpulserkennung 15, which is connected to the pulse transformer 5 by a special winding 14.
  • the voltage applied to the surge capacitor 7 increases by the charging of the surge capacitor 7 via the charging resistor 13, so that the voltage applied to the lamp 4 and the Zündangeskondensator 11 voltage increases.
  • the switching voltage of the Sidac 9 it closes briefly and the surge capacitor 7 is discharged via the primary winding 8 of the pulse transformer 5 and the Sidac 9, whereby an ignition pulse is generated at the high-pressure gas discharge lamp 4, via the coupled winding 14 and the Ignition pulse detection 15 of the control circuit 12 is communicated.
  • the control circuit 12 Upon detection of an ignition pulse, the control circuit 12 immediately opens the controllable switch 10, so that the resonant circuit formed by the surge capacitor 7, the Sidac 9 and the primary winding 8 of the pulse transformer 5 swings very quickly, since this resonant circuit no new energy is supplied. As a result, the holding current of the Sidac 9 drops very quickly, which allows shortly after the opening of the switch 10, the switch 10 can be closed again, so that a fast Zündimpuls foundation can be achieved.
  • a disadvantage of this circuit is that it does not take into account that the ignition voltage decreases with the line capacitance.
  • a control unit is provided which is provided in an ignition device for gas discharge lamps, this circuit providing an ignition pulse transmission starting from a TRIAC.
  • the present invention has a technique for (continuous) controlling the firing pulse amplitude so that, due to the regulation of the firing pulse amplitude, the setpoint for the firing voltage can be set close to the lower limit of the power window required by the lamp manufacturer, thereby reducing ballast loading as the other components reduced and thus their life can be significantly increased.
  • the control unit can control the switch-on time of the switch, wherein the switch-on time is optionally selected in synchronism with a predetermined phase position of the mains voltage.
  • an ohmic resistor and / or an inductance can be connected in series with the switch.
  • the Zündimpulstransformators can serve as a choke to limit the lamp current after successful ignition of a connected lamp.
  • the invention also relates to a ballast having a circuit as described above.
  • the invention also relates to a luminaire having a ballast as described above.
  • the switch-on duration of the switch starting from a mains-phase-synchronous switch-on of the switch can be controlled in this case.
  • the switch-on time of the switch can take place synchronously with a predetermined phase position of the mains voltage.
  • Fig. 1 is schematically shown a ballast, for example, for a high-pressure gas discharge lamp.
  • the mains voltage is applied to the terminals L, N (L2), wherein an optional compensation capacitor can be connected between these mains voltage terminals L, N (central compensation in the ballast can also be provided).
  • a pulse transformer VG of the ballast with a Zündwicklung ZW and a series-connected main winding HW can be seen, the pulse transformer VG is used after the ignition of the lamp schematically illustrated as a choke for the lamp current.
  • a generally designated ZG ignition ignition
  • the Zündimpulstransformator VG thus serves as a current limiting reactor after the lamp has been started.
  • the ignition winding ZW and the main winding HW serve as soon as the lamp burns, in a conventional manner to the current limit for the lamp.
  • the igniter ZG has on the one hand a series circuit (series resonant circuit) consisting of a current limiting resistor R1, an inductance L1 and a surge capacitor C1. Furthermore, the ignition device ZG has a switch S1 (for example, a bipolar and MOSFET transistor), by the control of which the charge / discharge processes of the surge capacitor C1 can be controlled.
  • a switch S1 for example, a bipolar and MOSFET transistor
  • the switch S1 is actuated by a control unit which controls the switching on / off operations of the switch as a function of a difference between a reference voltage U Z-REF detected by a comparator and a detected actual amplitude of the ignition pulses at the lamp LA.
  • the switch S1 (preferably a semiconductor in a diode rectifier bridge) is closed to ignite, so that an ignition surge current flows through the series circuit consisting of the ignition winding ZW, the surge capacitor C1, inductance L1 and the current limiting resistor R1.
  • This surge current is transformed into the main winding HW of the ignition pulse transformer VG to an ignition voltage pulse, with which the high-pressure gas discharge lamp can be ignited.
  • the triggering of the switch S1 is carried out as a function of a detected difference between a setpoint value U Z-REF and that of the actual amplitude of the firing pulses on the lamp.
  • this control can of course be changed continuously, ie in contrast to the prior art, the switch S1 can be controlled such that it can be switched on and off arbitrarily during a network half-wave.
  • Fig. 2 and Fig. 3 illustrated how the voltage in the surge capacitor C1 and, accordingly, the ignition voltage at the terminal LA can be changed substantially arbitrarily and continuously by the on and off behavior of the switch S1.
  • This arbitrary setting of the ignition pulse voltages of the terminal LA allows the efficient compensation of the already mentioned tolerances of the ignition system (mains voltage, line capacitance, ambient temperature range, grounded or ungrounded ballast etc.).
  • This makes it possible to set the target value for the ignition pulse amplitude U Z-REF just above the lower limit of the performance window required by the lamp manufacturer for the ignition, whereby the load of the ballast can be reduced and thus the life can be significantly increased.
  • Fig. 2 the case is shown that, as usual, shortly before reaching the apex of a mains half-wave (time t 1 ) of the switch S1 is closed, whereby at least one ignition pulse to this defined phase position of the mains voltage is triggered.
  • the series circuit (series resonant circuit) of the ignition circuit responds to this closing of the switch S1 with a Stosstrom to compensate for the charge difference across the surge capacitor C1. While the switch S1 remains closed, the series resonant circuit R1, L1, C1 oscillates out and the voltage across the surge capacitor continuously adapts to the current value of the applied mains voltage.
  • the switch S1 then remains closed for a relatively long time until a time t 2 .
  • the voltage applied to the surge capacitor C follows during this total on-time tx im essentially the current value of the applied mains voltage.
  • the switch S1 is opened again, so that substantially a voltage is applied to the pulse capacitor C1 and during the opening time of the switch S1 is held, the t the value of the mains voltage at the time corresponding to the second
  • the switch-off time t 2 is only very shortly before the next switch-on time (ignition time) t 3 , the difference between the voltage across the surge capacitor C1 and the value of the mains voltage at the ignition time t 3 is relatively low, which means a relatively low surge voltage at the surge capacitor C1 and, accordingly, a low firing pulse amplitude at terminal LA will result.
  • the closer the switch-off time t 2 is to the next firing point t 3 (in other words, the longer the ignition time tx of the switch S1 is at the fixed firing point), the lower will be the resulting firing pulse amplitude at the terminal LA.
  • the ignition pulse amplitude can thus optionally be set to zero if t 2 essentially corresponds to the switch-on and ignition time t 3 or the switch S1 remains permanently switched on.
  • Fig. 3 shows the scenario that the switch S1 after a switch-on and ignition t 1 after a relatively short duty cycle tx at a time t 2 , already opened again and thus at the surge capacitor C1 this relatively high value of the mains voltage at this time t 2 , is held. If now at a subsequent ignition (equal to the switch S1) at a time t 3, one or more ignition pulses are generated, they have a large amplitude (in comparison to the scenario of Fig. 2 ), because the surge voltage, ie the difference between the voltage held on the surge capacitor C1 (substantially equal to the value of the mains voltage at time t 2 ,) and the value of the mains voltage present at the ignition time t 3 is very large.
  • the switch S1 In extreme cases, i. on the other hand, if the switch S1 is switched off in the region of the peak of a first half-wave and ignition on the other hand takes place in the region of the peak of the following half-wave, the impulse voltage on the capacitor C1 assumes the maximum value, i. about twice the peak value of the mains voltage. By reducing the switch-on of the switch S1 can thus be continuously increased, the amplitude of the ignition pulse voltage at the terminal LA.
  • the surge voltage according to the invention can exceed the peak value of the mains voltage by means of a corresponding transfer of the surge capacitor (voltage increase).
  • the invention thus goes the way that the voltage across the surge capacitor C1 is adjustable, thus ultimately set the Zündimpulsamplitude.
  • the capacity in the ignition device ZG does not have to be changed.
  • the surge voltage is set according to the exemplary embodiment by the selection of the switch-on and switch-off of the switch within a network half-wave.
  • the ignition timing and thus the switch-on time t1, t3 is specified according to the requirements of the lamp manufacturer.
  • the switch-off time t2, t2 'and thus the duty cycle tx can be changed as desired.
  • the switch in this case a MOSFET transistor M1, is connected in a semiconductor bridge with a diode D1.
  • the target value for the ignition pulse amplitude Uz ref is predetermined by a suitable choice of a resistor R6.
  • the ignition pulse voltage at terminal LA is detected via a measuring resistor R2.
  • the input U br-in serves internal functions of the ASIC.
  • the voltages V dd for the control logic itself and the voltage V ss for an output driver for the drive signal OUT for the switch S1, M1 are controlled.
  • Each zero crossing can trigger a counting process in the control logic, the current count then representing the instantaneous phase position of the mains voltage. This is particularly important for the proper timing of the switch-on and thus ignition timing according to the requirements of luminaire manufacturers.
  • the actual rule logic is implemented by means of a so-called look-up table. That is, depending on the result of Zündintensives raws U zref - U zin ) is specified in the control logic by means of a function or such a table, at which time or after which On time tx the switch S1, M2 must be closed and / or reopened by issuing a entsrpechenden signal OUT.

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  • Circuit Arrangements For Discharge Lamps (AREA)

Description

Die vorliegende Erfindung bezieht sich auf Schaltungen zur Erzeugung von Zündimpulsen für eine Lampe, wie beispielsweise eine Hochdruck-Gasentladungslampe, sowie auf Verfahren zur Erzeugung von Zündimpulsen für eine Lampe. Schließlich bezieht sich die Erfindung auch auf Lampen-Vorschaltgeräte, die derartige Zündschaltungen aufweisen.The present invention relates to circuits for generating ignition pulses for a lamp, such as a high-pressure gas discharge lamp, and to methods for generating ignition pulses for a lamp. Finally, the invention also relates to lamp ballasts having such ignition circuits.

Generell ist es die Aufgabe von gattungsgemässen Zündschaltungen, sogenannte Zündspannungs-Impulse an die Lampe abzugeben, die eine sichere Lampenzündung während einer bestimmten Phasenlage der Netzspannung gewährleisten.In general, it is the task of generic ignition circuits to deliver what are known as ignition voltage pulses to the lamp, which ensure reliable lamp ignition during a specific phase position of the mains voltage.

Aus der WO 97/08921 ist die in Fig. 6 dargestellte Zündschaltung bekannt. Die in Fig. 6 schematisch gezeigte Zündschaltung weist eine als magnetisches Vorschaltgerät dienende Drossel 3, einen Impulstransformator 5, dessen Sekundärwicklung 6 in Serie mit der Drossel 3 und der Hochdruck-Gasentladungslampe 4 geschaltet ist, und dessen Primärwicklung 8 in Serie mit einem Schaltelement 9 geschaltet ist, sowie einen Stoßkondensator 7 auf, wobei der Stoßkondensator 7 einerseits sowie die Serienschaltung aus der Primärwicklung 8 und dem Schaltelement 9 andererseits eine Parallelschaltung bilden, die ihrerseits in Serie mit einem Ladewiderstand 13 zu einem steuerbaren Schalter 10 geschaltet ist. Der steuerbare Schalter 10 ist beispielsweise ein in einer Gleichrichterbrücke angesteuerter Bipolartransistor oder Feldeffekttransistor.From the WO 97/08921 is the in Fig. 6 shown ignition circuit known. In the Fig. 6 schematically shown ignition circuit has a magnetic ballast serving as a throttle 3, a pulse transformer 5, the secondary winding 6 is connected in series with the throttle 3 and the high-pressure gas discharge lamp 4, and the primary winding 8 is connected in series with a switching element 9, and a surge capacitor 7, wherein the surge capacitor 7 on the one hand and the series circuit of the primary winding 8 and the switching element 9 on the other hand form a parallel circuit, which in turn is connected in series with a charging resistor 13 to a controllable switch 10. The controllable switch 10 is, for example, a bipolar transistor or field effect transistor driven in a rectifier bridge.

Des weiteren ist ein Zündhilfskondensator 11 sowie eine Steuerschaltung 12 vorhanden, die zur Ansteuerung des steuerbaren Schalters 10 dient. Die Steuerschaltung 12 steuert den steuerbaren Schalter 10 zeitlich abhängig von dem Auftreten eines Zündimpulses für die Hochdruck-Gasentladungslampe 4, wobei ein Zündimpuls durch eine Zündimpulserkennung 15 erfasst wird, welche mit dem Impulstransformater 5 durch eine spezielle Wicklung 14 verbunden ist.Furthermore, a Zündhilfskondensator 11 and a control circuit 12 is provided which serves to control the controllable switch 10. The control circuit 12 controls the controllable switch 10 as a function of the occurrence of an ignition pulse for the high-pressure gas discharge lamp 4, wherein an ignition pulse is detected by a Zündimpulserkennung 15, which is connected to the pulse transformer 5 by a special winding 14.

Die Funktion der in Fig. 6 gezeigten Schaltung ist dabei wie folgt:

  • Zunächst ist der steuerbare Schalter 10 offen, so dass die aus dem Stoßkondensator 7, der Primärwicklung 8 des Impulstransformators 5 und dem Sidac 9 gebildete Parallelschaltung von der an den Anschlüssen 1 anliegenden Wechselspannungsversorgung getrennt ist. Die Steuerschaltung, bspw. ein Asic, enthält vorzugsweise einen Zähler, der in Betrieb gesetzt wird, wenn ein Nulldurchgang der Netzspannung erfolgt oder die Netzspannung eine bestimmte Höhe erreicht hat, was einem bestimmten Schaltwinkel entspricht. Durch Abzählen kann festgestellt werden, wann der geforderte Schaltwinkel, d. h. die Phasenlage die durch die Hersteller von Lampen gefordert zwischen 60° EL bis 90° EL bzw. 240° EL bis 270° EL, erreicht ist. Ist die gewünschte Phasenlage erreicht, so wird der steuerbare Schalter 10 geschlossen, wobei die an dem Zündhilfskondensator 11 anliegende Spannung kurzzeitig reduziert wird, da durch das Schließen des steuerbaren Schalters 10 der Stoßkondensator 7 dem Zündhilfskondensator 11 parallel geschaltet wird. Die Sekundärwicklung 6 des Impulstransformators 5 selbst ist niederohmig.
The function of in Fig. 6 shown circuit is as follows:
  • First, the controllable switch 10 is open so that the parallel circuit formed by the surge capacitor 7, the primary winding 8 of the pulse transformer 5 and the sidac 9 is disconnected from the AC power supply applied to the terminals 1. The control circuit, for example an Asic, preferably contains a counter which is put into operation when a zero crossing of the mains voltage occurs or the mains voltage has reached a certain level, which corresponds to a specific switching angle. By counting can be determined when the required switching angle, ie the phase position required by the manufacturer of lamps between 60 ° EL to 90 ° EL or 240 ° EL to 270 ° EL, is reached. If the desired phase position is reached, then the controllable switch 10 is closed, wherein the voltage applied to the Zündhilfskondensator 11 voltage is briefly reduced, since by closing the controllable switch 10, the surge capacitor 7 is connected in parallel to the Zündhilfskondensator 11. The secondary winding 6 of the pulse transformer 5 itself is low impedance.

Nach dem Schließen des steuerbaren Schalters 10 kommt es zu dem normalen Zündverhalten, d. h. die an dem Stoßkondensator 7 anliegende Spannung steigt durch das Aufladen des Stoßkondensators 7 über den Ladewiderstand 13 an, so dass auch die an der Lampe 4 bzw. den Zündhilfskondensator 11 anliegende Spannung ansteigt. Ist die Schaltspannung des Sidac 9 erreicht, so schließt dieses kurz und der Stoßkondensator 7 wird über die Primärwicklung 8 des Impulstransformators 5 und das Sidac 9 entladen, wodurch an der Hochdruck-Gasentladungslampe 4 ein Zündimpuls gezeugt wird, der über die gekoppelte Wicklung 14 und die Zündimpulserkennung 15 der Steuerschaltung 12 mitgeteilt wird.After closing the controllable switch 10, it comes to the normal ignition behavior, d. H. the voltage applied to the surge capacitor 7 increases by the charging of the surge capacitor 7 via the charging resistor 13, so that the voltage applied to the lamp 4 and the Zündhilfskondensator 11 voltage increases. When the switching voltage of the Sidac 9 is reached, it closes briefly and the surge capacitor 7 is discharged via the primary winding 8 of the pulse transformer 5 and the Sidac 9, whereby an ignition pulse is generated at the high-pressure gas discharge lamp 4, via the coupled winding 14 and the Ignition pulse detection 15 of the control circuit 12 is communicated.

Mit Erfassen eines Zündimpulses öffnet die Steuerschaltung 12 sofort den steuerbaren Schalter 10, so dass der aus dem Stoßkondensator 7, dem Sidac 9 und der Primärwicklung 8 des Impulstransformators 5 gebildete Schwingkreis sehr schnell ausschwingt, da diesem Schwingkreis keine neue Energie zugeführt wird. Dadurch wird der Haltestrom des Sidac 9 sehr schnell unterschritten, was erlaubt, dass kurz nach dem Öffnen des Schalters 10 der Schalter 10 wieder geschlossen werden kann, so dass eine schnelle Zündimpulsfolge erreicht werden kann.Upon detection of an ignition pulse, the control circuit 12 immediately opens the controllable switch 10, so that the resonant circuit formed by the surge capacitor 7, the Sidac 9 and the primary winding 8 of the pulse transformer 5 swings very quickly, since this resonant circuit no new energy is supplied. As a result, the holding current of the Sidac 9 drops very quickly, which allows shortly after the opening of the switch 10, the switch 10 can be closed again, so that a fast Zündimpulsfolge can be achieved.

Ein Nachteil dieser Schaltung ist es, dass sie nicht berücksichtigt, dass die Zündspannung mit der Leitungskapazität sinkt.A disadvantage of this circuit is that it does not take into account that the ignition voltage decreases with the line capacitance.

Aus der EP 479351 A1 ist eine selbst anpassende Zündschaltung bekannt, die tendenziell versucht, diesem Problem abzuhelfen.From the EP 479351 A1 For example, a self-adapting ignition circuit is known which tends to remedy this problem.

Gemäß dieser Schrift sind zwei parallel zueinander schaltbare Stoßkondensatoren vorgesehen. Wenn nunmehr eine Schaltung (IV in Fig. 1) erfasst, dass die an der Lampe selbst anliegenden Zündimpulse keine ausreichende Amplitude aufweisen, wird der zweite Stoßkondensator durch Betätigung eines Schalters zu dem eigentlichen ersten Stoßkondensator parallel geschaltet, was bekanntlich die Kapazität erhöht, wodurch in einem folgenden Zündvorgang die Zündimpulsamplitude entsprechend erhöht wird.According to this document two parallel switchable surge capacitors are provided. If now a circuit (IV in Fig. 1 ) detects that the voltage applied to the lamp itself Zündimpulse not sufficient Amplitude, the second surge capacitor is connected in parallel by actuation of a switch to the actual first surge capacitor, which is known to increase the capacitance, whereby in a subsequent ignition the Zündimpulsamplitude is increased accordingly.

Der Ablauf gemäß dieser EP 479 351 A1 ist also derart, dass immer mit einem Zündvorgang unter Verwendung eines einzigen Stoßkondensators begonnen wird und für den Fall, dass die Amplitude der Zündimpulse an der Lampe nicht ausreichend sein sollte, ein zweiter Kondensator parallel geschaltet wird. Vorgesehen ist also eine diskrete Erhöhung der Kapazität und somit der Zündimpulsamplitude. Eine Verringerung der Kapazität ist dagegen nicht vorgesehen.The process according to this EP 479 351 A1 is so that it always starts with an ignition using a single surge capacitor and in the event that the amplitude of the firing pulses to the lamp should not be sufficient, a second capacitor is connected in parallel. Thus, a discrete increase in the capacity and thus the ignition pulse amplitude is provided. A reduction in capacity is not provided.

Auch wenn gemäß der EP 479 351 A1 somit ein Versuch unternommen wird, eine ausreichende Zündimpulsamplitude in der Lampe sicherzustellen, so ermöglicht dies noch keine effiziente Ausregelung der zulässigen Toleranzen des gesamten Zündsystems bezüglich

  • Netzspannungsbereich,
  • Leitungskapazität,
  • Umgebungstemperatur,
  • Einsatz von Vorschaltgeräten (verschiedene Hersteller) mit unterschiedlichen Anzapfungen und unterschiedlichem Aufbau (derzeit muss für jedes Impulszündgerät ein genaues abgestimmtes Vorschaltgerät gebaut werden), und
  • dem Unterschied zwischen geerdeten und nicht geerdeten Vorschaltgeräten.
Even if according to the EP 479 351 A1 Thus, an attempt is made to ensure a sufficient Zündimpulsamplitude in the lamp, so this does not allow efficient control of the allowable tolerances of the entire ignition system with respect
  • Mains voltage range
  • Line capacity,
  • Ambient temperature,
  • Use of ballasts (different manufacturers) with different taps and different design (currently, a precise matched ballast must be built for each pulse ignitor), and
  • the difference between grounded and ungrounded ballasts.

Aus der EP 1 196 012 A ist eine Steuereinheit bekannt, die in einer Zündvorrichtung für Gasentladungslampen vorgesehen ist, wobei diese Schaltung eine von einem TRIAC ausgehende Zündimpulsübertragung vorsieht.From the EP 1 196 012 A For example, a control unit is provided which is provided in an ignition device for gas discharge lamps, this circuit providing an ignition pulse transmission starting from a TRIAC.

Aufgabe der vorliegenden Erfindung ist es dementsprechend, eine Technik für ein verbessertes Zündystem anzugeben, die in effizienter Weise eine ausreichende Zündimpulsamplitude an der Lampe sicherstellt.Accordingly, it is an object of the present invention to provide a technique for an improved ignition system that efficiently ensures a sufficient ignition pulse amplitude at the lamp.

Genauer gesagt hat die vorliegende Erfindung eine Technik zur (kontinuierlichen) Regelung der Zündimpulsamplitude zum Ziel, derart, dass aufgrund der Regelung der Zündimpulsamplitude der Sollwert für die Zündspannung nahe an die untere Grenze des vom Lampenhersteller geforderten Leistungsfensters gelegt werden kann, wodurch die Belastung des Vorschaltgeräts swie der übrigen Bauteile verringert und somit deren Lebensdauer erheblich erhöht werden kann.More specifically, the present invention has a technique for (continuous) controlling the firing pulse amplitude so that, due to the regulation of the firing pulse amplitude, the setpoint for the firing voltage can be set close to the lower limit of the power window required by the lamp manufacturer, thereby reducing ballast loading as the other components reduced and thus their life can be significantly increased.

Genauer gesagt wird die oben angeführte Aufgabe durch die Merkmale der unabhängigen Ansprüche gelöst. Die abhängigen Ansprüche bilden in zentralen Gedanken der vorliegenden Erfindung in besonders vorteilhafter Weise weiter.More specifically, the above object is solved by the features of the independent claims. The dependent claims form in central thoughts of the present invention in a particularly advantageous manner.

Gemäß einem Aspekt der vorliegenden Erfindung ist eine Schaltung zur Erzeugung von Zündimpulsen für eine Lampe vorgesehen, die aufweist:

  • einen Zündimpulstransformator,
  • eine Einrichtung zur Zeugung von Zündimpulsen an einer Primärwicklung des Zündimpulstransformators, die in die Sekundärwicklung des Zündimpulstransformators transformiert werden, wobei die Einrichtung eine Serienschaltung bestehend aus einem Stoßkondensator und einem Schalter parallel zu der Sekundärwicklung des Zündimpulstransformators und der Lampe aufweist, wobei bei geöffnetem Schalter die Ladung in dem Stoßkondensator im Wesentlichen erhalten bleibt und bei geschlossenem Schalter sich der Stoßkondensator auf den aktuellen Momentanwert der Netzspannung auflädt. Schließlich ist noch eine Steuereinheit vorgesehen, mittels der die Ein- und Ausschaltzeitpunkte des Schalters beliebig einstellbar sind.
According to one aspect of the present invention, there is provided a circuit for generating ignition pulses for a lamp, comprising:
  • an ignition pulse transformer,
  • a means for generating ignition pulses at a primary winding of the ignition pulse transformer, which are transformed into the secondary winding of the Zündimpulstransformators, the device comprising a series circuit consisting of a surge capacitor and a switch in parallel with the secondary winding of the Zündimpulstransformators and the lamp, wherein the switch is open is essentially retained in the surge capacitor and with the switch closed, the surge capacitor is charged to the current instantaneous value of the mains voltage. Finally, a control unit is provided by means of which the on and off times of the switch are arbitrarily adjustable.

Die Steuereinheit kann die Einschaltzeitdauer des Schalters steuern, wobei der Einschaltzeitpunkt gegebenenfalls fest synchron zu einer vorgegebenen Phasenlage der Netzspannung gewählt ist.The control unit can control the switch-on time of the switch, wherein the switch-on time is optionally selected in synchronism with a predetermined phase position of the mains voltage.

Zur Strombegrenzung kann ein Ohm'scher Widerstand und/oder eine Induktivität in Serie zu dem Schalter geschaltet sein.
der Zündimpulstransformators kann nach erfolgreicher Zündung einer angeschlossenen Lampe als Drossel zur Begrenzung des Lampenstrom dienen.To limit the current, an ohmic resistor and / or an inductance can be connected in series with the switch.
the Zündimpulstransformators can serve as a choke to limit the lamp current after successful ignition of a connected lamp.

Die Erfindung bezieht sich auch auf ein Vorschaltgerät, das eine Schaltung wie oben beschrieben aufweist.The invention also relates to a ballast having a circuit as described above.

Die Erfindung bezieht sich ebenfalls auf eine Leuchte, die ein Vorschaltgerät wie oben beschrieben aufweist.The invention also relates to a luminaire having a ballast as described above.

Gemäss einem weiteren Aspekt der vorliegenden Erfindung ist ein Verfahren zur Erzeugung von Zündimpulsen für eine Lampe vorgesehen, aufweisend die folgenden Schritte:

  • Erzeugung von Zündimpulsen an einer Primärwicklung des Zündimpulstransformators, die in die Sekundärwicklung des Zündimpulstransformators transformiert werden, wobei die Zündimpulse mittels einer Serienschaltung bestehend aus einem Stosskondensator und einem Schalter parallel zu der Sekundärwicklung des Zündimpulstransformators und der Lampe erzeugt werden, und
  • durch Öffnung des Schalters die Ladung in dem Stosskondensator im Wesentlichen erhalten bleibt und bei geschlossenem Schalter sich der Stosskondensator auf den aktuellen Momentanwert der Netzspannung auflädt,
dadurch gekennzeichnet, dass
die Öffnungs- bzw. Schliesszeitpünkte des Schalters beliebig einstellbar sind.According to a further aspect of the present invention, a method is provided for generating ignition pulses for a lamp, comprising the following steps:
  • Generating ignition pulses on a primary winding of the ignition pulse transformer which are transformed into the secondary winding of the ignition pulse transformer, the ignition pulses being generated by means of a series circuit consisting of a surge capacitor and a switch in parallel with the secondary winding of the ignition pulse transformer and the lamp, and
  • by opening the switch, the charge in the surge capacitor is essentially maintained and, when the switch is closed, the surge capacitor charges up to the current instantaneous value of the mains voltage,
characterized in that
the opening or closing time points of the switch are arbitrarily adjustable.

Die Einschaltdauer des Schalters ausgehend von einem Netzphasen-synchronen Einschalten des Schalters kann dabei gesteuert werden.The switch-on duration of the switch starting from a mains-phase-synchronous switch-on of the switch can be controlled in this case.

Der Einschaltzeitpunkt des Schalters kann synchron zu einer vorgegebenen Phasenlage der Netzspannung erfolgen.The switch-on time of the switch can take place synchronously with a predetermined phase position of the mains voltage.

Weitere Merkmale, Vorteile und Eigenschaften der vorliegenden Erfindung werden nun anhand der beigefügten Figuren der Zeichnungen und anhand eines exemplarischen Ausführungsbeispiels näher erläutert.Further features, advantages and features of the present invention will now be explained in more detail with reference to the accompanying figures of the drawings and with reference to an exemplary embodiment.

Dabei zeigen:

  • Fig. 1 eine schematische Darstellung einer erfindungsgemässen Zündschaltung,
  • Fig. 2 und 3 Diagramme, die die Regelung der Zündimpulsamplitude durch Wahl der Einschaltdauer eines Schalters der Zündschaltung illustrieren,
  • Fig. 4 eine detailliertere Ansicht der Zündschaltung in Fig. 1,
  • Fig. 5 eine detaillierte Ansicht der Steuereinheit einer erfindungsgemäßen Zündschaltung, und
  • Fig. 6 eine aus der WO 97/08921 bekannte Schaltung.
Showing:
  • Fig. 1 a schematic representation of an inventive ignition circuit,
  • Fig. 2 and 3 Diagrams illustrating the control of the ignition pulse amplitude by selecting the duty cycle of a switch of the ignition circuit,
  • Fig. 4 a more detailed view of the ignition circuit in Fig. 1 .
  • Fig. 5 a detailed view of the control unit of an ignition circuit according to the invention, and
  • Fig. 6 one from the WO 97/08921 known circuit.

In Fig. 1 ist schematisch ein Vorschaltgerät beispielsweise für eine Hochdruck-Gasentladungslampe gezeigt. Die Netzspannung wird dabei an die Anschlüsse L, N(L2) angelegt, wobei zwischen diesen Netzspannungsanschlüsse L, N ein optionaler Kompensationskondensator geschaltet sein kann (es kann auch eine Zentralkompensation im Vorschaltgerät vorgesehen sein). Weiterhin ist ein Impulstransformator VG des Vorschaltgeräts mit einer Zündwicklung ZW und einer dazu in Serie geschalteten Hauptwicklung HW ersichtlich, wobei der Impulstransformator VG nach dem Zünden der schematisch dargestellten Lampe als Drossel für den Lampenstrom dient. Zwischen der Zündwicklung ZW des Impulstransformators VG und einem Anschluss für die Netzspannung N(L2) ist ein allgemein mit ZG bezeichnetes Zündgerät (Zündschaltung) vorgesehen.In Fig. 1 is schematically shown a ballast, for example, for a high-pressure gas discharge lamp. The mains voltage is applied to the terminals L, N (L2), wherein an optional compensation capacitor can be connected between these mains voltage terminals L, N (central compensation in the ballast can also be provided). Furthermore, a pulse transformer VG of the ballast with a Zündwicklung ZW and a series-connected main winding HW can be seen, the pulse transformer VG is used after the ignition of the lamp schematically illustrated as a choke for the lamp current. Between the ignition winding ZW of the pulse transformer VG and a connection for the mains voltage N (L2) a generally designated ZG ignition (ignition) is provided.

Der Zündimpulstransformator VG dient also nach erfolgtem Lampenstart als Strombegrenzungsdrossel. Die Zündwicklung ZW und die Hauptwicklung HW dienen dabei, sobald die Lampe brennt, in an sich bekannter Weise zur Strombegrenzung für die Lampe.The Zündimpulstransformator VG thus serves as a current limiting reactor after the lamp has been started. The ignition winding ZW and the main winding HW serve as soon as the lamp burns, in a conventional manner to the current limit for the lamp.

Das Zündgerät ZG weist einerseits eine Serienschaltung (Serienschwingkreis) bestehend aus einem Strombegrenzungswiderstand R1, einer Induktivität L1 sowie einem Stoßkondensator C1 auf. Weiterhin weist das Zündgerät ZG einen Schalter S1 (beispielsweise einen Bipolar- und MOSFET-Transitor) auf, durch dessen Ansteuerung die Lade-/Entladevorgänge des Stoßkondensators C1 gesteuert werden können.The igniter ZG has on the one hand a series circuit (series resonant circuit) consisting of a current limiting resistor R1, an inductance L1 and a surge capacitor C1. Furthermore, the ignition device ZG has a switch S1 (for example, a bipolar and MOSFET transistor), by the control of which the charge / discharge processes of the surge capacitor C1 can be controlled.

Der Schalter S1 wird dabei durch eine Steuereinheit betätigt, die die Ein-/Ausschaltvorgänge des Schalters abhängig von einer durch einen Komparator erfassten Differenz zwischen einer Referenzspannung UZ-REF sowie einer erfassten der tatsächlichen Amplitude der Zündimpulse an der Lampe LA ansteuert.The switch S1 is actuated by a control unit which controls the switching on / off operations of the switch as a function of a difference between a reference voltage U Z-REF detected by a comparator and a detected actual amplitude of the ignition pulses at the lamp LA.

In bekannter Weise wird zum Zünden der Schalter S1 (vorzugsweise ein Halbleiter in einer Dioden-Gleichrichterbrücke) geschlossen, so dass ein Zünd-Stoßstrom über die Serienschaltung bestehend aus der Zündwicklung ZW, dem Stoßkondensator C1, Induktivität L1 sowie dem Strombegrenzungswiderstand R1 fließt. Dieser Stoßstrom wird in die Hauptwicklung HW des Zündimpulstransformators VG zu einem Zündspannungsimpuls transformiert, mit welchem die Hochdruck-Gasentladungslampe gezündet werden kann.In a known manner, the switch S1 (preferably a semiconductor in a diode rectifier bridge) is closed to ignite, so that an ignition surge current flows through the series circuit consisting of the ignition winding ZW, the surge capacitor C1, inductance L1 and the current limiting resistor R1. This surge current is transformed into the main winding HW of the ignition pulse transformer VG to an ignition voltage pulse, with which the high-pressure gas discharge lamp can be ignited.

Hinsichtlich Fig. 1 ist also zu beachten, dass einerseits die Ansteuerung des Schalters S1 abhängig von einer erfassten Differenz zwischen einem Sollwert UZ-REF und dem der der tatsächlichen Amplitude der Zündimpulse an der Lampe ausgeführt wird. Andererseits kann diese Ansteuerung natürlich kontinuierlich verändert werden, d.h. im Gegensatz zum Stand der Technik kann der Schalter S1 derart angesteuert werden, dass er während einer Netzhalbwelle beliebig ein- und ausgeschaltet werden kann.Regarding Fig. 1 Thus, it should be noted that, on the one hand, the triggering of the switch S1 is carried out as a function of a detected difference between a setpoint value U Z-REF and that of the actual amplitude of the firing pulses on the lamp. On the other hand, this control can of course be changed continuously, ie in contrast to the prior art, the switch S1 can be controlled such that it can be switched on and off arbitrarily during a network half-wave.

Das Einschalten stellt dabei bekanntlich den Zündzeitpunkt dar.Switching is known to be the ignition.

Im Folgenden wird bezugnehmend auf Fig. 2 und Fig. 3 dargestellt, wie durch das Ein- und Ausschaltverhalten des Schalters S1 die Spannung im Stoßkondensator C1 und dementsprechend auch die Zündspannung an der Klemme LA im wesentlichen beliebig und kontinuierlich verändert werden kann. Diese beliebige Einstellung der Zündimpulsspannungen der Klemme LA ermöglicht die effiziente Ausregelung der bereits angeführten Toleranzen des Zündsystems (Netzspannung, Leitungskapazität, Umgebungstemperaturbereich, geerdetes oder nicht geerdetes Vorschaltgerät etc.). Dies wiederum erlaubt es, den Sollwert für die Zündimpulsamplitude UZ-REF knapp über die untere Grenze des vom Lampenhersteller geforderten Leistungsfensters für den Zündvorgang zu legen, wodurch die Belastung des Vorschaltgeräts verringert und somit die Lebensdauer erheblich erhöht werden kann.In the following, reference is made to Fig. 2 and Fig. 3 illustrated how the voltage in the surge capacitor C1 and, accordingly, the ignition voltage at the terminal LA can be changed substantially arbitrarily and continuously by the on and off behavior of the switch S1. This arbitrary setting of the ignition pulse voltages of the terminal LA allows the efficient compensation of the already mentioned tolerances of the ignition system (mains voltage, line capacitance, ambient temperature range, grounded or ungrounded ballast etc.). This, in turn, makes it possible to set the target value for the ignition pulse amplitude U Z-REF just above the lower limit of the performance window required by the lamp manufacturer for the ignition, whereby the load of the ballast can be reduced and thus the life can be significantly increased.

In Fig. 2 ist der Fall gezeigt, dass wie üblich kurz vor dem Erreichen des Scheitels einer Netzhalbwelle (Zeitpunkt t1) der Schalters S1 geschlossen wird, wodurch wenigstens ein Zündimpuls zu dieser definieren Phasenlage der Netzspannung ausgelöst wird. Die Serienschaltung (Serienschwingkreis) des Zündkreises reagiert auf dises Schliessen des Schalters S1 mit einem Stosstrom, um die Ladungsdifferenz an dem Stosskondensator C1 auszugleichen. Während der Schalter S1 geschlossen bleibt, schwingt der Serienschwingkreis R1, L1, C1 aus und die Spannung an dem Stosskondensator passt sich laufend dem aktuellen Wert der anliegenden Netzspannung an.In Fig. 2 the case is shown that, as usual, shortly before reaching the apex of a mains half-wave (time t 1 ) of the switch S1 is closed, whereby at least one ignition pulse to this defined phase position of the mains voltage is triggered. The series circuit (series resonant circuit) of the ignition circuit responds to this closing of the switch S1 with a Stosstrom to compensate for the charge difference across the surge capacitor C1. While the switch S1 remains closed, the series resonant circuit R1, L1, C1 oscillates out and the voltage across the surge capacitor continuously adapts to the current value of the applied mains voltage.

In dem Szenario von Fig. 2 bleibt der Schalter S1 dann verhältnismäßig lange bis zu einem Zeitpunkt t2 geschlossen. Die an dem Stoßkondensator C anliegende Spannung folgt während dieser gesamten Einschaltzeit tx im wesentlichen dem aktuellen Wert der anliegenden Netzspannung. Zu dem Zeitpunkt t2 wird der Schalter S1 wieder geöffnet, so dass an dem Stoßkondensator C1 im Wesentlichen eine Spannung anliegt und während der Öffnungszeit des Schalter S1 gehalten wird, die dem Wert der Netzspannung zum Zeitpunkt t2 entspricht.In the scenario of Fig. 2 the switch S1 then remains closed for a relatively long time until a time t 2 . The voltage applied to the surge capacitor C follows during this total on-time tx im essentially the current value of the applied mains voltage. At time t 2, the switch S1 is opened again, so that substantially a voltage is applied to the pulse capacitor C1 and during the opening time of the switch S1 is held, the t the value of the mains voltage at the time corresponding to the second

Da der Ausschaltzeitpunkt t2 nur sehr kurz vor dem nächstfolgenden Einschaltzeitpunkt (Zündzeitpunkt) t3 liegt, ist die Differenz zwischen der Spannung an dem Stoßkondensator C1 und dem Wert der Netzspannung zum Zündzeitpunkt t3 verhältnismäßig gering, was also eine verhältnismäßig geringe Stosspannung an dem Stosskondensator C1 und entsprechend eine geringe Zündimpulsamplitude an der Klemme LA ergeben wird. Je näher also der Ausschaltzeitpunkt t2 an den nächstfolgenden Zündzeitpunkt t3 herangeschoben wird (mit anderen Worten, je länger bei feststehendem Zündzeitpunkt die Einschaltzeitdauer tx des Schalters S1 ist), desto niedriger wird die sich ergebende Zündimpulsamplitude an der Klemme LA sein. Die Zündimpulsamplitude kann somit gegebenenfalls bis auf Null gesetzt werden, wenn t2 im Wesentlichen dem Einschalt- und Zündzeitpunkt t3 entspricht bzw. der Schalter S1 ständig eingeschaltet bleibt.Since the switch-off time t 2 is only very shortly before the next switch-on time (ignition time) t 3 , the difference between the voltage across the surge capacitor C1 and the value of the mains voltage at the ignition time t 3 is relatively low, which means a relatively low surge voltage at the surge capacitor C1 and, accordingly, a low firing pulse amplitude at terminal LA will result. Thus, the closer the switch-off time t 2 is to the next firing point t 3 (in other words, the longer the ignition time tx of the switch S1 is at the fixed firing point), the lower will be the resulting firing pulse amplitude at the terminal LA. The ignition pulse amplitude can thus optionally be set to zero if t 2 essentially corresponds to the switch-on and ignition time t 3 or the switch S1 remains permanently switched on.

Fig. 3 zeigt andererseits das Szenario, dass der Schalter S1 nach einem Einschalt- und Zündzeitpunkt t1 nach verhältnismäßig kurzer Einschaltdauer tx zu einem Zeitpunkt t2, bereits wieder geöffnet wird und somit an dem Stoßkondensator C1 dieser verhältnismäßig hohe Wert der Netzspannung zu diesem Zeitpunkt t2, gehalten wird. Wenn nunmehr bei einem folgenden Zünden (gleich Einschalten des Schalters S1) zu einem Zeitpunkt t3 ein oder mehrere Zündimpulse erzeugt werden, so weisen diese eine große Amplitude (im Vergleich zum Szenario von Fig. 2) auf, da die Stossspannung, d.h. die Differenz zwischen der am Stoßkondensator C1 gehaltenen Spannung (im wesentlichen gleich dem Wert der Netzspannung zum Zeitpunkt t2,) und der zum Zündzeitpunkt t3 vorliegenden Wert der Netzspannung sehr groß ist. Fig. 3 on the other hand shows the scenario that the switch S1 after a switch-on and ignition t 1 after a relatively short duty cycle tx at a time t 2 , already opened again and thus at the surge capacitor C1 this relatively high value of the mains voltage at this time t 2 , is held. If now at a subsequent ignition (equal to the switch S1) at a time t 3, one or more ignition pulses are generated, they have a large amplitude (in comparison to the scenario of Fig. 2 ), because the surge voltage, ie the difference between the voltage held on the surge capacitor C1 (substantially equal to the value of the mains voltage at time t 2 ,) and the value of the mains voltage present at the ignition time t 3 is very large.

Im Extremfall, d.h. wenn das Ausschalten des Schalters S1 im Bereich des Scheitels einer ersten Netzhalbwelle erfolgt und das Zünden andererseits im Bereich des Scheitels der folgenden Netzhalbwelle erfolgt, nimmt die Stoßspannung an dem Kondensator C1 den Maximalwert ein, d.h. etwa das Doppelte des Spitzenwerts der Netzspannung. Durch Verringerung der Einschaltauer des Schalters S1 kann somit kontinuierlich die Amplitude der Zündimpulsspannung an der Klemme LA erhöht werden.In extreme cases, i. on the other hand, if the switch S1 is switched off in the region of the peak of a first half-wave and ignition on the other hand takes place in the region of the peak of the following half-wave, the impulse voltage on the capacitor C1 assumes the maximum value, i. about twice the peak value of the mains voltage. By reducing the switch-on of the switch S1 can thus be continuously increased, the amplitude of the ignition pulse voltage at the terminal LA.

In jedem Fall kann die Stosspannung gemäss der Erfindung durch entsprechendes Umladen des Stosskondensators den Scheitelwert der Netzspannung überschreiten (Spannungsüberhöhung).In any case, the surge voltage according to the invention can exceed the peak value of the mains voltage by means of a corresponding transfer of the surge capacitor (voltage increase).

Die Erfindung geht also den Weg, dass die Spannung an dem Stoßkondensator C1 einstellbar ist, um somit letztendlich die Zündimpulsamplitude einzustellen. Die Kapazität im Zündgerät ZG muss dagegen nicht verändert werden. Die Stosspannung wird dabei gemässe dem Ausführungsbeispiel durch die Wahl der Einschalt- und Ausschaltzeitpunkte des Schalters innerhalb einer Netzhalbwelle festgelegt.The invention thus goes the way that the voltage across the surge capacitor C1 is adjustable, thus ultimately set the Zündimpulsamplitude. The capacity in the ignition device ZG does not have to be changed. The surge voltage is set according to the exemplary embodiment by the selection of the switch-on and switch-off of the switch within a network half-wave.

Üblicherweise ist der Zündzeitpunkt und somit der Einschaltzeitpunkt t1, t3 gemäß den Anforderungen des Lampenherstellers vorgegeben. Dagegen kann gemäß der Erfindung der Ausschaltzeitpunkt t2, t2' und somit die Einschaltdauer tx beliebig verändert werden.Usually, the ignition timing and thus the switch-on time t1, t3 is specified according to the requirements of the lamp manufacturer. In contrast, according to the invention, the switch-off time t2, t2 'and thus the duty cycle tx can be changed as desired.

Unter Bezugnahme auf Fig. 4 soll nunmehr erläutert werden, wie mit einem Microcontroller oder ASIC U1 ein derartiger Regel-/Steuervorgang für die Zündimpulsamplitude ausgeführt werden kann.With reference to Fig. 4 will now be explained, as with a microcontroller or ASIC U1 such Control / control process for the Zündimpulsamplitude can be performed.

Der Schalter, in diesem Fall ein MOSFET-Transistor M1, ist in einer Halbleiterbrücke mit einer Diode D1 geschaltet. Der Sollwert für die Zündimpulsamplitude Uzref wird durch entsprechende Wahl eines Widerstands R6 vorgegeben. An einem Anschluß Uzin des ASICS U1 wird über einen Meßwiderstand R2 die Zündimpulsspannung an der Klemme LA erfasst.The switch, in this case a MOSFET transistor M1, is connected in a semiconductor bridge with a diode D1. The target value for the ignition pulse amplitude Uz ref is predetermined by a suitable choice of a resistor R6. At a connection Uz in the ASICS U1, the ignition pulse voltage at terminal LA is detected via a measuring resistor R2.

Der Eingang Ubr-in dient internen Funktionen des ASIC.The input U br-in serves internal functions of the ASIC.

Mittels einer (an sich bekannten) externen Bandgap-Referenz werden die Spannungen Vdd für die Steuerlogik selbst sowie die Spannung Vss für einen Ausgangstreiber für das Ansteuersignal OUT für den Schalter S1, M1 geregelt.By means of a (known per se) external bandgap reference, the voltages V dd for the control logic itself and the voltage V ss for an output driver for the drive signal OUT for the switch S1, M1 are controlled.

Am Eingang Uz-in kann auch die Lampenbrennspannung erfasst werden.At the input U z-in and the lamp burning voltage can be detected.

Weiterhin kann mittels des Eingangs Uzin der Nulldurchgang der Netzspannung erfasst werden. Jeder Nulldurchgang kann in der Steuerlogik einen Zählvorgang auslösen, wobei der aktuelle Zählwert dann die momentan vorliegende Phasenlage der Netzspannung wiedergibt. Dies ist insbesondere wichtig für die ordnungsgemäße Taktung der Einschaltpunkte und somit Zündzeitpunkte gemäß den Anforderungen von Leuchtenherstellern.Furthermore, can be detected by means of the input Uz in the zero crossing of the mains voltage. Each zero crossing can trigger a counting process in the control logic, the current count then representing the instantaneous phase position of the mains voltage. This is particularly important for the proper timing of the switch-on and thus ignition timing according to the requirements of luminaire manufacturers.

In der Steuerlogik ist beispielsweise mittels einer sogenannten Look-Up-Tabelle die eigentliche Regellogik implementiert. Das heisst, abhängig von dem Ergebnis des Zündspannungsvergleichs Uzref - Uzin) ist in der Steuerlogik mittels einer Funktion bzw. einer solchen Tabelle vorgegeben, zu welchem Zeitpunkt bzw. nach welcher Einschaltzeitdauer tx der Schalter S1, M2 durch Ausgabe eines entsrpechenden Signals OUT geschlossen und/oder wieder geöffnet werden muß.In the control logic, for example, the actual rule logic is implemented by means of a so-called look-up table. That is, depending on the result of Zündspannungsvergleichs U zref - U zin ) is specified in the control logic by means of a function or such a table, at which time or after which On time tx the switch S1, M2 must be closed and / or reopened by issuing a entsrpechenden signal OUT.

Claims (9)

  1. Circuit for generating starting pulses for a lamp, having:
    - a starting pulse transformer (VG),
    - a device (ZG) for generating starting pulses at a primary winding of the starting pulse transformer (VG) which are transformed into the secondary winding of the starting pulse transformer (VG), wherein the device (ZG) has a series circuit comprising a surge capacitor (C1) and a switch (S1, M1) in parallel with the secondary winding of the starting pulse transformer (VG) and the lamp, wherein
    - when a switch (S1, M1) is open, the charge in the surge capacitor (C1) is substantially maintained and, when the switch (S1, M1) is closed, the surge capacitor (C1) is charged to the present instantaneous value for the system voltage (L, N (L2)),
    characterized in that
    a control unit is provided, by means of which the making and breaking times of the switch can be adjusted as desired.
  2. Circuit according to Claim 1, characterized in that the control unit controls the making time period of the switch, wherein the making time is selected in synchronism with a predetermined phase angle of the system voltage.
  3. Circuit according to Claim 1 or 2, characterized in that, for current limitation, a nonreactive resistor (R1) and/or an inductance (L1) are connected in series with the switch (S1, M1).
  4. Circuit according to one of the preceding claims, characterized in that the starting pulse transformer (VG), after successful starting of a connected lamp, acts as inductor for limiting the lamp current.
  5. Ballast for a lamp, characterized in that said ballast has a circuit according to one of the preceding claims.
  6. Luminaire, having a ballast according to Claim 5.
  7. Method for generating starting pulses for a lamp, having the following steps:
    - generating starting pulses at a primary winding of the starting pulse transformer (VG) which are transformed into the secondary winding of the starting pulse transformer (VG), wherein the starting pulses are generated by means of a series circuit comprising a surge capacitor (C1) and a switch (S1, M1) in parallel with the secondary winding of the starting pulse transformer (VG) and the lamp, and
    - by opening of the switch (S1, M1), the charge in the surge capacitor (C1) is substantially maintained and, when the switch (S1, M1) is closed, the surge capacitor (C1) is charged to the present instantaneous value for the system voltage,
    characterized in that
    the opening or closing times of the switch (S1, M1) can be adjusted as desired.
  8. Method according to Claim 7, characterized in that the making period (tx) of the switch (S1, M1) is controlled starting from making of the switch (S1) in synchronism with the system phases.
  9. Method according to Claim 8, characterized in that the making time of the switch (S1, M1) is in synchronism with a predetermined phase angle of the system voltage.
EP04727829A 2003-04-30 2004-04-16 Starter circuit having regulated starting voltage Expired - Lifetime EP1618766B1 (en)

Applications Claiming Priority (2)

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DE10319511A DE10319511A1 (en) 2003-04-30 2003-04-30 Ignition circuit with regulated ignition voltage
PCT/EP2004/004064 WO2004098244A1 (en) 2003-04-30 2004-04-16 Starter circuit having regulated starting voltage

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EP1618766A1 EP1618766A1 (en) 2006-01-25
EP1618766B1 true EP1618766B1 (en) 2013-03-13

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US6452340B1 (en) * 1999-04-09 2002-09-17 Acuity Brands, Inc. Luminaire starting aid device
DE19923263A1 (en) * 1999-05-20 2000-11-23 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Circuit arrangement for igniting a lamp
IL138896A0 (en) * 2000-10-05 2001-11-25 Hashofet Eltam Ein An ignitor for discharge lamps

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AU2004234940B2 (en) 2009-06-25
EP1618766A1 (en) 2006-01-25
AU2004234940A1 (en) 2004-11-11
US7462992B2 (en) 2008-12-09
RU2347332C2 (en) 2009-02-20
DE10319511A1 (en) 2004-11-18
US20070080650A1 (en) 2007-04-12
CN1781343A (en) 2006-05-31
WO2004098244A1 (en) 2004-11-11
CN1781343B (en) 2011-06-08
RU2005137169A (en) 2006-04-10

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