EP0876077B1 - Method and apparatus for addition of signals existing as sampling values - Google Patents
Method and apparatus for addition of signals existing as sampling values Download PDFInfo
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- EP0876077B1 EP0876077B1 EP98440051A EP98440051A EP0876077B1 EP 0876077 B1 EP0876077 B1 EP 0876077B1 EP 98440051 A EP98440051 A EP 98440051A EP 98440051 A EP98440051 A EP 98440051A EP 0876077 B1 EP0876077 B1 EP 0876077B1
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- the invention relates to a method and a device for summing N> 1 band-limited time signals, each having a bandwidth ⁇ B, which are present as analog and / or digital samples, the respective sampling frequency f A > 2B.
- ADC analog-to-digital converter
- DAC digital-to-analog converter
- a linear addition of several band-limited time signals to a new sum signal occurs, inter alia, in audio technology, where audio signals are superimposed by sound mixing from several different sources, or in video technology, where video signals from two different sources to a new one Image signal are combined.
- Areas of application for sound mixing are, for example, in broadcasting, in the record industry and in the production of other sound carriers.
- a sound mixing in audio conferencing ie in a summation of multiple sound signals from different sources, in the field of telecommunications technology is required.
- Image mixing by superimposing a plurality of image signals is common, for example, in television, in the production of optical disc and image recording on other image carriers, video recorders, camcorders and the like.
- a disadvantage of the known methods is the relatively long computing time in the addition of the individual signals in a digital computer or in a hardware circuit of adder units.
- the object of the present invention is in contrast to improve a method of the type mentioned above so that the summation can be carried out with a significantly lower computational time, that optionally a variety of slow and expensive adders can be saved and that attenuation of the signals at processing and the associated loss of information is minimized.
- this object is achieved in a surprisingly simple and effective manner in that the samples of all N time signals are superimposed on one another in terms of time and shared in a low-pass filter of the filter bandwidth B '> B are entered, and that at the output of the low-pass filter, a sum signal is tapped.
- the samples become more different in the method according to the invention Time signals offset in time superimposed and implemented analogously by means of a passive low-pass filter.
- the samples of different signals, each sampled at a frequency f A are combined in a time division multiplexing to form a superimposed signal of frequency N ⁇ f A.
- an analog sum signal is then generated, which can be scanned for further processing at the frequency f A.
- a further advantage is that a device suitable for carrying out the method according to the invention can readily be integrated in an integrated circuit, for example in a VLSI chip.
- the inventive method can also be easily installed in a DSP software with a corresponding gain in computation time. The inventive method is suitable both for summation of digital and analog input values.
- a further preferred embodiment of the invention provides that the input of the temporally offset samples into the low-pass filter with a clock frequency N ⁇ f A.
- an analog low-pass filter can be used, at whose output a time-continuous sum signal appears, which produces a perfect summation of the partial signals.
- this method is further developed in that analog samples of the sum signal are obtained from the temporally continuous sum signal by sampling.
- a development of this embodiment provides that the oversampled sum signal is applied to a digital-to-analog (D / A) converter which operates at the clock frequency N ⁇ f A , and whose output signal via a post-filtering, preferably by means of an RC element, the time-continuous sum signal results.
- D / A digital-to-analog
- a very simple, cost-effective RC filter element can be used, which ensures sufficient suppression of periodically occurring in the frequency domain after a Fourier transformation mirror signals due to the oversampling.
- a higher sampling frequency by sampling rate conversion can be achieved by inserting fictitious samples "0" at intermediate points, whereby a perfect overall signal comes out at the end due to the low-pass filtering.
- the inventive method can be carried out at analog input values, when the summation and low-pass filtering is realized with a digital signal processor.
- the scope of the present invention also includes a device for summing N> 1 band-limited time signals, each having a bandwidth s B, which are present as analog and / or digital samples, wherein the respective sampling frequency f A > 2B, in which a time-division multiplex unit is provided in which are the samples of all N time signals offset in time to each other are superimposed, and in the subsequent to the time division multiplexing a low-pass filter of the filter bandwidth B '> B is provided, in which the temporally offset superimposed samples can be entered together, and at the output of a sum signal can be tapped.
- Fig. 1 a particularly simple schematic structure for the inventive summation of time signals from two different sources is shown, wherein the time signals are respectively input as samples with a sampling frequency f A.
- the sampling frequency f A must be greater than or equal to twice the bandwidth of the band-limited time signals.
- the timing signals from the two sources are input to a time division multiplexing unit 11 in which they are superimposed in temporal offset from each other.
- the sampled values of the time signals are equidistant in time, so that in the present example, the sampled values with a frequency 2 ⁇ f A emerge from the time-division multiplex unit 11. These are placed in a low pass filter 12 with a filter bandwidth B '> B entered. At the output of the low-pass filter 12 then the desired sum signal can be tapped.
- FIG. 1 An improved embodiment for the processing of digital input data is shown schematically in FIG.
- the present as digital samples in the example shown again from only two sources derived time signals of the time division multiplex unit 21 are entered, in which again a temporal offset, preferably made equidistant.
- the temporally offset signals are then supplied to a clocked in the present example with a frequency 2 ⁇ f A digital low-pass filter 22.
- the digital low-pass filter 22 Since the digital low-pass filter 22 always generates periodic continuations of the signals, which are undesirable, the sum signals are passed after passage through a digital-to-analog converter (DAC) 23 to another, but analog low-pass filter 24, which generated the small frequency components of the frequency domain Passing signals and attenuates the higher frequencies strong enough so that the unwanted periodic signal artifacts are suppressed.
- the DAC 23 is clocked in the present example as well as the digital low-pass filter 22 with a frequency 2 * f A , since only signals from two different sources, which were offset in the time division multiplexing unit 21 equidistant from each other, must be processed.
- the analog low-pass filter 24 may be a very simple, inexpensive RC element or consist of several such.
- FIGS. 3a and 3b illustrate the process of the method according to the invention schematically.
- the time signals of N sources are shown one below the other, the signals being indicated by "S", a subsequent digit for the number of the Source and another digit for the number of the sample within the initially analog signal are designated.
- These signals from N different sources are fed to the multiplex unit 31 shown schematically in FIG. 3b, in which they are superimposed with time offset from one another.
- an equidistant time offset is required, while the signals from different sources need not necessarily be equidistant time offset if a filter device or DAC can handle a correspondingly high signal processing speed.
- the resulting signal sequence at the output of time division multiplexer unit 31 is fed to a normal low pass filter 32 whose bandwidth B 'is approximately half the sampling frequency f A so that the signals of each individual source can be reconstructed from the sum signal.
- FIG. 4 schematically shows the processing of samples from initially analog signals which originate from different sources and are superimposed in time offset relative to one another in a time multiplexer unit (not shown explicitly in FIG. 4) such that there is a difference between the first sample S11 from the first source and the second sample S12 from the first source are all samples from all other sources (S21 to SN1).
- This sequence is fed to an analog low-pass filter 42, from which a corresponding continuous sum signal comes out in analog form.
- Fig. 5a shows the same process when inputting digital samples.
- the time-shifted superimposed signals are here again a low-pass filter 52, which is a digital low-pass filter, which is clocked at a frequency N ⁇ f A , supplied.
- a sum signal with digital samples of the frequency N ⁇ f A which, as shown in Fig. 5b, are supplied to a clocked with N ⁇ f A DAC 53 is formed.
- the output of the DAC 53 there are then analog samples with a frequency N ⁇ f A , which must be subjected to an analog low-pass filtering in an RC element 54 due to the above-described operation of digital low-pass filters.
- FIG. 6 shows diagrammatically how analogue signals which emerge from a time-division multiplexer unit 61 with respect to each other in time and superimposed are fed to an analogue low-pass filter 62 at whose output a sample-and-hold circuit 65 is provided.
- ADC analog-to-digital converter unit
- Fig. 7 finally shows schematically a device according to the invention with a time division multiplexing unit 71, an interpolation device 76 for insertion of "zero values" and corresponding sample rate conversion, a low pass filter 72 and a decimator 77 for selectively compacting the signal data according to the decimation method described above.
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Description
Die Erfindung betrifft ein Verfahren und eine Vorrichtung zur Summenbildung von N > 1 bandbegrenzten Zeitsignalen mit je einer Bandbreite ≤ B, die als analoge und/oder digitale Abtastwerte vorliegen, wobei die jeweilige Abtastfrequenz fA > 2B ist.The invention relates to a method and a device for summing N> 1 band-limited time signals, each having a bandwidth ≦ B, which are present as analog and / or digital samples, the respective sampling frequency f A > 2B.
Ein solches Verfahren ist aus der DE 32 00 934 A1 bekannt.Such a method is known from DE 32 00 934 A1.
Eine Summenbildung von Analogsignalen durch Addierer ist beispielsweise in dem Lehrbuch von Tietze und Schenk, "Halbleiterschaltungstechnik", 8. Auflage, 1986, Seiten 299 und 300 sowie 579 bis 581 beschrieben.A summation of analog signals by adders is described, for example, in the textbook by Tietze and Schenk, "Halbleiterschaltungstechnik", 8th edition, 1986, pages 299 and 300, and 579 to 581.
Die Aufsummierung von digitalen Signalen aus analogen Eingangssignalen mit einem zwischengeschalteten Analog-DigitalWandler (ADC) über einen digitalen Signalprozessor und einer Re-Analogisierung der verarbeiteten Signale mittels eines Digital-Analog-Wandlers (DAC) insbesondere im Bereich von Videosignalen ist beispielsweise in der EP 0 695 066 A2 beschrieben.The summation of digital signals from analog input signals with an intermediate analog-to-digital converter (ADC) via a digital signal processor and a re-analogization of the processed signals by means of a digital-to-analog converter (DAC), in particular in the range of video signals, for example, in EP 0 695 066 A2.
Eine lineare Addition von mehreren bandbegrenzten Zeitsignalen zu einem neuen Summensignal kommt unter anderem in der Audio-Technik vor, wo Audio-Signale durch Tonmischung von mehreren verschiedenen Quellen überlagert werden, oder in der Videotechnik, wo Videosignale durch Bildüberblendung von zwei verschiedenen Quellen zu einem neuen Bildsignal vereinigt werden. Anwendungsbereiche für die Tonmischung liegen beispielsweise beim Rundfunk, in der Schallplattenindustrie und bei der Herstellung anderer Tonträger. Außerdem wird eine Tonmischung bei Audio-Konferenzschaltungen, d.h. bei einer Summation von mehreren Tonsignalen verschiedener Quellen, im Bereich der Fernmeldetechnik erforderlich. Eine Bildmischung durch Überblendung mehrerer Bildsignale ist beispielsweise beim Fernsehen, bei der Herstellung von Bildplatten und Bildaufzeichnungen auf anderen Bildträgern, Videorecordern, Camcordern und dergleichen üblich. Bei Video-Konferenzen erfolgt zwar keine Bildmischung, jedoch werden Fenster für die unterschiedlichen Teilnehmer am Konferenzsystem in ein gemeinsames Bild eingeblendet.A linear addition of several band-limited time signals to a new sum signal occurs, inter alia, in audio technology, where audio signals are superimposed by sound mixing from several different sources, or in video technology, where video signals from two different sources to a new one Image signal are combined. Areas of application for sound mixing are, for example, in broadcasting, in the record industry and in the production of other sound carriers. In addition, a sound mixing in audio conferencing, ie in a summation of multiple sound signals from different sources, in the field of telecommunications technology is required. Image mixing by superimposing a plurality of image signals is common, for example, in television, in the production of optical disc and image recording on other image carriers, video recorders, camcorders and the like. Although there is no video mixing for video conferencing, there are windows for the different participants in the conference system in a common picture.
Bei dem aus der eingangs zitierten DE 32 00 934 A1 bekannten Verfahren zum Mischen von Niederfrequenzsignalen, die in Form von digitalen Abtastproben vorliegen, werden die für ein gemeinsames Endgerät bestimmten Impulse, die im jeweiligen Endgerät gemeinsam hörbar gemacht werden sollen, in einem analogen Addierer aufaddiert und jeweils einmal in einem Zeitrahmen in Form eines Summenimpulses übertragen, der das Endgerät während des gesamten Zeitrahmens steuert.In the known from the cited
Nachteilig bei den bekannten Verfahren ist die relativ lange Rechenzeit bei der Addition der einzelnen Signale in einem digitalen Rechner bzw. in einer Hardware-Schaltung von Addiereinheiten. Außerdem erfolgt eine erhebliche Dämpfung der Signale und damit ein Informationsverlust bei der Umwandlung von Analog- in Digitalsignale und umgekehrt bei der Re-Analogisierung der aufaddierten Signale im Falle einer digitalen Addition.A disadvantage of the known methods is the relatively long computing time in the addition of the individual signals in a digital computer or in a hardware circuit of adder units. In addition, there is a significant attenuation of the signals and thus a loss of information in the conversion of analog to digital signals and vice versa in the re-analogization of the added signals in the case of a digital addition.
Die Aufgabe der vorliegenden Erfindung liegt demgegenüber darin, ein Verfahren der eingangs genannten Art so zu verbessern, daß die Summation mit einer erheblich geringeren Rechenzeit durchgeführt werden kann, daß gegebenenfalls eine Vielzahl von langsamen und teueren Addiergliedern eingespart werden kann und daß eine Dämpfung der Signale bei der Verarbeitung und der damit einhergehende Informationsverlust minimiert wird.The object of the present invention is in contrast to improve a method of the type mentioned above so that the summation can be carried out with a significantly lower computational time, that optionally a variety of slow and expensive adders can be saved and that attenuation of the signals at processing and the associated loss of information is minimized.
Erfindungsgemäß wird diese Aufgabe auf ebenso überraschend einfache wie wirkungsvolle Art und Weise dadurch gelöst, daß die Abtastwerte aller N Zeitsignale zeitlich zueinander versetzt überlagert und gemeinsam in ein Tiefpaßfilter der Filterbandbreite B' > B eingegeben werden, und daß am Ausgang des Tiefpaßfilters ein Summensignal abgegriffen wird.According to the invention, this object is achieved in a surprisingly simple and effective manner in that the samples of all N time signals are superimposed on one another in terms of time and shared in a low-pass filter of the filter bandwidth B '> B are entered, and that at the output of the low-pass filter, a sum signal is tapped.
Im Gegensatz zu den bekannten Verfahren, bei denen die als analoge oder digitale Abtastwerte vorliegenden Signale unterschiedlicher Quellen für jedes Signal separat in analoge Signale umgesetzt werden, die mittels eines oder mehrerer analoger Addierer oder eines digitalen Prozessors addiert werden, werden beim erfindungsgemäßen Verfahren die Abtastwerte unterschiedlicher Zeitsignale zeitlich versetzt zueinander überlagert und mittels eines passiven Tiefpaßfilters analog umgesetzt. Die Abtastwerte von unterschiedlichen Signale, die jeweils mit einer Frequenz fA abgetastet wurden, werden in einem Zeitmultiplexverfahren zu einem überlagerten Signal mit der Frequenz N · fA zusammengefaßt. In der anschließenden Filterung mit einem Tiefpaßfilter der Filterbandbreite B' ≈ fA/2 wird dann ein analoges Summensignal generiert, das zur weiteren Verarbeitung mit der Frequenz fA abgetastet werden kann.In contrast to the known methods, in which the signals of different sources present as analog or digital samples for each signal are converted separately into analog signals which are added by means of one or more analog adders or a digital processor, the samples become more different in the method according to the invention Time signals offset in time superimposed and implemented analogously by means of a passive low-pass filter. The samples of different signals, each sampled at a frequency f A , are combined in a time division multiplexing to form a superimposed signal of frequency N · f A. In the subsequent filtering with a low-pass filter of the filter bandwidth B '≈ f A / 2, an analog sum signal is then generated, which can be scanned for further processing at the frequency f A.
Damit ergibt sich einerseits eine qualitativ bessere und schnellere Addition, zum anderen läßt sich wegen der Einsparung einer Addiereinheit bzw. eines entsprechenden Prozessors zur digitalen Addition der Eingangssignale eine kostengünstigere Realisierung der Summenbildung erreichen. Ein weiterer Vorteil besteht darin, daß eine zur Durchführung des erfindungsgemäßen Verfahrens geeignete Vorrichtung ohne weiteres in einem integrierten Schaltkreis, beispielsweise in einem VLSI-Chip integriert werden kann. Andererseits läßt sich das erfindungsgemäße Verfahren auch leicht in einer DSP-Software mit entsprechendem Gewinn an Rechenzeit einbauen. Das erfindungsgemäße Verfahren ist sowohl zur Summenbildung von digitalen als auch analogen Eingangswerten geeignet.On the one hand, this results in a qualitatively better and faster addition, on the other hand, because of the saving of an adder unit or of a corresponding processor for the digital addition of the input signals, a more cost-effective realization of the summation can be achieved. A further advantage is that a device suitable for carrying out the method according to the invention can readily be integrated in an integrated circuit, for example in a VLSI chip. On the other hand, the inventive method can also be easily installed in a DSP software with a corresponding gain in computation time. The inventive method is suitable both for summation of digital and analog input values.
Besonders bevorzugt ist eine Ausführungsform des erfindungsgemäßen Verfahrens, bei der die Abtastwerte der N Zeitsignale zeitlich äquidistant zueinander versetzt werden. Dadurch läßt sich eine von vornherein starre, stets bekannte und gleichbleibende zeitliche Relation der Signale von unterschiedlichen Quellen festlegen.Particularly preferred is an embodiment of the inventive method in which the samples of the N time signals are offset in time equidistantly from each other. As a result, it is possible to establish a rigid, always known and constant temporal relation of the signals from different sources from the outset.
Eine weitere bevorzugte Ausführungsform der Erfindung sieht vor, daß die Eingabe der zeitlich zueinander versetzten Abtastwerte in das Tiefpaßfilter mit einer Taktfrequenz N · fA erfolgt.A further preferred embodiment of the invention provides that the input of the temporally offset samples into the low-pass filter with a clock frequency N · f A.
Bei der Eingabe analoger Abtastwerte kann bei einer weiteren vorteilhaften Ausführungsform der Erfindung ein analoges Tiefpaßfilter verwendet werden, an dessen Ausgang ein zeitlich kontinuierliches Summensignal erscheint, das eine perfekte Summenbildung der Teilsignale bewirkt.In the case of the input of analog samples, in a further advantageous embodiment of the invention, an analog low-pass filter can be used, at whose output a time-continuous sum signal appears, which produces a perfect summation of the partial signals.
Vorzugsweise wird dieses Verfahren dadurch weitergebildet, daß aus dem zeitlich kontinuierlichen Summensignal durch Abtastung analoge Abtastwerte des Summensignals gewonnen werden.Preferably, this method is further developed in that analog samples of the sum signal are obtained from the temporally continuous sum signal by sampling.
Alternativ dazu ist bei anderen Ausführungsformen, bei denen digitale Abtastwerte eingegeben werden, die Verwendung eines digitalen Tiefpaßfilters vorgesehen, das mit der Taktfrequenz N · fA arbeitet, und an dessen Ausgang ein Summensignal mit N · fA Abtastwerten pro Zeiteinheit, d. h. in überabgetasteter Form vorliegt. Damit können alle Vorteile eines Oversampling-Verfahrens ausgenutzt werden.Alternatively, in other embodiments where digital samples are input, the use of a digital low pass filter operating at the clock frequency N * f A is provided, and at its output a sum signal having N * f A samples per unit time, ie, in oversampled form is present. Thus, all advantages of an oversampling method can be exploited.
Eine Weiterbildung dieser Ausführungsform sieht vor, daß das überabgetastete Summensignal auf einen Digital-Analog(D/A)-Wandler gegeben wird, der mit der Taktfrequenz N · fA arbeitet, und dessen Ausgangssignal über eine Nachfilterung, vorzugsweise mittels eines RC-Gliedes, das zeitlich kontinuierliche Summensignal ergibt. Anstelle einer aufwendigen Filtereinrichtung kann ein ganz einfaches, kostengünstiges RC-Filterglied verwendet werden, das aufgrund des Oversamplings eine ausreichende Unterdrückung von im Frequenzraum nach einer Fouriertransformation periodisch auftretenden Spiegelsignalen sicherstellt.A development of this embodiment provides that the oversampled sum signal is applied to a digital-to-analog (D / A) converter which operates at the clock frequency N · f A , and whose output signal via a post-filtering, preferably by means of an RC element, the time-continuous sum signal results. Instead of a complex filter device, a very simple, cost-effective RC filter element can be used, which ensures sufficient suppression of periodically occurring in the frequency domain after a Fourier transformation mirror signals due to the oversampling.
Besonders vorteilhaft ist eine Weiterbildung, bei der das überabgetastete Summensignal durch periodisches Weglassen von Abtastwerten (= Dezimation) auf eine niedrigere Abtastfrequenz i · fA < N · fA überführt wird, wobei vorzugsweise i = 1. Umgekehrt kann auch eine höhere Abtastfrequenz durch Abtastratenwandlung erreicht werden, indem an Zwischenstellen fiktive Abtastwerte "0" eingefügt werden, wobei aufgrund der Tiefpaßfilterung am Ende ein perfektes Gesamtsignal herauskommt.Particularly advantageous is a development in which the oversampled sum signal is transferred by periodically omitting samples (= decimation) to a lower sampling frequency i · f A <N · f A , preferably i = 1. Conversely, a higher sampling frequency by sampling rate conversion can be achieved by inserting fictitious samples "0" at intermediate points, whereby a perfect overall signal comes out at the end due to the low-pass filtering.
Besonders einfach und unaufwendig läßt sich das erfindungsgemäße Verfahren bei analogen Eingabewerten durchführen, wenn die Summenbildung und Tiefpaßfilterung mit einem digitalen Signalprozessor realisiert wird.Particularly simple and inexpensive, the inventive method can be carried out at analog input values, when the summation and low-pass filtering is realized with a digital signal processor.
In den Rahmen der vorliegenden Erfindung fällt auch eine Vorrichtung zur Summenbildung von N > 1 bandbegrenzten Zeitsignalen mit je einer Bandbreite s B, die als analoge und/ oder digitale Abtastwerte vorliegen, wobei die jeweilige Abtastfrequenz fA > 2B ist, bei der eine Zeitmultiplexeinheit vorgesehen ist, in der die Abtastwerte aller N Zeitsignale zeitlich zueinander versetzt überlagerbar sind, und bei der im Anschluß an die Zeitmultiplexeinheit ein Tiefpaßfilter der Filterbandbreite B' > B vorgesehen ist, in das die zeitlich versetzt überlagerten Abtastwerte gemeinsam eingegeben werden können, und an dessen Ausgang ein Summensignal abgegriffen werden kann.The scope of the present invention also includes a device for summing N> 1 band-limited time signals, each having a bandwidth s B, which are present as analog and / or digital samples, wherein the respective sampling frequency f A > 2B, in which a time-division multiplex unit is provided in which are the samples of all N time signals offset in time to each other are superimposed, and in the subsequent to the time division multiplexing a low-pass filter of the filter bandwidth B '> B is provided, in which the temporally offset superimposed samples can be entered together, and at the output of a sum signal can be tapped.
Weitere Vorteile der Erfindung ergeben sich aus der Beschreibung und der Zeichnung. Ebenso können die vorstehend genannten und die noch weiter aufgeführten Merkmale erfindungsgemäß jeweils einzeln für sich oder zu mehreren in beliebigen Kombinationen Verwendung finden. Die gezeigten und beschriebenen Ausführungsformen sind nicht als abschließende Aufzählung zu verstehen, sondern haben vielmehr beispielhaften Charakter für die Schilderung der Erfindung.Further advantages of the invention will become apparent from the description and the drawings. Likewise, the features mentioned above and those listed further in accordance with the invention can each be used individually for themselves or for several in any desired combinations. The embodiments shown and described are not to be understood as exhaustive enumeration, but rather have exemplary character for the description of the invention.
Die Erfindung ist in der Zeichnung dargestellt und wird anhand von Ausführungsbeispielen näher erläutert. Es zeigen:
- Fig. 1
- eine schematische Darstellung einer Vorrichtung zur Durchführung des erfindungsgemäßen Verfahrens mit angedeuteten Abtastsignalen;
- Fig. 2
- eine verbesserte Ausführungsform der Vorrichtung nach Fig. 1;
- Fig. 3a
- eine schematische Darstellung der Signale von verschiedenen Quellen im Zeitverlauf;
- Fig. 3b
- eine schematische Darstellung der zeitversetzten Zusammenführung und Tiefpaßfilterung der Eingangs-signale aus Fig. 3a;
- Fig. 4
- eine schematische Darstellung des Zeitverlaufs einer erfindungsgemäßen Summenbildung bei analogen Eingangswerten;
- Fig. 5a
- eine schematische Darstellung des Zeitverlaufs des erfindungsgemäßen Verfahrens bei der Summation von digitalen Eingangswerten;
- Fig. 5b
- eine Verbesserung der Vorrichtung von Fig. 5a;
- Fig. 6
- einen schematischen Aufbau für eine erfindungsgemäße Summenbildung mit analogem Signaleingang und Möglichkeit zur Abtastratenwandlung; und
- Fig. 7
- einen schematischen Aufbau zur Durchführung des erfindungsgemäßen Verfahrens mit Interpolation und/oder Dezimation.
- Fig. 1
- a schematic representation of an apparatus for performing the method according to the invention with indicated scanning signals;
- Fig. 2
- an improved embodiment of the device of Fig. 1;
- Fig. 3a
- a schematic representation of the signals from different sources over time;
- Fig. 3b
- a schematic representation of the time-shifted merging and low-pass filtering of the input signals of Fig. 3a;
- Fig. 4
- a schematic representation of the time course of a sum according to the invention with analog input values;
- Fig. 5a
- a schematic representation of the time course of the inventive method in the summation of digital input values;
- Fig. 5b
- an improvement of the device of Fig. 5a;
- Fig. 6
- a schematic structure for an inventive summation with analog signal input and possibility for sampling rate conversion; and
- Fig. 7
- a schematic structure for carrying out the method according to the invention with interpolation and / or decimation.
In Fig. 1 ist ein besonders einfacher schematischer Aufbau zur erfindungsgemäßen Summenbildung von Zeitsignalen aus zwei verschiedenen Quellen dargestellt, wobei die Zeitsignale jeweils als Abtastwerte mit einer Abtastfrequenz fA eingegeben werden. Dabei muß die Abtastfrequenz fA größer oder mindestens gleich dem doppelten der Bandbreite der bandbegrenzten Zeitsignale sein.In Fig. 1, a particularly simple schematic structure for the inventive summation of time signals from two different sources is shown, wherein the time signals are respectively input as samples with a sampling frequency f A. The sampling frequency f A must be greater than or equal to twice the bandwidth of the band-limited time signals.
Die Zeitsignale aus den beiden Quellen werden in eine Zeitmultiplexeinheit 11 eingegeben, in der sie zeitlich zueinander versetzt überlagert werden. Vorteilhafterweise sind die Abtastwerte der Zeitsignale zeitlich äquidistant, so daß im vorliegenden Beispiel aus der Zeitmultiplexeinheit 11 Abtastwerte mit einer Frequenz 2 · fA herauskommen. Diese werden in ein Tiefpaßfilter 12 mit einer Filterbandbreite B' > B eingegeben. Am Ausgang des Tiefpaßfilters 12 kann dann das gewünschte Summensignal abgegriffen werden.The timing signals from the two sources are input to a time
Eine verbesserte Ausführungsform für die Verarbeitung von digitalen Eingangsdaten ist in Fig. 2 schematisch dargestellt. Dabei werden die als digitale Abtastwerte vorliegenden, im gezeigten Beispiel wiederum aus lediglich zwei Quellen stammenden Zeitsignale der Zeitmultiplexeinheit 21 eingegeben, in der wieder ein zeitlicher Versatz, vorzugsweise äquidistant vorgenommen wird. Die zeitlich versetzt zueinander überlagerten Signale werden dann einem im vorliegenden Beispiel mit einer Frequenz 2 · fA getakteten digitalen Tiefpaßfilter 22 zugeführt. Da das digitale Tiefpaßfilter 22 immer auch periodische Fortsetzungen der Signale erzeugt, die unerwünscht sind, werden die Summensignale nach Durchgang durch einen Digital-Analog-Konverter (DAC) 23 einem weiteren, jedoch analogen Tiefpaßfilter 24 zugeführt, welches im Frequenzraum die kleinen Frequenzanteile der erzeugten Signale durchläßt und die höheren Frequenzen stark genug abdämpft, so daß die unerwünschten periodischen Signalartefakte unterdrückt werden. Der DAC 23 wird im vorliegenden Beispiel ebenso wie das digitale Tiefpaßfilter 22 mit einer Frequenz 2 * fA getaktet, da lediglich Signale aus zwei verschiedenen Quellen, die in der Zeitmultiplexeinheit 21 äquidistant zueinander versetzt wurden, verarbeitet werden müssen. Das analoge Tiefpaßfilter 24 kann ein ganz einfaches, preisgünstiges RC-Glied sein oder aus mehreren solchen bestehen.An improved embodiment for the processing of digital input data is shown schematically in FIG. The present as digital samples, in the example shown again from only two sources derived time signals of the time
Die Figuren 3a und 3b illustrieren den Gang des erfindungsgemäßen Verfahrens schematisch: In Fig. 3a sind untereinander die Zeitsignale von N Quellen dargestellt, wobei die Signale mit "S", einer nachfolgenden Ziffer für die Nummer der Quelle und einer weiteren Ziffer für die Nummer des Abtastwertes innerhalb des zunächst analogen Signales bezeichnet sind. Diese Signale von N verschiedenen Quellen werden der in Fig. 3b schematisch dargestellten Multiplexeinheit 31 zugeführt, in welcher sie zeitversetzt zueinander überlagert werden. Für die Abtastwerte aus derselben Quelle ist ein äquidistanter Zeitversatz erforderlich, während die Signale von verschiedenen Quellen nicht notwendigerweise äquidistant zeitversetzt sein müssen, falls eine Filtereinrichtung oder ein DAC eine entsprechend hohe Signalverarbeitungsgeschwindigkeit bewältigen kann.FIGS. 3a and 3b illustrate the process of the method according to the invention schematically. In FIG. 3a, the time signals of N sources are shown one below the other, the signals being indicated by "S", a subsequent digit for the number of the Source and another digit for the number of the sample within the initially analog signal are designated. These signals from N different sources are fed to the
Die resultierende Signalsequenz am Ausgang der Zeitmultiplexeinheit 31 wird einem normalen Tiefpaßfilter 32 zugeführt, dessen Bandbreite B' ungefähr der halben Abtastfrequenz fA entspricht, damit die Signale jeder einzelnen Quelle aus dem Summensignal rekonstruiert werden können.The resulting signal sequence at the output of time
Fig. 4 zeigt schematisch die Verarbeitung von Abtastwerten aus zunächst analogen Signalen, die aus verschiedenen Quellen stammen und in einer, in Fig. 4 nicht mehr explizit dargestellten Zeitmultiplexereinheit zeitlich zueinander versetzt so überlagert sind, daß sich zwischen dem ersten Abtastwert S11 aus der ersten Quelle und dem zweiten Abtastwert S12 aus der ersten Quelle sämtliche Abtastwerte aus allen anderen Quellen (S21 bis SN1) befinden. Diese Sequenz wird einem analogen Tiefpaßfilter 42 zugeführt, aus welchem ein entsprechendes kontinuierliches Summensignal in analoger Form herauskommt.4 schematically shows the processing of samples from initially analog signals which originate from different sources and are superimposed in time offset relative to one another in a time multiplexer unit (not shown explicitly in FIG. 4) such that there is a difference between the first sample S11 from the first source and the second sample S12 from the first source are all samples from all other sources (S21 to SN1). This sequence is fed to an analog low-
Fig. 5a zeigt denselben Vorgang bei der Eingabe digitaler Abtastwerte. Die zeitversetzten überlagerten Signale werden hier wiederum einem Tiefpaßfilter 52, bei dem es sich um ein digitales Tiefpaßfilter handelt, welches mit einer Frequenz N · fA getaktet wird, zugeführt. Am Ausgang des digitalen Tiefpaßfilters 52 entsteht ein Summensignal mit digitalen Abtastwerten der Frequenz N · fA, die, wie in Fig. 5b gezeigt ist, einem ebenfalls mit N · fA getakteten DAC 53 zugeführt werden. Am Ausgang des DAC 53 liegen dann analoge Abtastwerte mit einer Frequenz N · fA vor, die aufgrund der oben beschriebenen Funktionsweise von digitalen Tiefpaßfiltern noch einer analogen Tiefpaßfilterung in einem RC-Element 54 unterzogen werden müssen.Fig. 5a shows the same process when inputting digital samples. The time-shifted superimposed signals are here again a low-
Teilt man den zeitlichen Fluß der digitalen Abtastwerte in gleiche Blöcke zu je N Abtastwerten ein, so genügt es in der Regel, den jeweils ersten Abtastwert eines jeden Blockes zu behalten und die jeweils übrigen (N- 1) Abtastwerte zu ignorieren. Die in dieser sogenannten Dezimationsprozedur ausgewählten Abtastwerte haben eine Folgefrequenz fA und stellen ebenfalls das gewünschte Summensignal exakt dar.If one divides the temporal flow of the digital samples into equal blocks of N samples each, then it is usually sufficient to keep the first sample of each block and to ignore the remaining (N-1) samples. The samples selected in this so-called decimation procedure have a repetition frequency f A and also exactly represent the desired sum signal.
Umgekehrt kann mit Hilfe einer sogenannten Abtastratenwandlung auch eine Interpolation von Abtastwerten erfolgen. In Fig. 6 ist schematisch dargestellt, wie analoge Signale, die aus einer Zeitmultiplexereinheit 61 zeitlich zueinander versetzt und überlagert herauskommen, einem analogen Tiefpaßfilter 62 zugeführt werden, an dessen Ausgang eine Sample-Hold-Schaltung 65 vorgesehen ist. Dieser wiederum schließt sich eine Analog-Digital-Wandlereinheit (ADC) 63 an, nach der dann eine digitale Weiterverarbeitung der Signale möglich wird. Zur Abtastratenwandlung werden dann an geeigneten Stellen, an denen jeweils keine Abtastwerte vorliegen, "Nullwerte" interpolativ eingefügt, um die Abtastfrequenz zu erhöhen.Conversely, with the aid of a so-called sample rate conversion, interpolation of samples can also be performed. FIG. 6 shows diagrammatically how analogue signals which emerge from a time-
Fig. 7 schließlich zeigt schematisch eine erfindungsgemäße Vorrichtung mit einer Zeitmultiplexeinheit 71, einer.Inter-polationsvorrichtung 76 zur Einfügung von "Nullwerten" und entsprechenden Abtastratenwandlung, einem Tiefpaßfilter 72 sowie einem Dezimator 77 zur wahlweisen Kompaktierung der Signaldaten nach dem oben beschriebenen Dezimationsverfahren. Fig. 7 finally shows schematically a device according to the invention with a time
Claims (10)
- A method for the summation of N > 1 band-limited time signals, each having a bandwidth ≤ B, and being present in the form of analog or digital scanning values, wherein the respective scanning frequency is fA > 2B,
characterised in that,
the scanning values of all N time signals are overlaid in time displaced manner relative to one another, and are input jointly into a low-pass filter (12; 22; 32; 42; 52; 62; 72) of the filter bandwidth B' > B, and that at the output from the low-pass filter (12; 22; 32; 42; 52; 62; 72) an aggregate signal is picked up. - A method according to Claim 1, characterised in that the scanning values of the N time signals are displaced so that they are equidistant to one another in time.
- A method according to one of Claims 1 or 2, characterised in that the input into the low-pass filter (12; 22; 32; 42; 52; 62; 72) of scanning values which are displaced in time relative to one another takes place at a stroke frequency N . fA.
- A method according to one of the preceding claims, characterised in that in the case of analog scanning values, an analog low-pass filter (11; 32; 42; 62) is used, at the output of which an aggregate signal appears which is continuous in time.
- A method according to Claim 4, characterised in that analog scanning values of the aggregate signal are obtained, by scanning, from the aggregate signal which is continuous in time.
- A method according to one of Claims 1 to 3, characterised in that in the case of digital scanning values a digital low-pass filter (12; 22; 52; 72) is used which operates at the stroke frequency N . fA, at the output of which an aggregate signal is present with N . fA scanning values per unit of time, i.e. in overscanned form.
- A method according to Claim 6, characterised in that the overscanned aggregate signal is given to a digital-analog (D/A) converter (23; 53) which operates at the stroke frequency N . fA, and the output signal of which, through afterfiltering, results in the aggregate signal which is continuous in time.
- A method according to Claim 6 or 7, characterised in that the overscanned aggregate signal is converted by the periodic omission of scanning values (= decimation) to a lower scanning frequency i . fA < N . fA.
- A method according to one of Claims 1 to 3 or 6 to 8, characterised in that summation and low-pass filtering are carried out using a digital signal processor.
- An apparatus for the summation of N > 1 band-limited time signals, each having a bandwidth ≤ B, and being present in the form of analog or digital scanning values, wherein the respective scanning frequency is fA > 2B,
characterised in that,
a time-multiplex unit (11; 21; 31; 61; 71) is designed in such a way that the scanning values of all N time signals are overlaid so that they are displaced in time relative to one another, and in such a way that following on from the time-multiplex unit (11; 21; 31; 61; 71) a low-pass filter (12; 22; 32; 42; 52; 62; 72) of the filter bandwidth B' > B is configured in such a way that the scanning values which are overlaid so that they are displaced in time relative to one another are input jointly into the low-pass filter, and an aggregate signal is picked up at the output thereof.
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| DE19716314A DE19716314A1 (en) | 1997-04-18 | 1997-04-18 | Method and device for adding signals present as samples |
| DE19716314 | 1997-04-18 |
Publications (3)
| Publication Number | Publication Date |
|---|---|
| EP0876077A2 EP0876077A2 (en) | 1998-11-04 |
| EP0876077A3 EP0876077A3 (en) | 2001-02-07 |
| EP0876077B1 true EP0876077B1 (en) | 2007-04-18 |
Family
ID=7826956
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| EP98440051A Expired - Lifetime EP0876077B1 (en) | 1997-04-18 | 1998-03-13 | Method and apparatus for addition of signals existing as sampling values |
Country Status (5)
| Country | Link |
|---|---|
| US (1) | US6272181B1 (en) |
| EP (1) | EP0876077B1 (en) |
| JP (1) | JP4056126B2 (en) |
| CA (1) | CA2230481A1 (en) |
| DE (2) | DE19716314A1 (en) |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2000069087A1 (en) * | 1999-05-10 | 2000-11-16 | Infineon Technologies Ag | Receiver circuit for a communications terminal and method for processing signals in a receiver circuit |
| US6922160B1 (en) * | 2002-10-09 | 2005-07-26 | Unisys Corporation | Scalable bus system and method for communicating digital data using analog modulation and demodulation |
| US20060187971A1 (en) * | 2005-02-18 | 2006-08-24 | Lum Richard K K | Method and apparatus for concurrently transmitting a digital control signal and an analog signal from a sending circuit to a receiving circuit |
| US7480012B1 (en) * | 2005-02-24 | 2009-01-20 | Pixelworks, Inc. | Multiplexed video digitization system and method |
| US7698582B2 (en) * | 2005-12-23 | 2010-04-13 | Schweitzer Engineering Laboratories, Inc. | Apparatus and method for compensating digital input delays in an intelligent electronic device |
Family Cites Families (16)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US3614521A (en) * | 1969-11-28 | 1971-10-19 | Us Air Force | Multichannel multiplexed quasi three-dimensional display system |
| US3787785A (en) * | 1972-05-15 | 1974-01-22 | Collins Radio Co | Phase representative digital signal modulating apparatus |
| US4313195A (en) * | 1979-04-23 | 1982-01-26 | Sangamo Weston, Inc. | Reduced sample rate data acquisition system |
| FR2498403A1 (en) | 1981-01-21 | 1982-07-23 | Telephonie Ind Commerciale | METHOD AND DEVICE FOR MIXING LOW FREQUENCY SIGNALS TRANSMITTED BY DIFFERENT TIMEWAYS TO A SAME TELEPHONE RECEIVER |
| US4479212A (en) * | 1982-03-12 | 1984-10-23 | At&T Bell Laboratories | Conference circuit |
| JPS60237527A (en) * | 1984-05-11 | 1985-11-26 | Mitsubishi Electric Corp | A-d converting device |
| JPS60249460A (en) * | 1984-05-25 | 1985-12-10 | Nec Corp | Audio conference bridge system |
| US4994899A (en) * | 1988-03-23 | 1991-02-19 | Scientific Atlanta, Inc. | Frequency generation for extended bandwidth MAC color television encoding and decoding |
| JPH0773219B2 (en) * | 1988-06-16 | 1995-08-02 | 富士通株式会社 | Parallel-serial converter |
| US5208545A (en) * | 1991-03-27 | 1993-05-04 | Schweitzer Engineering Laboratories Inc. | Apparatus and method for eliminating phase skew in a multi-channel data acquisition system |
| DE4113119A1 (en) * | 1991-04-22 | 1992-10-29 | Siemens Ag | Measuring mean period duration of pulse train - forming integration time value, corresp. to integration time, by adding preset measuring time and rest time value |
| US5193000A (en) * | 1991-08-28 | 1993-03-09 | Stereographics Corporation | Multiplexing technique for stereoscopic video system |
| US5596647A (en) * | 1993-06-01 | 1997-01-21 | Matsushita Avionics Development Corporation | Integrated video and audio signal distribution system and method for use on commercial aircraft and other vehicles |
| DE4426935A1 (en) * | 1994-07-29 | 1996-02-01 | Rohde & Schwarz | Digital residual sideband modulator for video signals |
| DE9419712U1 (en) * | 1994-12-08 | 1995-01-26 | Siemens AG, 80333 München | Circuit for forming an analog output signal corresponding to the sum of two signals |
| JPH08205105A (en) * | 1995-01-26 | 1996-08-09 | Hitachi Denshi Ltd | Digital signal transmission system |
-
1997
- 1997-04-18 DE DE19716314A patent/DE19716314A1/en not_active Withdrawn
-
1998
- 1998-03-13 EP EP98440051A patent/EP0876077B1/en not_active Expired - Lifetime
- 1998-03-13 DE DE59813972T patent/DE59813972D1/en not_active Expired - Lifetime
- 1998-03-26 US US09/048,544 patent/US6272181B1/en not_active Expired - Fee Related
- 1998-04-01 CA CA002230481A patent/CA2230481A1/en not_active Abandoned
- 1998-04-17 JP JP10826598A patent/JP4056126B2/en not_active Expired - Fee Related
Also Published As
| Publication number | Publication date |
|---|---|
| CA2230481A1 (en) | 1998-10-18 |
| EP0876077A3 (en) | 2001-02-07 |
| EP0876077A2 (en) | 1998-11-04 |
| US6272181B1 (en) | 2001-08-07 |
| JPH1175273A (en) | 1999-03-16 |
| DE19716314A1 (en) | 1998-10-22 |
| DE59813972D1 (en) | 2007-05-31 |
| JP4056126B2 (en) | 2008-03-05 |
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