EP0034076A2 - Solenoid driving system - Google Patents
Solenoid driving system Download PDFInfo
- Publication number
- EP0034076A2 EP0034076A2 EP81400094A EP81400094A EP0034076A2 EP 0034076 A2 EP0034076 A2 EP 0034076A2 EP 81400094 A EP81400094 A EP 81400094A EP 81400094 A EP81400094 A EP 81400094A EP 0034076 A2 EP0034076 A2 EP 0034076A2
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- EP
- European Patent Office
- Prior art keywords
- current
- terminal
- output
- pull
- gate
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
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- 239000003990 capacitor Substances 0.000 claims abstract description 27
- 230000004913 activation Effects 0.000 claims abstract description 14
- 239000000446 fuel Substances 0.000 claims description 21
- 230000004044 response Effects 0.000 claims description 9
- 238000002347 injection Methods 0.000 claims description 8
- 239000007924 injection Substances 0.000 claims description 8
- 230000001105 regulatory effect Effects 0.000 claims description 7
- XUIMIQQOPSSXEZ-UHFFFAOYSA-N Silicon Chemical compound [Si] XUIMIQQOPSSXEZ-UHFFFAOYSA-N 0.000 claims description 6
- 229910052710 silicon Inorganic materials 0.000 claims description 6
- 239000010703 silicon Substances 0.000 claims description 6
- 230000001276 controlling effect Effects 0.000 claims description 4
- 230000003213 activating effect Effects 0.000 claims description 3
- 230000009849 deactivation Effects 0.000 claims description 2
- 230000000977 initiatory effect Effects 0.000 claims description 2
- 229920006395 saturated elastomer Polymers 0.000 claims description 2
- 230000003139 buffering effect Effects 0.000 claims 3
- 230000000295 complement effect Effects 0.000 claims 1
- 238000007493 shaping process Methods 0.000 claims 1
- 230000000903 blocking effect Effects 0.000 description 6
- 230000008878 coupling Effects 0.000 description 4
- 238000010168 coupling process Methods 0.000 description 4
- 238000005859 coupling reaction Methods 0.000 description 4
- 238000010586 diagram Methods 0.000 description 3
- 230000001052 transient effect Effects 0.000 description 3
- 238000002485 combustion reaction Methods 0.000 description 1
- 230000007423 decrease Effects 0.000 description 1
- 230000001419 dependent effect Effects 0.000 description 1
- 230000000694 effects Effects 0.000 description 1
- 230000017525 heat dissipation Effects 0.000 description 1
- 230000000737 periodic effect Effects 0.000 description 1
- 239000007787 solid Substances 0.000 description 1
- 230000001629 suppression Effects 0.000 description 1
Images
Classifications
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
- H01F7/00—Magnets
- H01F7/06—Electromagnets; Actuators including electromagnets
- H01F7/08—Electromagnets; Actuators including electromagnets with armatures
- H01F7/18—Circuit arrangements for obtaining desired operating characteristics, e.g. for slow operation, for sequential energisation of windings, for high-speed energisation of windings
- H01F7/1805—Circuit arrangements for holding the operation of electromagnets or for holding the armature in attracted position with reduced energising current
- H01F7/1816—Circuit arrangements for holding the operation of electromagnets or for holding the armature in attracted position with reduced energising current making use of an energy accumulator
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- F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
- F02—COMBUSTION ENGINES; HOT-GAS OR COMBUSTION-PRODUCT ENGINE PLANTS
- F02D—CONTROLLING COMBUSTION ENGINES
- F02D41/00—Electrical control of supply of combustible mixture or its constituents
- F02D41/20—Output circuits, e.g. for controlling currents in command coils
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
- H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
- H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
- H03K17/60—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being bipolar transistors
- H03K17/64—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being bipolar transistors having inductive loads
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- F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
- F02—COMBUSTION ENGINES; HOT-GAS OR COMBUSTION-PRODUCT ENGINE PLANTS
- F02D—CONTROLLING COMBUSTION ENGINES
- F02D41/00—Electrical control of supply of combustible mixture or its constituents
- F02D41/20—Output circuits, e.g. for controlling currents in command coils
- F02D2041/2003—Output circuits, e.g. for controlling currents in command coils using means for creating a boost voltage, i.e. generation or use of a voltage higher than the battery voltage, e.g. to speed up injector opening
- F02D2041/2006—Output circuits, e.g. for controlling currents in command coils using means for creating a boost voltage, i.e. generation or use of a voltage higher than the battery voltage, e.g. to speed up injector opening by using a boost capacitor
-
- F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
- F02—COMBUSTION ENGINES; HOT-GAS OR COMBUSTION-PRODUCT ENGINE PLANTS
- F02D—CONTROLLING COMBUSTION ENGINES
- F02D41/00—Electrical control of supply of combustible mixture or its constituents
- F02D41/20—Output circuits, e.g. for controlling currents in command coils
- F02D2041/2003—Output circuits, e.g. for controlling currents in command coils using means for creating a boost voltage, i.e. generation or use of a voltage higher than the battery voltage, e.g. to speed up injector opening
- F02D2041/201—Output circuits, e.g. for controlling currents in command coils using means for creating a boost voltage, i.e. generation or use of a voltage higher than the battery voltage, e.g. to speed up injector opening by using a boost inductance
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- F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
- F02—COMBUSTION ENGINES; HOT-GAS OR COMBUSTION-PRODUCT ENGINE PLANTS
- F02D—CONTROLLING COMBUSTION ENGINES
- F02D41/00—Electrical control of supply of combustible mixture or its constituents
- F02D41/20—Output circuits, e.g. for controlling currents in command coils
- F02D2041/2003—Output circuits, e.g. for controlling currents in command coils using means for creating a boost voltage, i.e. generation or use of a voltage higher than the battery voltage, e.g. to speed up injector opening
- F02D2041/2013—Output circuits, e.g. for controlling currents in command coils using means for creating a boost voltage, i.e. generation or use of a voltage higher than the battery voltage, e.g. to speed up injector opening by using a boost voltage source
-
- F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
- F02—COMBUSTION ENGINES; HOT-GAS OR COMBUSTION-PRODUCT ENGINE PLANTS
- F02D—CONTROLLING COMBUSTION ENGINES
- F02D41/00—Electrical control of supply of combustible mixture or its constituents
- F02D41/20—Output circuits, e.g. for controlling currents in command coils
- F02D2041/2017—Output circuits, e.g. for controlling currents in command coils using means for creating a boost current or using reference switching
-
- F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
- F02—COMBUSTION ENGINES; HOT-GAS OR COMBUSTION-PRODUCT ENGINE PLANTS
- F02D—CONTROLLING COMBUSTION ENGINES
- F02D41/00—Electrical control of supply of combustible mixture or its constituents
- F02D41/20—Output circuits, e.g. for controlling currents in command coils
- F02D2041/202—Output circuits, e.g. for controlling currents in command coils characterised by the control of the circuit
- F02D2041/2058—Output circuits, e.g. for controlling currents in command coils characterised by the control of the circuit using information of the actual current value
Definitions
- This invention relates generally to systems for energizing electromagnetic devices having solenoids and, more particularly, to a solenoid driving system having a single boost voltage circuit used to activate a plurality of electromagnetic devices.
- Electronic fuel injection control system for internal combustion engines such as diesel engines may include a plurality of electromagnetically actuated fuel injection valves that are sequentially charged with a determinable quantity of fuel during a fuel metering interval and which during a subsequent interval are caused to inject this determinable quantity of fuel into the engine.
- a characteristic of many electromagnetically actuated devices is that the solenoid associated therewith requires a first high level current to cause the solenoid to activate or pull in a movable member. By utilizing a second substantially lower value of current to the solenoid coil, it is possible to maintain the solenoid (injector) in an activated state.
- Futhermore it is known in the art that to increase the speed of operation of a solenoid, it is desirable to overdrive the solenoid by applying a large first level of driving current for a limited period of time and to reduce the driving current to the second or holding level once the solenoid has been initially activated.
- the injector activation and fuel metering periods get closer in time and the metered quantity of fuel must be delivered to injector at an accelerated rate.
- the metering signals will begin to overlap one another.
- a solenoid driving system for energizing a number of electromagnetic devices, said system being adapted to receive a plurality of electrical metering pulses, one pulse associated with each device, for activating particular devices and comprising:
- the provision of the single boost generator means reduces the cost of the fuel system and provides for uniform, repeatable and rapid opening of each solenoid.
- the utilization of the regulating means decreases the power requirements of the system and related heat dissipation problems.
- the gate control means in cooperation with the boost generating means permits efficient system operation for wide ranges of metering pulse width intervals including conditions defined by overlapping metering intervals while not requi-ring complicated circuitry to prematurely terminate a particular metering pulse width.
- System 20 employs a single booster circuit 22 to assist in developing sufficient voltage to open a plurality of electromagnetic fuel injectors.
- the booster circuit 22 comprises a boost control 24 and a boost generator 26, which are both shown in greater detail in Figure 2.
- the output of the booster circuit 22 is connected to a plurality of solid state switches such as the plurality of silicon controlled rectifiers (SCR) 30a-n, . where n corresponds to the number of injector coils 54a-n.
- SCR 30 contains an anode terminal 32a-n, a cathode terminal 34a-n, and a gate terminal 36a-n.
- An SCR gate control circuit 40 is connected to the gate terminal 36 of each rectifier 30 through a plurality of signal lines 42a-n.
- the system further contains a plurality of series connected circuits.
- Each series circuit includes a diode 50 having its anode connected to a positive voltage source +V and having its cathode connected to one terminal 52 of an electromagnetic fuel injection valve coil 54.
- Another terminal 56 of the coil 54 is connected to a respective driver 60.
- the output of the driver 60 is connected to one terminal of a current sensing resistor 64, the other terminal of which is connected to ground or some other suitable electrical potential.
- each driver includes a Darlington pair 62.
- the system further includes a plurality of current regulator and mode control circuits 70a-n, each of which is connected to its associated driver 60a-n via . control lines 72a-n, respectively.
- Each current regulator and mode control circuit 70 is responsive to a metering signal input thereto which is generated in synchronism with a repeating engine event.
- the metering signals are generated by an electronic control unit (ECU) 90.
- the current regulator and mode control circuit 70 senses the voltage appearing across each respective sense resistor 64. This feedback voltage is transmitted to each current regulator and mode control circuit 70 via a plurality of feedback lines 74a-n.
- the system 20 further requires and generates additional timing and control signals: these are the pull-in and arm signals respectively.
- Each Metering signal (meter 1 through meter N) is connected to an input terminal .of one of the monostable multivibrators 30a-n.
- each multivibrator 80 will generate at its inverting terminal ( Q ) the inverted pull-in signal, and generate at its non-inverting terminal (Q) the pull-in signal.
- Each inverted pull-in signal is routed to a respective current regulator and mode control circuit 70.
- the non-inverted pull-in signal from each multivibrator 80 is connected through a line 130 (lines 130a-n) to the SCR gate control circuit 40 and to one of the input terminals of an OR gate 82 the output of which has been designated as the arm signal.
- the output of OR gate 82 is connected to an inverting amplifier 84 which generates an inverted arm signal (ARM) at its output terminal.
- the output of amplifier 84 is connected as illustrated in Figure 1 to the booster circuit 22.
- FIG. 2 illustrates a more detailed embodiment of the circuitry shown in Figure 1 necessary to activate coil 54a. More particularly, there is shown a booster circuit 22 comprising a boost control circuit 24, the output of which controls the state of a boost generator 26.
- the boost control circuit 24 comprises a comparator 100 receiving at its inverting terminal the inverted ARM signal.
- the comparator 100 is appropriately biased and functions as a level shifter and buffer.
- the output of comparator 100 is connected to the base . terminal of an npn transistor 102 which performs driver and signal inversion functions.
- the collector of transistor 102 is connected to the input of a Darlington pair 104.
- the output terminal 106 of the Darlington pair is connected via an output line 108 to an input terminal which is connected to - 109 which is connected to the boost generator 26.
- the boost generator 26 includes a first storage capacitor 110 having a terminal 112 which is connected to the positive battery potential+V and a terminal 114 connected via a line 28 to each SCR 30 as previously described.
- a boost coil 116 is also connected between terminal 112 and the input terminal 109.
- a diode 118 is connected between the end of boost coil 116 connected to terminal 109 and terminal 114. The diode 118 is polled so that current flow. is in the direction of terminal 109 to terminal 114.
- the boost generator 26 further includes a series combination of a Zener doide 120 and a blocking diode 122 connected between terminals 112 and 114.
- the Zener diode 120 is connected so as to regulate the voltage across the storage capacitor 110.
- the blocking diode-122 is connected to prevent current from flowing from terminal 112 to terminal 114.
- the output of the boost generator 26, that is terminal 114 is connected via line 28 to the anode of each SCR 30.
- the cathode of SCR 30a is connected to the cathode of the coupling diode 50a.
- the anode of the coupling diode 50a is connected in common to terminal 112 and to the positive potential voltage source +V such as a battery.
- the SCR gate control circuit 40 receives the plurality of pull-in signals,one associated with each coil, via input lines 130a-n. It is apparent that only line 130a is shown in Figure 2. The following discussion relates to the circuitry necessary to receive and condition one of these pull-in signals to appropriately activate one of the SCR's 30. It should be appreciated that the SCR gate control circuit 40 contains a number of such circuits as hereinafter described.
- the pull-in signal i.e. pull-in 1
- the pull-in signal is communicated via line 130a to the base of a.npn transistor 132a.
- the output or collector terminal of transistor 132a is connected to the base of a transistor 134a, which has its emitter terminal grounded.
- the collector terminal of transistor 132a is connected via a resistor 136a to a reference power supply potential which is less than the first voltage source, such as the 8 volt potential as indicated in Figure 2.
- the collector terminal of transistor 134a is connected to this reference power supply via a resistor 138a and a diode 140a serially connected.
- the collector of transistor 134a is connected to the gate terminal of a SCR 142a.
- the anode of SCR 142a is connected to one terminal of a second reference storage capacitor 144a..
- the other terminal of the reference capacitor 144a is connected to the reference power supply voltage source via terminal 112.
- the anode of SCR 142a - is also connected to the input terminal 109 via a resistor-diode combination 146a.
- the cathode of SCR 142a is connected to a voltage divider having resistances 140a, b and c.
- the gate terminal of SCR 30a is connected to the common node of resistors
- the current reference generator 150 further includes a pull-in current level adjust circuit 152, a hold current level adjust circuit 154 and a peak current control circuit 156. More particularly, the current reference generator includes an input comparator 160 receiving at its inverted input an inverted pull-in signal.
- Comparator 160 operates as a voltage level shifter and buffer having its output connected. via a potentiometer 162 to a reference voltage source such as the 8 volt potential.
- the potentiometer 162 provides the pull-in current level adjustment.
- the output of comparator 160 is also connected to the parallel combination of a resistor 155 and a capacitor 157 forming the peak current control.circuit.156.
- the peak current control circuit 156 may be a differentiator and insures a sufficient level of high voltage to saturate the output (transistor 174) of the current regulator 170 until the boost voltage from capacitor 110 is dissipated.
- the output of the peak' current control circuit 156 is connected to the anode of a blocking diode 166, the cathode of which is connected to the hold current level adjust circuit which comprises potentiometer 168.
- the cathode of the blocking diode 166 is further connected to the input of the current regulator 170.
- the input to the current regulator 170 comprises the non-inverting input terminal of an operational amplifier 172.
- the output of operational amplifier 172 is connected via a voltage divider to the base of a npn transistor .174, the emitter terminal of which is connected to the input or base terminal of the driver 60a.
- Driver 60a comprises a Darlington pair 176a.
- the emitter of the Darlington pair 176a is connected to one terminal of the sense resistor 64a.
- the other terminal of the sense resistor 64a as indicated is grounded.
- the emitter output of the Darlington pair 176a is communicated via a feedback resistor to the inverting input terminal of the operational amplifier 172a therein creating a current sensing feedback path.
- the cathode terminal of SCR 30a and the coupling diode 50a are connected to the input terminal of a transient suppressor comprising the parallel combination of a capacitor 178a and a resistor 180a.
- the input terminal of this parallel combination is also connected to the input terminal 52a of the injection coil 54a.
- the other terminal of the transient suppressor is connected to the cathode of a blocking diode 182a.
- the anode of blocking diode 18 2 a is connected to terminal 56a of coil 54a.
- the anode of diode 182a and terminal 56a of the coil 54a are connected to the collector terminal of the Darl i n gt on pair 176a. circuit
- Each current regulator and mode control circuit 70 further includes an on-off control circuit 188 comprising a level switching comparator 190 receiving at its inverting input via a line 192 a metering signal such as METER 1..
- the output of the level switching comparator 190 is connected to the base terminal of an inverting transistor 194.
- the collector of transistor 194 is connected to the base terminal of transistor 174.
- FIG. 3 illustrates the operation of the circuit disclosed in Figures 1 and 2 during an illustrative single coil activation or fuel injection event.
- the boost voltage (line 6, Figure 3) will be maintained at a quiescent voltage level.
- the boost voltage illustrated in line 6 represents the voltage stored on the storage capacitor 110 which is typically greater than the voltage level of the reference power supply.
- the coil current which is shown in line 7 of Figure 3, is zero.
- the booster circuit 22 comprising the boost control circuit 24 and the boost generator 26 is as follows: As the inverted ARM signal ( ARM ) goes low, current is drawn from the battery through the boost coil 116 and the Darlington pair 104 to ground. When the ARM signal goes high, the Darlington pair 104 is turned off, causing a capacitor charging current path to exist wherein the current which is flowing through the boost coil 116 now flows through diode 118 to charge the storage capacitor 110. Part of the current flows through the diode-resistor combination 146 and charges each capacitor 144. As previously mentioned, the booster circuit 22 includes a Zener diode 120 and diode 122 serially connected.
- the Z ener diode 120 limits the voltage across the capacitor 110 and also provides a relatively constant reference voltage thereacross.
- the Zener diode 120 provides a 130-140 volt reference. However, this voltage is dependent on the coil characteristics and can be any level.
- the purpose of the diode 118 is. to prevent the voltage on the charged capacitor from being returned to the coil 116.
- Diode 122 prevents current from flowing through the Zener diode 120 in the forward direction after the boost is dissipated.
- the coil 54- is coupled to the battery through diode 50. This direct coupling of the battery to the coil 54 and other sections of the circuit permits battery current to flow automatically when the voltage on the storage capacitor 110 becomes less than the forward voltage of diode 50.
- the SCR gate control circuit 40 receives at its input a pull-in signal on input line 130.
- Each pull-in signal may be derived from a particular meter signal which is related to a periodic activation or engine event such as a crankshaft position.
- the meter signals may be derived in a known manner from any of the known variety of crankshaft position sensors or electronic control units.
- the occurrence of the positive pull-in signal causes transistor 132 to become conductive, therein causing the voltage at the collector of transistor 132 to approach ground potential. This voltage potential is communicated to the base of transistor 134 and is of such magnitude as to return transistor 134 to a nonconducting state. At this point the gate terminal of SCR 142 is activated.
- the voltage appearing across the storage capacitor 144 upon the activation of SCR 142 is applied to the voltage divider 148, which in turn activates SCR 30.
- SCR 30 Upon the activation of SCR 30 by the positive pull-in signal the stored energy in the storage capacitor 110 is caused to flow through the coil 54, assuming, of course, that a particular driver 60 has been so activated by an associated on-off control circuit 188.
- Each SCR 30 requires that the gate potential be higher than the cathode potential in order to trigger it. A fraction of the boost energy is diverted to obtain a higher voltage to fire SCR 30. This is accomplished in the preferred embodiment using the diode-resistor combination 146, capacitor 144, SCR 142, and resistors of voltage divider 148.
- the path of current flow is from the storage capacitor 110 or from the battery through a particular injector coil 54 and through a driver 60.
- the driver 60 which can be the Darlington pair 176 is turned off, current flows from the coil 54 through diode 182 and into the resistor-capacitor combination 178-180.
- the resistor-capacitor combination 178-190 provides transient suppression during coil activation periods as well as a discharge path during non-activation periods for the coil current.
- comparator 190 When the metering signal goes high, comparator 190 output becomes low, which in turn places transistor 194 into a cut-off state. When transistor 194 is placed into a cut-off state, the transistor 174 is activated. This in turn activates the Darlington pair 176 to permit current flow from the storage capacitor 110 through the injector coil 54 and through the sense resistor 64 to ground.
- the output of the current reference generator 150 is a voltage waveform which is shown in Figure 3.
- the inverted pull-in signal which is connected to the inverting input of comparator 160 is in a high state, causing its output to be near ground potential.
- diode 166 is reverse-biased, essentially isolating the peak current control circuit 156.
- the current reference voltage is determined by the hold current level adjust circuit 1 54 .
- the capacitor in the peak current control circuit 156 will discharge to zero volts.
- the inverted pull-in signal connected to comparator 160, goes to a low voltage, e.g. near ground.
- the output comparator 160 which is essentially an open collector device, goes to a high impedance state.
- the pull-in current level adjust circuit 152 and peak current control circuit 156 cause diode 166 to become forward-biased. The net effect of this is to cause the voltage at the cathode of diode 166 to be higher, due to the additional parallel resistance.
- the current reference voltage is now determined by the voltage divider which consists of the potentiometer 168 and the parallel combination of resistor 169 and the series circuit of the pull-in current level adjust circuit and peak current control circuit.
- the capacitor 157 in the peak current control 156 is discharged and effectively shorts out the resistor. 155.
- This initial lower resistance causes the current reference voltage to have a slight overshoot, or peak, at the start to insure that the output stage of the driver remains saturated long enough to dissipate all of the boost energy and indeed get up to the pull-in current as fast as possible.
- FIG. 4 is a timing diagram for a system with six high pressure common rai.l injectors.
- injection occurs. at the end of each metering or activating period, as shown in Figure 4.
- the duration of the metering signal, as well as the injection advance, are generated as a function of engine parameters in a known manner by the electronic control unit 90 (Fig. 1).
- the duration of the pull-in signal would generally be fixed for any given application and is generally a function of the solenoid valve, as is the pull-in current level and boost voltage. Variable duration pull-in signals may also find application under certain circumstances.
- the arming signal duration is usually a fixed time period for a given valve coil and is determined by the valve coil parameters and the boost circuit parameters. Arming generally occurs at some convenient point in time when the circuit is not being used. For this application, arming would take place immediately following pull-in.
- the single booster circuit 22 can effectively drive a plurality of injector coils 54 during periods of excessive engine speeds. During these periods of high engine speed, the corresponding engine revolution period is proportionately reduced therein requiring that the metering signals for each injector be generated with a characteristic pulse overlap as illustrated in Figure 4.
- Figure 4 further illustrates the time synchronization, of the respective metering and pull-in signals and the resultant boost voltage pulse train generated in response thereto.
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- Engineering & Computer Science (AREA)
- Physics & Mathematics (AREA)
- Electromagnetism (AREA)
- Power Engineering (AREA)
- Chemical & Material Sciences (AREA)
- Combustion & Propulsion (AREA)
- Mechanical Engineering (AREA)
- General Engineering & Computer Science (AREA)
- Fuel-Injection Apparatus (AREA)
- Electrical Control Of Air Or Fuel Supplied To Internal-Combustion Engine (AREA)
Abstract
Selenoid driving system for electronically actuating in a predetermined sequence a plurality of solenoid coils (54), said driving system including: a single booster circuit (22) having an inductor (116) for receiving energy from a power supply and a capacitor (110) for storing a portion of this electrical energy prior to activation of a particular solenoid coil (54); a circuitry (40) associated with each solenoid coil (54) for energizing said solenoid coil (54) by causing the capacitor (110) to discharge therethrough and to regenerate the stored voltage potential prior to the time for energizing another solenoid coil (54); and a current regulator and mode control circuit (150, 170) to control the magnitude of current flowing through each solenoid coil (54).
Description
- This invention relates generally to systems for energizing electromagnetic devices having solenoids and, more particularly, to a solenoid driving system having a single boost voltage circuit used to activate a plurality of electromagnetic devices.
- Electronic fuel injection control system for internal combustion engines such as diesel engines may include a plurality of electromagnetically actuated fuel injection valves that are sequentially charged with a determinable quantity of fuel during a fuel metering interval and which during a subsequent interval are caused to inject this determinable quantity of fuel into the engine. A characteristic of many electromagnetically actuated devices is that the solenoid associated therewith requires a first high level current to cause the solenoid to activate or pull in a movable member. By utilizing a second substantially lower value of current to the solenoid coil, it is possible to maintain the solenoid (injector) in an activated state. Futhermore, it is known in the art that to increase the speed of operation of a solenoid, it is desirable to overdrive the solenoid by applying a large first level of driving current for a limited period of time and to reduce the driving current to the second or holding level once the solenoid has been initially activated.
- As the frequency of activation increases, such as when the speed of an engine increases, the injector activation and fuel metering periods get closer in time and the metered quantity of fuel must be delivered to injector at an accelerated rate. At some determinable engine operating condition, in order to deliver the metering quantity of fuel to each injector, the metering signals will begin to overlap one another. However, to operate the engine at these increased speeds it has been common practice to simultaneously inject fuel into a number of cylinders or to resort to complicated pulse width variation circuits to operate the system at high speeds.
- In accordance with the present invention there is provided a solenoid driving system for energizing a number of electromagnetic devices, said system being adapted to receive a plurality of electrical metering pulses, one pulse associated with each device, for activating particular devices and comprising:
- a voltage source;
- a plurality of electromagnetic devices, each device including a solenoid having a coil having a first terminal connected to said voltage source and a second terminal;
- regulating means, one associated with each said device, for selectively permitting current to flow through specified ones of said devices;
- current sensing means connected to each of said regulating means for sensing the level of current flowing through a specific one of said devices;
- driver means one associated with each of said devices; connected in series with said coil and said current sensing means for establishing a current flow path therethrough in response to a particular metering signal;
- diode means connected in series with said voltage source and the said coil of each of said devices;
- boost generator means connected to said voltage source and to each of said devices for periodically generating, prior to each metering pulse, a boost voltage energization signal having a voltage potential greater than the voltage potential of said voltage source;
- signal generating means for generating a pull-in signal in response to the initiation of each of the metering signals wherein the duration of each of said pull-in signals is a determinable fraction of the duration of a particular one of said metering pulses;
- boost control means responsive to the plurality of said pull-in signals for causing said boost generator means to regenerate said energization signal;
- gate means, one associated with each of said devices, having activation and deactivation states of operation, for controlling the application of the energization signal during the activation state to its associated cne of said devices; and
- gate control means responsive to a particular one of said pull-in signals for controlling the state of said gate means.
- The present invention having the above features provides the following advantages:
- The provision of the single boost generator means reduces the cost of the fuel system and provides for uniform, repeatable and rapid opening of each solenoid. The utilization of the regulating means decreases the power requirements of the system and related heat dissipation problems. The gate control means in cooperation with the boost generating means permits efficient system operation for wide ranges of metering pulse width intervals including conditions defined by overlapping metering intervals while not requi-ring complicated circuitry to prematurely terminate a particular metering pulse width.
- .One way of carrying out the invention is described in detail below with reference to the drawings which illustrate one specific embodiment of this invention, in which:
- Figure 1 is a block diagram of the preferred embodiment of the present invention.
- Figure 2 is an electrical circuit diagram illustrating the circuitry to drive one of -a plurality of electromagnetic fuel injectors.
- Figure 3 illustrates the wave forms generated by the circuit of Figure 2.
- Figure 4 illustrates the wave forms generated by a control system which is designed to energize six electromagnetic fuel injectors.
- A Multiple Injector High Performance Drive
System 20 is illustrated in Figures 1.System 20 employs asingle booster circuit 22 to assist in developing sufficient voltage to open a plurality of electromagnetic fuel injectors. Thebooster circuit 22 comprises a boost control 24 and aboost generator 26, which are both shown in greater detail in Figure 2. The output of thebooster circuit 22 is connected to a plurality of solid state switches such as the plurality of silicon controlled rectifiers (SCR) 30a-n, . where n corresponds to the number ofinjector coils 54a-n. Each SCR 30 contains an anode terminal 32a-n, a cathode terminal 34a-n, and agate terminal 36a-n. An SCRgate control circuit 40 is connected to the gate terminal 36 of each rectifier 30 through a plurality ofsignal lines 42a-n. The system further contains a plurality of series connected circuits. Each series circuit includes a diode 50 having its anode connected to a positive voltage source +V and having its cathode connected to one terminal 52 of an electromagnetic fuel injection valve coil 54. Another terminal 56 of the coil 54 is connected to a respective driver 60. The output of the driver 60 is connected to one terminal of a current sensing resistor 64, the other terminal of which is connected to ground or some other suitable electrical potential. In the preferred embodiment, as shown in Figure 1, each driver includes a Darlington pair 62. The system further includes a plurality of current regulator andmode control circuits 70a-n, each of which is connected to its associateddriver 60a-n via . control lines 72a-n, respectively. Each current regulator and mode control circuit 70 is responsive to a metering signal input thereto which is generated in synchronism with a repeating engine event. The metering signals are generated by an electronic control unit (ECU) 90. The current regulator and mode control circuit 70 senses the voltage appearing across each respective sense resistor 64. This feedback voltage is transmitted to each current regulator and mode control circuit 70 via a plurality offeedback lines 74a-n. - The
system 20 further requires and generates additional timing and control signals: these are the pull-in and arm signals respectively. Each Metering signal (meter 1 through meter N) is connected to an input terminal .of one of themonostable multivibrators 30a-n. In response to each metering signal, each multivibrator 80 will generate at its inverting terminal (Q ) the inverted pull-in signal, and generate at its non-inverting terminal (Q) the pull-in signal. Each inverted pull-in signal is routed to a respective current regulator and mode control circuit 70. The non-inverted pull-in signal from each multivibrator 80 is connected through a line 130 (lines 130a-n) to the SCRgate control circuit 40 and to one of the input terminals of anOR gate 82 the output of which has been designated as the arm signal. The output of ORgate 82 is connected to an invertingamplifier 84 which generates an inverted arm signal (ARM) at its output terminal. The output ofamplifier 84 is connected as illustrated in Figure 1 to thebooster circuit 22. - Reference is now made to Figure 2, which illustrates a more detailed embodiment of the circuitry shown in Figure 1 necessary to activate
coil 54a. More particularly, there is shown abooster circuit 22 comprising a boost control circuit 24, the output of which controls the state of aboost generator 26. The boost control circuit 24 comprises acomparator 100 receiving at its inverting terminal the inverted ARM signal. Thecomparator 100 is appropriately biased and functions as a level shifter and buffer. The output ofcomparator 100 is connected to the base . terminal of annpn transistor 102 which performs driver and signal inversion functions. The collector oftransistor 102 is connected to the input of a Darlingtonpair 104. The output terminal 106 of the Darlington pair is connected via an output line 108 to an input terminal which is connected to - 109 which is connected to theboost generator 26. Theboost generator 26 includes a first storage capacitor 110 having aterminal 112 which is connected to the positive battery potential+V and aterminal 114 connected via a line 28 to each SCR 30 as previously described. Aboost coil 116 is also connected betweenterminal 112 and the input terminal 109. Adiode 118 is connected between the end ofboost coil 116 connected to terminal 109 andterminal 114. Thediode 118 is polled so that current flow. is in the direction of terminal 109 toterminal 114. Theboost generator 26 further includes a series combination of a Zener doide 120 and a blockingdiode 122 connected betweenterminals terminal 112 toterminal 114. As mentioned, the output of theboost generator 26, that is terminal 114, is connected via line 28 to the anode of each SCR 30. The cathode ofSCR 30a is connected to the cathode of thecoupling diode 50a. The anode of thecoupling diode 50a is connected in common toterminal 112 and to the positive potential voltage source +V such as a battery. - The SCR
gate control circuit 40 receives the plurality of pull-in signals,one associated with each coil, viainput lines 130a-n. It is apparent thatonly line 130a is shown in Figure 2. The following discussion relates to the circuitry necessary to receive and condition one of these pull-in signals to appropriately activate one of the SCR's 30. It should be appreciated that the SCRgate control circuit 40 contains a number of such circuits as hereinafter described. The pull-in signal, i.e. pull-in 1, is communicated vialine 130a to the base ofa.npn transistor 132a. The output or collector terminal oftransistor 132a is connected to the base of atransistor 134a, which has its emitter terminal grounded. The collector terminal oftransistor 132a is connected via a resistor 136a to a reference power supply potential which is less than the first voltage source, such as the 8 volt potential as indicated in Figure 2. The collector terminal oftransistor 134a is connected to this reference power supply via aresistor 138a and adiode 140a serially connected. In addition, the collector oftransistor 134a is connected to the gate terminal of a SCR 142a. The anode of SCR 142a is connected to one terminal of a second reference storage capacitor 144a.. The other terminal of the reference capacitor 144a is connected to the reference power supply voltage source viaterminal 112. The anode of SCR 142a -is also connected to the input terminal 109 via a resistor-diode combination 146a. The cathode of SCR 142a is connected to a voltagedivider having resistances 140a, b and c. The gate terminal ofSCR 30a is connected to the common node ofresistors 148b and 148c. - Reference is now made to the phantom lines and other connected components that are shown within the SCR gate
circuit control circuit 40. These phantom lines illustrate the suggested connection of additional components 142b, 144b etc. to permit the controlled energization of other coils such ascoil 54b (see Figure 1). - Reference is now made to one of the current regulator and mode control circuit 70 which is shown comprising a
current reference generator 150 and a current regulator 170. Thecurrent reference generator 150 further includes a pull-in current level adjustcircuit 152, a hold current level adjustcircuit 154 and a peakcurrent control circuit 156. More particularly, the current reference generator includes aninput comparator 160 receiving at its inverted input an inverted pull-in signal. -
Comparator 160 operates as a voltage level shifter and buffer having its output connected. via apotentiometer 162 to a reference voltage source such as the 8 volt potential. Thepotentiometer 162 provides the pull-in current level adjustment. - The output of
comparator 160 is also connected to the parallel combination of aresistor 155 and acapacitor 157 forming the peak current control.circuit.156. The peakcurrent control circuit 156 may be a differentiator and insures a sufficient level of high voltage to saturate the output (transistor 174) of the current regulator 170 until the boost voltage from capacitor 110 is dissipated. The output of the peak'current control circuit 156 is connected to the anode of a blocking diode 166, the cathode of which is connected to the hold current level adjust circuit which comprisespotentiometer 168. The cathode of the blocking diode 166 is further connected to the input of the current regulator 170. The input to the current regulator 170 comprises the non-inverting input terminal of anoperational amplifier 172. The output ofoperational amplifier 172 is connected via a voltage divider to the base of a npn transistor .174, the emitter terminal of which is connected to the input or base terminal of thedriver 60a.Driver 60a comprises a Darlington pair 176a. The emitter of the Darlington pair 176a is connected to one terminal of thesense resistor 64a. The other terminal of thesense resistor 64a as indicated is grounded. The emitter output of the Darlington pair 176a is communicated via a feedback resistor to the inverting input terminal of the operational amplifier 172a therein creating a current sensing feedback path. - The cathode terminal of
SCR 30a and thecoupling diode 50a are connected to the input terminal of a transient suppressor comprising the parallel combination of a capacitor 178a and a resistor 180a. The input terminal of this parallel combination is also connected to theinput terminal 52a of theinjection coil 54a. The other terminal of the transient suppressor is connected to the cathode of a blocking diode 182a. The anode of blocking diode 182a is connected to terminal 56a ofcoil 54a. The anode of diode 182a and terminal 56a of thecoil 54a are connected to the collector terminal of the Darlington pair 176a. circuit - Each current regulator and mode control circuit 70 further includes an on-off
control circuit 188 comprising alevel switching comparator 190 receiving at its inverting input via a line 192 a metering signal such asMETER 1.. The output of thelevel switching comparator 190 is connected to the base terminal of an inverting transistor 194. The collector of transistor 194 is connected to the base terminal of transistor 174. - Reference is now made to Figure 3 which illustrates the operation of the circuit disclosed in Figures 1 and 2 during an illustrative single coil activation or fuel injection event. In response to a previous ARM signal (the inverted ARM signal, ARM, is shown on
line 4 of Figure 3') the boost voltage (line 6, Figure 3) will be maintained at a quiescent voltage level. It should be realized that the boost voltage illustrated inline 6 represents the voltage stored on the storage capacitor 110 which is typically greater than the voltage level of the reference power supply. In the quiescent condition, the coil current, which is shown in line 7 of Figure 3, is zero. The operation of thebooster circuit 22 comprising the boost control circuit 24 and theboost generator 26 is as follows: As the inverted ARM signal (ARM ) goes low, current is drawn from the battery through theboost coil 116 and theDarlington pair 104 to ground. When the ARM signal goes high, theDarlington pair 104 is turned off, causing a capacitor charging current path to exist wherein the current which is flowing through theboost coil 116 now flows throughdiode 118 to charge the storage capacitor 110. Part of the current flows through the diode-resistor combination 146 and charges each capacitor 144. As previously mentioned, thebooster circuit 22 includes a Zener diode 120 anddiode 122 serially connected. The Zener diode 120 limits the voltage across the capacitor 110 and also provides a relatively constant reference voltage thereacross. In the preferred embodiment, the Zener diode 120 provides a 130-140 volt reference. However, this voltage is dependent on the coil characteristics and can be any level. The purpose of thediode 118 is. to prevent the voltage on the charged capacitor from being returned to thecoil 116.Diode 122 prevents current from flowing through the Zener diode 120 in the forward direction after the boost is dissipated. The coil 54- is coupled to the battery through diode 50. This direct coupling of the battery to the coil 54 and other sections of the circuit permits battery current to flow automatically when the voltage on the storage capacitor 110 becomes less than the forward voltage of diode 50. The SCRgate control circuit 40 receives at its input a pull-in signal on input line 130. Each pull-in signal may be derived from a particular meter signal which is related to a periodic activation or engine event such as a crankshaft position. The meter signals may be derived in a known manner from any of the known variety of crankshaft position sensors or electronic control units. The occurrence of the positive pull-in signal causes transistor 132 to become conductive, therein causing the voltage at the collector of transistor 132 to approach ground potential. This voltage potential is communicated to the base of transistor 134 and is of such magnitude as to return transistor 134 to a nonconducting state. At this point the gate terminal of SCR 142 is activated. The voltage appearing across the storage capacitor 144 upon the activation of SCR 142 is applied to the voltage divider 148, which in turn activates SCR 30. Upon the activation of SCR 30 by the positive pull-in signal the stored energy in the storage capacitor 110 is caused to flow through the coil 54, assuming, of course, that a particular driver 60 has been so activated by an associated on-offcontrol circuit 188. Each SCR 30 requires that the gate potential be higher than the cathode potential in order to trigger it. A fraction of the boost energy is diverted to obtain a higher voltage to fire SCR 30. This is accomplished in the preferred embodiment using the diode-resistor combination 146, capacitor 144, SCR 142, and resistors of voltage divider 148. - During these injector coil activation periods, which span the duration of each meter signal the path of current flow is from the storage capacitor 110 or from the battery through a particular injector coil 54 and through a driver 60. During periods when the driver 60, which can be the Darlington pair 176 is turned off, current flows from the coil 54 through diode 182 and into the resistor-capacitor combination 178-180. In this manner, the resistor-capacitor combination 178-190 provides transient suppression during coil activation periods as well as a discharge path during non-activation periods for the coil current.
- When the metering signal goes high,
comparator 190 output becomes low, which in turn places transistor 194 into a cut-off state. When transistor 194 is placed into a cut-off state, the transistor 174 is activated. This in turn activates the Darlington pair 176 to permit current flow from the storage capacitor 110 through the injector coil 54 and through the sense resistor 64 to ground. - Reference is made to the
current reference generator 150 and the current regulator 170 which controls the pull-in and hold current. Normally, current is supplied by theoperational amplifier 172 to the base of transistor 174 during metering. During this interval transistor 194 is biased off. When the meter signal goes low, transistor 194 conducts and diverts the base current of 174, effectively cutting off the drive current to coil 54. - The output of the
current reference generator 150 is a voltage waveform which is shown in Figure 3. Normally, the inverted pull-in signal which is connected to the inverting input ofcomparator 160 is in a high state, causing its output to be near ground potential. In this condition, diode 166 is reverse-biased, essentially isolating the peakcurrent control circuit 156. The current reference voltage is determined by the hold current level adjustcircuit 154. In addition, in this state, the capacitor in the peakcurrent control circuit 156 will discharge to zero volts. - When the metering pulse is initiated, it is desired to regulate the current flowing through coil 54 to the higher pull-in current. At that point in time, the inverted pull-in signal, connected to
comparator 160, goes to a low voltage, e.g. near ground. Theoutput comparator 160, which is essentially an open collector device, goes to a high impedance state. When this occurs, the pull-in current level adjustcircuit 152 and peakcurrent control circuit 156 cause diode 166 to become forward-biased. The net effect of this is to cause the voltage at the cathode of diode 166 to be higher, due to the additional parallel resistance. The current reference voltage is now determined by the voltage divider which consists of thepotentiometer 168 and the parallel combination ofresistor 169 and the series circuit of the pull-in current level adjust circuit and peak current control circuit. - At the instant the inverted pull-in pulse goes low, the
capacitor 157 in the peakcurrent control 156 is discharged and effectively shorts out the resistor. 155. This initial lower resistance causes the current reference voltage to have a slight overshoot, or peak, at the start to insure that the output stage of the driver remains saturated long enough to dissipate all of the boost energy and indeed get up to the pull-in current as fast as possible. - Reference is now made to Figure 4 which is a timing diagram for a system with six high pressure common rai.l injectors. When using this type of injector fuel, injection occurs. at the end of each metering or activating period, as shown in Figure 4. The duration of the metering signal, as well as the injection advance, are generated as a function of engine parameters in a known manner by the electronic control unit 90 (Fig. 1). The duration of the pull-in signal would generally be fixed for any given application and is generally a function of the solenoid valve, as is the pull-in current level and boost voltage. Variable duration pull-in signals may also find application under certain circumstances. Pull-in always occurs at the beginning of the valve coil energization period (in this case at the start of metering, as shown in Figure 4). The arming signal duration is usually a fixed time period for a given valve coil and is determined by the valve coil parameters and the boost circuit parameters. Arming generally occurs at some convenient point in time when the circuit is not being used. For this application, arming would take place immediately following pull-in.
- One of the advantages of the present invention is that the
single booster circuit 22 can effectively drive a plurality of injector coils 54 during periods of excessive engine speeds. During these periods of high engine speed, the corresponding engine revolution period is proportionately reduced therein requiring that the metering signals for each injector be generated with a characteristic pulse overlap as illustrated in Figure 4. Figure 4 further illustrates the time synchronization, of the respective metering and pull-in signals and the resultant boost voltage pulse train generated in response thereto.
Claims (14)
1. A solenoid driving system for energizing a plurality of electromagnetic devices, each device including a solenoid having a coil (54) having a first terminal (52) connected to a voltage source (+V) and a second terminal (56), said system being adapted to receive a plurality of electrical metering pulses, one pulse associated with each device, for activating particular devices and being characterized in that it comprises: regulating means (70), one associated with each said device, for selectively permitting current to flow through specified ones of said devices; current sensing means (64) connected to each of said regulating means (70) for sensing the level of current flowing through a specific one of said devices; driver means (60), one associated with each of said devices, connected in series with said coil (54) and said current sensing means (64) for establishing a current flow path therethrough in response to a particular metering signal; diode means (50) connected in series with said voltage source and the said coil (54) of each of said devices; boost generator means (22,26) connected to said voltage source-and to each of said devices for periodically generating, prior to each metering pulse, a boost voltage energization signal having a voltage potential greater than the voltage potential of said voltage source; signal generating means (80) for generating a pull-in signal in response to the initiation of each of the metering signals wherein the duration of each of said pull-in signals is a determinable fraction of the duration of a particular one of said metering pulses; boost control means (82,84,24) responsive to the plurality of said pull-in signals for causing said boost generator means (22,26) to regenerate said energization signal; gate means (30), one associated with each of said devices, having activation and deactivation states of operation, for controlling the application of said energization signal during the activation state to its associated one of said devices; and gate control means (40) responsive to a particular one of said pull-in signals for controlling the state of said gate means (30).
2. A system as claimed in claim 1, characterized in that each of said pull-in signals is of a fixed duration.
3. A system as claimed in claim 1, characterized in that said gate means (30) comprises a silicon controlled rectifier (30) having its anode terminal (32) connected to the output of said boost generator means (22,26), its cathode terminal (34) connected to the common point of said diode means (50) and said coil (54) and further having its gate terminal (36) connected to the output of an associated one of said gate control means (40).
4. A system as claimed in claim 3, characterized in that said gate control means (40) comprises: level shifting means (132,134,136,138,140) for receiving and for buffering an associated one of said pull-in signals; switch means (142,148) interposed between said level shifting means (132-140) and the gate terminal (36) of said silicon controlled rectifier (30) for energizing said gate terminal.
5. A system as claimed in claim 4, characterized in that said switch means (142,148) includes a second silicon controlled rectifier (142) having cathode, anode and gate terminals wherein said gate terminal is connected to the output of said level shifting means (132-140), said cathode . terminal is coupled to said gate terminal (36) of an associated one of said silicon controlled rectifiers (30) of said gate means (30); and said gate control means (40) further includes a storage capacitor means (144) having a first terminal connected to said voltage source and further having a second terminal connected to the anode of said second silicon controlled rectifier (142) for storing a portion of said energization signal and a diode-resistor series combination (146) wherein the anode terminal of said diode is connected to the output of said boost control means (82,84,24) and one terminal of said resistor is connected to said second terminal'of said storage capacitor means (144).
6. A system as claimed in claim 1, characterized in that said regulating means (70) includes: current reference generator means (150), one associated with each said device, responsive to said pull-in signals for generating a first and a second reference current level wherein said first reference current level is greater than or equal to the value of current necessary to activate a particular one of said devices and wherein said second reference current level corresponds to a level of current necessary to hold said device in an open or activated state; and current regulator means (170) connected to said current reference generator means (150) and to said current sensing means (64) for regulating the current flowing .through said device in accordance with said first and said second reference current level.
7. A system as claimed in claim 6, characterized in that said current sensing means (64) comprises a sense resistor (64) connected to the second terminal (56) of said coil (54).
8. A system as claimed in claim 6, characterized in that said current reference generator means (150) includes: a hold current level adjust circuit (154) for establishing said second reference current level; a pull-in current level adjust circuit (152) for establishing said first reference current level; a peak current control circuit (156) for shaping the peak current level of the pull-in current to maintain said driver means (60) in a saturated state during the interval that energy is being dissipated through said coil (54) and said current sensing means (64); level shifter (160) adapted to receive the complement signal of said pull-in signal, the output of which is connected in common to said pull-in current level adjust circuit (152) and said peak current control circuit (156); and a diode (166) having its anode connected to the output of said peak current control circuit (156) and having its cathode connected to said hold current level adjust circuit (154) and also connected to said current regulator means (170).
9. A system as claimed in claim 8, characterized in that said boost control means (82,84,24) comprises: an OR gate (82) receiving each of said pull-in signals; inverting amplifier means (84) for inverting the output of said OR gate (82); level shifting means (100) receiving at an inverting input terminal the output of said inverting amplifier means (84) for buffering the received signal; NPN transistor (102) having its base terminal connected to the output of said level shifting means (100), and having its emitter terminal connected to a voltage source (+8V); and output driver means (104), having an output terminal (106) connected to said boost generator means (22,26) for applying a control signal to the input terminal of said boost generator means (22,26).
10. A system as claimed in claim 6, characterized in that said current regulator means (170) comprises: an amplifier (172) responsive to the output of said current reference generator means (150) and to the voltage across said current sensing means (64); an on/off control circuit (190, 194) responsive to a particular metering pulse; an output transistor (174) of the NPN type having its base connected to the output of said amplifier (172) and the output of said on/off control circuit(190,194), the collector terminal of said output transistor (174) being connected to a voltage source (+8V) and the emitter terminal of said output transistor (174) being connected to the input of said driver means (60), and in that said on/off control circuit (190,194) includes: level switching comparator means (190) receiving at an inverting input terminal a particular metering pulse for buffering said metering pulse; a transistor (194) of the NPN type having its base terminal connected to the output of said level switching comparator means (190) and having its cathode terminal connected to the base of said output transistor (174).
11. A system as claimed in claim 1, characterized in that said boost generator means (22,26) comprises: first means (116,118,120,122) for removing from said voltage source (+V) a first value of electrical energy in response to control signals input thereto; and second means (110) for receiving electrical energy from said first means (116-122) and for storing a voltage potential therein.
12. A system as claimed in claim 1, characterized in that there is provided means (90) for sequentially generating said plurality of metering pulses, each of said metering pulses being of a determinable duration.
13. A system as claimed in claim 1, characterized in that each of said devices is a fuel injector, adapted to receive fuel, of the type having means for generating a fuel metering mode initiated in response to a particular.one of said metering pulses for storing a determinable quantity of fuel therein and having means for generating an injection mode for ejecting said stored quantity of fuel therefrom in correspondence with the termination of said metering pulse.
14. A system as claimed in claim 12, characterized in that said means (90) for sequentially generating said plurality of metering pulses is adapted to generate a train of pulses wherein a subsequently generated metering pulse overlaps the immediately preceding pulse.
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
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US06/117,679 US4327693A (en) | 1980-02-01 | 1980-02-01 | Solenoid driver using single boost circuit |
US117679 | 2002-04-05 |
Publications (2)
Publication Number | Publication Date |
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EP0034076A2 true EP0034076A2 (en) | 1981-08-19 |
EP0034076A3 EP0034076A3 (en) | 1981-09-23 |
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Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
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EP81400094A Withdrawn EP0034076A3 (en) | 1980-02-01 | 1981-01-23 | Solenoid driving system |
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US (1) | US4327693A (en) |
EP (1) | EP0034076A3 (en) |
JP (1) | JPS56124211A (en) |
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US9611797B2 (en) * | 2012-10-30 | 2017-04-04 | National Instruments Corporation | Direct injection flexible multiplexing scheme |
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FR93062E (en) * | 1966-04-13 | 1969-02-07 | Jacques Bassot | Improvements to electronic injection devices and injectors used with these devices. |
FR2051074A5 (en) * | 1969-06-11 | 1971-04-02 | Cav Ltd | |
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US3889162A (en) * | 1974-02-04 | 1975-06-10 | Ledex Inc | Solenoid driving means |
FR2370216A1 (en) * | 1976-11-05 | 1978-06-02 | Renault | CONTROL DEVICE BY CURRENT PROGRAM OF SEVERAL SOLENOID VALVES WITH SIMULTANEOUS ASYNCHRONOUS OPERATION OR NOT |
US4112477A (en) * | 1977-06-06 | 1978-09-05 | General Motors Corporation | Circuit for energizing a fuel injector valve coil |
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US3665901A (en) * | 1968-12-27 | 1972-05-30 | Sopromi Soc Proc Modern Inject | System controlling the speedy energization of electromagnets, chiefly those controlling the opening of electromagnetic injectors in internal combustion engines |
US3882829A (en) * | 1969-10-08 | 1975-05-13 | Takeo Sasaki | Fuel injection control device |
US4173030A (en) * | 1978-05-17 | 1979-10-30 | General Motors Corporation | Fuel injector driver circuit |
-
1980
- 1980-02-01 US US06/117,679 patent/US4327693A/en not_active Expired - Lifetime
- 1980-12-19 CA CA000367199A patent/CA1167909A/en not_active Expired
-
1981
- 1981-01-23 EP EP81400094A patent/EP0034076A3/en not_active Withdrawn
- 1981-01-31 JP JP1372281A patent/JPS56124211A/en active Pending
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Publication number | Priority date | Publication date | Assignee | Title |
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FR93062E (en) * | 1966-04-13 | 1969-02-07 | Jacques Bassot | Improvements to electronic injection devices and injectors used with these devices. |
FR2051074A5 (en) * | 1969-06-11 | 1971-04-02 | Cav Ltd | |
DE2262864A1 (en) * | 1971-12-27 | 1973-06-28 | Acf Ind Inc | ELECTRONICALLY CONTROLLED INJECTION DEVICE FOR COMBUSTION MACHINES |
US3889162A (en) * | 1974-02-04 | 1975-06-10 | Ledex Inc | Solenoid driving means |
FR2370216A1 (en) * | 1976-11-05 | 1978-06-02 | Renault | CONTROL DEVICE BY CURRENT PROGRAM OF SEVERAL SOLENOID VALVES WITH SIMULTANEOUS ASYNCHRONOUS OPERATION OR NOT |
US4112477A (en) * | 1977-06-06 | 1978-09-05 | General Motors Corporation | Circuit for energizing a fuel injector valve coil |
Cited By (29)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
FR2533263A1 (en) * | 1982-09-16 | 1984-03-23 | Renault | Device for control of rapidly-actuated electromagnetic members, such as solenoid valves or injectors for internal combustion engines |
EP0106743A3 (en) * | 1982-09-27 | 1985-10-16 | The Bendix Corporation | Switching type circuit for fuel injector |
EP0105780A2 (en) * | 1982-09-27 | 1984-04-18 | AlliedSignal Inc. | Boost voltage generator |
EP0105780A3 (en) * | 1982-09-27 | 1985-12-27 | The Bendix Corporation | Boost voltage generator |
EP0112089A1 (en) * | 1982-12-01 | 1984-06-27 | Solex (U.K.) Limited - In Liquidation | An air/fuel induction system for a multi-cylinder internal combustion engine |
US4545345A (en) * | 1982-12-01 | 1985-10-08 | Solex (U.K.) Limited | Air/fuel induction system for a multi-cylinder internal combustion engine |
EP0110699A1 (en) * | 1982-12-01 | 1984-06-13 | Solex (U.K.) Limited - In Liquidation | An air/fuel induction system for a multi-cylinder internal combustion engine |
US4617904A (en) * | 1982-12-01 | 1986-10-21 | Solex (U.K.) Limited | Air/fuel induction system for a multi-cylinder internal combustion engine |
FR2538942A1 (en) * | 1982-12-29 | 1984-07-06 | Renault | Device for control of electromagnetic unit(s) with rapid action, such as electrovalve(s) or injector(s) |
FR2569239A1 (en) * | 1984-03-05 | 1986-02-21 | Mesenich Gerhard | Electromagnet injection valve, esp. for fuel injection in IC engines |
EP0184940A2 (en) * | 1984-12-12 | 1986-06-18 | Technological Research Association Of Highly Reliable Marine Propulsion Plant | A method of controlling electromagnetic actuators and a controller therefor |
EP0184940A3 (en) * | 1984-12-12 | 1987-11-25 | Technological Research Association Of Highly Reliable Marine Propulsion Plant | A method of controlling electromagnetic actuators and a controller therefor |
FR2579820A1 (en) * | 1985-03-28 | 1986-10-03 | Renault | DEVICE FOR CONTROLLING ELECTROMAGNETIC ORGANS WITH QUICK ACTUATION |
EP0196960A1 (en) * | 1985-03-28 | 1986-10-08 | Regie Nationale Des Usines Renault | Fast acting control device for electromagnetic devices |
EP0305342A1 (en) * | 1987-08-25 | 1989-03-01 | MARELLI AUTRONICA S.p.A. | Circuit for controlling inductive loads, particularly for the operation of the electro-injectors of a diesel engine |
EP0305344A1 (en) * | 1987-08-25 | 1989-03-01 | MARELLI AUTRONICA S.p.A. | A circuit for the piloting of inductive loads, particularly for operating the electro-injectors of a diesel-cycle internal combustion engine |
EP0306839A1 (en) * | 1987-09-07 | 1989-03-15 | Sikora, Gernot, Dipl.-Ing. | Method and device for driving solenoids, particularly in injection valves |
WO1989002523A1 (en) * | 1987-09-07 | 1989-03-23 | Gernot Sikora | Process and device for driving electromagnets, in particular in injection valves |
WO1989003931A1 (en) * | 1987-10-30 | 1989-05-05 | Siemens-Bendix Automotive Electronics L.P. | A voltage doubler and system therefor |
FR2625260A1 (en) * | 1987-12-28 | 1989-06-30 | Peugeot | DEVICE FOR CONTROLLING AND CONTROLLING FUEL INJECTORS OF A MULTICYLINDER INTERNAL COMBUSTION ENGINE IN PARTICULAR AT TWO TIMES |
EP0323318A1 (en) * | 1987-12-28 | 1989-07-05 | Automobiles Peugeot | Device for controlling and checking fuel injectors in a multicylinder combustion engine, particularly two-stroke ones |
EP0560657A1 (en) * | 1992-03-10 | 1993-09-15 | Thomson-Csf | Energy transmission device for a mechanical control, particularly to control the braking pressure in a brake |
FR2688620A1 (en) * | 1992-03-10 | 1993-09-17 | Thomson Csf | MECHANICAL CONTROL ENERGY TRANSMISSION DEVICE, IN PARTICULAR FOR CONTROLLING THE BRAKING PRESSURE IN A BRAKE. |
US5438909A (en) * | 1992-03-10 | 1995-08-08 | Thomson-Csf | Device for energy transmission for mechanical control, in particular for the control of braking pressure in a brake |
EP0622536A2 (en) * | 1993-04-30 | 1994-11-02 | Chrysler Corporation | Electronic fuel injector driver circuit |
EP0622536A3 (en) * | 1993-04-30 | 1995-11-22 | Chrysler Corp | Electronic fuel injector driver circuit. |
CN109548771A (en) * | 2018-12-27 | 2019-04-02 | 佛山市顺德区乐雪儿电器有限公司 | Electromagnetism charge inductive type electric mosquito flap |
WO2020135617A1 (en) * | 2018-12-27 | 2020-07-02 | 佛山市顺德区乐雪儿电器有限公司 | Electromagnetic charge-sensitive electric mosquito swatter |
CN109548771B (en) * | 2018-12-27 | 2024-02-23 | 佛山市顺德区乐雪儿电器有限公司 | Electromagnetic charge induction type electric mosquito swatter |
Also Published As
Publication number | Publication date |
---|---|
JPS56124211A (en) | 1981-09-29 |
EP0034076A3 (en) | 1981-09-23 |
CA1167909A (en) | 1984-05-22 |
US4327693A (en) | 1982-05-04 |
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Inventor name: BUSSER, DARRYL WARREN |