CN219394471U - High-voltage energy-storage pulse capacitor charging power supply - Google Patents
High-voltage energy-storage pulse capacitor charging power supply Download PDFInfo
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- CN219394471U CN219394471U CN202223175436.3U CN202223175436U CN219394471U CN 219394471 U CN219394471 U CN 219394471U CN 202223175436 U CN202223175436 U CN 202223175436U CN 219394471 U CN219394471 U CN 219394471U
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Abstract
The utility model relates to a high-voltage energy-storage pulse capacitor charging power supply, which comprises an ACDC module, a voltage sensor, a current sensor HA and at least two DCDC modules, wherein the ACDC module is connected with the voltage sensor HA; each DCDC module is provided with an H-bridge inversion module H1, a plurality of paths of secondary side transformers T1 and at least two diode rectifying units, the primary sides of the paths of secondary side transformers T1 are connected with the H-bridge inversion module H1, the secondary sides of the paths of secondary side transformers T1 are provided with at least two single-phase windings, the outputs of the single-phase windings are respectively connected with the diode rectifying units, and the outputs of the diode rectifying units are sequentially connected in series; all the H bridge inverter modules H1 take electricity from the ACDC modules together, and the total output formed by sequentially connecting the outputs of the DCDC modules in series charges a load capacitor C2. The power supply provided by the utility model can reduce the output ripple of the high-voltage energy storage pulse capacitor charging power supply on the premise of meeting the high-voltage output of the power supply.
Description
Technical Field
The utility model relates to the field of power electronics, in particular to a high-voltage energy storage pulse capacitor charging power supply.
Background
The high-voltage energy-storage pulse capacitor is a high-peak current device widely applied to aviation and power industry, has special application, and can provide power for the high-energy-consumption industry. The capacitive energy storage type pulse technology is widely applied to the fields of electromagnetic emission, high-energy microwaves, laser nuclear fusion, strong particle beams and the like. With the development of the age, the high-voltage energy storage pulse capacitor has higher and higher requirements on a charging power supply. Firstly, the voltage level is developed from tens of kV to hundreds of kV; secondly, the charging mode is also developed from single constant voltage current limiting charging to multiple modes such as constant current charging, constant power charging, constant resistance charging and the like; in addition, high requirements are put on voltage and current ripple of the charging power supply.
Fig. 1 is a main circuit structure diagram of a common high-voltage energy-storage pulse capacitor charging power supply, which consists of a three-phase uncontrollable rectification circuit, a filter circuit, an H-bridge inversion circuit, an LC resonance circuit, a high-frequency transformer, an uncontrollable rectification circuit, an output filter circuit, a resistor R1, a voltage and current sensor and the like. In fig. 1, C2 is a high-voltage energy storage pulse capacitor, which is an object to be charged, and is also a load. The LC resonant circuit is used for enabling the H-bridge to work in a soft switching state in an inversion mode so as to reduce switching loss.
In the circuit structure of fig. 1, during operation, after the three-phase ac power supply is rectified uncontrollably, a 6-pulse dc voltage is obtained, and the pulse voltage is further passed through the C11 filter circuit to obtain a smoother dc bus voltage. After a charging command is obtained by the control system, if the charging command is constant-current charging, the control system uses a current sensor Am1 signal as a basis, controls the duty ratio or the frequency inversion of an H bridge to generate a high-frequency approximate alternating-current voltage waveform according to a given current, the high-frequency approximate alternating-current voltage waveform is obtained at the secondary side of a transformer after the voltage is boosted by the transformer Tr1, then the high-frequency approximate alternating-current voltage waveform is rectified into direct current through uncontrollable rectification, high-voltage direct-current output is obtained after the direct-current charging is carried out through a filter circuit, a load capacitor C2 is charged through a resistor R1, and the resistor R1 plays a role of maximum current limiting. After the load capacitor C2 is fully charged, the load end control device instantly releases the energy on the capacitor C2, and the power supply charges the load capacitor again.
The charging power supply has the following problems:
1) The filter circuit added at the output end of the power supply plays a role of output filtering, but becomes a part of the load capacitor when the load capacitor is charged and discharged, so that the charge and discharge energy is inaccurate, and even the normal operation of the system is affected;
2) The transformer directly adopts diode rectification after rising to the highest voltage, because alternating voltage is very high, rectifying bridge arm needs a large amount of diodes to connect in series and divide voltage, and the highest withstand voltage of diode in the market is only 10kV at present, if 100kV output is needed, each bridge arm needs at least 10 such diodes to connect in series. The diode series connection is easy to have the problem of unbalanced voltage division, and a static voltage-sharing circuit and a dynamic voltage-sharing circuit are required to be designed for the series connection diodes, and diode device screening, parameter matching and the like are required. In a word, the reliability of the power supply product is greatly reduced, and the mass production is not easy. If the direct current output voltage is 100kV, the turns ratio of the primary side of the transformer is 1:100 on the premise that the input voltage is 1000V, and the primary side of the transformer has a large transformation ratio, so that the voltage of the secondary side can be greatly changed due to small voltage adjustment of the primary side, and the ripple performance of the power supply is not ideal.
Disclosure of Invention
The utility model aims to improve or partially improve the defects in the prior art, and reduces the output ripple of the high-voltage energy-storage pulse capacitor charging power supply on the premise of meeting the high-voltage output of the power supply.
For this purpose, a high-voltage energy-storage pulse capacitor charging power supply is provided, which comprises an ACDC module, a voltage sensor, a current sensor HA and at least two DCDC modules; each DCDC module is provided with an H-bridge inversion module H1, a plurality of secondary side transformers T1 and at least two diode rectification units, the primary sides of the plurality of secondary side transformers T1 are connected with the output of the H-bridge inversion module H1, the secondary sides of the plurality of secondary side transformers T1 are provided with at least two single-phase windings, the output of each single-phase winding is respectively connected to one diode rectification unit, and the output of each diode rectification unit is sequentially connected in series to form the output of the DCDC module; the ACDC modules are used for taking electricity to the outside, the H bridge inverter modules H1 of the DCDC modules take electricity from the output ends of the ACDC modules together, and the total output formed by sequentially connecting the outputs of the DCDC modules in series is used for charging the load capacitor C2; the voltage sensor is used for acquiring a voltage signal reflecting the total output, and the current sensor HA is used for acquiring a current signal reflecting the total output.
Further, the current sensors HA have a plurality and are in number corresponding to the DCDC modules, and each current sensor HA is configured to be mounted on the primary side of each of the multiple secondary-side transformers T1.
Further, each DCDC module is further provided with an inductance Lr and a capacitance Cr, and the inductance Lr and the capacitance Cr are respectively connected in series to two ends of the primary side of the multi-path secondary side transformer T1 of the DCDC module.
Further, the output of each DCDC module is sequentially connected in series to form a total output positive electrode, and the total output positive electrode charges the load capacitor C2 through the diode D1, wherein the anode of the diode D1 faces the positive electrode.
Further, the voltage sensor comprises a voltage dividing circuit formed by connecting a plurality of resistors in series, and the voltage dividing circuit is connected across the two ends of the total output in parallel with the load capacitor C2.
Furthermore, the ACDC module is an ac/dc conversion module adopting a vienna rectification method.
The utility model adopts a mode of connecting a plurality of DCDC modules in series, improves the equivalent switching frequency of power supply output, and improves the equivalent switching frequency of output under the conditions of smaller load capacitance and short charging time requirement, thereby obviously improving the ripple wave of the output power supply, namely, the method is mainly used for application occasions with higher requirements on high-voltage output ripple wave.
In addition, the high-voltage energy storage pulse charging power supply does not consume energy in a discharging loop at the moment that any energy storage filter element is not arranged on the secondary side of the power supply transformer, namely, the capacitor is discharged after the load capacitor is fully charged. From the waveform, the power supply stops outputting the power externally at the moment of discharging, and no energy storage element discharges the power externally. That is, the utility model skillfully utilizes the load capacitor as the output filter circuit of the power supply, not only obtains smooth charging voltage waveform, but also does not increase the difficulty of discharging the load capacitor by the load, and has no redundant energy loss.
In addition, by arranging a plurality of output paths of the transformer winding, each path of independent diodes are sequentially connected in series after rectification, on one hand, the primary side turns ratio of the transformer can be reduced, the static voltage-sharing and dynamic voltage-sharing designs led out by diode series connection are avoided, and the problem that a plurality of diodes are easy to damage in series connection is solved.
Drawings
Fig. 1 shows a main circuit structure diagram of a conventional compact high-voltage energy-storage pulse capacitor charging power supply.
Fig. 2 shows an electrical diagram of a high voltage energy storage capacitor pulse charging power supply of the present utility model.
Fig. 3 shows the trigger waveforms with the two modules offset from each other by 90 °.
Fig. 4 shows an electrical simulation of the high voltage electric Rong Maichong charging power supply of the present utility model.
Fig. 5 shows an electrical simulation waveform diagram of the high voltage electric Rong Maichong charging power supply.
Detailed Description
The technical scheme of the utility model is further described below with reference to the attached drawings and specific embodiments.
The high-voltage energy-storage pulse capacitor charging power supply is input into three phases of 380V, the output direct-current voltage is DC10kV-DC100kV, constant-current, constant-voltage, constant-power and constant-resistance mode pulse output can be realized, the rated power of the power supply is 30kW, the rated voltage is DC100kV, and the rated current is 0.3A. The power supply runs in two quadrants, the alternating current of the power grid can be converted into direct current and input to the capacitive load, and the energy of the capacitive load at the direct current end cannot be inverted back to the power grid.
In order to meet the high-voltage output of the power supply and reduce the ripple of the output power supply, the high-voltage Rong Maichong charging power supply main circuit electric principle topological scheme block diagram is shown in fig. 2, and consists of an ACDC module, a voltage sensor, a current sensor HA and two DCDC modules. The ACDC module is used for taking electricity from outside. The DCDC module adopts a plurality of modes of establishing ties, and the DCDC module comprises H bridge contravariant module H1, multichannel secondary side transformer T1 and 5 diode rectification units, encapsulates in a module, and the primary side of multichannel secondary side transformer T1 meets with H bridge contravariant module H1's output, and next limit has 5 single-phase windings, and the output of each single-phase winding is connected to a diode rectification unit respectively, and the output of each diode rectification unit establishes ties in proper order and forms the output of this DCDC module. The H bridge inverter modules H1 of the DCDC modules take power from the output ends of the ACDC modules together, and the total output formed by sequentially connecting the outputs of the DCDC modules in series charges a load capacitor C2. The voltage sensor is used for acquiring a voltage signal reflecting the total output, and the current sensor HA is used for acquiring a current signal reflecting the total output.
When the DC module of the capacitor pulse charging power supply converting 1000V into 100kV works, a transformer outputs 5 paths of secondary sides, REC1-REC5 are respectively rectified, 10kV can be obtained at maximum after each path of secondary sides are rectified, and 50kV voltage can be obtained at maximum after the REC1-REC5 are connected in series. In fig. 2, two DCDC modules are connected in series, so that 100kV power output can be obtained at maximum.
In order to reduce the ripple of the output power supply, the alternating current frequency of the H bridge inversion output of each DCDC module is unchanged, 100kHz is still adopted for independent control, carrier phases of the modules are staggered, and the frequency of the direct current output power supply is indirectly improved. Here two DCDC modules are connected in series, the equivalent switching frequency being 200kHz. The specific staggering principle is 180 DEG/N, N being the number of DCDC modules. The 1000V-to-100 kV pulse power supply is formed by connecting two DCDC modules in series, so that the carrier phase shift angle is 90 degrees, and the actual waveform is shown in figure 3. In fig. 3, the first two waveforms are H-bridge trigger waveforms of the DCDC1 module, and the second two waveforms are H-bridge trigger waveforms of the DCDC2 module. From the waveform diagram, it can be seen that the IGBT trigger waveforms of the two modules are offset from each other by 90 °.
Fig. 4 discloses an electrical simulation of a high-voltage power supply Rong Maichong, wherein a given current is 20A, when the power supply is charged to 99ms, a control center closes PWM output to stop charging a capacitor, and simultaneously controls a discharging loop switch S1 to be closed, and the instantaneous discharging of the energy on a 200nF capacitor is completed within 1ms, and a discharging resistor in a simulation model takes 1 Ω. After 1ms, the control switch S1 is turned off, the power supply continues to charge the capacitor, and after 99ms, discharging is completed within 1ms, and the process is repeated. The frequency of the PWM wave is 100kHz, because the carrier phase shift 90 degrees is adopted by the two DCDC modules in series connection, and the actual carrier output frequency of the power supply is 200kHz.
The simulation waveform diagram of the high-voltage power Rong Maichong charging power supply is shown in fig. 5, waveform 1 is an output voltage waveform, waveform 2 is a primary side input current waveform of a transformer in the DCDC1 module, and waveform 3 is a current waveform of a rectifier diode D11. It can be seen from waveform 1 that the capacitance has been charged to 100kV early in 99ms and discharged to 0V in 1 ms. From the waveform, after the equivalent output frequency is improved, the waveform of the ripple wave of the output power supply has no obvious change.
The utility model adopts a mode of connecting a plurality of DCDC modules in series, improves the equivalent switching frequency of power supply output, and improves the equivalent switching frequency of output under the conditions of smaller load capacitance and short charging time requirement, thereby obviously improving the ripple wave of the output power supply, namely, the method is mainly used for application occasions with higher requirements on high-voltage output ripple wave.
In addition, the high-voltage energy storage pulse charging power supply does not consume energy in a discharging loop at the moment that any energy storage filter element is not arranged on the secondary side of the power supply transformer, namely, the capacitor is discharged after the load capacitor is fully charged. From the waveform, the power supply stops outputting the power externally at the moment of discharging, and no energy storage element discharges the power externally. That is, the utility model skillfully utilizes the load capacitor as the output filter circuit of the power supply, not only obtains smooth charging voltage waveform, but also does not increase the difficulty of discharging the load capacitor by the load, and has no redundant energy loss.
In addition, by arranging a plurality of output paths of the transformer winding, each path of independent diodes are sequentially connected in series after rectification, on one hand, the primary side turns ratio of the transformer can be reduced, the static voltage-sharing and dynamic voltage-sharing designs led out by diode series connection are avoided, and the problem that a plurality of diodes are easy to damage in series connection is solved.
The power supply structure shown in fig. 1 also has drawbacks including: in the constant current, constant power and constant resistance modes, PI control is required by taking current as a closed loop, a current sensor is installed on a direct current output side, as in Am1 in fig. 1, the direct current output side is a direct current high voltage output end, when the charging power is constant, the higher the voltage is, the smaller the current is, the more difficult the control system detects micro current, the accuracy is low, the output current cannot be accurately controlled, if the input voltage of the pulse power supply is DC1000V, the output voltage is DC100kV, and if the output end is charged with 0.1A, the current of the input end is 10A. If the PI regulation is formed by weak current at the output end, the system is difficult to stabilize.
To improve the above problem, as shown in fig. 2, further, a plurality of current sensors HA are provided, the number of which corresponds to that of DCDC modules, and the positions of the current sensors HA are configured to be mounted on the primary side of each of the multiple secondary transformers T1. Because the voltage of the output end of the power supply is 100 times of the input voltage, and under the condition of constant power, the current is inversely proportional to the voltage, so in order to rectify and accurately and reliably measure the actual charging current, the control system converts the high-voltage direct-current charging current given by a user into the current of the primary side of the transformer according to the transformer transformation ratio and the winding number, the current is the given current, the effective value of the alternating current of the low-voltage input end is detected to carry out PI regulation, and because the secondary side is low voltage, the sensor has no extra-high voltage requirement in the type selection, and the cost is reduced.
In the constant current pulse charging mode, PI (proportional integral) adjustment is carried out on the difference value between a given direct current output current I and an actual direct current output current I to obtain a modulation wave, the modulation wave is compared with a triangular carrier wave to obtain PWM pulses with the duty ratio changing in real time to control the on or off of an H bridge arm IGBT, and the H bridge inverts an alternating voltage waveform with adjustable voltage amplitude. When the charging current is larger than the given value current, the effective value voltage inverted by the H bridge is reduced, so that the charging current is reduced; when the charging current is smaller than the given value current, the effective value voltage of the inversion of the H bridge is increased, so that the charging current is increased. The charging current is fluctuated around a given current value by PI iterative adjustment.
For a constant-power and constant-resistance pulse charging mode, the output voltage is sampled in real time according to the given power or resistance value, the current given current value is calculated, and then the current given current value is sent into the PI regulator.
More preferably, each DCDC module is further provided with an inductance Lr (such as L11 and L101 in fig. 2) and a capacitance Cr (such as C11 and C101 in fig. 2), where the inductance Lr and the capacitance Cr are respectively connected in series to two ends of the primary side of the multi-path secondary side transformer T1 of the DCDC module, and the H-bridge inverter module generates high-frequency ac, and outputs the high-frequency ac to the primary side of the transformer after current limiting, filtering and blocking by the inductance L1 and the capacitance C1, where inductance L1 has a large inductance, and mainly plays a role in current limiting and filtering and also plays a role in reducing H-bridge switching loss. Furthermore, the ACDC module is an alternating current-direct current conversion module adopting a Vienna rectification mode, the AC380V obtains 1000V direct current bus voltage after passing through the AC/DC module, and the ACDC directly uses a standard module adopting the Vienna rectification mode, so that 1000V direct current bus voltage can be directly obtained, the power factor is improved, and the harmonic interference of a power supply to a power grid is reduced. The method comprises the steps of obtaining an alternating current waveform through H-bridge inversion, introducing an LC circuit in consideration of the square wave pulse of the H-bridge inversion waveform, enabling the waveform passing through the LC to be basically similar to a sinusoidal alternating current waveform, boosting through a transformer to obtain a plurality of paths of high-voltage alternating current waveform outputs, rectifying through diodes to obtain direct current voltages, and connecting the rectified direct current voltages in series to form a higher rectified voltage output.
In this embodiment, the voltage sensor includes a voltage dividing circuit formed by connecting a plurality of resistors in series, and the voltage dividing circuit is connected across two ends of the total output and is connected in parallel with the load capacitor C2, where although a voltage sampling circuit is added to the output end of the power supply, there is no energy loss basically due to a large resistance value of the sampling resistor, and the energy loss is negligible.
As a further development, the positive pole of the total output formed after the outputs of the individual DCDC modules are connected in series in sequence can be provided to charge the load capacitor C2 via the diode D1, wherein the anode of the diode D1 faces the positive pole. Because the high-voltage energy storage pulse capacitor can generate smaller negative voltage in the discharging process, the diode D1 is added at the output end of the charging power supply, and direct connection of the reverse current of the capacitive load to the diode rectification can be prevented.
The power supply structure of the embodiment has the advantages that:
1) The control is simple, and the inversion of one H bridge is controlled through PI regulation;
2) The method for converting the given direct current at the output end into the primary alternating current effective value to participate in operation reduces the requirement of the current sensor and improves the sampling precision of the system on the current. If the current sensor is arranged at the direct current output end, the sampling current is small, the sensor needs to withstand an ultrahigh-voltage environment, the insulation requirement on the sensor is high, the sensor is not easy to purchase, a method of converting given output current into equivalent alternating current at the primary side of the transformer is adopted, and the current sensor is adopted by a conventional sensor;
3) The high-voltage energy-storage pulse charging power supply does not consume energy in a discharging loop at the moment that any energy-storage filter element is not arranged on the secondary side of the power supply transformer, namely, the capacitor discharges after the load capacitor is fully charged. From the waveform, the power supply stops outputting the power externally at the moment of discharging, and no energy storage element discharges the power externally. That is, the utility model skillfully utilizes the load capacitor as the output filter circuit of the power supply, not only obtains smooth charging voltage waveform, but also does not increase the difficulty of discharging the load capacitor by the load and has no redundant energy loss;
4) The mode of connecting a plurality of DCDC modules in series is adopted, so that the equivalent switching frequency of power supply output is improved, and under the conditions of smaller load capacitance and short charging time requirement, the equivalent switching frequency of output is improved, and the ripple wave of the output power supply is obviously changed;
5) The output voltage detection adopts the voltage division mode of the output resistor for detection, and has low cost and simple and convenient detection.
The above-described embodiments are only a few preferred embodiments of the present utility model, and many alternative modifications and combinations of the above-described embodiments will be apparent to those skilled in the art based on the technical solutions of the present utility model and the related teachings of the above-described embodiments, and are also within the scope of the claims of the present utility model.
Claims (7)
1. The utility model provides a high voltage energy storage pulse capacitor charging power supply which characterized in that:
the system comprises an ACDC module, a voltage sensor, a current sensor HA and at least two DCDC modules;
each DCDC module is provided with an H-bridge inversion module H1, a plurality of secondary side transformers T1 and at least two diode rectification units, the primary sides of the plurality of secondary side transformers T1 are connected with the output of the H-bridge inversion module H1, the secondary sides of the plurality of secondary side transformers T1 are provided with at least two single-phase windings, the output of each single-phase winding is respectively connected to one diode rectification unit, and the output of each diode rectification unit is sequentially connected in series to form the output of the DCDC module;
the ACDC modules are used for taking electricity to the outside, the H bridge inverter modules H1 of the DCDC modules take electricity from the output ends of the ACDC modules together, and the total output formed by sequentially connecting the outputs of the DCDC modules in series is used for charging the load capacitor C2;
the voltage sensor is used for acquiring a voltage signal reflecting the total output, and the current sensor HA is used for acquiring a current signal reflecting the total output.
2. The high voltage energy storage pulse capacitor charging power supply according to claim 1, wherein:
the current sensors HA have a plurality and correspond in number to DCDC modules, and the positions of the current sensors HA are configured to be mounted on the primary side of each of the multiple secondary-side transformers T1.
3. A high voltage energy storage pulse capacitor charging source according to claim 2, wherein: each DCDC module is further provided with an inductor Lr and a capacitor Cr, and the inductor Lr and the capacitor Cr are respectively connected in series with two ends of the primary side of the multi-path secondary side transformer T1 of the DCDC module.
4. A high voltage energy storage pulse capacitor charging source according to claim 3, wherein: the ACDC module is an alternating current-direct current conversion module adopting a Vienna rectification mode.
5. The high voltage energy storage pulse capacitor charging power supply according to claim 1, wherein: the output of each DCDC module is sequentially connected in series, and then the positive electrode of the total output is formed to charge the load capacitor C2 through the diode D1, wherein the anode of the diode D1 faces the positive electrode.
6. The high voltage energy storage pulse capacitor charging power supply according to claim 1, wherein: the voltage sensor comprises a voltage dividing circuit formed by connecting a plurality of resistors in series, and the voltage dividing circuit is connected across the two ends of the total output and is connected with the load capacitor C2 in parallel.
7. The high voltage energy storage pulse capacitor charging power supply according to claim 1, wherein:
the H bridge inverter modules H1 of the DCDC modules are independently controlled, the alternating current frequencies output by the H bridge inverter modules H1 are identical, carrier phases among the H bridge inverter modules H1 are staggered, wherein the staggering principle is 180 degrees/N, and N is the number of the DCDC modules.
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