CN205103699U - Electric circuit - Google Patents
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- CN205103699U CN205103699U CN201520771373.9U CN201520771373U CN205103699U CN 205103699 U CN205103699 U CN 205103699U CN 201520771373 U CN201520771373 U CN 201520771373U CN 205103699 U CN205103699 U CN 205103699U
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Abstract
The utility model relates to an electric circuit. Linear regulator includes the drive electric circuit who has input and output, and wherein, this output is configured as the control terminal that is used for the drive power transistor so that convey load current. Error amplifier plays the poor effect of enlargeing with the formation error signal of this input department at this drive electric circuit between reference signal and feedback signal. Compensation electric circuit includes the series connection electric circuit who is formed by compensating capacitor and adjustable resistance electric circuit, and wherein, the electric circuit that should establish ties is coupled to this input of this drive electric circuit. The operation of electric current sensing electric circuit is with this load current of sensing. This adjustable resistance electric circuit's resistance in response to institute's sensing to load current and change.
Description
Technical field
The utility model relates to adjuster circuit, and relates to the adjuster circuit of the corrective network comprised for providing constant bandwidth in large load current scope particularly.
Background technology
Conventional adjuster circuit 10 is shown with reference to Fig. 1, Fig. 1.Circuit 10 comprises power transistor 12, and this power transistor has and is coupled to voltage source node (V
input) the first conducting terminal and be coupled to output node (V
export) the second conducting terminal.Power transistor 12 can comprise or n trench MOSFET device (wherein, first conducting terminal is drain node and the second conducting terminal is source node) or p trench MOSFET device (wherein, the first conducting terminal be source node and the second conducting terminal is drain node).The control terminal (such as, the gate node of MOSFET element) of power transistor by the output terminal of unitary gain voltage buffer circuit 14 with grid voltage V
griddrive.The input end of buffer circuits 14 is coupled to the output terminal of error amplifier circuit 16, and this error amplifier circuit generates error signal Vc.Such as, error amplifier circuit 16 can comprise differential amplifier (as OP-AMP), and this differential amplifier has and coupled to receive the first input end of reference voltage (Vref) and coupled to receive the second input end of feedback voltage (Vfb).In the implementation using n channel power transistor 12, first input end is the non-inverting input of amplifier circuit 16 and the second input end is inverting input.Otherwise in the implementation using p channel power transistor 12, first input end is the inverting input of amplifier circuit 16 and the second input end is non-inverting input.Feedback circuit network 18 is coupled to this output node V
exportand between the second input end of amplifier circuit 16.Such as, feedback circuit network 18 can comprise the resistive divider circuit formed by resistor R1 and R2 be connected in series.
Circuit 10 utilizes negative feedback to export (V with the stable voltage obtained for load (LOAD) on certain output current scope
export).At output node V
exportplace provides load capacitor 20 to reduce output noise and to improve transient response.Little load current range compensates negative feedback stability for selected output capacitor not difficult.But, if load current on a large scale on change; be difficult to obtain compensate.In the application, load current can significantly in different operational scenarios.In the normal operation period, load current can be changed to some amperes from tens milliamperes, and during low power standby mode, load current can be low to moderate some micromicroamperes.The circuit 10 of Fig. 1 cannot operate in such load current range.
For providing greater flexibility in the application, prior art needs a kind of adjuster circuit that can process the improvement of large load current scope.
Utility model content
In an embodiment, a kind of circuit comprises: for the control circuit of linear regulator, this control circuit comprises the driving circuit with input end and output terminal, this output terminal is configured to control terminal for driving power transistor to transmit load current, and this control circuit comprises the error amplifier be configured to for amplifying the difference between reference signal and feedback signal to generate error signal at this input end of this driving circuit further; And compensating circuit, this compensating circuit comprises: the series circuit formed by compensation condenser and variable resistance circuit, and this series circuit is coupled to this input end of this driving circuit; And current sensing circuit, this current sensing circuit is configured to for sensing this load current and changing the resistance of this variable resistance circuit in response to sensed load current.
According to an embodiment, described variable resistance circuit comprises transistor, and described transistor has and the current conduction path of described compensation condenser coupled in series and the control terminal of output terminal being coupled to described current sensing circuit.
According to an embodiment, described transistor is the circuit block of current mirroring circuit.
According to an embodiment, described current sensing circuit is configured to for generating current sensor, and wherein, described current mirroring circuit has the input end be configured to for receiving described current sensor.
According to an embodiment, described current sensing circuit is configured to for generating current sensor, and described current sensor is a part for described load current.
According to an embodiment, described current sensing circuit comprises sensing transistor, described sensing transistor has the control terminal of the described output terminal being coupled to described driving circuit, and described sensing transistor has the conducting terminal be configured to for exporting described current sensor.
According to an embodiment, described current sensing circuit comprises adjuster circuit, and described adjuster circuit is configured to the voltage for forcing to equal at the voltage at the described conducting terminal place of described sensing transistor the corresponding conducting terminal place at described power transistor.
According to an embodiment, described adjuster circuit comprises: differential amplifier, and described differential amplifier has the first input end of the described conducting terminal being coupled to described sensing transistor and is coupled to second input end of corresponding conducting terminal of described power transistor; And regulator transistor, described regulator transistor has the conducting path that couples with the conduction paths in series of described sensing transistor and has the control terminal of the output terminal being coupled to described differential amplifier.
According to an embodiment, described circuit comprises the load capacitor of the output terminal being coupled to described power transistor further, wherein, and the value that described part has the electric capacity according to described load capacitor and arranges.
According to an embodiment, described circuit comprises the load capacitor of the output terminal being coupled to described power transistor further, and wherein, described part has ratio according to the electric capacity of described load capacitor and the electric capacity of described compensation condenser and the value arranged.
According to an embodiment, described circuit comprises the feedback circuit of the output terminal being coupled to described power transistor further, and described feedback circuit is configured to for generating described feedback signal.
In an embodiment, a kind of circuit comprises: driving circuit, and this driving circuit has input end and output terminal, and this output terminal is configured to control terminal for driving power transistor to transmit load current; And compensating circuit, this compensating circuit comprises: compensation condenser; Variable resistance circuit, this variable resistance circuit and this compensation condenser coupled in series are to form the series circuit of this input end being coupled to this driving circuit; And current sensing circuit, this current sensing circuit is configured to for sensing this load current and changing the resistance of this variable resistance circuit in response to sensed load current.
According to an embodiment, described variable resistance circuit comprises transistor, and described transistor has and the current conduction path of described compensation condenser coupled in series and the control terminal of output terminal being coupled to described current sensing circuit.
According to an embodiment, described current sensing circuit is configured to for generating current sensor, and wherein, the described control terminal of described transistor is coupled to receive described current sensor.
According to an embodiment, described current sensor is a part for described load current.
According to an embodiment, described circuit comprises the load capacitor of the output terminal being coupled to described power transistor further, wherein, and the value that described part has the electric capacity according to described load capacitor and arranges.
According to an embodiment, described circuit comprises the load capacitor of the output terminal being coupled to described power transistor further, and wherein, described part has ratio according to the electric capacity of described load capacitor and the electric capacity of described compensation condenser and the value arranged.
Accompanying drawing explanation
In order to understand embodiment better, incite somebody to action now only by way of example with reference to accompanying drawing, in the accompanying drawings:
Fig. 1 is the circuit diagram of conventional adjuster circuit;
Fig. 2 is the circuit diagram of the embodiment of the adjuster circuit comprising corrective network;
Fig. 3 is the circuit diagram for the corrective network in the circuit of Fig. 2; And
Fig. 4 A-4C is the Bode diagram of the stability analysis of the adjuster circuit of Fig. 2 and Fig. 3.
Embodiment
The embodiment of adjuster circuit 100 is shown referring now to Fig. 2, Fig. 2.Circuit 100 comprises power transistor 112, and this power transistor has and is coupled to voltage source node (V
input) the first conducting terminal and be coupled to output node (V
export) the second conducting terminal.Power transistor 112 can comprise or n trench MOSFET device (wherein, first conducting terminal is drain node and the second conducting terminal is source node) or p trench MOSFET device (wherein, the first conducting terminal be source node and the second conducting terminal is drain node).The control terminal (such as, the gate node of MOSFET element) of power transistor by the output terminal of unitary gain voltage buffer circuit 114 with voltage V
griddrive.The input end of buffer circuits 114 is coupled to the output terminal of error amplifier circuit 116, and this error amplifier circuit generates error signal Vc.Such as, error amplifier circuit 116 can comprise differential amplifier (as OP-AMP), and this differential amplifier has and coupled to receive the first input end of reference voltage (Vref) and coupled to receive the second input end of feedback voltage (Vfb).In the implementation using n channel power transistor 112, first input end is the non-inverting input of amplifier circuit 116 and the second input end is inverting input.Otherwise in the implementation using p channel power transistor 112, first input end is the inverting input of amplifier circuit 116 and the second input end is non-inverting input.Feedback circuit network 118 is coupled to this output node V
exportand between the second input end of amplifier circuit 116.Such as, feedback circuit network 118 can comprise resistive divider circuit.
Circuit 100 comprises corrective network 150 further.Network 150 comprises current sensing circuit 152, and this current sensing circuit is coupled exports V with senses flow overpower transistor 112 to being connected to
exportload current (the I of the load at place
load).Network 150 comprises compensation condenser Cc further, the variable backoff resistor R3 coupled in series between the non-inverting input of this compensation condenser and unitary gain voltage buffer circuit 114 and ground connection reference power source node (GND).In response to the load current I sensed by current sensing circuit 152
loadcarry out the variable-resistance control to resistor R3.
The details of the embodiment of the circuit implementations for corrective network 150 is shown referring now to Fig. 3, Fig. 3.Current sensing circuit 152 is coupled exports V with senses flow overpower transistor 112 to being connected to
exportthe load current of load at place and output sensing electric current (I
sensing), this current sensor is load current I
loadthe part (1/y) of size.Current sensing circuit 152 comprises sensing transistor 154, and this sensing transistor has and is coupled to voltage source node (V
input) the first conducting terminal and the second conducting terminal.If power transistor 112 is n channel devices, then sensing transistor 154 is n trench MOSFET device (wherein, the first conducting terminal be drain node and the second conducting terminal is source node); Or if power transistor 112 is p channel devices, then sensing transistor is p trench MOSFET device (wherein, the first conducting terminal be source node and the second conducting terminal is drain node).The control terminal (such as, the gate node of MOSFET element) of sensing transistor 154 is connected to the control terminal of power transistor 112.Sensing transistor 154 is 1:y ratio copies of power transistor 112.
Current sensing circuit 152 comprises the regulating circuit formed by differential amplifier 156 and transistor 158 further.The non-inverting input of amplifier 156 is connected to receive output node (V
export) voltage at place.The inverting input of amplifier 156 is connected to the second conducting terminal of sensing transistor 154 with receiver voltage V
current mirror.Transistor 158 makes its source and drain path be connected with the source and drain paths in series of sensing transistor 154.The grid 158 of transistor is connected to the output terminal of amplifier 156.Regulating circuit operation is with coercive voltage V
current mirrorequal voltage V
export.When this happens, power transistor 112 and sensing transistor 154 have identical source voltage, grid voltage and drain voltage.Thus, flow through the electric current I of transistor 154 and 158
sensingbe a part for the load current flowing through power transistor 112, this part is by 1:y ratio (that is, the I of sensing transistor and power transistor
sensing=I
load/ y) arrange.
Current sensor I
sensingbe applied to the input end of the current mirroring circuit 164 formed by transistor 166 and transistor 168.Transistor 166 and 168 is n trench MOSFET device, wherein, and transistor 168 x times (that is, these transistors are the copies with 1:x zoom ratio) less of transistor 166.Current conduction path and the compensation condenser 160 of transistor 168 are connected in series.Current mirroring circuit 164 correspondingly exports offset current (I
compensate), this offset current is current sensor I
sensinga part (1/x), and more specifically, be load current I
loada part (1/ (yx)).The source terminal of transistor 166 and 168 is coupled to ground nodes, and transistor 166 with 168 gate terminal be coupled in together with and be coupled to the drain terminal of transistor 166 at the input end of current mirroring circuit 164.The drain terminal of transistor 168 at the output of current mirroring circuit 164 with the electric current I that affords redress
compensate.The compensation condenser 160 with electric capacity Cc is connected between the output terminal of current mirroring circuit 164 and the non-inverting input of unitary gain voltage buffer circuit 114.
In an embodiment, error amplifier circuit 116 has the operation transconductance amplifier (OTA) that mutual conductance is gm1.This circuit 116 is first order of the backfeed loop for regulator 100.At output is voltage difference between reference voltage Vref and feedback voltage Vfb.
Unitary gain voltage buffer circuit 114 is that the amplifier circuit of gm2 is formed by having mutual conductance.
Power transistor 112 has mutual conductance gm3 and grid capacitance C
grid.The size of transistor 112 is defined by the ratio (Wp/Lp) of its width and length.
Transistor 166 has mutual conductance gm4.The size of transistor 166 is defined by the ratio (Wn/Ln) of its width and length.
The size of transistor 168 is defined by the ratio (Wm/Lm) of its width and length.
Transistor 168 is used as the variohm (Fig. 2, R3) be connected in series with compensation condenser 160.The drain-source resistance (Rc) of transistor 168 is arranged by the gate source voltage (Vgs) of transistor 168.The Vgs of transistor 168 equals the Vgs of transistor 166.The electric current I that the size of Vgs by transistor 166 of transistor 166 and the drain-source from transistor 166 flow out
sensingarrange.Thus the value of the resistance Rc of transistor 168 is according to load current I
loadchange and change, because I
sensing=I
load/ y.
Once design is closed, the value of gm1, gm2, gm3 and Cc in this design is fixed value.
But the value of Rc changes along with the value of gm4, and gm4 is along with I
sensingand change, I
sensingalong with I
loadand change.So the value of Rc is along with I
loadand change.
Rc is the resistance between the drain electrode of transistor 158 and source electrode.Transistor 158 works in triode region.Thus,
Wherein, M166 and M168 refers to transistor 166 and 168 respectively.
Due to,
and (Vgs
m168-Vth
m168)=(Vgs
m166-Vth
m166),
Then
Thus mutual conductance gm3 is along with I
loadand change.
Suppose that feedback is unit feedback, this is the worst situation for stabiloity compensation.There is three limits and a zero point in the feedback loop.The first limit P1 is there is at Vc Nodes.At V
gridthere is the second limit P2 in Nodes.At V
exportthere is the 3rd limit P3 in Nodes.Z1 at zero point is there is at Vc Nodes.
Fig. 4 A-4C shows three Bode diagrams for stability analysis.Fig. 4 A is the Bode diagram from node Vfb to node Vc.Fig. 4 B is from node Vc to node V
exportbode diagram.Fig. 4 C is the Bode diagram of negative feedback loop.
In Fig. 4 C Bode diagram, there is a limit and a zero point.The unity gain bandwidth at this zero point is not
zero point is positioned at
once this design is closed,
value be fixing.
value change along with load current.
In the Bode diagram of Fig. 4 B, unity gain bandwidth is positioned at
second limit is positioned at
the value of gm3 and gm2 is all along with I
loadand change.
If we but make V
exportthe unity gain bandwidth of/Vc Bode diagram is positioned at the frequency place at the zero point of Vc/Vfb Bode diagram, and the Bode diagram of backfeed loop is such by what go out as shown in FIG. 4 C.There is three limits and a zero point.The frequency at zero point is
or
identical frequency.Unity gain bandwidth is positioned at
also need to ensure,
be positioned at ratio
in higher frequency.So, by selected load capacitance, the unity gain bandwidth of regulating loop is the steady state value not relying on load current.
Calculating for simplifying, supposing x=1.So, simplify:
So, if the sensing ratio 1:y of current sensing circuit meets above equation, and
be positioned at ratio
in higher frequency, the unity gain bandwidth of regulator always
and thus do not rely on load current.In bandwidth
in, there is two limits and a zero point.The phase margin of backfeed loop should be acceptable.System stability does not rely on load current.
Such analysis hypothesis P channel mosfet is used for power transistor 112.As discussed, power transistor 112 can comprise n channel device alternatively.In this case, for error amplifier circuit 116, input polarity changes on gm1.These calculate and will almost calculate identical, except as shown below with provided those above:
Because transistor 112,166 and 168 is all N-type, we make:
K′
n＝K′
p
So,
Again, if the sensing ratio 1:y of current sensing circuit meets above equation, and
be positioned at ratio
in higher frequency, the unity gain bandwidth of regulator always
and thus do not rely on load current.In bandwidth
in, there is two limits and a zero point.The phase margin of backfeed loop should be acceptable.System stability does not rely on load current.
By to the complete of exemplary embodiment of the present utility model and informational description exemplary and non-limiting example provide before description.But for those skilled in the relevant art, in view of description above, when reading this instructions with appended claims by reference to the accompanying drawings, various amendment and adaptation can become obvious.But, will still fall within scope of the present utility model as determined in appended claims all such and similar amendment of the utility model instruction.
Claims (17)
1. a circuit, is characterized in that, comprising:
For the control circuit of linear regulator, described control circuit comprises the driving circuit with input end and output terminal, described output terminal is configured to control terminal for driving power transistor to transmit load current, and described control circuit comprises the error amplifier be configured to for amplifying the difference between reference signal and feedback signal to generate error signal at the described input end of described driving circuit further; And
Compensating circuit, described compensating circuit comprises:
The series circuit formed by compensation condenser and variable resistance circuit, described series circuit is coupled to the described input end of described driving circuit; And
Current sensing circuit, described current sensing circuit is configured to for sensing described load current and changing the resistance of described variable resistance circuit in response to sensed load current.
2. circuit as claimed in claim 1, it is characterized in that, described variable resistance circuit comprises transistor, and described transistor has and the current conduction path of described compensation condenser coupled in series and the control terminal of output terminal being coupled to described current sensing circuit.
3. circuit as claimed in claim 2, it is characterized in that, described transistor is the circuit block of current mirroring circuit.
4. circuit as claimed in claim 3, it is characterized in that, described current sensing circuit is configured to for generating current sensor, and wherein, described current mirroring circuit has the input end be configured to for receiving described current sensor.
5. circuit as claimed in claim 1, it is characterized in that, described current sensing circuit is configured to for generating current sensor, and described current sensor is a part for described load current.
6. circuit as claimed in claim 5, it is characterized in that, described current sensing circuit comprises sensing transistor, described sensing transistor has the control terminal of the described output terminal being coupled to described driving circuit, and described sensing transistor has the conducting terminal be configured to for exporting described current sensor.
7. circuit as claimed in claim 6, it is characterized in that, described current sensing circuit comprises adjuster circuit, and described adjuster circuit is configured to the voltage for forcing to equal at the voltage at the described conducting terminal place of described sensing transistor the corresponding conducting terminal place at described power transistor.
8. circuit as claimed in claim 7, it is characterized in that, described adjuster circuit comprises:
Differential amplifier, described differential amplifier has the first input end of the described conducting terminal being coupled to described sensing transistor and is coupled to second input end of corresponding conducting terminal of described power transistor; And
Regulator transistor, described regulator transistor has the conducting path that couples with the conduction paths in series of described sensing transistor and has the control terminal of the output terminal being coupled to described differential amplifier.
9. circuit as claimed in claim 5, it is characterized in that, described circuit comprises the load capacitor of the output terminal being coupled to described power transistor further, wherein, the value that described part has the electric capacity according to described load capacitor and arranges.
10. circuit as claimed in claim 5, it is characterized in that, described circuit comprises the load capacitor of the output terminal being coupled to described power transistor further, and wherein, described part has ratio according to the electric capacity of described load capacitor and the electric capacity of described compensation condenser and the value arranged.
11. circuit as claimed in claim 1, it is characterized in that, described circuit comprises the feedback circuit of the output terminal being coupled to described power transistor further, and described feedback circuit is configured to for generating described feedback signal.
12. 1 kinds of circuit, is characterized in that, comprising:
Driving circuit, described driving circuit has input end and output terminal, and described output terminal is configured to control terminal for driving power transistor to transmit load current; And
Compensating circuit, described compensating circuit comprises:
Compensation condenser;
Variable resistance circuit, described variable resistance circuit and described compensation condenser coupled in series are to form the series circuit of the described input end being coupled to described driving circuit; And
Current sensing circuit, described current sensing circuit is configured to for sensing described load current and changing the resistance of described variable resistance circuit in response to sensed load current.
13. circuit as claimed in claim 12, it is characterized in that, described variable resistance circuit comprises transistor, and described transistor has and the current conduction path of described compensation condenser coupled in series and the control terminal of output terminal being coupled to described current sensing circuit.
14. circuit as claimed in claim 13, it is characterized in that, described current sensing circuit is configured to for generating current sensor, and wherein, the described control terminal of described transistor is coupled to receive described current sensor.
15. circuit as claimed in claim 14, it is characterized in that, described current sensor is a part for described load current.
16. circuit as claimed in claim 15, it is characterized in that, described circuit comprises the load capacitor of the output terminal being coupled to described power transistor further, wherein, the value that described part has the electric capacity according to described load capacitor and arranges.
17. circuit as claimed in claim 16, it is characterized in that, described circuit comprises the load capacitor of the output terminal being coupled to described power transistor further, and wherein, described part has ratio according to the electric capacity of described load capacitor and the electric capacity of described compensation condenser and the value arranged.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201520771373.9U CN205103699U (en) | 2015-09-30 | 2015-09-30 | Electric circuit |
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201520771373.9U CN205103699U (en) | 2015-09-30 | 2015-09-30 | Electric circuit |
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| CN205103699U true CN205103699U (en) | 2016-03-23 |
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Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN105955390A (en) * | 2016-07-01 | 2016-09-21 | 唯捷创芯(天津)电子技术股份有限公司 | Low-dropout linear regulator module, chip and communication terminal |
| CN109687688A (en) * | 2017-10-13 | 2019-04-26 | 英飞凌科技奥地利有限公司 | Switch the sensor network mismatch compensation of voltage regulator by input voltage and input current sensing |
| CN110036578A (en) * | 2016-10-04 | 2019-07-19 | 菲尼萨公司 | Each DC and AC current distributing in optical receiver |
-
2015
- 2015-09-30 CN CN201520771373.9U patent/CN205103699U/en active Active
Cited By (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN105955390A (en) * | 2016-07-01 | 2016-09-21 | 唯捷创芯(天津)电子技术股份有限公司 | Low-dropout linear regulator module, chip and communication terminal |
| CN110036578A (en) * | 2016-10-04 | 2019-07-19 | 菲尼萨公司 | Each DC and AC current distributing in optical receiver |
| CN110036578B (en) * | 2016-10-04 | 2022-04-15 | 菲尼萨公司 | Respective DC and AC current splitting in an optical receiver |
| CN114598395A (en) * | 2016-10-04 | 2022-06-07 | 菲尼萨公司 | Respective DC and AC current splitting in an optical receiver |
| CN109687688A (en) * | 2017-10-13 | 2019-04-26 | 英飞凌科技奥地利有限公司 | Switch the sensor network mismatch compensation of voltage regulator by input voltage and input current sensing |
| CN109687688B (en) * | 2017-10-13 | 2024-05-10 | 英飞凌科技奥地利有限公司 | Sense network mismatch compensation for switching voltage regulators by input voltage and input current sensing |
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