CN2048977U - Linear phase comparator - Google Patents
Linear phase comparator Download PDFInfo
- Publication number
- CN2048977U CN2048977U CN 89202960 CN89202960U CN2048977U CN 2048977 U CN2048977 U CN 2048977U CN 89202960 CN89202960 CN 89202960 CN 89202960 U CN89202960 U CN 89202960U CN 2048977 U CN2048977 U CN 2048977U
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- China
- Prior art keywords
- frequency
- frequency divider
- phase
- adjustable frequency
- linear phase
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Abstract
The utility model relates to a linear phase comparator. The utility model is characterized in that the utility model adopts the scheme of a digital biharmonic frequency mixer. A whole circuit comprises two input channels, a common oscillator, a frequency demultiplier, two harmonic mixers and a linear phase demodulator. The measuring accuracy is high, the degree of linearity is good and the phase demodulation accuracy can not be influenced by the frequency nominal value of an incoming frequency signal. The linear phase comparator is a high-accuracy surveying instrument for checking the phase variation.
Description
The utility model relates to the radio survey field, particularly a kind of linear ratio phase instrument.
Linear ratio phase instrument is to be used for frequency marking comparison, the high precision instrument that phase change detects.At present, prior art is when solving phase place comparison problem, employing gate circuit that has or integrated circuit trigger are to two direct phase demodulations of comparison signal, is exactly this as U.S. HpK34-59991A than phase instrument instructions, and this scheme exists poor linearity, adjustment inconvenience and the defective of " dead band " and non-linear phenomena is arranged than phase time under high frequency.The U.S. 3.986,113 patents adopt the scheme of double mixer width of cloth phase detection, though the linearity and " dead band " are made moderate progress, but still exist the measuring accuracy of phase comparator and low frequency relevant with the frequency nominal value than phase precision low and auxiliary common oscillator frequency in the deficiency that must not do different changes on year-on-year basis during phase frequency rate value.
The purpose of this utility model is to avoid the weak point of above-mentioned prior art and provides a kind of linearity good, and is easy to operate, and can normalization under difference input comparison frequency provides the linear phase comparative device of high measuring accuracy.
Realize that the utility model purpose principal character is to have adopted the scheme entire circuit of digital biharmonic frequency mixer phase differential to comprise three passages and a linear phase detector, wherein two input signal channels are identical, connect adjustable frequency divider by amplification and rectification circuit respectively, the output terminal of adjustable frequency divider connects digital harmonic mixer and constitutes.Higher-order of oscillation passage is to connect adjustable frequency divider by the high frequency common oscillator, and the output of adjustable frequency divider is connected in the biharmonic frequency mixer of two input channels, constitutes higher-order of oscillation passage.Reference signal f
o(t) with measured signal f
x(t) be connected respectively to the amplification and rectification circuit of two passages, it is shaped as pulsating wave, this pulsating wave is input to adjustable frequency divider, adjustable frequency divider is except frequency division not, also carry out 10 frequency divisions, or 100 frequency divisions, the purpose of frequency division is to adapt to low situation than phase precision, two input signals behind adjustable frequency divider are input to digital harmonic mixer again.Oscillating impulse f by the output of high frequency common oscillator
c(t) by adjustable frequency divider not frequency division, 10 frequency divisions or 100 frequency divisions also be connected to the biharmonic frequency mixer, respectively with reference signal f
o(t) and measured signal f
x(t) harmonic wave carries out mixing, by two Beat Signals of harmonic mixer output, delivers to linear phase detector and carries out phase demodulation again, and on behalf of the phase place of two Beat Signals, its output voltage change relatively.
If the frequency of common oscillator is:
f
c（t）＝F（t）－△F（t） ①
The frequency values of two-way comparison signal is respectively:
f
o（t）＝F（t）／m ②
f
x（t）＝F（t）／n＋△f（t） ③
Wherein, m, n are positive integer, and m can equate also can not wait with n.
f
c(t) respectively with f
o(t) m subharmonic and f
x(t) two Beat Signals that obtain behind the n harmonic mixing are:
f
Clap 1(t)=△ F(t) 4.
f
Clap 2(t)=n △ f(t)+△ F(t) 5.
Phase difference between two Beat Signals
Clap(t) be:
φ
Clap(t) |
t o=2 π ∫
t o(n △ f(t)+△ F(t)) dt=2 π ∫
t o△ F(t) dt
＝2π∫
t on△f（t）dt＝nφ（t）｜
t o
So because of the complete symmetry of two signalling channels
φ
Clap(t)=n φ (t) is 6.
This phase differential has reflected measured signal f
x(t) relative datum signal f
o(t) phase change result has reflected that also displayed value has doubled n doubly, and with common oscillator f
c(t) it doesn't matter in variation.So both exempted of the influence of common oscillator self frequency system sum of errors stochastic error, improved comparison accuracy again measuring.
The utility model has been owing to used harmonic mixer and had a mind to the common oscillator that offset 10MHz counts KHz, and when input signal was the fractional frequency of 10MHz, its phase demodulation was equivalent to carry out being higher than on the input signal n 10MHz doubly, so precision of phase discrimination is with respect to f
x(t) doubled n doubly.Along with the difference of n value, the result of multiplication is also different, can normalize to different comparison frequency (meeting (2), (3) formula) thus to be equivalent to f
c(t) carry out phase demodulation under the situation of integral part frequency, so the precision of phase demodulation is not subjected to the influence of input frequency signal frequency nominal value height.In addition, because the Beat Signal of harmonic mixer output is a phase demodulation under lower frequency, therefore can under incoming frequency value condition with higher, obtain good linearty.Be provided with in the instrument 10 frequency dividers and 100 frequency dividers can adapt in, the contrast situation of low precision, their adding obtains the phase demodulation of equivalent 1MHz or 100KHz respectively.
Below in conjunction with accompanying drawing structure of the present utility model is described in further detail.
Fig. 1 is a block scheme of the present utility model.
Fig. 2 is a wiring diagram of the present utility model.
Triode BG among Fig. 2
1, reverser IC
1With triode BG
2, reverser IC
8And peripheral resistance R, capacitor C and diode D constitute the amplification and rectification circuit of two input signal channels respectively.Integrated circuit (IC)
2, IC
3, IC
6, IC
7, IC
9, IC
10Constitute three-aisled 10 frequency divisions or 100 frequency division adjustable frequency dividers respectively.D type flip flop IC
4With IC
11Constitute two digital harmonic mixers respectively.Integrated inverter ic
5Constitute the high frequency common oscillator with crystal J and peripheral cell R, C.K switch
3 * 3Be respectively that frequency division, 10 frequency divisions or 100 fractional frequency signals are not sent into d type flip flop IC respectively in three passages
4With IC
11The connection switch.Integrated circuit (IC)
12Be a JK flip-flop, constitute linear phase detector.Integrated transporting discharging IC
13Constitute output amplifier with peripheral cell R, C.In the amplification and rectification circuit of two input signal channels, inverter ic
1With IC
8Output terminal be connected respectively to ten frequency divider IC
2With IC
9CP
1End.Ten frequency divider IC
2, IC
3With IC
9, IC
10Pass through K switch respectively
3 * 3Be connected to d type flip flop IC
4, IC
11CP end.Integrated inverter ic
5Output terminal be connected to ten frequency divider IC
6CP
1End, IC
5Output and ten frequency divider IC
6, IC
7Pass through K switch respectively
3 * 3Be connected to d type flip flop IC
4With IC
11D end.The Q end of two triggers is connected respectively to JK flip-flop IC
12CP
1And CP
2End.IC
12Q end be connected to amplifier IC
13Input end, by IC
13Output reflected that two phase of input signals are poor.
Digital harmonic mixer of the present utility model can be with the also available resolution element of d type flip flop.Linear phase detector can be formed with the also available gate circuit of JK flip-flop.Adjustable frequency divider can be with one ten also available a plurality of ten frequency dividers of frequency divider.
Claims (3)
1, a kind of linear ratio phase instrument, comprise two input signal channels,, a higher-order of oscillation passage and a linear phase detector, it is characterized in that two input signal channels are identical, connect adjustable frequency divider by amplification and rectification circuit respectively, the output terminal of adjustable frequency divider connects digital harmonic mixer and constitutes, higher-order of oscillation passage is to connect adjustable frequency divider by the high frequency common oscillator, the output terminal of adjustable frequency divider is connected to the other end of two harmonic mixers, reference signal fo (t) and measured signal fx (t) carry out harmonic mixing with public oscillation frequency fc (t) respectively, and two Beat Signals of its output are connected to linear phase detector.
2, according to claim 1 than phase instrument, it is characterized in that three-aisled adjustable frequency divider is identical, and be connected to digital harmonic mixer by switch K.
3, according to claim 1 than phase instrument, it is characterized in that digital harmonic mixer is to be made of d type flip flop, adjustable frequency divider IC
2, IC
3With IC
9, IC
10Output terminal be connected respectively to d type flip flop IC
4With IC
11CP end, adjustable frequency divider IC
6, IC
7Output terminal be connected to two d type flip flop IC
4With IC
11D end, the Q end of two triggers is connected to linear phase detector IC
12Input end.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 89202960 CN2048977U (en) | 1989-03-15 | 1989-03-15 | Linear phase comparator |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 89202960 CN2048977U (en) | 1989-03-15 | 1989-03-15 | Linear phase comparator |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CN2048977U true CN2048977U (en) | 1989-12-06 |
Family
ID=4860609
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN 89202960 Withdrawn CN2048977U (en) | 1989-03-15 | 1989-03-15 | Linear phase comparator |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN2048977U (en) |
Cited By (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2008006242A1 (en) * | 2006-07-04 | 2008-01-17 | Zte Corporation | A method and a device of detecting phase with high precision |
| CN101233678B (en) * | 2005-07-25 | 2011-05-04 | Nxp股份有限公司 | Receiver for amplitude-modulated signals and method for detecting phase error of receiver |
| CN103399030A (en) * | 2013-07-30 | 2013-11-20 | 四川九洲空管科技有限责任公司 | System and method for detecting phase difference of answering signals under air traffic control 3/A mode |
| CN103809425A (en) * | 2014-01-27 | 2014-05-21 | 中国电子科技集团公司第十研究所 | Online calibration device and calibration method for atomic frequency standards |
| CN107678048A (en) * | 2017-10-10 | 2018-02-09 | 唐山学院 | Method is pre-selected in the ultrafast clock correction forecasting model of satellite clock |
| CN110007149A (en) * | 2019-03-28 | 2019-07-12 | 河北远东通信***工程有限公司 | A kind of linear ratio phase method of digitlization phase shift auxiliary |
| CN110007150A (en) * | 2019-03-28 | 2019-07-12 | 河北远东通信***工程有限公司 | A kind of linear ratio phase method of Direct Digital Phase Processing |
-
1989
- 1989-03-15 CN CN 89202960 patent/CN2048977U/en not_active Withdrawn
Cited By (11)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101233678B (en) * | 2005-07-25 | 2011-05-04 | Nxp股份有限公司 | Receiver for amplitude-modulated signals and method for detecting phase error of receiver |
| US8463227B2 (en) | 2005-07-25 | 2013-06-11 | Nxp B.V. | Receiver for amplitude-modulated signals |
| WO2008006242A1 (en) * | 2006-07-04 | 2008-01-17 | Zte Corporation | A method and a device of detecting phase with high precision |
| CN103399030A (en) * | 2013-07-30 | 2013-11-20 | 四川九洲空管科技有限责任公司 | System and method for detecting phase difference of answering signals under air traffic control 3/A mode |
| CN103399030B (en) * | 2013-07-30 | 2016-05-25 | 四川九洲空管科技有限责任公司 | A kind of system and method for realizing answer signal phase difference detection under blank pipe 3/A pattern |
| CN103809425A (en) * | 2014-01-27 | 2014-05-21 | 中国电子科技集团公司第十研究所 | Online calibration device and calibration method for atomic frequency standards |
| CN103809425B (en) * | 2014-01-27 | 2016-08-17 | 中国电子科技集团公司第十研究所 | The on-line calibration device of atomic frequency standard and calibration steps |
| CN107678048A (en) * | 2017-10-10 | 2018-02-09 | 唐山学院 | Method is pre-selected in the ultrafast clock correction forecasting model of satellite clock |
| CN107678048B (en) * | 2017-10-10 | 2021-01-15 | 唐山学院 | Pre-selection method of ultrafast clock error forecasting model of satellite clock |
| CN110007149A (en) * | 2019-03-28 | 2019-07-12 | 河北远东通信***工程有限公司 | A kind of linear ratio phase method of digitlization phase shift auxiliary |
| CN110007150A (en) * | 2019-03-28 | 2019-07-12 | 河北远东通信***工程有限公司 | A kind of linear ratio phase method of Direct Digital Phase Processing |
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Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C14 | Grant of patent or utility model | ||
| GR01 | Patent grant | ||
| C19 | Lapse of patent right due to non-payment of the annual fee | ||
| CF01 | Termination of patent right due to non-payment of annual fee |