CN202818281U - Radio-frequency front-end transceiver for a silent surface filter of a multi-standard mobile terminal - Google Patents
Radio-frequency front-end transceiver for a silent surface filter of a multi-standard mobile terminal Download PDFInfo
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- CN202818281U CN202818281U CN2012202909496U CN201220290949U CN202818281U CN 202818281 U CN202818281 U CN 202818281U CN 2012202909496 U CN2012202909496 U CN 2012202909496U CN 201220290949 U CN201220290949 U CN 201220290949U CN 202818281 U CN202818281 U CN 202818281U
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Abstract
The utility model discloses a radio-frequency front-end transceiver for a silent surface filter of a multi-standard mobile terminal. The radio-frequency front-end transceiver comprises a receiver, a frequency synthesizer and a transmitter, wherein the front end of the receiver is provided with one or a plurality of radio-frequency tracking filters. The radio-frequency tracking filters are integrated on the radio-frequency front-end transceiver, it is not necessary to arrange a plurality of sound surface filters on the input end of the receiver in the radio-frequency front-end transceiver, simultaneously the number of the input ends of the receiver in the radio-frequency front-end transceiver is reduced, thus the production cost of the mobile terminal is obviously reduced and the area of the whole chip of the mobile terminal is also reduced, moreover the power consumption of the radio-frequency tracking filters in the receiver of the radio-frequency front-end transceiver is saved, the performance of the radio-frequency tracking filter is improved, and furthermore the whole performance and market competition force of the mobile terminal are improved, and great practical significance is obtained.
Description
Technical field
The utility model relates to the mobile communication technology field, particularly relates to a kind of radio-frequency front-end transceiver without SAW (Surface Acoustic Wave) filter of many standards portable terminal.
Background technology
At present, along with the development of smart mobile phone and panel computer, the traffic carrying capacity of global Mobile data increases substantially.Wherein, LTE(Long Term Evolution, Long Term Evolution) exploitation of technology, not only improved the availability of frequency spectrum of radio communication, also increased simultaneously message transmission rate and the accessible data capacity of radio communication.
At present, the wireless communication spectrum of LTE technology (frequency is up to 3.8 GHz) can be divided into 43 wave bands, and 1 to 21 wave band is listed in the LTE-FDD(Frequency Division Duplexing (FDD)), and the LTE-TDD(time division duplex frequency range that 33 to 43 wave bands are listed in).
Because mobile operator anticipates that the data use amount of telex network will increase substantially, like this so that mobile operator need to effectively utilize existing wireless communication spectrum resource, and implement as early as possible to cover comparatively widely LTE technology of frequency range.In order to promote extensively popularizing of LTE technology, when carrying out the LTE infrastructure construction, the signal transmitting and receiving technology in the portable terminal also needs synchronously or the faster speed development.At this time, mobile operator and other producers need to go into overdrive to carry out the technical research of portable terminal, purpose is so that a portable terminal, it has the function of multiband, multi-mode, two technology, namely so that the signal transceiver that portable terminal has can cover existing LTE radio communication wave band, simultaneously can compatible conventional communication networks (TD-SCDMA of WCDMA, EVDO, CDMA and GSM network), and support TDD and FDD technology.Need to prove that for present 3G (Third Generation) Moblie technology (3rd-generation, 3G), it includes four kinds of standard: CDMA2000, WCDMA, TD-SCDMA, WiMAX.
Wherein, as shown in table 1, signal transceiver (being the radio-frequency front-end transceiver) for the 0.7 ~ 2.7GH frequency range that has portable terminal now, in order to allow portable terminal can process simultaneously FDD and TDD technology (function that namely has two technology), to support 1 ~ 21 FDD wave band and 33 ~ 41 TDD frequency range, need to improve the digital operating ability of portable terminal, by described signal transceiver is connected with baseband processor, thus the computational load between proper placement baseband processor and the signal transceiver.
Table 1 distributes chart for the wireless communication spectrum of existing the 4th generation radio communication LTE, and is as follows:
Referring to Fig. 1, for the portable terminal that has at present the LTE/TD-SCDMA communication function (such as a mobile phone), it has generally included six functional modules, be specially: LTE/TD-SCDMA radio-frequency front-end transceiver, 2G(Generation Mobile Telecommunication System technology, for example GSM) radio-frequency front-end transceiver, baseband processor (Base band), application processor (Application Processor), memory (Memory) and power management module (Power Management Unit).
In order to cover TD-LTE(timesharing Long Term Evolution) with the TD-SCDMA(TD SDMA) all channels of communicating by letter, referring to Fig. 2, the signal transmitter (TX) that existing tradition has the portable terminal of LTE/TD-SCDMA communication function also has the two-way output, simultaneously, use SAW (Surface Acoustic Wave) filter (SAW filter) by the front end at signal transceiver (being radio-frequency front-end transceiver RFIC) inner receiver, to reduce interfering with each other between two wave bands.For example, for the transceiver (RX) that is used for receiving TD-SCDMA and TD-LTE signal, have the wave band that four signals receive, be specially 34 wave bands, 38 wave bands, 39 wave bands and 40 wave bands, altogether need to use four SAW (Surface Acoustic Wave) filter.And for the transceiver (LTE RX) that is used for receiving the TD-LTE signal, require variation (diversity) to improve data transfer rate and sensitivity, therefore, have three and be specifically designed to the LTE wave band that receives the TD-LTE signal, be specially: 38 wave bands, 39 wave bands and 40 wave bands.Therefore, as shown in Figure 2, the signal transceiver of portable terminal (being the radio-frequency front-end transceiver) has altogether 7 signal input parts and 7 SAW (Surface Acoustic Wave) filter, be specially: throw (SP7T) radio-frequency (RF) switch place at hilted broadsword seven and have 4 signal input parts, the place has 3 signal input parts at SP3T (SP3T) switch.Therefore, the signal RF input of existing portable terminal is more, and has more Surface Acoustic Wave Filter, thereby cause the production cost of signal transceiver (being the radio-frequency front-end transceiver) of portable terminal higher, lost the price competitiveness of portable terminal, and greatly increased the area of the whole chip of portable terminal, the mobile terminal chip area is larger, and then has had a strong impact on the market application foreground of portable terminal.
Therefore, at present in the urgent need to developing a kind of technology, it can be under the prerequisite that guarantees mobile terminal performance, effectively reduce the production cost of mobile terminal radio frequency front-end transceiver and the area that reduces transponder chip, and then area and the production cost of the whole chip of reduction portable terminal, improve the price competitiveness of portable terminal, enlarge the market application foreground of portable terminal.
The utility model content
In view of this, the purpose of this utility model provides a kind of radio-frequency front-end transceiver without SAW (Surface Acoustic Wave) filter of many standards portable terminal, the integrated Radio Frequency Tracking filter that arranges in this radio-frequency front-end transceiver, can not need at the input of radio-frequency front-end transceiver inner receiver a plurality of SAW (Surface Acoustic Wave) filter quantity be set, reduce simultaneously the input quantity of radio-frequency front-end transceiver inner receiver, the area that therefore can significantly reduce the production cost of portable terminal and reduce the whole chip of portable terminal, and can save the power consumption of Radio Frequency Tracking filter in the radio-frequency front-end transceiver inner receiver, improve the performance of Radio Frequency Tracking filter, and then the overall performance of lifting mobile terminal and the market competitiveness, be of great practical significance.
For this reason, the utility model provides a kind of radio-frequency front-end transceiver without SAW (Surface Acoustic Wave) filter of many standards portable terminal, include a receiver, a frequency synthesizer and a transmitter, the front end of described receiver is provided with one or more Radio Frequency Tracking filter.
Wherein, described receiver includes two low noise amplifier LNA, and the end of described two low noise amplifier LNA joins with a signal input part RXIN respectively;
The other end of described two low noise amplifier LNA joins with a variable gain amplifier VGA respectively, the mixer combination that each described variable gain amplifier VGA connects respectively a Radio Frequency Tracking filter and is comprised of two frequency mixer Mixer, and be connected with a power detector between two described variable gain amplifier VGA;
Each described mixer combination and variable-gain intermediate frequency are amplified and low pass filter PGA/LPF joins, and each variable-gain intermediate frequency amplification and low pass filter join with two digital to analog converter ADC respectively, and each digital to analog converter ADC and baseband processor are joined.
Wherein, described frequency synthesizer includes and receives the local oscillator generator, and described reception local oscillator generator respectively sending and receiving is penetrated two mixer combination in local oscillator generator, divider, multi-modulus frequency divider MMD and the described receiver;
Described divider connects voltage controlled oscillator VCO, loop filter LF and phase discriminator and voltage pump concatenation module successively, described phase discriminator and voltage pump concatenation module connect respectively a Numerically Controlled Oscillator and a multi-modulus frequency divider, described multi-modulus frequency divider meets respectively described divider and a modulator DSM, and described voltage controlled oscillator VCO is also joined with an automatic frequency controller AFC.
Wherein, described transmitter includes four digital to analog converter combinations, and each digital to analog converter combination includes a frequency mixer and a radio frequency digital to analog converter RFDAC, and described frequency mixer and radio frequency digital to analog converter RFDAC join;
Wherein frequency mixer and the same low band transformer in the combination of two digital to analog converters joins, and two digital to analog converters in making up radio frequency digital to analog converter RFDAC and the emission local oscillator generator in the described frequency synthesizer join; Frequency mixer and same high band transformer in the combination of two other digital to analog converter join, and digital to analog converter in making up radio frequency digital to analog converter RFDAC and the emission local oscillator generator in the described frequency synthesizer join.
Wherein, described low noise amplifier LNA includes N-type MOS switching tube M1 and N-type MOS switching tube M2, and the source electrode of the source electrode of described MOS switching tube M1 and N-type MOS switching tube M2 is connected with the two ends of an inductance L s respectively;
The grid of described MOS switching tube M1 connects respectively a capacitor C 10 and resistance R 1, and described capacitor C 10 and the first differential signal input port INP join; The grid of described MOS switching tube M2 connects respectively a capacitor C 20 and resistance R 2, and described capacitor C 20 and the second differential signal input port INN join; The other end of the other end of described resistance R 1 and resistance R 2 joins with a direct current biasing control signal input port B ias together.
Wherein, described variable gain amplifier VGA includes a plurality of MOS switching tube M3, M13, M23, M4, M14 and M24, wherein, the source electrode of described MOS switching tube M3, M13 and M23 is connected with the drain electrode of MOS switching tube M1 among the described low noise amplifier LNA simultaneously; The source electrode of described MOS switching tube M4, M14 and M24 is connected with the drain electrode of MOS switching tube M2 among the described low noise amplifier LNA simultaneously;
The grid of described MOS switching tube M3 and the grid of M4 intersect rear and power supply end V
DDJoin;
Described MOS switching tube M13 and M14 join with first a gain control signal port GC respectively, and described MOS switching tube M23 and M24 join with second a gain control signal port GCB respectively;
Rear and the total output OUT of first signal are intersected in the drain electrode of described MOS switching tube M3 and M13 together
PJoin, rear and the total output OUT of secondary signal are intersected in the drain electrode of described MOS switching tube M4 and M14 together
NJoin; In addition, the drain electrode of described MOS switching tube M23, M24 respectively with power supply end V
DDJoin.
Wherein, described Radio Frequency Tracking filter includes the negative transconductance module, the total output OUT of described negative transconductance module and described first signal
PWith the total output OUT of secondary signal
NJoin;
The total output OUT of first signal
PWith the total output OUT of secondary signal
NBetween be provided with a frequency range tunable capacitor C
b, described electric capacity storehouse frequency range tunable capacitor C
bBe parallel with an inductance L
D, described inductance L
DWith power supply end V
DDJoin.
Wherein, described negative transconductance module includes a plurality of negative transconductances unit, have respectively a first signal output Outp and a secondary signal output Outn on each negative transconductance unit, first signal output Outp while and the total output OUT of first signal of all negative transconductance unit
PJoin secondary signal output Outn while and the total output OUT of secondary signal of all negative transconductance unit
NJoin.
Wherein, each described negative transconductance unit includes MOS switching tube M5, M6, M7 and M8, wherein, the drain electrode of described switching tube M7 and the grid of M8 intersect rear and first signal output Outp joins, the grid of described M7 and the drain electrode of M8 are intersected rear and secondary signal output Outn joins, and the source electrode of described switching tube M7 and M8 joins with the drain electrode of switching tube M5 simultaneously;
The grid of described switching tube M5 and M6 links together, described switching tube M5 and M6 ground connection, the drain electrode of described switching tube M6 respectively with grid, direct current biasing control signal input port B ias, described Bias and a power supply end V
DDJoin.
Wherein, also include a tracking filter Q factor Q correcting circuit, this circuit includes a frequency mixer, a local oscillator generator and a figure adjustment engine, wherein, described Radio Frequency Tracking filter joins with described frequency mixer and figure adjustment engine respectively, and described frequency mixer joins with described local oscillator generator, figure adjustment engine respectively.
The technical scheme that is provided by above the utility model as seen, compared with prior art, the utility model provides a kind of radio-frequency front-end transceiver without SAW (Surface Acoustic Wave) filter of many standards portable terminal, the integrated Radio Frequency Tracking filter that arranges in this radio-frequency front-end transceiver, come external signal is selected according to the difference that this terminal signaling receives frequency range by the Radio Frequency Tracking filter, thereby can not need at the input of radio-frequency front-end transceiver inner receiver a plurality of SAW (Surface Acoustic Wave) filter quantity be set, reduce simultaneously the signal input part quantity of radio-frequency front-end transceiver inner receiver, the area that therefore can significantly reduce the production cost of portable terminal and reduce the whole chip of portable terminal, thereby therefore the market competitiveness of lifting mobile terminal is of great practical significance.
In addition, the utility model can also be saved the power consumption of Radio Frequency Tracking filter in the radio-frequency front-end transceiver inner receiver, improves the performance of Radio Frequency Tracking filter, and then the overall performance of lifting mobile terminal and the market competitiveness, is of great practical significance.
Description of drawings
Fig. 1 is existing a kind of structure diagram with portable terminal of LTE/TD-SCDMA communication function;
Fig. 2 is existing signal transmission schematic diagram with portable terminal of LTE/TD-SCDMA communication function;
The signal transmission schematic diagram without the applied many standards portable terminal of radio-frequency front-end transceiver of SAW (Surface Acoustic Wave) filter of a kind of many standards portable terminal that Fig. 3 provides for the utility model;
The structured flowchart without the radio-frequency front-end transceiver of SAW (Surface Acoustic Wave) filter of a kind of many standards portable terminal that Fig. 4 provides for the utility model;
Fig. 5 is for having the position view of SAW (Surface Acoustic Wave) filter in traditional portable terminal now;
The position view without radio frequency tracking filter in the receiver in the radio-frequency front-end transceiver of SAW (Surface Acoustic Wave) filter of a kind of many standards portable terminal that Fig. 6 provides for the utility model;
Concrete syndeton schematic diagram between the Radio Frequency Tracking filter, low noise amplifier LNA and the variable gain amplifier VGA that have without each rf filtering front-end module in the receiver in the radio-frequency front-end transceiver of SAW (Surface Acoustic Wave) filter of a kind of many standards portable terminal that Fig. 7 provides for the utility model;
Fig. 8 for a kind of many standards portable terminal of providing at the utility model without in each rf filtering front-end module in the receiver of the radio-frequency front-end transceiver of SAW (Surface Acoustic Wave) filter, the circuit theory schematic diagram of the negative transconductance unit that Radio Frequency Tracking filter wherein has;
In the radio-frequency front-end transceiver without SAW (Surface Acoustic Wave) filter of Fig. 9 for a kind of many standards portable terminal of providing at the utility model, the output spectrum figure of the Radio Frequency Tracking filter that each rf filtering front-end module has in the receiver;
In the radio-frequency front-end transceiver without SAW (Surface Acoustic Wave) filter of Figure 10 for a kind of many standards portable terminal of providing at the utility model, the correcting circuit block diagram of the Q factor Q of the Radio Frequency Tracking filter that each rf filtering front-end module has in the receiver.
Embodiment
In order to make those skilled in the art person understand better the utility model scheme, the utility model is described in further detail below in conjunction with drawings and embodiments.
Referring to Fig. 3, the utility model provides a kind of many standards portable terminal, can cover TD-LTE(timesharing Long Term Evolution) with the TD-SCDMA TD SDMA) all channels of communicating by letter, TD-LTE and TD-SCDMA signal are carried out reception ﹠ disposal, it includes a baseband processor BBIC 101, radio-frequency front-end transceiver RFIC 102, two transmitting terminal power amplifier PA 103 and a radio-frequency (RF) switch 104, described radio-frequency (RF) switch 104 is connected with an antenna 105, wherein:
Baseband processor BBIC 101, are used for carrying out data processing and the storage of mobile communication process;
Radio-frequency front-end transceiver RFIC 102, be connected with baseband processor 101, an antenna 105 respectively, be used for the external signal by a plurality of wave bands of antenna reception, and receive the difference of frequency range according to external signal, external signal is selected, then selected signal is transmitted to transmitting terminal power amplifier 103;
Each transmitting terminal power amplifier PA 103 is connected with radio-frequency front-end transceiver RFIC 102, is used for received signal is amplified processing, then sends the antenna 105 that is connected to by described radio-frequency (RF) switch, carries out the signal emission by antenna 105.
In the utility model, referring to Fig. 3, described radio-frequency (RF) switch 104 is specially hilted broadsword four and throws (SP4T) switch.
For the utility model, described radio-frequency front-end transceiver RFIC 102 includes a receiver 1021, a frequency synthesizer 1022 and transmitter 1,023 three parts, and wherein, described receiver 1021 is used for receiving in real time the signal that exterior antenna is transmitted; Described frequency synthesizer 1022 joins with receiver, transmitter respectively, for generation of local oscillation signal, and the signal at the frequency of local oscillation signal and transmitter or receiver place is carried out the frequency stack is synthetic to be processed; Described transmitter 1023 is used for signal is passed through radio-frequency (RF) switch, finally launches.
[0028]In the utility model, on the specific implementation, described radio-frequency front-end transceiver RFIC 102 is provided with one or more Radio Frequency Tracking filter at the front end of receiver 1021, described Radio Frequency Tracking filter is the band pass filter that can carry out to the signal of the required frequency of portable terminal preliminary election, it is the filter of Q factor Q enhancement mode, can suppress outside image frequency, reduce local oscillator via the radiation of antenna.Therefore, radio-frequency front-end transceiver 102 of the present utility model can receive according to external signal the difference of frequency range by being provided with this Radio Frequency Tracking filter, and external signal is selected.For example, present need not in the communication spectrum, and for the TD-SCDMA signal of 34 wave bands, its frequency range is 2010 ~ 2025MHZ; For the TD-LTE signal of 38 wave bands, its frequency range is 2570-2620 MHZ; For the TD-LTE signal of 39F wave band, its frequency range is 1880 ~ 1900MHZ; For the TD-SCDMA signal of 39S wave band, its frequency range is 1900 ~ 1920MHZ; For the TD-SCDMA signal of 40 wave bands, its frequency range is 2300 ~ 2400MHZ.Therefore, in view of the TD-LTE signal of different-waveband has different frequency ranges with the TD-SCDMA signal, therefore, the utility model only needs according to different frequency ranges, and can distinguish different-waveband, dissimilar signal, realization is selected external signal, has avoided the phase mutual interference between two band signal.
[0029]Therefore, as mentioned above, the utility model compared with prior art, be provided with the Radio Frequency Tracking filter by the front end at receiver 1021, thereby need not to be provided for again reducing a plurality of SAW (Surface Acoustic Wave) filter that interfere with each other (SAW filter) between two wave bands, referring to Fig. 3, correspondingly can also reduce simultaneously the signal input part quantity of radio-frequency front-end transceiver inner receiver, the area that therefore can significantly reduce the production cost of portable terminal and reduce the whole chip of portable terminal, and then the market competitiveness of lifting mobile terminal.
[0030]Referring to Fig. 4, for the utility model, provide a kind of radio-frequency front-end transceiver without SAW (Surface Acoustic Wave) filter of many standards portable terminal in the lump, radio-frequency front-end transceiver of the present utility model can be realized single-ended input, binary channel output and single-frequency synthesizer.On the specific implementation, the utility model radio-frequency front-end transceiver RFIC 102 includes receiver 1021, frequency synthesizer 1022 and transmitter 1,023 three parts, wherein:
For receiver (Receiver) 1021, it includes two low noise amplifier LNA, the end of described two low noise amplifier LNA joins with a signal input part RXIN respectively, one of them signal input part RXIN directly connects antenna 105, and another one signal input part RXIN joins by radio-frequency (RF) switch 104 and antenna 105; The other end of described two low noise amplifier LNA joins with a variable gain amplifier VGA respectively, the mixer combination that each described variable gain amplifier VGA connects respectively a Radio Frequency Tracking filter (Tracking Filter) and is comprised of two frequency mixer Mixer, and be connected with a power detector (Power Detector) between two described variable gain amplifier VGA; Each described mixer combination and a variable-gain intermediate frequency are amplified and low pass filter (PGA/LPF, being about to intermediate frequency programmable gain amplifier PGA and low pass filter LPF is cascaded) join, each variable-gain intermediate frequency is amplified and low pass filter joins with two digital to analog converter ADC respectively, and each digital to analog converter ADC and baseband processor 101 are joined.
[0031]In receiver 1021, referring to Fig. 4, include two rf filtering front-end modules, each rf filtering front-end module is comprised of an interconnective low noise amplifier LNA, variable gain amplifier VGA and Radio Frequency Tracking filter (Tracking Filter).
[0032]In the utility model, the radio-frequency front-end transceiver that provides for the utility model, it can include the identical receiver 1021 of two line structures, indicate variation (Diversity) sign above it, be special in realizing the standard-required of LTE, utilize variation, multichannel to improve data transfer rate and sensitivity.
[0033]Need to prove that for receiver 1021 parts, the first module wherein is low noise amplifier (Low Noise Amplifier, LNA), in the low noise while of assurance itself, by the noise of its consistent rear module that gains.Thereafter variable gain amplifier module (Variable Gain Amplifier, VGA), be used for the gain of control low noise amplifier, satisfy the requirement of receiver dynamic range, namely according to making receiver can regulate according to the size of input signal the size of its gain.Tracking filter (Tracking Filter) is used for according to receiving channels information, adjusts the filter center frequency, and the filtering band disturbs outward, and the frequency mixer after the protection is operated in its linearity scope.Power detector (Power Detector) is used for the filtered signal power size of perception, for baseband processor provides signal power information receiver is set.Frequency mixer Mixer is used for the frequency signal of local oscillator generator and receive frequency mixing, the frequency signal that receives is converted into low frequency signal, intermediate frequency programmable gain amplifier (Programmable Gain Amplifier, PGA), further small-signal is amplified to the accessible amplitude of analog to digital converter, ride gain adapts to different input signal amplitudes simultaneously.Low pass filter (Low Pass Filter, LPF) is interference signal outside intermediate frequency filtering band further, guarantees that signal is in the accessible dynamic range of signals of digital to analog converter (Analog to Digital Converter, ADC).It is digital signal that digital to analog converter ADC is used for analog signal conversion, processes to offer digital baseband processor (Baseband, BB).
[0034]For frequency synthesizer (Synthesizer) 1022, it includes and receives local oscillator generator (RX LO GEN), described reception local oscillator generator respectively sending and receiving is penetrated two mixer combination in local oscillator generator (TX LO GEN), divider, multi-modulus frequency divider MMD and the described receiver 1021, and described multi-modulus frequency divider MMD meets respectively four digital to analog converter ADC in the described receiver 1021;
In addition, described divider meets voltage controlled oscillator VCO, loop filter (LF) and phase discriminator and voltage pump concatenation module (PFD/CP successively, be about to the module that voltage pump CP and phase discriminator PFD are cascaded), described phase discriminator and voltage pump concatenation module connect respectively a Numerically Controlled Oscillator and multi-modulus frequency divider (/N), described multi-modulus frequency divider meets respectively described divider and a modulator DSM; Described voltage controlled oscillator VCO is also joined with an automatic frequency controller AFC.
[0035]Need to prove, for frequency synthesizer (Synthesizer) 1022, (the Digital Controlled Crystal Oscillator of Numerically Controlled Oscillator wherein, DCXO, be digital control crystal oscillator) the outer crystal oscillator of the comparatively accurate sheet of utilization, oscillating circuit is combined and is produced accurate 26MHz frequency signal as the reference source of frequency synthesizer in sheet, voltage controlled oscillator (Voltage Controlled Oscillator, VCO) after the frequency signal that produces removes 2 through analog divider, pass through again multi-modulus frequency divider (Multi-Modules Divider, MMD) formed the 26MHz frequency signal, by phase discriminator (Phase Frequency Detector, PFD) reference source with the Numerically Controlled Oscillator generation compares, the difference of their frequency and phase place is by voltage pump (Charge Pump, CP) be converted into voltage, come the voltage of feedback adjusting voltage controlled oscillator VCO, thus the accurate frequency signal of stable output.In addition, assorted the disturbing of introducing for suppressing multi-modulus frequency divider MMD, between voltage pump CP and voltage controlled oscillator VCO, add loop filter (Loop Filter, LF) and automatic frequency control (Automatic Frequency Control, AFC), realize the frequency of voltage controlled oscillator VCO before locking carried out coarse adjustment.Modulator (Delta-Sigma Modulator, DSM) is used for introducing modulation signal by adjusting the frequency division multiple of multi-modulus frequency divider MMD.For the direct modulating mode of the frequency synthesizer of the modulation system (being GMSK) of GSM uses.
[0036]For described transmitter 1023, it includes four digital to analog converter combinations, each digital to analog converter combination includes a frequency mixer and a radio frequency digital to analog converter RFDAC, described frequency mixer and radio frequency digital to analog converter RFDAC join (as shown in Figure 4), wherein, frequency mixer in the combination of two digital to analog converters is B34 and 39 with the wave band of same low band transformer 100(low frequency) join, and radio frequency digital to analog converter RFDAC and the emission local oscillator generator in described frequency synthesizer 1022 (TX LO GEN) of two digital to analog converters in making up joins; Frequency mixer in two other digital to analog converter combination and the wave band of same high band transformer 200(high frequency are B38 and B40) join, and radio frequency digital to analog converter RFDAC and the emission local oscillator generator in the described frequency synthesizer 1022 (TX LO GEN) in the digital to analog converter combination join.
[0037]Referring to Fig. 4, described low band transformer 100 and a low frequency signal output TX_LB join, described high band transformer 200 joins with a high-frequency signal output TX_HB respectively, and described low frequency signal output TX_LB and high-frequency signal output TX_HB join with transmitting terminal power amplifier PA 103 respectively.
[0038]In addition, the digital to analog converter that the digital to analog converter combination that described low band transformer 100 is connected is connected with described high band transformer 200 makes up both and joins by first a channel I and described baseband processor 101, and the another one digital to analog converter that the another one digital to analog converter combination that described low band transformer 100 is connected is connected with described high band transformer 200 makes up both and joins by a second channel Q and described baseband processor 101.
[0039]Need to prove, for transmitter 1023, it is divided into high band (TX_HB) and low band (TX_LB) according to output frequency, carry out signal output from high-frequency signal output TX_HB and low frequency signal output TX_LB respectively, high band covering frequence wave band is from 2300MHz to 2620MHz, low band covering frequence wave band is from 1880MHz to 2025MHz, and is corresponding for obtaining best peak value, and corresponding high band transformer 200 and low band transformer 100 are arranged respectively.The quadrature I output of high band and Q output are cancelled image signal in the 200 places addition of high band transformer, owing to be differential design, local-oscillator leakage is herein cancellation also.The quadrature I output of low band and Q output are cancelled image signal in the place's addition of low band transformer, owing to be differential design, local-oscillator leakage is herein cancellation also.The local oscillator quadrature I of low band and Q frequency input signal are that 1880MHz is to 2025MHz, the local oscillator quadrature I of high band and Q frequency input signal be 23000MHz to 2620MHz, high band and low band part is accepted respectively the positive input signal TXI and the TXQ that are come by baseband processor BBIC.RFDAC is radio frequency digital to analog converter, and the back has a detailed description.
[0040]Fig. 5 is for having the position view of SAW (Surface Acoustic Wave) filter in traditional portable terminal now.
[0041]In the lump referring to Fig. 2, Fig. 5, in the realization framework of a kind of traditional mobile terminal radio-frequency front-end transceiver shown in Figure 2, each wave band all needs to have SAW (Surface Acoustic Wave) filter (SAW filter) separately to come the outer interference signal of inhibition zone, SAW (Surface Acoustic Wave) filter SAW filter is positioned at outside the receiver of radio-frequency front-end transceiver, namely is positioned at outside the chip.As shown in Figure 5, in view of SAW (Surface Acoustic Wave) filter SAW filter has the negative effect of the decay of inserting to system signal when the inhibition zone external noise disturbs, so have the index request that the interior low noise amplifier LNA of the sheet of normally used radio-frequency front-end transceiver need to satisfy low noise and high-amplification-factor gain simultaneously now.For example, the gain of the multiplication factor of low noise amplifier LNA requires to be the 15dB(decibel) and noise factor to require be 2dB, and input 1dB compression point is-the 15dBm(dBm), i.e. input power value the when multiplication factor of input signal gain drops to than the low 1dB of linear gain is-15dBm.
[0042]For Fig. 2 and SAW (Surface Acoustic Wave) filter SAW filter shown in Figure 5, because this SAW (Surface Acoustic Wave) filter SAW filter is the discrete component that arranges separately, be arranged on outside the radio-frequency front-end transceiver of portable terminal, therefore, increased the production cost of portable terminal, so that portable terminal is when carrying out the signal reception ﹠ disposal of multiband, many standards, the whole chip area of portable terminal is larger, is unfavorable for the volume miniaturization of the portable terminals such as mobile phone.
[0043]In order to solve in the above-mentioned existing portable terminal SAW (Surface Acoustic Wave) filter SAW filter is arranged on outside the radio-frequency front-end transceiver, thereby the problem that whole chip area is larger, and reduce the low noise of low noise amplifier LNA and the index request of high-amplification-factor gain.Referring to Fig. 6, shown in Figure 7, the utility model provides a kind of radio-frequency front-end transceiver without SAW (Surface Acoustic Wave) filter of many standards portable terminal, is applicable to emission and receives asynchronous time-division multiple address system, for example TD-LTE, TD-SCDMA and gsm system.It need not to arrange SAW (Surface Acoustic Wave) filter SAW filter outside the radio-frequency front-end transceiver, but in the receiver of radio-frequency front-end transceiver the integrated Radio Frequency Tracking filter (Tracking Filter) that arranges, can not need at the input of radio-frequency front-end transceiver inner receiver a plurality of SAW (Surface Acoustic Wave) filter quantity be set, reduce simultaneously the signal input part quantity of radio-frequency front-end transceiver inner receiver, the area that therefore can significantly reduce the production cost of portable terminal and reduce the whole chip of portable terminal, the market competitiveness of final lifting mobile terminal.Compare with index request shown in Figure 5, owing to there is not the insertion decay of the 2dB of SAW (Surface Acoustic Wave) filter SAW filter introducing, the gain of the multiplication factor of low noise amplifier LNA requires to reduce to the 11dB(decibel) and noise factor require only to be 4dB, rise to-the 13dBm(dBm and input the 1dB compression point)
[0044]The following describes the concrete technology implementation procedure without the radio-frequency front-end transceiver of SAW (Surface Acoustic Wave) filter of a kind of many standards portable terminal that the utility model provides.
[0045]Concrete syndeton schematic diagram between the Radio Frequency Tracking filter, low noise amplifier LNA and the variable gain amplifier VGA that have without each rf filtering front-end module in the receiver in the radio-frequency front-end transceiver of SAW (Surface Acoustic Wave) filter of a kind of many standards portable terminal that Fig. 7 provides for the utility model.
[0046]Referring to Fig. 7, in the receiver without the radio-frequency front-end transceiver of SAW (Surface Acoustic Wave) filter of a kind of many standards portable terminal that the utility model provides, described low noise amplifier LNA meets variable gain amplifier VGA and Radio Frequency Tracking filter Tracking Filter successively, form together the rf filtering front-end module by low noise amplifier LNA, variable gain amplifier VGA and Radio Frequency Tracking filter (Tracking Filter), wherein:
Referring to Fig. 7, described low noise amplifier LNA includes N-type MOS switching tube M1 and N-type MOS switching tube M2, and the source electrode of the source electrode of described MOS switching tube M1 and N-type MOS switching tube M2 is connected with the two ends of an inductance L s respectively;
The grid of described MOS switching tube M1 connects respectively a capacitor C 10 and resistance R 1, and described capacitor C 10 and the first differential signal input port INP join; The grid of described MOS switching tube M2 connects respectively a capacitor C 20 and resistance R 2, and described capacitor C 20 and the second differential signal input port INN join; The other end of the other end of described resistance R 1 and resistance R 2 joins with a direct current biasing control signal input port B ias together, and this direct current biasing control signal input port is used for input direct-current bias control signal Bias.
[0047]Need to prove that for rf filtering front-end module shown in Figure 7, the external signal of multiband, many standards is by described the first differential signal input port INP and the second differential signal input port INN input.On the specific implementation, in the lump referring to Fig. 3, Fig. 4, described the first differential signal input port INP and the second differential signal input port INN can receive by antenna the external signal of a plurality of wave bands of input.Then external signal is coupled to described MOS switching tube M1 and M2 by capacitor C 10 and C20 respectively by described the first differential signal input port INP and the second differential signal input port INN input.
[0048]Need to prove that Bias is exactly the direct current biasing control signal (for example by from a reference power source or the reference current that transmitted by baseband processor BBIC 101, the size of this reference power source can be set in advance according to user's needs) of circuit.Radio-frequency front-end transceiver block diagram is mainly taken as the leading factor with the flow direction of frequency signal, but for circuit can be worked, and being necessary for circuit provides corresponding direct current to dispose, unlatching and disconnection that direct current biasing can control module.
[0049]In the utility model, described direct current biasing control signal input port B ias can pass through resistance R 1 and R2, be respectively MOS switching tube M1 and M2 stable dc bias current Bias is provided, then by MOS switching tube M1 and M2 the external signal of input is played the effect of amplification, and can realize the input impedance coupling by inductance L s.
[0050]Referring to Fig. 7, described variable gain amplifier VGA includes a plurality of MOS switching tube M3, M13, M23, M4, M14 and M24, wherein, the source electrode of described MOS switching tube M3, M13 and M23 is connected with the drain electrode of MOS switching tube M1 among the described low noise amplifier LNA simultaneously; The source electrode of described MOS switching tube M4, M14 and M24 is connected with the drain electrode of MOS switching tube M2 among the described low noise amplifier LNA simultaneously;
The grid of described MOS switching tube M3 and the grid of M4 intersect rear and power supply end V
DDJoin;
Described MOS switching tube M13 and M14 join with first a gain control signal port GC respectively, and described MOS switching tube M23 and M24 join with second a gain control signal port GCB respectively;
Rear and the total output OUT of first signal are intersected in the drain electrode of described MOS switching tube M3 and M13 together
PJoin, rear and the total output OUT of secondary signal are intersected in the drain electrode of described MOS switching tube M4 and M14 together
NJoin; In addition, the drain electrode of described MOS switching tube M23, M24 respectively with power supply end V
DDJoin.
[0051]Referring to Fig. 7, described Radio Frequency Tracking filter Tracking Filter includes the negative transconductance module, the total output OUT of described negative transconductance module and described first signal
PWith the total output OUT of secondary signal
NJoin;
Described negative transconductance module includes a plurality of negative transconductances unit (Unit1 ~ UnitN as shown in Figure 7, N are the integer greater than 1), is comprised of side by side described a plurality of negative transconductances unit.Wherein, have respectively a first signal output Outp and a secondary signal output Outn on each negative transconductance unit, the first signal output Outp of all negative transconductance unit links together (being that whole correspondences are connected), first signal output Outp while and the total output OUT of first signal of all negative transconductance unit
PJoin;
The secondary signal output Outn of all negative transconductance unit is connected to together (being that whole correspondences are connected), secondary signal output Outn while and the total output OUT of secondary signal of all negative transconductance unit
NJoin;
All negative transconductance unit ground connection; And signal controlling interface control1, the control2 of described a plurality of negative transconductances unit and the described N of controlN(are the arbitrary integer greater than 0) independent separately, each negative transconductance unit meets respectively a direct current biasing control signal input port B ias, each described Bias respectively with power supply end V
DDJoin.
[0052]Referring to Fig. 7, in the utility model, the total output OUT of first signal
PWith the total output OUT of secondary signal
NRespectively with described receiver 1021 in the mixer combination that is formed by two frequency mixer Mixer join.The total output OUT of first signal
PWith the total output OUT of secondary signal
NBetween be provided with a frequency range tunable capacitor C
b, come electric capacity storehouse frequency range tunable capacitor C by baseband processor BBIC 101 output frequency range control signal Vband
bControl, so that the output signal frequency of Radio Frequency Tracking filter is set to needed working frequency range;
Described electric capacity storehouse frequency range tunable capacitor C
bBe parallel with an inductance L
D, described inductance L
DWith power supply end V
DDJoin.
[0053]Need to prove, in the utility model, described OUT
PAnd OUT
NBe two ports of the differential output signal of Radio Frequency Tracking filter of the present utility model, one section is anode, and an end is negative terminal, and is corresponding with two differential input signal port INN and INP.
[0054]In the lump referring to Fig. 7, Fig. 8, the described negative transconductance of in the Radio Frequency Tracking filter each unit includes MOS switching tube M5, M6, M7 and M8, wherein, the drain electrode of described switching tube M7 and the grid of M8 intersect rear and first signal output Outp joins, the grid of described M7 and the drain electrode of M8 are intersected rear and secondary signal output Outn joins, and the source electrode of described switching tube M7 and M8 joins with the drain electrode of switching tube M5 simultaneously;
The grid of described switching tube M5 and M6 links together, described switching tube M5 and M6 ground connection, the drain electrode of described switching tube M6 respectively with grid, direct current biasing control signal input port B ias, described Bias and a power supply end V
DDJoin.
[0055]Referring to Fig. 7, Fig. 8,, need to prove that can realize gain control by MOS switching tube M3, M13, M23, M4, M14 and M24, wherein, M3 is connected with M4 and is deleted the utmost point and connect V for the utility model
DD, always conducting; When the first gain control signal GC is high level, and the second gain control signal GCB is when being low level, M13 and M14 conducting, and M23 and M24 close, and the external signal of input all outputs to the total output OUT of first signal after through gain and filtering processing
PWith the total output OUT of secondary signal
NSo be high gain mode this moment;
On the contrary, when the first gain control signal GC is low level, and the second gain control signal GCB is when being high level, and M13 and M14 close, M23 and M24 conducting, and the part of the external signal of input outputs to the total output OUT of first signal
PWith the total output OUT of secondary signal
N, and another part signal passes through V
DDHold and loss, so be low gain mode this moment.
[0056]In the utility model, need to prove, M23 links to each other with VDD with M24, and do not link to each other with VOUTN with VOUTP, so, when the first gain control signal GC is high level, and the second gain control signal GCB is when being low level, M13 and M14 conducting, M23 and M24 close, after processing through gain and filtering, all output to the total output OUTP of first signal and the total output OUTN of secondary signal, so be high gain mode at this moment by the external signal of described the first differential signal input port INP and the second differential signal input port INN input;
Otherwise, when the first gain control signal GC is low level, and the second gain control signal GCB is when being high level, M13 and M14 close, M23 and M24 conducting, the part of the external signal of described the first differential signal input port INP and the second differential signal input port INN input outputs to the total output OUTP of first signal and the total output OUTN of secondary signal by M23, M24, and another part signal is successively by arriving V behind M3, the M4
DDHold and loss, so be low gain mode this moment.Need to prove, when a part of signal is linked into V
DDThe time, signal just can not enter next module, V
DDFor high-frequency signal, be exactly the meaning the same with the earth GND, so signal flows into V
DDJust be equivalent to signal and be attenuated, therefore, the signal that the arrives vdd terminal decay that is depleted.
[0057]For the utility model, the output of the tracking filter in its radio-frequency front-end signal transceiver in the receiver comprises the sheet internal inductance L that quality Q is relatively poor
D, the frequency range of frequency range control signal Vband control is adjusted capacitor C
bAnd the programmable negative transconductance unit combination of transconductance value, transconductance value can arrange by two kinds of ways, a kind of is to adjust bias current by Bias, a kind of is to realize by the number (1 to N) of adjusting the negative transconductance unit, because the device size of negative transconductance unit is usually less, the change of mutual conductance can not affect output frequency center excursD.
[0058]Fig. 8 is negative transconductance element circuit figure in the tracking filter.Referring to Fig. 8, baseband processor BBIC 101 controls switch and the size of current (transconductance value) of negative transconductance unit by the Bias control signal, M6 is secondary tubular type interface unit, be the negative transconductance unit by stable electric current by mirror device M5, M7 and M8 cross-couplings connect into negative transconductance, and the signal differential that forms at last outputs to first signal output Outp and secondary signal output outn.
[0059]Need to prove, in the utility model, described direct current biasing control signal Bias is comprised of two parts, a part is whether to flow into the negative transconductance unit for the control electric current, control the opening and closing of negative transconductance unit, another part is to control the size of current that enters the negative transconductance unit by analog circuit (for example switching tube circuit), thereby controls the size of this negative transconductance value, electric current is larger, and the negative transconductance value is larger.For example, on the specific implementation, baseband processor BBIC101 can control whether inflow current is to the negative transconductance unit among the described direct current biasing control signal Bias by conducting and the cut-off of switch MOS pipe, thereby controls the switch of negative transconductance unit.The metal-oxide-semiconductor conducting, the negative transconductance unit has electric current to pass through, and the negative transconductance unit is opened; During the metal-oxide-semiconductor cut-off, the negative transconductance unit does not have electric current to pass through, and the negative transconductance unit is closed.On the specific implementation, baseband processor BBIC101 can also control its transconductance value by the size of current of control figure programming Control inflow negative transconductance unit, and transconductance value increases with the increase of electric current.
In the utility model, the whole effective impedance R of the output of described Radio Frequency Tracking filter Tracking Filter
EqFor:
In addition, the whole effectively Q factor Q value of the output of described Radio Frequency Tracking filter Tracking Filter is:
Need to prove that when the value of gmn increased, Q value increased, the selectivity raising of Radio Frequency Tracking filter, as shown in Figure 9, when the gmn value near 1/R
pThe time, Q value approach infinity, the filtering and amplifying circuit in the Radio Frequency Tracking filter satisfies oscillating condition, the resonance frequency vibration when beginning is set to oscillator according to this Radio Frequency Tracking filter.Reduce gradually negative transconductance value gmn this moment, makes its nonoscillatory, gets back to the amplification filtering pattern, and the Q of the Radio Frequency Tracking filter cavity of this moment is the highest, and selectivity is best.As shown in Figure 9, the Q factor Q value of Radio Frequency Tracking filter can be brought up to about 100 from 3.
Need to prove that at this selectivity is exactly the outer ability of disturbing of filter rejection frequency signal band.Better to the larger selectivity of decay with outer interfering frequency signal.The quality factor in LC chamber are better, and selectivity is better.Another of Q is defined as Q=Rp/X, and Rp is the effective impedance of cavity, the reactance value when X is resonance, so Q is larger, Rp is larger, and desired output frequency signal is also larger with respect to other out-of-band signalings, so selectivity is better.Because when gmn is increased to when equaling 1/Rp, Q be infinity, so starting oscillation reduces gmn at this moment when just beginning nonoscillatory, the Radio Frequency Tracking filter is the amplifier pattern, because Q is very high, so the filter effect selectivity is fine.
Figure 10 is the correction block diagram of the Q factor Q of tracking filter of the present utility model.Rf filtering front-end module of the present utility model also includes a tracking filter Q factor Q correcting circuit, this circuit includes a frequency mixer, a local oscillator generator and a figure adjustment engine, wherein, referring to Figure 10, described Radio Frequency Tracking filter joins with described frequency mixer and figure adjustment engine respectively, and described frequency mixer joins with described local oscillator generator, figure adjustment engine respectively.
Referring to Figure 10, the utility model can also be controlled whole trimming process and sequential by the figure adjustment engine, and concrete trimming process is:
1, the Vband frequency range control signal of sending by baseband processor BBIC is regulated frequency range and is adjusted capacitor C b value, thereby the Signal Regulation that will export the total output OUTP of first signal and the total output OUTN of secondary signal is to the target working frequency range;
2, the input of low noise amplifier LNA is disconnected from antenna, be set to oscillator by the mode tracking filter that increases the negative transconductance unit, producing centre frequency is the oscillator signal of fosc;
3, the local frequency fLO of local oscillator (being the oscillator of the frequency synthesizer 1022 among the radio-frequency front-end transceiver RFIC 102) is set to the centre frequency fosc of desired frequency band (being the target working frequency range), namely so that fLO=fosc;
4, the medium frequency output end DC direct current biasing of figure adjustment engine by frequency mixer Mixer detect oscillator starting of oscillation whether;
Need to prove that the starting of oscillation of Radio Frequency Tracking filter whether judgement is that the output signal that detects frequency mixer by corrected engine by numeral decides.Local frequency fLO is the 1022 transceiver frequency synthesizers generation by Fig. 4, fosc is the frequency of oscillation of Radio Frequency Tracking filter, output signal frequency after these two signal mixing is fLO-fosc, so when fLO=fosc, output signal frequency after the mixing is zero, direct current DC namely, this can be corrected engine by numeral and detect.And as the frequency of oscillation fosc=0 of Radio Frequency Tracking filter, namely not starting of oscillation of tracking filter, but or the starting of oscillation frequency be not equal to fLO, frequency mixer Mixer can not export DC, whether judges thus the tracking filter starting of oscillation.
5, reduce the negative transconductance value, until the front end vibration disappears, record negative transconductance value arranges;
6, increase a fixing negative transconductance value stability that surplus guarantees front-end amplifier is set, unlikely vibration when normal operation.This moment, output Q value was best, and selectivity is best.
Need to prove, it is an interior functional module of baseband processor BBIC that described numeral is corrected engine, and its effect is the output signal that detects frequency mixer Mixer, determines whether direct current DC, it can carry out spectrum analysis to the low frequency signal after the mixing, the size of determining device frequency and signal.
In addition, frequency synthesizer 1022 among the radio-frequency front-end transceiver RFIC 102 of foregoing Fig. 4 is used under the correction mode of the Q factor Q of Radio Frequency Tracking filter described in the utility model, use as the local oscillator generator, that is to say that the local oscillator generator is exactly the frequency synthesizer 1022 of foregoing Fig. 4.Because this pattern is to carry out before the transceiver normal operation, frequency synthesizer 1022 does not have other tasks at this moment.
Also need to prove, under the correction mode of the Q factor Q of Radio Frequency Tracking filter described in the utility model, in the lump referring to Fig. 3, Fig. 4, the module that activates not only includes baseband processor BBIC, also includes: the mixer combination, the variable-gain intermediate frequency that be arranged in the Radio Frequency Tracking filter, low noise amplifier LNA, variable gain amplifier VGA of receiver 1021, are comprised of two frequency mixer Mixer are amplified and low pass filter PGA/LPF and digital to analog converter ADC; Be arranged in reception local oscillator generator, divider, multi-modulus frequency divider MMD, voltage controlled oscillator VCO, loop filter LF and phase discriminator and the voltage pump concatenation module of frequency synthesizer 1022, and described phase discriminator and voltage pump concatenation module a Numerically Controlled Oscillator and a multi-modulus frequency divider of connecing respectively, and described multi-modulus frequency divider the modulator DSM, the automatic frequency controller AFC that described voltage controlled oscillator VCO connects that connect.
For the radio-frequency front-end transceiver that the utility model provides, it has following advantage:
1, do not need the SAW filter, reduce the scheme cost;
2, do not need the SAW filter, alleviated system to the LNA index request, system power dissipation is lower;
4, system simplification has improved many standards, the feasibility of multi-band transceiver;
4 Design of digital, filtering control accurately.
For the utility model, need to prove, the radio-frequency front-end transceiver without SAW (Surface Acoustic Wave) filter of a kind of many standards portable terminal that provides for above-mentioned the utility model, it is the integrated Radio Frequency Tracking filter (Tracking Filter) that arranges in the receiver of radio-frequency front-end transceiver, gain and the linear index of low noise amplifier LNA and tracking filter module all loosen to some extent in the sheet of whole radio-frequency front-end transceiver, and the input 1dB compression point that linear index requires (being the multiplication factor gain of the input signal input power value when dropping to than the low 1dB of linear gain) has been brought up to-13dBm ~ 2dB from existing-15dBm.
The radio-frequency front-end transceiver without SAW (Surface Acoustic Wave) filter of a kind of many standards portable terminal that provides for above-mentioned the utility model, the function that it has the single-ended signal input and can accept multi-band signal in addition, are provided.For the utility model, compared with prior art, owing to there is not the SAW (Surface Acoustic Wave) filter of front end, the front end transconductance stage (Gm) of low noise amplifier LNA not only can be amplified small-signal, simultaneously in the face of power up to the band of 0dBm outside during interference signal (Blocker), can not distortion.For this reason, the utility model can be taked AB class and the compound transconductance stage of category-A, and the interference signal arriving is that it is undistorted to provide more electric current to guarantee by the AB class, and guarantees small-signal linearity degree and sensitivity by the category-A transconductance stage outside band.Variable gain amplifier VGA is used for guaranteeing the dynamic range of receiver.
Radio Frequency Tracking filter of the present utility model is positioned at the output of low noise amplifier LNA, by outputting inductance, electric capacity storehouse and negative transconductance three parts form, 1880～2620MHz target frequency bands relatively is conducive to the realization of higher Q value sheet internal inductance, to such an extent as to frequency is not very high and inductance value need not need too greatly very large chip area, the electric capacity storehouse is used for the adjustment aim frequency range, and negative transconductance can be brought up to whole Q value more than 20.Simultaneously in conjunction with duty ratio 25% local oscillator signals, passive frequency mixer and intermediate frequency filtering afterwards, integral body reaches the 20MHz out of band signal inhibition ability of 20dBc, can reach the system index requirement.
For the utility model, only need to use a frequency synthesizer.Because TD-LTE and TD-SCDMA are the systems of time division duplex (TDD), therefore reception and emission can be carried out in timesharing (not simultaneously), so the receiver in the radio-frequency front-end transceiver and reflector can use same frequency synthesizer, therefore, compare with the radio-frequency front-end transceiver of existing bifrequency compositor system, the radio-frequency front-end transceiver that the utility model provides can greatly reduce the complexity of system, simultaneously owing to reduce the production cost of chip area and reduction transponder chip.
[0074]Referring to shown in Figure 3, reflector of the present utility model can be realized binary channel output.In order to improve output spectrum degree of purity, efficient and the linearity of transmitter in the radio-frequency front-end transceiver of the present utility model, the signal of transmitter of the present utility model is divided into independent high and low frequency two-way output, the wave band of high frequency is B38 and B40, and the wave band of low frequency is B34 and 39.As a same reason, for the utility model, the RFDAC in the radio-frequency front-end transponder chip and transformation and single both-end transducer also are divided into independent high and low frequency path, in order to optimize separately.
Therefore, in sum, the Radio Frequency Tracking filter in the radio-frequency front-end transceiver that provides for the utility model in the receiver, its required power consumption is lower, also reduces chip area, reduces production costs.Simultaneously, because it can be under the control of frequency range control signal, realize self adaptation adjustment mutual conductance, so that the Radio Frequency Tracking filter is in whole frequency range, phase noise is consistent with the starting of oscillation performance, no matter be in low-frequency range or in low-frequency range namely, can realize having less noise and guarantee easy starting of oscillation.
In sum, compared with prior art, the radio-frequency front-end transceiver without SAW (Surface Acoustic Wave) filter of a kind of many standards portable terminal that the utility model provides, the integrated Radio Frequency Tracking filter that arranges in this radio-frequency front-end transceiver, come external signal is selected according to the difference that this terminal signaling receives frequency range by the Radio Frequency Tracking filter, thereby can not need at the input of radio-frequency front-end transceiver inner receiver a plurality of SAW (Surface Acoustic Wave) filter quantity be set, reduce simultaneously the signal input part quantity of radio-frequency front-end transceiver inner receiver, the area that therefore can significantly reduce the production cost of portable terminal and reduce the whole chip of portable terminal, thereby therefore the market competitiveness of lifting mobile terminal is of great practical significance.
In addition, the utility model can also be saved the power consumption of Radio Frequency Tracking filter in the radio-frequency front-end transceiver inner receiver, improves the performance of Radio Frequency Tracking filter, and then the overall performance of lifting mobile terminal and the market competitiveness, is of great practical significance.
The above only is preferred implementation of the present utility model; should be pointed out that for those skilled in the art, under the prerequisite that does not break away from the utility model principle; can also make some improvements and modifications, these improvements and modifications also should be considered as protection range of the present utility model.
Claims (10)
1. the radio-frequency front-end transceiver without SAW (Surface Acoustic Wave) filter of standard portable terminal more than a kind is characterized in that, includes a receiver, a frequency synthesizer and a transmitter, and the front end of described receiver is provided with one or more Radio Frequency Tracking filter.
2. radio-frequency front-end transceiver as claimed in claim 1 is characterized in that, described receiver includes two low noise amplifier LNA, and the end of described two low noise amplifier LNA joins with a signal input part RXIN respectively;
The other end of described two low noise amplifier LNA joins with a variable gain amplifier VGA respectively, the mixer combination that each described variable gain amplifier VGA connects respectively a Radio Frequency Tracking filter and is comprised of two frequency mixer Mixer, and be connected with a power detector between two described variable gain amplifier VGA;
Each described mixer combination and variable-gain intermediate frequency are amplified and low pass filter PGA/LPF joins, and each variable-gain intermediate frequency amplification and low pass filter join with two digital to analog converter ADC respectively, and each digital to analog converter ADC and baseband processor are joined.
3. radio-frequency front-end transceiver as claimed in claim 2, it is characterized in that, described frequency synthesizer includes and receives the local oscillator generator, and described reception local oscillator generator respectively sending and receiving is penetrated two mixer combination in local oscillator generator, divider, multi-modulus frequency divider MMD and the described receiver;
Described divider connects voltage controlled oscillator VCO, loop filter LF and phase discriminator and voltage pump concatenation module successively, described phase discriminator and voltage pump concatenation module connect respectively a Numerically Controlled Oscillator and a multi-modulus frequency divider, described multi-modulus frequency divider meets respectively described divider and a modulator DSM, and described voltage controlled oscillator VCO is also joined with an automatic frequency controller AFC.
4. radio-frequency front-end transceiver as claimed in claim 3, it is characterized in that, described transmitter includes four digital to analog converter combinations, and each digital to analog converter combination includes a frequency mixer and a radio frequency digital to analog converter RFDAC, and described frequency mixer and radio frequency digital to analog converter RFDAC join;
Wherein frequency mixer and the same low band transformer in the combination of two digital to analog converters joins, and two digital to analog converters in making up radio frequency digital to analog converter RFDAC and the emission local oscillator generator in the described frequency synthesizer join; Frequency mixer and same high band transformer in the combination of two other digital to analog converter join, and digital to analog converter in making up radio frequency digital to analog converter RFDAC and the emission local oscillator generator in the described frequency synthesizer join.
5. such as each described radio-frequency front-end transceiver in the claim 2 to 4, it is characterized in that, described low noise amplifier LNA includes N-type MOS switching tube M1 and N-type MOS switching tube M2, and the source electrode of the source electrode of described MOS switching tube M1 and N-type MOS switching tube M2 is connected with the two ends of an inductance L s respectively;
The grid of described MOS switching tube M1 connects respectively a capacitor C 10 and resistance R 1, and described capacitor C 10 and the first differential signal input port INP join; The grid of described MOS switching tube M2 connects respectively a capacitor C 20 and resistance R 2, and described capacitor C 20 and the second differential signal input port INN join; The other end of the other end of described resistance R 1 and resistance R 2 joins with a direct current biasing control signal input port B ias together.
6. radio-frequency front-end transceiver as claimed in claim 5, it is characterized in that, described variable gain amplifier VGA includes a plurality of MOS switching tube M3, M13, M23, M4, M14 and M24, wherein, the source electrode of described MOS switching tube M3, M13 and M23 is connected with the drain electrode of MOS switching tube M1 among the described low noise amplifier LNA simultaneously; The source electrode of described MOS switching tube M4, M14 and M24 is connected with the drain electrode of MOS switching tube M2 among the described low noise amplifier LNA simultaneously;
The grid of described MOS switching tube M3 and the grid of M4 intersect rear and power supply end V
DDJoin;
Described MOS switching tube M13 and M14 join with first a gain control signal port GC respectively, and described MOS switching tube M23 and M24 join with second a gain control signal port GCB respectively;
Rear and the total output OUT of first signal are intersected in the drain electrode of described MOS switching tube M3 and M13 together
PJoin, rear and the total output OUT of secondary signal are intersected in the drain electrode of described MOS switching tube M4 and M14 together
NJoin; In addition, the drain electrode of described MOS switching tube M23, M24 respectively with power supply end V
DDJoin.
7. radio-frequency front-end transceiver as claimed in claim 6 is characterized in that, described Radio Frequency Tracking filter includes the negative transconductance module, the total output OUT of described negative transconductance module and described first signal
PWith the total output OUT of secondary signal
NJoin;
The total output OUT of first signal
PWith the total output OUT of secondary signal
NBetween be provided with a frequency range tunable capacitor C
b, described electric capacity storehouse frequency range tunable capacitor C
bBe parallel with an inductance L
D, described inductance L
DWith power supply end V
DDJoin.
8. radio-frequency front-end transceiver as claimed in claim 7, it is characterized in that, described negative transconductance module includes a plurality of negative transconductances unit, have respectively a first signal output Outp and a secondary signal output Outn on each negative transconductance unit, first signal output Outp while and the total output OUT of first signal of all negative transconductance unit
PJoin secondary signal output Outn while and the total output OUT of secondary signal of all negative transconductance unit
NJoin.
9. radio-frequency front-end transceiver as claimed in claim 8, it is characterized in that, each described negative transconductance unit includes MOS switching tube M5, M6, M7 and M8, wherein, the drain electrode of described switching tube M7 and the grid of M8 intersect rear and first signal output Outp joins, the grid of described M7 and the drain electrode of M8 are intersected rear and secondary signal output Outn joins, and the source electrode of described switching tube M7 and M8 joins with the drain electrode of switching tube M5 simultaneously;
The grid of described switching tube M5 and M6 links together, described switching tube M5 and M6 ground connection, the drain electrode of described switching tube M6 respectively with grid, direct current biasing control signal input port B ias, described Bias and a power supply end V
DDJoin.
10. such as each described radio-frequency front-end transceiver in the claim 2 to 4, it is characterized in that, also include a tracking filter Q factor Q correcting circuit, this circuit includes a frequency mixer, a local oscillator generator and a figure adjustment engine, wherein, described Radio Frequency Tracking filter joins with described frequency mixer and figure adjustment engine respectively, and described frequency mixer joins with described local oscillator generator, figure adjustment engine respectively.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN2012202909496U CN202818281U (en) | 2012-06-20 | 2012-06-20 | Radio-frequency front-end transceiver for a silent surface filter of a multi-standard mobile terminal |
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN2012202909496U CN202818281U (en) | 2012-06-20 | 2012-06-20 | Radio-frequency front-end transceiver for a silent surface filter of a multi-standard mobile terminal |
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| Publication Number | Publication Date |
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| CN202818281U true CN202818281U (en) | 2013-03-20 |
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|---|---|---|---|
| CN2012202909496U Withdrawn - After Issue CN202818281U (en) | 2012-06-20 | 2012-06-20 | Radio-frequency front-end transceiver for a silent surface filter of a multi-standard mobile terminal |
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| Country | Link |
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| CN (1) | CN202818281U (en) |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102723964A (en) * | 2012-06-20 | 2012-10-10 | 天津里外科技有限公司 | Radio frequency front-end transceiver of silent surface filter of multi-standard mobile terminal |
| CN112242876A (en) * | 2020-10-28 | 2021-01-19 | 高拓讯达（北京）科技有限公司 | Method for obtaining clock signal provided by external clock source and wireless communication device |
-
2012
- 2012-06-20 CN CN2012202909496U patent/CN202818281U/en not_active Withdrawn - After Issue
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102723964A (en) * | 2012-06-20 | 2012-10-10 | 天津里外科技有限公司 | Radio frequency front-end transceiver of silent surface filter of multi-standard mobile terminal |
| CN102723964B (en) * | 2012-06-20 | 2014-09-03 | 天津里外科技有限公司 | Radio frequency front-end transceiver of silent surface filter of multi-standard mobile terminal |
| CN112242876A (en) * | 2020-10-28 | 2021-01-19 | 高拓讯达（北京）科技有限公司 | Method for obtaining clock signal provided by external clock source and wireless communication device |
| CN112242876B (en) * | 2020-10-28 | 2021-08-10 | 高拓讯达（北京）科技有限公司 | Method for obtaining clock signal provided by external clock source and wireless communication device |
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