CN1611047A

CN1611047A - Non-zero complex weighted space-time code for multiple antenna transmission

Info

Publication number: CN1611047A
Application number: CN02807290.1A
Authority: CN
Inventors: K·库基; A·霍蒂宁; O·蒂尔科宁; M·库塞拉; Y·凯派宁
Original assignee: Nokia Oyj
Current assignee: Nokia Technologies Oy
Priority date: 2001-03-28
Filing date: 2002-03-26
Publication date: 2005-04-27
Anticipated expiration: 2022-03-26
Also published as: BR0208208A; WO2002080375A3; CA2440033A1; EP1512256A4; AU2002251395A1; CN100536450C; CA2440033C; MXPA03008030A; JP2005503045A; EP1512256A2; WO2002080375A2; RU2003131399A; RU2276463C2

Abstract

The present invention presents a method and apparatus for phase hopping and space-time coding signals for transmission on multiple antennas (160,162,164,166). The method and apparatus provides expansion of a N x N' space time block code to a M x M' space time block code, where M>N, by using phase hopping on the symbols within the N x N' space time block code to allow transmission of the space time block code on a number of diversity antennas greater than N'. A result of M antenna diversity may be achieved for M transmit antennas.

Description

The non-zero complex weighted space-time code that is used for the multiple antenna transmission

FIELD OF THE INVENTION

The present invention relates to a kind of method and apparatus that is used for realizing the transmission diversity of wireless telecommunication system, especially, relate to a kind of be used for the multiple antenna transmission carry out non-zero complex weighted and method and apparatus space-time code to signal.

The background of invention

Along with the development of wireless communication system, improve gradually about the requirement of the wireless system design of equipment and performance requirement aspect.Following wireless system, compare with the second generation digital system of using at present with the simulation of the first generation, it should be the 3rd or fourth-generation system, except needs provide high-quality voice service, also needs to provide the data, services of high-quality high transfer rate.Consistent with the service performance demand of system, on device design, exist restriction, the influence that this is bigger the design of portable terminal.Third and fourth generation mobile radio terminal will need littler, lighter, a plurality of effective energy unit that the required data, services of intrinsic sound and these following wireless systems can be provided.

Time dependent multipath fading is an effect in the wireless system because receiver signal constructive and destructive and, the signal of a transmission along many roads leading to receiver through propagation, thereby caused the decay of received signal.The method that known being used at present overcomes the multipath fading effect has following, for example, carries out time-interleavedly with self-correcting code, utilizes spread spectrum techniques to realize the diversity of frequency, perhaps transmitter energy control technology.But each in these technology is used in the third and fourth generation wireless system and is all existed defective.The time-interleaved unnecessary delay of having introduced, spread spectrum techniques is in order to overcome big coherence bandwidth, need bigger allocated bandwidth, the higher transmitter energy that the energy control technology need be more required than intrinsic receiver-transmitter Feedback Technology, Feedback Technology has improved the complexity of portable terminal.The influence that these all shortcomings are all passive realize the required characteristic of the third and fourth generation portable terminal.

Antenna diversity is the another kind of technology that is used for overcoming wireless system multipath fading effect.In diversity reception, the antenna of two or more physical separation is used to receive the signal of a transmission, and signal is merged and conversion process then, thereby has produced the signal of a reception.The shortcoming of diversity reception is that physical separation required between the antenna makes and can't uses diversity reception on the forward link in new wireless system, and need small-sized portable terminal in new wireless system.Be used to realize that the another kind of method of antenna diversity is a transmission diversity.In transmission diversity, a signal is transmitted from two or more antennas, by using for example maximum likelihood sequence estimator (MLSE), least mean-square error (MMSE) receiver is handled at receiver end to receiver or their approximation behind the maximum a then.Transmission diversity has more actual application in the forward link of wireless system, wherein, and realization multiple antenna that can be more easy in the base station than in portable terminal.

Now studied the situation of the transmission diversity of two antennas in good condition.Alamouti has advised a kind of method of diversity transmission of two antennas that second level diversity is provided for the complex values signal.S.Alamouti, " the simple transmit diversity technique that is used for radio communication " (IEEE selects communication zone magazine, 1451-1458, in October, 1998).The Alamouti method relates at a symbol period transmits two signals simultaneously from two antennas.In a symbol period, the signal that sends from first antenna is represented as S0, and the signal that sends from second antenna is represented as S1.In next symbol period, the signal that sends from first antenna is-S1 ^*, the signal that sends from second antenna is represented as S0 ^*, wherein ^*For complex conjugate is represented symbol.A simple diversity transmission system also can realize at encoding domain.For example, two of same-sign are duplicated the parallel transmission of walsh code that can use two quadratures.Same technology also can be used to construct the coding method of a frequency domain.

The Alamouti method can not directly expand to plural antenna.The method of the space-time block coding that the use complex signal planisphere that people such as Tarokh have proposed a kind of rate=1/2 of use and 3/4 transmits on three and four antennas.V.Tarokh, H.Jafarkhani, and A.Calderbank, " space-time block coding of orthogonal design " (IEEE about the journal of information theory, 1456-1467, in July, 1999).This method has a shortcoming, has lost transmission ratio, and many level nature of ST coded identification have increased the required peak value-average ratio that transmits, and the strict demand that has increased the linear power amplifier design.The other method that alleviates these problems is " the plural space-time block coding that is used for the 4Tx antenna " that put forward by O.Tirkkonen and A.Hottinen (a Global Communications System journal in November, 2000,2000, san francisco, usa).The method of other suggestion comprises rate=1, orthogonal set emission (OTD)+4 antenna time-space diversity emission (STTD) method.L.Jalloul, K.Kuchi and J.Chen, " performance evaluation of CDMA diversity transmitting method " (IEEE media technology conference proceedings, autumn in 1999) and M.Harrison and K.Kuchi " opening of the High Data Rate on 2 and 4 elements and the emission of closed circulation diversity " (the submission 3GPP-C30-19990817-017 of Motorola).This method needs an external encode, and owing to second sequential interleaved gain of STTD piece (Alamouti piece) and use OTD piece provides second diversity order.The performance of this method depends on the intensity of external encode.Because this method needs external encode, it is not suitable for uncoded system.For the situation of the convolutional encoding of rate=1/3, the performance of the ST block coding method of OTD+STTD method and Tarokh rate=3/4 method is identical.The method of another rate=1 is at O.Tirkkonen, ABOARIU and A.Hottinen, and " the minimum nonopiate ratel space-time block coding that is used for the 3+Tx antenna " has related in (ISSSTA journal, in September, 2000).But the method for advising in this article has reached high performance has needed a complicated receiver.

Therefore, if a kind of method and apparatus is arranged, can provide the diversity transmission on more than two antennas, the design complexity that does not increase system simultaneously will be very favorable.

Summary of the invention

The invention provides a kind of method and apparatus that is used on a plurality of antennas, transmitting non-zero complex weighted and space-time code signal.This method and apparatus provides the space-time block coding that expands to a M * M ' by the non-zero complex weighted space-time block coding with a N * N ' that uses circulation and symbol in the space-time block coding of N * N ', wherein N is the number of transmission path, N ' is the number of output symbol on each transmission path, here, M＞N, thus allow space-time block coding on M multiple antenna, to launch.The diversity transmission path can comprise the antenna or the wave beam of separation.The temporary transient length of bigger coding M ' can equal the temporary transient length of source code N '.In this method and apparatus, produce a transformation results that comprises a space-time block coding thereby on an incoming symbol stream, carry out conversion.The N of a space-time block coding output stream then, each all comprises the individual output symbol of N ', be repeated, thereby and the stream of at least one repetition carry out M stream of the individual output symbol of non-zero complex weighted generation N ' in time, be used on M diversity transmission path, transmitting.The non-zero complex weighted phase shifts that comprises.

In one embodiment, N is at least 2, and M is at least 3.In in the individual output symbol of N ' N stream at least two, corresponding to N primary flow in the individual output symbol of N ', each is launched on first at least one antenna then, and is launched in second at least one antenna one of in the non-zero complex weighted stream of M-N in the individual symbol of N ' at least one.First at least one antenna and second at least one antenna can comprise any one in M the antenna.

In another embodiment, this method and apparatus can realize in a transmitter with public or dedicated pilot channel, can effectively the decode channel estimation of the required coefficient of space-time code of this public or dedicated pilot channel.In this embodiment, that public and dedicated pilot channel can be independent in transmitter or two combined realizations.In the alternate embodiment of this embodiment, transmitting training sequence on N diversity transmission path so just can make the individual independently diversity transmission path of estimation N become possibility.For this reason, the pilot channel coded sequence of a special use can be multiplexed on N of the individual output symbol of the N ' stream of each original space-time block coding, flows and pilot channel sequence thereby produce N of the individual output symbol of N '.Thereby circulate then and the non-zero complex weighted M phase shifted streams and the pilot channel sequence that can be employed the individual symbol of generation N '.In the N of the individual output symbol of the N ' primary flow at least two and pilot channel sequence one in first at least one antenna then are launched, and at least one and pilot channel sequence in the M-N of the individual output symbol of N ' complex weighted stream then in second at least one antenna be launched.The another kind of method that can estimate N channel is an emission common pilot channel signal, N common pilot channel signal just launched on each in first at least one antenna like this, and the complex weighted copy of some M-N of N common pilot channel just is launched in second at least one antenna.To constitute the employed factor of the complex weighted stream of M-N of the individual output symbol of N ' identical with being used for N primary flow according to the individual output symbol of N ' for the employed complex weighted factor of common channel on each second at least one antenna.In these embodiments, receiver can be known method that also can not know to be used for N * N ' space-time block coding is expanded to M * N ' space-time block coding, and employed temporary transient weighting sequence.

In another embodiment, N is at least 2, and M is at least 3, and pilot channel can be configured to estimate N+1 diversity transmission path at least.The N of the individual output symbol of N ' stream at least one, original N stream corresponding to the individual output symbol of N ', on first at least one antenna, launch then, be launched at least one of the complex weighted stream of M-N of the individual symbol of N ' in second at least one antenna.Be launched in different common pilot channel each in first at least one antenna and second at least one antenna at least one.In these embodiment examples, receiver need be used for N * N ' space-time block coding is expanded to the part knowledge of the method for M * N ' space-time block coding at least, and employed temporary transient weighting sequence.

Complex weighted can the realization in each complex weighted symbols streams among each embodiment by complex weighted pattern one-period or at random is applied to.Relation between the symbols streams of launching on each antenna complex weighted also can be scheduled.

Brief description of drawings

Accompanying drawing 1a has shown the block diagram of transmitter according to an embodiment of the invention;

Accompanying drawing 1b has shown the block diagram of the part of common pilot channel STTD transmitter according to an embodiment of the invention;

Accompanying drawing 3 has shown the block diagram of the part of dedicated pilot channel STTD transmitter according to another embodiment of the invention;

Accompanying drawing 4 has shown the block diagram with the part of the embodiment of the matching used receiver of the transmitter of accompanying drawing 1;

Accompanying drawing 5 has shown the block diagram with the part of the embodiment of the matching used receiver of transmitter of accompanying drawing 2 or accompanying drawing 3;

Accompanying drawing 6 has shown the embodiment of the rake formula finger of the STTD demodulator 508 in the accompanying drawing 5.

Accompanying drawing 7 has shown the block diagram of the part of STS transmitter according to an embodiment of the invention;

Accompanying drawing 8 has shown the block diagram of the part of OTD transmitter according to an embodiment of the invention;

Accompanying drawing 9 has shown the block diagram with the part of an embodiment of the matching used receiver of transmitter of accompanying drawing 7;

Accompanying drawing 10 has shown the block diagram with the part of an embodiment of the matching used receiver of transmitter of accompanying drawing 8;

Accompanying drawing 11 has shown the block diagram of the part of a long ST block encoding transmitter according to an embodiment of the invention;

Accompanying drawing 12 has shown the block diagram of a public/biography according to another embodiment of the invention with the part of pilot channel STTD transmitter;

Accompanying drawing 13 has shown the block diagram with the part of the matching used receiver of the transmitter of accompanying drawing 12; And

Accompanying drawing 14 has shown the block diagram with the energy control section of the matching used receiver of the transmitter of accompanying drawing 12.

Accompanying drawing 15 has shown the planisphere that has defined a phase shifts pattern of using in each embodiment of the present invention.

Detailed description of the present invention

Referring now to accompanying drawing 1a, shown the block diagram of a transmitter 150 according to an embodiment of the invention here.Transmitter 150 comprises input 152, be used to receive an incoming symbol stream, block code processor 154, thereby be used on an incoming symbol stream, carrying out conversion and produce a transformation results of representing by the orthogonal space-time block encoding, and export the symbols streams of two transformation results, non-zero complex weighted device 156, be used for carrying out non-zero complex weighted to first of two symbols streams, non-zero complex weighted device 158, be used for to two symbols second and carry out non-zero complex weightedly, a RF transmitter 160 is used in antenna 1 first symbols streams of emission, a RF transmitter 162, be used for the non-zero complex weighted stream at antenna 2 emission symbols, a RF transmitter 164 is used in second symbols streams of antenna 3 emissions, and a RF transmitter 166, be used for second symbols streams that moves at antenna 4 transmitter, phases.Thereby antenna 1-4 can polarize each other and place the diversity reception that enhancing is provided.For example,

antenna

1 or 2

antenna

3 or 4 perpendicular polarizations of can be respectively placing with horizontal polarization.The example of the transmitter among the accompanying drawing 1a can be realized with various forms, as long as it is suitable for and can expands to different technologies and the system of transmitting by 2 * N ' block encoding on 4 diversity transmission paths.In transmitter 150, each in 4 diversity transmission paths comprises the antenna of a separation, antenna 1-antenna 4.Can comprise code division multiple access (CDMA) system, time division multiple access (TDMA) system, perhaps other any digital communication systems that can introduce transmission diversity.In the alternate embodiment of accompanying drawing 1a, non-zero complex weighted can all on selected transmission road warp, being performed, thus between the transmission of antenna 1 and antenna 2 or antenna 3 and antenna 4, produce phase shifts.For example, non-zero complex weightedly also can before being input to RF transmitter 160 and 164, be employed, produce the non-zero complex weighted version of each symbols streams, but between the signal that transmits, keep a relative phase shifts.An alternate embodiment 150 of transmitter 150 can be used and be less than the path that 4 antennas are realized 4 diversity transmission.For example, the signal that is input to RF transmitter 164 or 166 can be connected in together and transmit in an independent antenna.Another kind of substituting also is possible, wherein used to be less than 4 diversity transmission paths, for example, only have in two data flow one can be by non-zero complex weighted and on two diversity paths, transmit.In the alternate embodiment of accompanying drawing 1a, non-zero complex weighted operation can be performed in RF transmitter block 160,162,164,166, promptly non-zero complex weighted can be as a continuous phasescan after the modulation and the baseband filtering of space-time code symbol.

The non-zero complex weighted of these transmission on

antenna

2 and 4 can be performed according to various alternative.For example, phase pattern W1 (t)=exp (j that on antenna 2, uses ^*Pi ^*Phase-in-degrees/180) can be employed, and phase pattern-W1 (t), the phase place of its skew W1 (t) is 180 degree, can be used on antenna 4.The example of the phase shifts pattern of angle on the antenna on the 4PSK planisphere 2 be 0,90,180, and on 270} and the antenna 4 be 180,270,0,90}.Accompanying drawing 15 has shown the planisphere of the another kind of phase shifts pattern that can use in each embodiment of the present invention.The mobile number of degrees of this sequence 0,135,270,45,180,315,90,225} can be transmitted on the antenna 2 on antenna 4, use simultaneously the move angle pattern 180,315,90,225,0,135,270,45}.Phase shifts can be periodically or at random.Periodic phase shifts refers to a predetermined phase pattern, for example, periodically repeats complex weighted W1 (t).Thereby the complex weighted path of a maximum length that made complex weighted sequence definition of can being defined is so that as far as possible independently carry out continuous sampling to effective channel.This can produce and interweave redundancy and reduce the delay transmission.It can be the sequence of the random phase that chooses from a MPSK planisphere that employed pseudo-random phase moves.In addition, in the time of the relevant tolerance of the energy control of estimating channel coefficient inclusive NAND zero complex weighted channel, another kind of non-zero complex weighted scheme is favourable, and the phase difference in this scheme between the continuous phase state is as much as possible little.In this case, in the duration of an encoding block, phase state can cover 360 degree.Channel interweaves and also can be used in the embodiment of legacy system.Also may carry out non-zero complex weighted sequence can be independent as much as possible with the symbol of uniting the output of such interleaver that interweaves.And by changing the relative phase place between

antenna

1 and 2 and 3 and 4 respectively, thereby this method can be performed all have a phase shifts or scanning on all antenna elements, but

antenna

1,2, and the phase shifts between 3,4 is held.For example, utilize phasescan, on antenna 1, have the phasescan of a 50Hz, and the phasescan that on antenna 2, has one-50Hz, thereby have the effective scanning of a 100Hz.Similar for antenna 3 and antenna 4.

Also can be every T change a phase place rotation second.The selection of T decided according to total duration of data symbol and the method that is used for the estimating channel coefficient.Phase place can be held and not become shared total duration of data symbol, and wherein at least one space-time code piece and corresponding special use or common pilot sequence/training sequence can be used to carry out suitable channel estimation.Pilot frequency sequence can be a walsh code as using in the cdma system, or is used for the sequence of the training symbol of correcting feature preferably that has of channel estimation in tdma system.Frequency pilot sign can be used identical non-zero complex weighted coefficient with data in the space-time piece.In addition, pilot tone can not have being transmitted of phase step yet.In this case, effective channel of data can be estimated the associating derivation from the dancing mode of a previously known with according to the channel that a non-dancing mode channel obtains.Under the non-zero complex weighted situation that is applied to public guide frequency, can use identical or different phase patterns with public guide frequency for data.Use the channel estimation of non-jump pilot tone or training sequence (transmission on public or dedicated channel) that better channel estimation is provided owing to channel is more stable.

Referring now to accompanying drawing 1b, be the part block diagram of common pilot channel space-time diversity transmission (STTD) transmitter 100 according to an embodiment of the invention here.Transmitter 100 can be as 4 antenna transmit diversity of the version 99 of a wideband CDMA (WCDMA) that extends to third generation system standard.Transmitter 100 comprises input 126, block code processor 124, traffic channel symbol stream are handled the input 102a-102d of branch, antenna gain block 104a-104d,

phase shifter

106a and 106b,

phase shifter input

112a and 112b, encoded multiplier 108a-108d, pilot frequency sequence handle the input 114a-114d of branch, antenna gain block 116a-116d, encoded multiplier 118a-118d, RF transmitter 128 comprises RF transmitter 128z-128d and antenna 1-4.

In accompanying drawing 1b, the data that are transmitted are received at input 126, these data comprise a channel coding and comprise the incoming symbol stream X (t) that interweaves of symbol S1S2.Coding produces a transformation results that comprises one 2 * 2 orthogonal space-time block encoding thereby block code processor 124 per two receiving symbol S1S2 carry out once.In the present embodiment, thus block code processor 124 can carry out the Alamouti conversion and produce a block encoding, represent with following matrix form:

[\begin{matrix} S_{1} & S_{2} \\ {- S}_{2}^{*} & S_{1}^{*} \end{matrix}] - - - (1)

Matrix is divided into 4 streams of two symbols then, and each in these streams all is input to traffic channel symbol stream and handles among the input 102a-102d of branch.As shown in Figure 1, stream S1S2 is imported into 102a, and S1S2 is imported into 102b ,-S2 ^*S1 ^*Be imported into 102c ,-S2 ^*S1 ^*Be imported into 102d.Non-zero complex weighted by antenna gain block 104a-104d and

phase shifter

106a and 106b execution.Each is handled the antenna gain of branch and adjusts in antenna gain block 104a-104d.After the antenna gain was adjusted,

phase shifter

106a and 106b were applied to the stream S1S2 of antenna gain block 104b output and the stream-S2 of antenna gain block 104d output with a phase shift ^*S1 ^*Thereby phase shifter controll block 112a comes phase shift

control phase shifter

106a and 106b with 112b by using a phase step pattern continuous or that separate.Then to CDMA scrambled code of encoded multiplier 108a-108d input, thereby produce the stream S1S2 that flows to RF transmitter 128a, on antenna 1, launch, flow to the stream S1S2 (exp (j Φ k1) of RF transmitter 128b, on antenna 2, launch, flow to stream-S1 of RF transmitter 128c ^*S2 ^*, emission on antenna 3, and the stream-S2 that flows to RF transmitter 128d ^*S1 ^*(exp (j Φ k2), emission on antenna 4.The RF transmitter can be carried out base band pulse and be shaped, modulation and carrier up conversion.In some equipment, can after base band pulse shaping and modulation step, select application phase to jump or scanning.

Common pilot channel sequence X1-X4 is imported into pilot frequency sequence and handles the input 114a-114d of branch.Pilot frequency sequence is processed separately by gain block 116a-116d and encoded multiplier 118a-118d then.The coding output of encoded multiplier 118a-118d is input to respectively among the RF reflector 128a-128d of RF transmitter 130 then.

Pilot frequency sequence X1 is launched on antenna 1 then, and pilot frequency sequence X2 is launched on antenna 2, and pilot frequency sequence X3 is launched on antenna 3, and pilot frequency sequence X4 is launched on antenna 4.

Referring now to accompanying drawing 4, its be one with accompanying drawing 1b in the part block diagram of transmitter 100 matching used receivers.Accompanying drawing 4 has shown a signal processing of harrowing in the formula finger in a receiver components.What receive is received and is input to channel estimation process device 402a-402d respectively from transmitter 100 pilot transmitted sequence X 1-X4.Channel estimator 404 is carried out channel estimation function then, for example to the rolling average function of the low-pass filtering of each channel 1-4.The estimated value of channel 1-4 outputs to adder 410a from output 406a-406d then, phase shifter 408a, adder 410b and phase shifter 408b.Phase shifter 408a receives input and moves employed identical phase shift estimated value the traffic channel symbol S1S2 that is launched with the antenna 2 of transmitter 100 for channel 2 from phase shifting control piece 414a.Phase shifter 408b receives input and moves the traffic channel symbol-S2 that is launched with the antenna 4 of transmitter 100 for channel 4 from phase shifting control piece 414b ^*S1 ^*In employed identical phase shift estimated value.The estimation phase version of channel 2 merges by adder 410a mutually with the estimated value of channel 1, and the estimation phase version of channel 4 and the estimation of channel 3 merge in adder 410b.The estimated value that channel 1 and 2 (412a) merges and the merging estimated value of channel 3 and 4 (412b) are imported into STTD demodulator 418 then, and demodulator 418 uses channel estimation to handle the transmission signals of reception.The rectification signal is then at rake formula combiner, thus the processed symbol S1S2 that receives that produces in deinterleaving and the channel decoder 420.

In the common pilot channel embodiment of 4 alternative antenna diversities, public pilot channel the transmission before in the mode identical with business channels by phase shift.Referring now to accompanying drawing 2, it is the part block diagram of a common pilot channel STTD transmitter 200 according to another embodiment of the invention.Transmitter 200 comprises input 226, and block code processor 224, traffic channel symbol stream are handled the input 202a-202d of branch, antenna gain block 204a-204d,

phase shifter

206a and 206b, pilot frequency sequence is handled the input 241a-214d of branch, antenna gain block 216a-216d, phase shifter 218a and 218b, phase

shifting control piece

224a and 224b, encoded multiplier 220a-220d, encoded multiplier input 222, RF transmitter 228 comprises RF transmitter 228a-228d, and antenna 1-4.

Business channels in the transmitter 200 handle with transmission with accompanying drawing 1 in transmitter 100 in employed business channels handle identical mode and be performed.But the public guide frequency that transmitter 200 has used by phase shift.Common pilot channel sequence P1 is imported into pilot frequency sequence and handles input 214a of branch and 214b, and common pilot channel sequence P2 is imported into pilot frequency sequence and handles input 214c of branch and 214d.Pilot frequency sequence is processed separately by antenna gain block 216a-216d then.Be imported into encoded multiplier 220a from the pilot frequency sequence P1 of antenna gain block 216a output.Be imported into encoded multiplier 220c from the pilot frequency sequence P2 of antenna gain block 216c output.Be imported into phase shifter 218a from the pilot frequency sequence P2 of antenna gain block 216b output.Be imported into phase shifter 218b from the pilot frequency sequence P2 of antenna gain block 216d output.Phase shifter 218a and 218b carry out a phase shifts respectively at the controller of phase-shift controller 224a and 224b.Phase shifts can be the identical continuous mode that uses in business channels or the phase step pattern of separation.The phase shift pilot tone road sequence P1 of phase shifter 218a output is imported into encoded multiplier 220b then, and the shifted pilot sequence P2 that exports from phase shifter 218b is imported into encoded multiplier 220d then.The coding pilot frequency sequence P1 of encoded multiplier 220a output is imported into RF transmitter 228a, transmission on antenna 1.The coding shifted pilot sequence P1 of encoded multiplier 220b output is imported into RF transmitter 228b, transmission on antenna 2, the coding pilot frequency sequence P2 of encoded multiplier 220c output is imported into RF transmitter 228c, transmission on antenna 3, and the coding shifted pilot sequence P that exports from encoded multiplier 220b is imported into RF transmitter 228d, transmission on antenna 4.

Phase shifter 218a and 218b can carry out phase shifts according to various alternative, for example, and above-mentioned phase shifts performed in the embodiment of accompanying drawing 1.

Referring now to accompanying drawing 5, its be with accompanying drawing 2 in the part block diagram of the matching used receiver embodiment 500 of transmitter.Receiver 500 comprises channel 1 and the channel 2 input 502a of estimation process branch and channel 3 and the channel 4 input 502b of estimation process branch, channel estimator 504, STTD demodulator 508, transmission signals input 510 and rake formula combiner, deinterleaver and channel decoder 512.

Be imported into input 502a from the antenna 1 of transmitter 200 and antenna 2 at the reception pilot frequency sequence P1 (ch1+ch2 Φ) that channel 1 and channel 2 receive respectively.Be imported into input 502b from the antenna 3 of transmitter 200 and antenna 4 at the reception pilot frequency sequence P2 (ch3+ch4 Φ) that channel 3 and channel 4 receive respectively.Channel estimator 504 is used such as low-pass filtering rolling average function and is carried out the channel estimation, and is the estimated value of a channel 1 and a merging of channel 2 (chest1,2) output, is the estimated value of a channel 3 and a merging of channel 4 (chest3,4) output.The channel estimation value is imported into STTD demodulator 508 then, and this demodulator uses the channel estimation value to handle the transmission signals that receives from input 510.The signal of rectification is then at rake formula combiner, and is processed in deinterleaver and the channel decoder 512, thereby produces the symbol S1S2 that receives.Accompanying drawing 6 has shown an embodiment of the rake formula finger of the STTD demodulator 508 in the accompanying drawing 5, the transmission signals that this finger utilizes

channel

1,2 and

channel

3,4 to come rectification to receive.

In another embodiment of 4 antenna diversities, special-purpose pilot channel can be employed in the version of a WCDMA of the transmitter in the accompanying drawing 1 150.Referring now to accompanying drawing 3, it is the part block diagram of a dedicated pilot channel STTD transmitter 300 according to another embodiment of the invention.Transmitter 300 comprises input 318, block code processor 316, channel symbol stream is handled the input 302a-302d of branch, antenna gain block 304a-304d, phase shifter 306a and 306b, phase shifter input 312a and 312b, encoded multiplier 308a-308d, encoded multiplier input 310 and antenna 1-4.

Transmitter 300 in the accompanying drawing 3 is an equipment that uses the dedicated pilot channel, and dedicated pilot transmits by pilot frequency sequence is embedded in the traffic channel symbol stream.The operational mode of input 126 and block code processor 124 is identical in input 318 and block code processor 316 and the accompanying drawing 1.In transmitter 300, when symbol S1S2 was imported into symbols streams processing input 302a of branch and 302b, pilot channel sequence U1 is imported into input 302a and 302b, and was multiplexed between the S1S2 symbols.-S2 ^*S1 ^*Be imported into symbols streams and handle input 302c of branch and 302d, pilot channel sequence U2 is imported into input 302c and 302d, and-S2 ^*S1 ^*Symbols between carry out multiplexed.Another kind may be 4 different dedicated pilot sequence of definition, one of each transmit antenna.

The symbols streams multiplexed at input 302a-302d is input to antenna gain block 304a-304d respectively then.Channel gain is applied to antenna gain block 304a-304d.The stream that comprises S1S2 and pilot frequency sequence U1 outputs to encoded multiplier 308a from antenna gain block 304a.The stream that comprises S1S2 and pilot frequency sequence U1 outputs to phase shifter 306a from antenna gain block 304b, and there, signal flow carries out phase shifts according to the input of phase shifting control piece 312a, is imported into encoded multiplier 308b then.Comprise-S2 ^*S1 ^*Output to encoded multiplier 308c with the stream of pilot frequency sequence U2 from antenna gain block 304c, phase homogeneous turbulence then ,-S2 ^*S1 ^*Output to phase shifter 306b with pilot frequency sequence from antenna gain block 304d, flow there according to the input of phase-shift controller 312b and carry out phase shifts, be input to encoded multiplier 308d then.Encoded multiplier 308a-308d multiply by a scrambled code with suitable stream.The stream S1S2 of code multiplied and pilot frequency sequence U1 are imported into RF transmitter 314a then, emission on antenna 1.The stream S1S2 of code multiplied phase shifted and pilot frequency sequence U1 are imported into RF transmitter 314b, emission on antenna 2.Stream-the S2 of code multiplied ^*S1 ^*Be imported into RF transmitter 314c with pilot frequency sequence U2, emission on antenna 3, and the stream-S2 of code multiplied phase shifts ^*S1 ^*Be imported into RF transmitter 314d with pilot frequency sequence U2, emission on antenna 4.RF transmitter 314a-314d carried out modulation and carrier up conversion before antenna 1-4 emission stream.The RF transmitter can be carried out the pulse shaping of base band, modulation and carrier up conversion.In some equipment, can after base band pulse moulding and modulation, select to use the non-zero weighting.

Receiver in the accompanying drawing 5 can change with accompanying drawing 3 in transmitter 300 supporting uses.In this case, receiver 500 can similarly move, except input 502a and 502b respectively to channel estimator 504c input U1 (Ch1+Ch2 Φ) and U2 (Ch3+Ch4 Φ).

In another embodiment of 4 antenna diversities, dedicated pilot channel and common pilot channel can be used in the embodiment of an associating.Referring now to accompanying drawing 12, it is the part block diagram of a dedicated/common pilot channel STTD transmitter 1200 according to another embodiment of the invention.

Transmitter 1200 is identical with the operational mode of transmitter 300 in the accompanying drawing 3 basically, has just increased common pilot channel on antenna 1 and antenna 3.Common pilot channel P1 and P2 are input to pilot frequency sequence respectively and are handled input 1218a of branch and 1218b.Pilot frequency sequence is processed separately by antenna gain block 1220a and 1220b and encoded multiplier 1222a and 1222b then.Be input to the RF transmitter 1214a and the 1214c of RE transmitter 1214 then respectively from the coding of encoded multiplier 1222a and 1222b output.The RF transmitter can be carried out base band pulse and be shaped, modulation, carrier up conversion.In some equipment, also can be shaped and the weighting of modulation selection application later on non-zero at base band pulse.

Transmitter in the accompanying drawing 12 provides the common pilot channel of non-jump on antenna 1 and antenna 3, at

antenna

1,2, provide special-purpose pilot channel on 3,4.Pilot frequency sequence can be multiplexed in a time slot, for example in one embodiment, has 15 time slots in a transmission frame.Antenna gain can be controlled the different of channel setting to public and special use.Antenna gain also can change in time.

Referring now to accompanying drawing 13, its be one with accompanying drawing 12 in the part block diagram of the matching used receiver of transmitter.Receiver 1300 comprises channel 1 and the channel 2 processing branches with

input

1302a and 1302b and channel 3 with

input

1302c and 1302d and channel 4 processing branches.Phase shift input 1304, channel estimator 1306, STTD demodulator 1310, transmission signals input 312 and deinterleaving and decoding device 1314.

The pilot frequency sequence P1 that receives, U1, P2 and U2 and input are input to the 1302a of receiver 1300 respectively, 1302b, 1302c and 1302d.Channel estimator 1306 is carried out the channel estimation, for example, utilizes a low-pass filtering with average function, and be channel 1 and 2 (chest1,2) estimated value of a merging of 1308a output is the estimated value of a channel 3 and a merging of channel 4 (chest3,4) output.The channel estimation value is imported into STTD demodulator 1310 then, and this demodulator utilizes the channel estimation value to handle the transmission signals that receives from input 1312.The rectification signal is then at rake formula combiner, and is processed in deinterleaver and the channel decoder 1314, thereby produces the symbol S1S2 that receives.

A kind of known technology of phase step is to use for the purpose of energy control.Referring now to accompanying drawing 14, it has shown the part that is used for a receiver of estimated energy control according to an embodiment of the invention.Receiver 1400 comprises channel estimator 1402, the channel estimation input 1404a-1404d of branch, phase shift input 1408a and 1408b, phase shifter 1406a and 1406b, channel estimation output 1410a and 1410b, square piece 1412a and 1412b, energy controller 1414.

Channel estimator 1402 is in a given time slot " t " process, for four all antennas calculate channel coefficients according to the public or dedicated channel from for example transmitter 1200.It can be the channel prediction of a time slot t+1, and alternately, the estimation of the channel of time slot t can be used in the fading channel that slowly changes.These channel coefficients are represented as Chanest#1 (t) respectively at input 1404a-1404d, Chanest#2 (t), Chanest#3 (t), Chanest#4 (t).For multiple rake formula finger, for example, Chanest#1 (t) is that a corresponding vector channel of all rake formula fingers with antenna 1 is estimated.

The knowledge of the existing knowledge of the phase step of use phase shifts input 1408a and 1408b and the estimation of the channel of current time slots " t ", the channel coefficients of time slot " t+1 " can be estimated:

Chanest#12(t)＝Chanest#1(t)+Chanest#2(t)e ^Φ12(t+1)

Chanest#34(t)＝Chanest#3(t)+Chanest#4(t)e ^Φ34(t+1)(2)

Wherein Φ 12, and Φ 34 is known priority.

The received signal energy budget of time slot (t+1) can be calculated according to Chanest#12 (t+1) and Chanest#12 (t+1):

received_power(t+1)＝‖Chanest#12(t+1)‖ ²+‖Chanest#34(t+1)‖ ²

Utilize the energy budget that receives, processor 1414 has produced an energy control command.

Method and apparatus of the present invention also can be concentrated at the branch in walsh code territory and realize.Referring now to accompanying drawing 7, it is the part block diagram of space-time diffusion (STS) transmitter 700 according to an embodiment of the invention.

Transmitter 700 is STS embodiment of the transmitter 150 among the accompanying drawing 1a, and wherein space-time piece processor is carried out conversion in the walsh code territory.The STS block code matrix of using can be represented as:

[\begin{matrix} S 1 {\tilde{W}}_{1} & - S 2^{*} {\tilde{W}}_{2} \\ S 2 {\tilde{W}}_{1} & + {S 1}^{*} {\tilde{W}}_{2} \end{matrix}]

Wherein

{\tilde{W}}_{1} = [\begin{matrix} W 1 & W 1 \end{matrix}], {\tilde{W}}_{2} = [\begin{matrix} W 1 & - W 1 \end{matrix}] - - - (3)

As among the accompanying drawing 1a embodiment did, each row and its phase shifts version of matrix are launched on antenna 1-4 respectively.Each the row on symbol S1 and S2 in two symbol periods by synchronized transmissions, rather than successively the emission.Data symbol is imported into transmitter 700 at the input 718 of channel encoder 720.Channel encoder 720 coding, perforation interweaves and forms and imports data symbol, and every an encoder output symbol S1 as even data, every an encoder output symbol S2 as odd data.Even data receives piece 702a by symbol then, b, and e, f, walsh function blocks 704b and 704d, walsh multipliers 706a, b, e, f, adder 708a-708d and complex adder 710a and 710b are processed.Odd data receives piece 702e by symbol, d, and g, h, walsh function blocks 704b and 704d, walsh multipliers 706c, d, g, h, adder 708a-708d and complex adder 710a and 710b are processed.The result of complex adder 710a output is a row matrix

, the result of complex adder 710b output is a row matrix

Be imported into complex multiplier 712a then, produce

{S 1 {\tilde{W}}_{1} - S 2^{*} {\tilde{W}}_{2}} e^{jφ 1},

Be imported into complex multiplier 712b, produce

{S 2 {\tilde{W}}_{1} + {S 1}^{*} {\tilde{W}}_{2}} e^{jφ 2} . {\tilde{SW}}_{1} - {S 2}^{*} {\tilde{W}}_{2}

Be imported into RF transmitter 714a then, transmission on antenna 1,

{S 1 {\tilde{W}}_{1} - {S 2}^{*} {\tilde{W}}_{2}} e^{jφ 1}

Be imported into RF transmitter 714b, transmission on antenna 2, Be imported into RF transmitter 714c, transmission on antenna 3, and

{S 2 {\tilde{W}}_{1} + {S 1}^{*} {\tilde{W}}_{2}} e^{jφ 2} .

Be imported into RF transmitter 714d, transmission on antenna 4.

Referring now to accompanying drawing 9, its be one shown with accompanying drawing 7 in the part block diagram of an embodiment of transmitter 700 matching used receivers 900.Transmitter 700 comprises input 912, walsh function blocks 902b and 902d, walsh multipliers 902a and 902c, channel multipliers 904a-904d, complex adder 906a and 906b, multiplier (MUX) 908, and output 910.The signal of a reception is received at input 912, and is handled by the STS demodulator.Pilot channel transmission is identical with the situation of STTD with the channel estimation process.412a and 412b in the accompanying drawing 4 under the situation of channel estimation 904c and 904b and non-jump common pilot channel are identical.For the situation of jump public guide frequency or dedicated pilot transmission, the channel estimation can obtain from the channel estimation block 504 of Fig. 5.These channel estimated values are imported into the STS demodulator of Fig. 9 as h1 and h2, and h1 is corresponding to coming from antenna 1, the merging channel estimation of antenna 2, and h2 is corresponding to coming from antenna 3, the channel estimation of antenna 4.When utilizing 902a, b, c, d and 904a, b, c, d and 906a, b have carried out after the STS rectification, and 908 output is exactly the signal of STS rectification, and this signal is sent to rake formula combiner, deinterleaver and the channel decoder module of Fig. 5.

Here Jian Yi invention also can be used among the embodiment of an orthogonal set of the present invention (OTD) transmission.Referring now to accompanying drawing 8, it is the part block diagram of an OTD transmitter 800 according to an embodiment of the invention.Transmitter 800 comprises input 822, channel encoder 820, symbol receiver module 802a-802d, walsh function blocks 804a and 804b, walsh multipliers 806a-806d, complex adder 808a-808d, complex multiplier 810a and 810b, RF transmitter 812a-812d.Transmitter is the embodiment of an orthogonal set transmission (OTD) of the transmitter 150 among the accompanying drawing 1a, and its space-time block code processor is carried out conversion in the walsh code territory.Employed OTD block code matrix can be represented like this:

[\begin{matrix} S 1 {\tilde{W}}_{1} \\ S 2 {\tilde{W}}_{2} \end{matrix}]

Here

{\tilde{W}}_{1} = [\begin{matrix} W_{1} & W_{1} \end{matrix}], {\tilde{W}}_{2} = [\begin{matrix} W_{1} & {- W}_{1} \end{matrix}] - - - (4)

As finishing among the accompanying drawing 1a, each row and its phase shifts version of matrix all are sent to antenna 1-antenna 4 respectively.Data symbol is imported into transmitter 800 at the input 822 of channel encoder 820.Channel encoder 820 coding, perforation, interweave and forms import data symbol and every an encoder output symbol S1 as even data, each encoder output symbol S2 is as odd data.Even data is passed through symbol receiver module 802a and 802b then, walsh function blocks 804a, and walsh multipliers 806a and 806b and complex adder 808a are processed.Odd data passes through symbol receiver module 802c and 802d, walsh function blocks 804b, and walsh multipliers 806c and 806d and complex adder 808b are processed.The result of complex adder 808a output is , the result of complex adder 808b output is Be imported into complex multiplier 818a then, produce

{S 1 {\tilde{W}}_{1}} e^{jφ 1}, S 2 {\tilde{W}}_{2}

Be imported into complex multiplier 818b, produce

{S 2 {\tilde{W}}_{2}} e^{jφ 2} . S 1 {\tilde{W}}_{1}

Be imported into RF transmitter 812a then, be used for emission on antenna 1,

{S 2 {\tilde{W}}_{2}} e^{jφ 2}

Be imported into RF transmitter 812b, be used for emission on antenna 2,

Be imported into transmitter 812c, be used for emission on antenna 3, and

{S 2 {\tilde{W}}_{2}} e^{jφ 2}

Be imported into RF transmitter 812d, be used for transmission on antenna 4.

Referring now to accompanying drawing 10, its shown with accompanying drawing 8 in the part block diagram of an embodiment of transmitter 800 matching used receivers 100.Transmitter 800 comprises input 1010, walsh function blocks 1002a and 1002b, walsh multipliers 1010a and 1010b,

multiplier

1004a and 1004b, multiplier 1006 and output 1008.The receiving inputted signal that receives at input 912 utilizes channel coefficients h1 ^*And h2 ^*Knowledge, use OTD demodulator 1000 by rectification.The derivation mode of explaining in the channel coefficients h1 of this OTD module and h2 and accompanying drawing 4 and the accompanying drawing is identical.OTD demodulator 1000 utilizes 1010,1010a, and b and 1012a, b and 1004a, b and 1006 is implemented.OTD rectification output 1008 is sent to rake formula combiner, deinterleaver and the channel decoding module 512 of accompanying drawing 5.

Embodiment in the accompanying drawing 1 also can use in the TDMA reflector in an EDGE system.Referring now to accompanying drawing 11, it is the part block diagram of the ST block encoding transmitter of length according to an embodiment of the invention.Transmitter 1100 comprises input 1118,1120, symbols streams is handled the input 1116a-1116d of branch, and time reversal, module 1102 and 1104, complex conjugate module 1106a and b, multiplier 1108, phase multiplier 1110a and 1110b, phase place multiplication control module 1112a and 1112b and antenna 1,2,3,4.Channel encoder 1120 coding, perforation interweaves and forms a symbols streams that receives at receiving terminal 1118.Channel encoder 1120 also is divided into the odd and even number data flow with the symbols streams of input.Even data stream is imported into input 1116a of branch and RF transmitter 1122a, be used on antenna 1, launching in first half the process of a data pulse, odd data stream is imported into input 1116c of branch and RF transmitter 1112c, is used for emission on antenna 2 in first half the cycle of this data pulse.In second of a pulse half process, even data stream is imported into the input 1116b of branch, at module 1102 time of receptions time reversal, carry out complex conjugate and be sent to RF transmitter 1122c at complex conjugate module 1106a, be used for emission on antenna 3.In second of this data pulse half process, odd data stream is imported into the input 1116d of branch, at module 1104 time of receptions time reversal, 1106b carries out complex conjugate in the complex conjugate module, multiply by a negative at multiplier 1108, be sent to RF transmitter 1122d then, emission on antenna 4.A training sequence SEQ1 is embedded in the exomonental centre of antenna 1, and a training sequence SEQ2 is embedded in the exomonental centre of antenna 2.Phase multiplier 1112a uses multiplier module 1110a and 1110b to import respectively with 1112d and moves on to RF transmitter 1122b and 1122d mutually.The output of phase multiplier 1112a is imported into RF transmitter 1112b then, emission on antenna 2, and the output of phase multiplier 1112b is imported into RF transmitter 1122d, is used for emission on antenna 4.The RF transmitter can be carried out the pulse shaping of base band, modulation, and carrier up conversion.In some equipment, can after base band shaping and modulation step, select application phase to multiply each other.

The phase place of using in

phase multiplier

1122a and 1122b is rotated in the length process of pulse and can remains unchanged, and phase place is that the basis changes with the pulse in a pulse.Phase place can the selection cycle or at random from a previous MPSK planisphere of explaining.In a preferred embodiment, the rotation of the phase place on the antenna 4 is rotated the phase shift of one 180 degree with the phase place on the antenna 2 or be multiply by and keeps identical for one-1.Phase multiplication can be carried out before base band shaping or afterwards.In an alternate embodiment of accompanying drawing 11, the emission of antenna 1 and antenna 3 can be carried out charge inside.

Transmitter shown in the accompanying drawing 3 also can be employed in the middle of the EDGE with certain change.The space-time code of describing in 316 is applied to block mode, rather than the symbol mode in EDGE equipment.Block length can be selected as pulse first half.In EDGE, half length and second half length of first of pulse equals 58 symbols.In this case, S1 and S2 represent a symbolic blocks, () ^*The time reversal and the complex conjugation operation of expression symbolic blocks.S1 ^*Expression symbolic blocks S1 has carried out time reversal and complex conjugate.-S2 ^*Expression symbolic blocks S2 has carried out sign-inverted, complex conjugate and multiply by-1.0.Pilot frequency sequence U1 and U2 can be selected as two training sequences, for example known CAZAC sequence.Diffuse code 308a, b, c, d are not applied to EDGE.Phase multiplication blocks 306a and 306b are retained.

A receiver that is 2 antenna time-space block encodings design also can use the embodiment of the receiver in accompanying drawing 1 or the accompanying drawing 2.

According to top description and embodiment, although those skilled in the art should be able to recognize what method and apparatus formula of the present invention was described with reference to certain embodiments, but be understood that for embodiment described above and can make various changes and distortion, in not deviating from as the spirit and scope of the present invention that claim limited subsequently, various embodiment of the present invention can both be implemented.

Claims

1. one kind is used for the method that transmits from a plurality of antennas, and described method comprises step:

Receive the symbols streams of a transmitter;

Carry out conversion on described incoming symbol, thereby produce a transformation results, described transformation results comprises the orthogonal space-time block encoding of a N * N ', and produces individual first signal of N ';

In time, in individual first signal of the N ' of described transformation results at least one carried out non-zero complex weighted, thereby produce at least one secondary signal, this secondary signal has phase shifts with respect to one individual first signal of N ' that produces it from it; And

Each of individual first signal of described N ' of the basic described transformation results of emission simultaneously on of first at least one antenna, each of described at least one secondary signal of emission on of second at least one antenna.

2. the method for claim 1, wherein said incoming symbol stream comprises symbol S1, S2, described space-time block coding comprises one 2 * 2 space-time block coding, and the individual signal of described N ' comprises respectively at t1, the stream (S1 of t2 emission, S2), and respectively at t1, (the S2 of t2 emission ^*, S1 ^*).

3. the method for claim 1, wherein said incoming symbol stream comprises symbol S1, S2, described space-time block coding comprises one 2 * 2 space-time block coding, the individual signal of described N ' comprises respectively at t1, stream (the S1 ,-S2 of t2 emission ^*), and respectively at t1, (S2, the S1 of t2 emission ^*).

4. the method for claim 1, wherein said first at least one antenna and described second at least one antenna comprise the individual antenna of first a plurality of N ' and second individual antenna of a plurality of N ' respectively, described incoming symbol stream comprises a traffic channel symbol stream, and wherein said method further comprises step:

Launching each of the individual common pilot channel signal of 2N ' on the individual antenna of described first a plurality of N ' of a separation or on described second the individual antenna of a plurality of N ' a separation.

5. the method for claim 1, wherein said incoming symbol stream comprise a business channels stream, and described method further comprises step:

Receive the individual common pilot channel signal of N ' at described transmitter;

In time, the individual common pilot channel signal of described N ' is carried out non-zero complex weighted, thereby produce the individual non-zero complex weighted common pilot channel signal of N ';

Each of the basic individual common pilot channel signal of the described N ' of emission simultaneously on of described first at least one antenna is at an individual non-zero complex weighted common pilot channel signal of the described N ' of emission of described second at least one antenna.

6. the method for claim 1, wherein said incoming symbol stream comprise a business channels stream, and wherein said method further comprises step:

Insert N ' after in individual first signal of the described N ' of described transformation results one thus each of individual pilot signal produces individual first signal of N ' of the pilot signal that comprises insertion;

Wherein said non-zero complex weighted step comprise in time each of individual first signal of N ' of the described pilot signal that comprises insertion is carried out non-zero complex weighted, thereby produce the individual secondary signal of N ' of the pilot signal that comprises insertion; And

Wherein said step of transmitting is included in each of one of first at least one antenna individual first signal of described N ' of going up the pilot signal that basic emission simultaneously comprises insertion, each of the individual secondary signal of N ' of the described pilot signal that comprises insertion of emission on of second at least one antenna.

7. the method for claim 1, wherein said non-zero complex weighted step comprise uses a continuous analogue phase scanning to carry out phase shifts to one in individual first signal of described N '.

8. the method for claim 1, wherein said non-zero complex weighted step comprises the predetermined jump sequence of a phase shifts in individual first signal of described N '.

9. method as claimed in claim 8, wherein the jump weighting to described predetermined jump sequence is to derive to come out from the PSK planisphere with Z condition, and wherein all states all utilize identical frequency to sample in a frame emission.

10. method as claimed in claim 8, wherein the jump weighting to described predetermined jump sequence is to derive to come out from the PSK planisphere with Z condition.

11. the method for claim 1, wherein said space-time block coding comprise 2 * 2STS block encoding, and individual first signal of described N ' is included in the stream (S1W1-S2 that t1 transmits ^*W2) and the stream (S2W1+S1 that transmits at time t1 ^*W2), wherein W1 and W2 are continuous series connection of at least two walsh codes.

12. the method for claim 1, wherein said space-time block coding comprise 2 * 2STS block encoding, and individual first signal of described N ' is included in the stream (S1W1+S2W2) that t1 transmits, at the stream (S2 of time t1 emission ^*W1+S1 ^*W2), wherein W1 and W2 are continuous series connection of at least two walsh codes.

13. a device that is used to launch a signal, described transmitter comprises:

An incoming symbol stream;

A processor produces a transformation results thereby be used for carrying out conversion on described incoming symbol stream, and described transformation results comprises the orthogonal space-time block encoding of a N * N ', and produces individual first signal of N ';

At least one weighter, carry out non-zero complex weighted in individual first signal of the N ' of described transformation results at least one in time, thereby produce a secondary signal, each of described at least one second weighted signal has phase shifts with respect to one individual first signal of N ' that produces it from it, and;

A transmitter is used on of first at least one antenna individual first signal of described N ' of basic each described transformation results of emission simultaneously, the individual secondary signal of each described N ' of emission on of second at least one antenna.

14. device as claimed in claim 13, wherein said incoming symbol stream comprises symbol S1, S2, described space-time block coding comprises one 2 * 2 space-time block coding, and individual first signal of described N ' comprises respectively at t1, the stream (S1 of t2 emission, S2), and respectively at t1, (the S2 of t2 emission ^*, S1 ^*).

15. device as claimed in claim 13, wherein said incoming symbol stream comprises symbol S1, S2, and described space-time block coding comprises one 2 * 2 space-time block coding, the individual signal of described N ' comprises respectively at t1, stream (the S1 ,-S2 of t2 emission ^*), and respectively at t1, (S2, the S1 of t2 emission ^*).

16. method as claimed in claim 13, wherein said first at least one antenna and described second at least one antenna comprise the individual antenna of first a plurality of N ' and second individual antenna of a plurality of N ' respectively, described incoming symbol stream comprises a traffic channel symbol stream, and wherein said transmitter further comprises:

At least one input is used for receiving the individual common pilot channel of N ' on described transmitter;

A weighter, described non-zero complex weighted device are used in time the individual common pilot channel signal of each described N ' being carried out non-zero complex weighted, thereby produce the individual non-zero complex weighted common pilot channel signal of N '; And

Wherein said transmitter further is included in the individual common pilot channel signal of each described N ' of emission on the separate antenna of described first at least one antenna, the individual non-zero complex weighted common pilot channel signal of each described N ' of emission on a separate antenna of described second at least one antenna.

17. device as claimed in claim 13, wherein said incoming symbol stream comprise a business channels stream, wherein said device further comprises:

A multiplexer is used for inserting each N ' after of individual first signal of the described N ' of described transformation results thereby individual pilot signal produces individual first signal of N ' of the pilot signal that comprises insertion;

At least one weighter, be used in time to described each to comprise that the individual signal of described N ' of the pilot signal of insertion carries out non-zero complex weighted, thereby produce the individual secondary signal of N ' of the pilot signal that comprises insertion; And

Wherein said transmitter is included in each described individual first signal of described N ' that comprises the pilot signal of insertion of emission of going up the basic while of first at least one antenna, each described individual secondary signal of N ' that comprises the pilot signal of insertion of emission on of second at least one antenna.

18. device as claimed in claim 13, wherein said at least one weighter phase place use continuous analogue phase scanning each in the individual signal of at least one described N ' to move.

19. device as claimed in claim 13, wherein said at least one weighter phase place uses a predetermined jump sequence to move at individual first signal of described N '.

20. device as claimed in claim 19 is to come out from the derivation of PSK planisphere by the random permutation according to possible Z state of the continuous time slot that is used for frame emission to the jump weighting of described predetermined jump sequence wherein.

21. device as claimed in claim 13, wherein said space-time block coding comprise 2 * 2STS block encoding, and individual first signal of described N ' is included in the stream (S1W1-S2 of t1 emission ^*W2) with at the stream (S2W1+S1 of time t1 emission ^*W2), wherein W1 and W2 are continuous series connection of at least two walsh codes.

22. device as claimed in claim 13, wherein said space-time block coding comprise 2 * 2STS block encoding, and individual first signal of described N ' is included in the stream (S1W1+S2W2) of t1 emission, at the stream (S2 of time t1 emission ^*W1+S1 ^*W2), wherein W1 and W2 are continuous series connection of at least two walsh codes.

23, a kind of being used for from the method for a signal of a plurality of antenna emissions, described method comprises step:

Receive the symbols streams of a transmitter;

Thereby carry out a conversion and produce a transformation results on described incoming symbol stream, described transformation results comprises the orthogonal space-time block encoding of a N * N ', and produces individual first signal of N ';

In time, carry out non-zero complex weighted in individual first signal of the N ' of described transformation results at least one, thereby produce at least one secondary signal, each described at least one secondary signal has been carried out phase shifts with respect to one individual first signal of N ' that produces it from it, and move the phase place of a predetermined jump sequence on wherein said non-zero complex weighted at least one that is included in individual first signal of described N ', wherein the jump weighting to described predetermined jump sequence is to derive from a PSK planisphere with 8 states, and wherein the angle of Yu Ding jump sequence is (0,135,270,45,180,315,90,225); And

Individual first signal of described N ' of basic each described transformation results of emission simultaneously on of first at least one antenna, each described at least one secondary signal of emission on of second at least one antenna.

24. be used to launch the device of a signal in one, described transmitter comprises:

An incoming symbol stream;

A processor produces a transformation results thereby be used for carrying out a conversion on described incoming symbol stream, and described transformation results comprises the orthogonal space-time block encoding of a N * N ', and produces individual first signal of N ';

At least one weighter, be used in time, carry out non-zero complex weighted in individual first signal of the N ' of described transformation results at least one, thereby produce at least one secondary signal, each described at least one secondary signal has been carried out phase shifts with respect to one in individual first signal of N ' that produces it, and wherein said non-zero complex weighted at least one that is included in individual first signal of described N ' moves the phase place of a predetermined jump sequence, wherein the jump weighting to described predetermined jump sequence is to derive from a PSK planisphere with 8 states, and wherein the angle of Yu Ding jump sequence is (0,135,270,45,180,315,90,225); And

A transmitter, individual first signal of described N ' that is used for basic each described transformation results of emission simultaneously on of first at least one antenna, each described at least one secondary signal of emission on of second at least one antenna.