CN1592058A - Difference sum dc-dc converter and method thereof - Google Patents
Difference sum dc-dc converter and method thereof Download PDFInfo
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- CN1592058A CN1592058A CN 03156452 CN03156452A CN1592058A CN 1592058 A CN1592058 A CN 1592058A CN 03156452 CN03156452 CN 03156452 CN 03156452 A CN03156452 A CN 03156452A CN 1592058 A CN1592058 A CN 1592058A
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Abstract
A delta-sigma DC-DC converter and its method includes an output stage, a sensing circuit, a conduction amplifier, a charge/discharge circuit and a driver, among which, the output stage is connected between an input voltage and a low voltage to be controlled and switched to generate an output voltage, the sensing circuit senses the output voltage to generate a feedback signal to be compared with a reference voltage by said conduction amplifier to generate a current different value to the said charge/discharge circuit, the said driver compares the first and second reference signals with the charged voltage provided by the charge/discharge circuit to generate a driving signal to be provided to the output stage.
Description
Technical field
The present invention be relevant a kind of direct current to direct current transducer and method thereof, particularly about a kind of difference and (Delta-sigma can be expressed as delta sigma) direct current to direct current transducer and method thereof.
Background technology
Direct current has been widely used in various electronic products to direct current transducer, its role is to the direct voltage of input is done the adjusting of voltage quasi position, for example boosts or step-down, and makes it to be stabilized between the voltage value that sets.In computer system, because CPU, internal memory and the employed power supply of hard disk are inequality, therefore need direct current that direct current transducer is regulated different voltages, so that being provided, uses each operating unit in the computer system.
Traditional direct current is the work period of adjusting an output stage with a drive signal to direct current transducer, and output voltage is maintained under the certain limit.Traditional direct current is to produce a feedback signal by the detecting output voltage to direct current transducer, and by an error amplifier relatively this feedback signal and a reference signal to produce an error signal, again by a pulse-width modulation (PWM) comparator relatively this error signal and a sawtooth signal to produce a pwm signal, by a driver drives output stage.In this type of transducer, use a saw-toothed oscillator to produce the accurate position of a sawtooth signal as a pulse-width modulation (PWM) comparator, adjust the work period of this output stage.
The present invention proposes a kind of direct current of different operating principle that uses to direct current transducer and method thereof.
Summary of the invention
One of purpose of the present invention is to propose a kind of difference and direct current to direct current transducer, and it does not use PWM comparator and sawtooth generator, but utilizes charge-discharge principle to regulate transducer.
According to one embodiment of present invention, a kind of Delta-sigma direct current comprises that to direct current transducer an output stage is connected between an input voltage and the low pressure, and controlled switching is to produce an output voltage; This output voltage of one sensing circuit senses produces a feedback signal; One conduction amplifier comparison, one reference signal and this feedback signal produce an electric current residual quantity; One charge-discharge circuit connects this electric current and produces a charging voltage; And one driver relatively this charging voltage and first and second reference signal produce a drive signal with this work period and give this output stage.
The method that the present invention uses is: mainly comprise the following steps:
Switch an output stage that is connected between an input voltage and the low pressure, to produce an output voltage;
This output voltage of sensing is to produce a feedback signal;
Relatively this feedback signal and a reference voltage are to produce an electric current residual quantity;
Connect this electric current residual quantity to a charging circuit, to produce a charging voltage;
And relatively this charging voltage and first and second reference signal are given this output stage to produce a drive signal.
Description of drawings
Fig. 1 is the circuit diagram of Delta-sigma direct current of the present invention to direct current transducer;
Figure 2 shows that the circuit diagram of the conduction amplifier among Fig. 1;
Fig. 3 is three kinds of operator schemes of the present invention oscillograms of moment when load loads.
The figure number explanation
10 Delta-sigma direct currents are to direct current transducer 12 low-pressure side nmos pass transistors
14 high-pressure side nmos pass transistors, 16 inductance
18 converter output ends, 20 SR flip-flops
22 resistance, 24 resistance
The anti-phase input of 26 conduction amplifier 26a
The noninverting input of 26b 26c output
28 current sources, 30 current sources
32 electric capacity, 34 comparators
The noninverting input of the anti-phase input of 34a 34b
34c exports 36 comparators
The noninverting input of the anti-phase defeated 36b of 36a
36c exports 38 switches
40 switches, 42 PMOS transistors
44 PMOS transistors, 46 PMOS transistors
48 PMOS transistors, 50 nmos pass transistors
52 nmos pass transistors, 54 nmos pass transistors
56 nmos pass transistors, 58 current sources
Embodiment
Fig. 1 is the circuit diagram of Delta-sigma direct current of the present invention to direct current transducer 10.One output stage is made up of a low-pressure side nmos pass transistor 12 and a high-pressure side nmos pass transistor 14, the source electrode of low-pressure side nmos pass transistor 12 is connected to an earth terminal GND, drain is connected to converter output end 18 via inductance 16, the source electrode of high-pressure side nmos pass transistor 14 is connected to output 18 via inductance 16, and drain is connected to an input supply voltage V
INThe gate of low-pressure side nmos pass transistor 12 and high-pressure side nmos pass transistor 14 is connected respectively to the complementary output Q and the Q of a SR flip-flop 20, switch to be controlled by drive signal LG and HG, the work period of SR flip-flop 20 control high and low pressure side nmos pass transistors 14,12, produce output current I
OUTThe inductance 16 of flowing through, and produce output voltage V at converter output end 18
OUTOne resistance 22 and the 24 voltage divider sensing output voltage V of forming
OUT, to produce feedback signal VFB.One conduction amplifier 26 has an anti-phase input 26a connection feedback signal VFB and is connected a reference voltage V with a noninverting input 26b
REF, conduction amplifier 26 is feedback signal VFB and reference voltage V relatively
REFAnd produce an electric current residual quantity I at output 26c
GMIn the charge-discharge circuit of current source 28,30 and an electric capacity 32 compositions, by electric current residual quantity I
GMThe charging current I that provides with current source 28 and 30
C, to produce a charging voltage V
C, current source 28 has an electric current I
1, current source 30 has an electric current I
2, charging current I
CWith electric current I
2And equal electric current I
1And electric current residual quantity I
GMAnd, promptly
I
C+I
2＝I
1+I
GM (EQ-1)。According to mathematical expression EQ-1, can be by Control current I
1And I
2And electric current residual quantity I
GMAnd change charging current I
CSize.Comparator 34 and 36 and the driver formed of SR flip-flop 20 produce drive signal HG and the LG that switches high and low pressure side nmos pass transistor 14,12.Comparator 34 has an anti-phase input 34a and connects a reference voltage V
REF1Be connected charging voltage V with a noninverting input 34b
C, comparator 34 comparison reference voltage V
REF1And charging voltage V
C, 34c produces one first comparison signal in output, and it is a high or low accurate position voltage.Comparator 36 has an anti-phase input 36a and connects charging voltage V
CBe connected reference voltage V with a noninverting input 36b
REF2, comparator 36 comparison reference voltage V
REF2And charging voltage V
C, 36c produces one second comparison signal in output, and it is a high or low accurate position voltage.SR flip-flop 20 has two input S and R connects first and second comparison signal respectively, when first or second comparison signal is high levle, output HG produces high levle voltage and output LG produces low level voltage, to open high-pressure side nmos pass transistor 14, otherwise, when first or second comparison signal is low level, output drive signal LG produces high levle voltage, to open low-pressure side nmos pass transistor 12, by the work period of drive signal HG and LG control high and low pressure side nmos pass transistor 14,12.
The Delta-sigma direct current more comprises switch 38 and 40 to direct current transducer 10, and switch 38 is connected between current source 28 and the output 26c, and switch 40 is connected between output 26c and the current source 30, drive signal LG control switch 38 and 40 unlatching or close.When output LG produces high levle voltage, switch 38 unlatchings and switch 40 are closed so that charging current I to be provided
CFlows into capacitor 32 promotes charging voltage V
C, when output LG produces low level voltage, switch 38 cuts out and switch 40 is opened so that charging current I
CFlow out electric capacity 32 and reduce charging voltage V
C
The Delta-sigma direct current has three kinds of operator schemes to direct current transducer 10, and it is to be set by conduction amplifier 26.Under the Delta-sigma pattern, electric current residual quantity I
GMBe to flow into amplifier 26, promptly 26 in amplifier has suction electric current (sinking) ability, when the load current instantaneous variation, by feedback signal VFB and reference voltage V
REFDifference adjust work period of high and low pressure side nmos pass transistor 14 and 12.Under magnetic hysteresis (hysteresis) pattern, electric current residual quantity I
GMCan flow into amplifier 26 or flow out from amplifier 26, promptly amplifier 26 has the electric current of suction and output current (sourcing) ability simultaneously, makes output voltage V
OUTBe adjusted under the scope.Under peak valley (valley) pattern, electric current residual quantity I
GMBe to flow out from amplifier 26, promptly amplifier 26 has the output current ability, makes output voltage V
OUTMaintain on the accurate position of a low pressure.
According to mathematical expression EQ-1, under three kinds of operator schemes, electric current residual quantity I
GMVary in size, influence charging current I
CSize also inequality.Under the Delta-sigma pattern, amplifier 26 has the suction current capacity, makes electric current I
1Charging current I need be provided
C, electric current I
2And electric current residual quantity I
GM, therefore, mathematical expression EQ-1 is revised as under the Delta-sigma pattern
I
C+I
2+I
GM＝I
1 (EQ-2)。Under the magnetic hysteresis pattern, amplifier 26 has the electric current of suction and output current ability simultaneously, so electric current residual quantity I among the mathematical expression EQ-1
GMChange charging current I according to sucking electric current or output current
CAnd under the peak valley pattern, amplifier 26 has the output current ability, electric current residual quantity I
GMAnd electric current I
1Charging current I is provided
CAnd electric current I
2, therefore, according to mathematical expression EQ-1 control charging current I
C
Delta-sigma direct current of the present invention is to direct current transducer 10, its current source 28 and 30 electric current I that provide
1And I
2Be according to input and output voltage V
INAnd V
OUTProportion relation.
Figure 2 shows that the circuit diagram of conduction amplifier 26 among Fig. 1, it comprises PMOS transistor 42,44,46,48 and nmos pass transistor 50,52,54,56 and current source 58, the source electrode of PMOS transistor 42 connects the source electrode of PMOS transistor 48, the drain of PMOS transistor 42 connects the drain and the gate of nmos pass transistor 54, the drain of PMOS transistor 48 connects the drain and the gate of nmos pass transistor 56, the source electrode of PMOS transistor 44 connects the source electrode of PMOS transistor 46, the gate of PMOS transistor 44 is connected the gate of PMOS transistor 46 with drain, the drain of PMOS transistor 44 connects the drain of nmos pass transistor 50, the drain of PMOS transistor 46 connects the drain of nmos pass transistor 52, the gate of nmos pass transistor 50 connects the gate of nmos pass transistor 54, the gate of nmos pass transistor 52 connects the gate of nmos pass transistor 56, nmos pass transistor 50,52,54 and 56 source electrode connects earth terminal, current source 58 is between the source electrode of the source electrode of PMOS transistor 44 and PMOS transistor 42, the gate of PMOS transistor 42 connects feedback signal VFB, and the gate of PMOS transistor 48 connects reference voltage V
REF, the drain of PMOS transistor 46 and nmos pass transistor 52 connects electric capacity 32.Transducer 10 has three kinds of operator schemes, and it is Delta-sigma pattern, magnetic hysteresis pattern and peak valley pattern, and these three kinds of operator schemes are 26 decisions of design conduction amplifier.Shown in Figure 2 is that transducer 10 is used in the conduction amplifier 26 under the magnetic hysteresis pattern, as reference voltage V
REFGreater than feedback signal VFB, 46 conductings of PMOS transistor also produce electric current residual quantity I
GMTo electric capacity 32, electric current residual quantity I
GMFlow to electric capacity 32, have the output current ability, as reference voltage V
REFLess than feedback signal VFB, nmos pass transistor 52 conductings also suck electric current residual quantity I
GMTo conduction amplifier 26.Therefore, under the magnetic hysteresis pattern, conduction amplifier 26 has output current and sucks the ability of electric current.Under the Delta-sigma pattern, conduction amplifier 26 does not have PMOS transistor 46, so 26 of conduction amplifier have the ability that sucks electric current.Under the peak valley pattern, conduction amplifier 26 does not have nmos pass transistor 52, so 26 abilities with output current of conduction amplifier.
Fig. 3 is that the circuit of Fig. 1 is in the oscillogram during in the load current instantaneous variation under three kinds of operator schemes.Under the Delta-sigma pattern, output current I
OUTMoment rises, and causes output voltage V when time T 1
OUTHurriedly fall, the Delta-sigma direct current is to the work period of direct current transducer 10 adjustment high and low pressure side MOS transistor 14,12, conduction amplifier 26 comparison reference voltage V when descending according to output voltage
REFBecome big with the difference of feedback signal VFB, make the suction current capacity of conduction amplifier 26 strengthen the electric current I that current source 28 is provided
1Be electric current residual quantity I
GMWith charging current I
CAnd, therefore, flow to the charging current I of electric capacity 32
CDescend, cause charging voltage V
CDescend, and then make first and second comparison signal time of first and second comparator 34 and 36 outputs elongated, so the work period increasing, otherwise then the work period diminishes.Along with reference voltage V
REFBigger with the difference of feedback signal VFB, make that the work period of high-pressure side MOS transistor 14 is bigger, otherwise, reference voltage V
REFLittler with the difference of feedback signal VFB, then the work period of high-pressure side MOS transistor 14 littler, therefore, under the Delta-sigma pattern, the work period of high and low pressure side nmos pass transistor 14,12 is in response to reference voltage V
REFAdjust with the difference of feedback signal VFB, in order to do output voltage is maintained in the scope.
Under the magnetic hysteresis pattern, output current I
OUTMoment rises, output voltage V when time T 1
OUTHurriedly fall, because conduction amplifier 26 has output current simultaneously and suck the ability of electric current, so the Delta-sigma direct current will maintain standard-sized sheet to direct current transducer 10 work period, make output voltage V
OUTMaintain a ceiling voltage V
MAXAn and minimum voltage V
MINBetween.In output voltage V
OUTLess than minimum voltage V
MINThe time, conduction amplifier 26 provides the ability of output current, in order to do making charging voltage V
CRising is ordered about output voltage V to increase the work period of high-pressure side nmos pass transistor 14
OUTRise to minimum voltage V
MINMore than, otherwise, output voltage V
OUTGreater than ceiling voltage V
MAXThe time, conduction amplifier 26 provides the ability that sucks electric current, in order to do making charging voltage V
CDecline makes output voltage V to reduce the work period of high-pressure side nmos pass transistor 14
OUTDrop to ceiling voltage V
MAXBelow.
Under the peak valley pattern, be to make output voltage V
OUTBe not less than minimum voltage V
MIN, this pattern is at output current I
OUTMoment is when rising, in time T 1 output voltage V
OUTHurriedly fall, it produces feedback signal VFB by resistance 22 and 24 sensings, and conduction amplifier 26 has the ability of output current, and under the load current instantaneous variation, conduction amplifier 26 is output voltage V relatively
OUTAnd feedback signal VFB makes the electric current residual quantity I of output 26c generation
GMIncrease, order about charging voltage V
CRise,, make output voltage V so that the SR flip-flop provides a drive signal of opening high-pressure side nmos pass transistor 14
OUTRise.
The present invention be to use charge-discharge circuit and general conduction amplifier with control output voltage within certain scope, and known direct current is to use pulse-width modulation (PWM) comparator and adjusts output voltage within certain scope, both operating principle differences with sawtooth waveforms accurate position as a comparison direct current transducer.
More than the narration done for preferred embodiment of the present invention be purpose for illustrating, accurately be disclosed form and be not intended to limit the present invention, based on above instruction or to make an amendment or change from embodiments of the invention study be possible, embodiment has the knack of this operator and utilizes the present invention to select in practical application with various embodiment and narrate for explaining orally principle of the present invention and allowing, and technological thought attempt of the present invention is decided by following claim and equalization thereof.
Claims (11)
1. a Delta-sigma direct current is characterized in that direct current transducer, comprising:
One output stage is connected between an input voltage and the low pressure, and controlled switching is to produce an output voltage;
One sensing circuit produces a feedback signal with this output voltage of sensing;
One conduction amplifier is so that relatively a reference voltage and this feedback signal produce an electric current residual quantity;
One charge-discharge circuit connects this electric current residual quantity and produces a charging voltage;
And a driver, produce a drive signal with relatively this charging voltage and first and second reference signal and give this output stage.
2. transducer as claimed in claim 1 is characterized in that, this charge-discharge circuit comprises:
One first current source between a high pressure and a node is controlled by this drive signal;
One second current source between this node and a low pressure is controlled by this drive signal;
And an electric capacity, connect this node, to produce this charging voltage.
3. transducer as claimed in claim 1 is characterized in that, this driver comprises:
One first comparator is so that relatively this first reference signal and this charging voltage produce one first comparison signal;
One second comparator is so that relatively this second reference signal and this charging voltage produce one second comparison signal;
And a flip-flop, to produce this drive signal in response to this first and second comparison signal.
4. transducer as claimed in claim 1 is characterized in that, this electric current residual quantity flows to this conduction amplifier under the Delta-sigma pattern.
5. transducer as claimed in claim 1 is characterized in that, this electric current residual quantity flows to this conduction amplifier or flows out from this conduction amplifier under the magnetic hysteresis pattern.
6. transducer as claimed in claim 1 is characterized in that, this electric current residual quantity flows out from this conduction amplifier under the peak valley pattern.
7. transducer as claimed in claim 2 is characterized in that the ratio of this first and second current source is proportional to the ratio of this input and output voltage.
8. transducer as claimed in claim 3 is characterized in that, this flip-flop comprises a SR flip-flop.
9. a direct current is characterized in that DC voltage transforming method, comprises the following steps:
Switch an output stage that is connected between an input voltage and the low pressure, to produce an output voltage;
This output voltage of sensing is to produce a feedback signal;
Relatively this feedback signal and a reference voltage are to produce an electric current residual quantity;
Connect this electric current residual quantity to a charging circuit, to produce a charging voltage;
And relatively this charging voltage and first and second reference signal are given this output stage to produce a drive signal.
10. method as claimed in claim 9 is characterized in that the step that produces this charging voltage comprises the following steps:
By this electric current residual quantity to a capacitor charge and discharge;
Switch one first electric current by this drive signal and be connected to this electric capacity;
And switch and draw one second electric current from this electric capacity by this drive signal.
11. method as claimed in claim 9 is characterized in that, relatively the step of this charging voltage and this first and second reference signal comprises the following steps:
Relatively this first reference signal and this charging voltage are to produce one first comparison signal;
Relatively this second reference signal and this charging voltage are to produce one second comparison signal;
And, produce this drive signal in response to this first and second comparison signal.
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CNB031564526A CN100431249C (en) | 2003-08-28 | 2003-08-28 | Difference sum dc-dc converter and method thereof |
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CNB031564526A CN100431249C (en) | 2003-08-28 | 2003-08-28 | Difference sum dc-dc converter and method thereof |
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| Publication Number | Publication Date |
|---|---|
| CN1592058A true CN1592058A (en) | 2005-03-09 |
| CN100431249C CN100431249C (en) | 2008-11-05 |
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| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CNB031564526A Expired - Fee Related CN100431249C (en) | 2003-08-28 | 2003-08-28 | Difference sum dc-dc converter and method thereof |
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Cited By (9)
| Publication number | Priority date | Publication date | Assignee | Title |
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| CN101018014B (en) * | 2005-11-29 | 2010-12-15 | 株式会社理光 | Compact voltage step-up/step-down switching regulator |
| CN101213460B (en) * | 2005-05-04 | 2011-08-31 | Nxp股份有限公司 | A peak or zero current comparator |
| CN101548456B (en) * | 2007-07-27 | 2012-07-11 | 株式会社理光 | Switching regulator and method for controlling operation thereof |
| CN107493018A (en) * | 2016-06-10 | 2017-12-19 | 半导体元件工业有限责任公司 | Automatic tuning current limiter |
| CN108173414A (en) * | 2017-12-29 | 2018-06-15 | 成都芯源***有限公司 | Multiphase converter and load current transient rise detection method thereof |
| CN108169658A (en) * | 2017-12-14 | 2018-06-15 | 上海华虹宏力半导体制造有限公司 | The output current test circuit and test method of device blocks |
| CN115696689A (en) * | 2022-11-17 | 2023-02-03 | 中船重工安谱（湖北）仪器有限公司 | Light source driving system and method of fluorescent polymer detector |
| CN117093047A (en) * | 2023-08-30 | 2023-11-21 | 合芯科技(苏州)有限公司 | Acceleration voltage stabilizing circuit, low-dropout linear voltage stabilizer and electronic product |
| CN117093047B (en) * | 2023-08-30 | 2024-08-30 | 合芯科技(苏州)有限公司 | Acceleration voltage stabilizing circuit, low-dropout linear voltage stabilizer and electronic product |
Family Cites Families (3)
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| US6246220B1 (en) * | 1999-09-01 | 2001-06-12 | Intersil Corporation | Synchronous-rectified DC to DC converter with improved current sensing |
| JP4314709B2 (en) * | 1999-12-28 | 2009-08-19 | ソニー株式会社 | Switching power supply |
| JP3572292B2 (en) * | 2002-01-29 | 2004-09-29 | 松下電器産業株式会社 | Switching power supply circuit |
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- 2003-08-28 CN CNB031564526A patent/CN100431249C/en not_active Expired - Fee Related
Cited By (11)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101213460B (en) * | 2005-05-04 | 2011-08-31 | Nxp股份有限公司 | A peak or zero current comparator |
| CN101018014B (en) * | 2005-11-29 | 2010-12-15 | 株式会社理光 | Compact voltage step-up/step-down switching regulator |
| CN101548456B (en) * | 2007-07-27 | 2012-07-11 | 株式会社理光 | Switching regulator and method for controlling operation thereof |
| CN107493018A (en) * | 2016-06-10 | 2017-12-19 | 半导体元件工业有限责任公司 | Automatic tuning current limiter |
| CN108169658A (en) * | 2017-12-14 | 2018-06-15 | 上海华虹宏力半导体制造有限公司 | The output current test circuit and test method of device blocks |
| CN108173414A (en) * | 2017-12-29 | 2018-06-15 | 成都芯源***有限公司 | Multiphase converter and load current transient rise detection method thereof |
| CN108173414B (en) * | 2017-12-29 | 2020-04-21 | 成都芯源***有限公司 | Multiphase converter and load current transient rise detection method thereof |
| CN115696689A (en) * | 2022-11-17 | 2023-02-03 | 中船重工安谱（湖北）仪器有限公司 | Light source driving system and method of fluorescent polymer detector |
| CN115696689B (en) * | 2022-11-17 | 2023-11-21 | 中船重工安谱（湖北）仪器有限公司 | Light source driving system and method for fluorescent polymer detector |
| CN117093047A (en) * | 2023-08-30 | 2023-11-21 | 合芯科技(苏州)有限公司 | Acceleration voltage stabilizing circuit, low-dropout linear voltage stabilizer and electronic product |
| CN117093047B (en) * | 2023-08-30 | 2024-08-30 | 合芯科技(苏州)有限公司 | Acceleration voltage stabilizing circuit, low-dropout linear voltage stabilizer and electronic product |
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| Publication number | Publication date |
|---|---|
| CN100431249C (en) | 2008-11-05 |
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