CN1520082A - Synchronization method of carrier frequency and communication equipment in digital communication system - Google Patents

Synchronization method of carrier frequency and communication equipment in digital communication system Download PDF

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CN1520082A
CN1520082A CNA031151094A CN03115109A CN1520082A CN 1520082 A CN1520082 A CN 1520082A CN A031151094 A CNA031151094 A CN A031151094A CN 03115109 A CN03115109 A CN 03115109A CN 1520082 A CN1520082 A CN 1520082A
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training symbol
communication system
signal
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CN1317843C (en
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黎光洁
陶云南
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Nokia Shanghai Bell Co Ltd
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Alcatel Lucent Shanghai Bell Co Ltd
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Abstract

At sending end, training symbols are inserted into every other section of digital modulated communication signals and then the signals are sent. The training symbols are composed of special impulse function sequence in frequency domain. At receiving end, FFT transforms received training symbols to frequency domain. In frequency domain, after training symbols are multiplied by conjugate symbols of the training symbols, result is divided into multiple sections with identical length, then corresponding weight factors are assigned to each section, and multiple sections are superimposed as one section. Chirp-Z transform and interpolation operation are carried out for the data in the one section so as to obtain position of maximum amplitude. Frequency shift is evaluated from formula fe=fs(omega-K/2) based on position of maximum amplitude. fe controls oscillation frequency of oscillator to reach frequency synchronism.

Description

Carrier frequency Synchronizing method and communicator in the digital communication system
Technical field
The present invention relates to digital communication system, be specifically related to the carrier frequency Synchronizing method in this system and implement the transmitter and receiver of this method.
Background technology
In digital communication system, the carrier shift that the frequency deviation of the local oscillator of transmitter or receiver or Doppler effect cause can cause communication quality to descend.Especially in OFDM (OFDM) communication system, quite responsive to frequency shift (FS), if do not carry out Frequency Synchronization, ofdm communication system can't be communicated by letter.For head it off, Frequency Synchronization is crucial, the most frequently usedly in the scheme of existing Frequency Synchronization be, the transmitter of communicator at one end, send two identical training symbols in company with signal of communication, then at the receiver of other end communicator, the phase difference by two training symbols relatively successively sending estimates frequency shift (FS).After estimating frequency shift (FS), by loop filter, go control generator to adjust the frequency of local carrier then, frequency deviation information so that allow local carrier frequency and transmitting terminal carrier frequency synchronization.The shortcoming that this technical scheme exists is to need two identical training symbols, and overhead is bigger, and adopts the precision of general difference method low.
Summary of the invention
The present invention is in order to address the above problem, and its purpose is to provide that a kind of overhead is little, precision is high, the effective method of carrier frequency synchronization and implement the transmitter and receiver of this method in the digital communication system of contrary frequency selectivity influence of fading.
A further object of the present invention provides the transmitter and receiver of method and this method of enforcement of carrier frequency synchronization in the little digital communication system of a kind of frequency offset estimation overhead.
A further object of the present invention provides the method for the high carrier frequency synchronization of the low precision of a kind of computation complexity and the transmitter and receiver of this method of enforcement.
The method of carrier frequency synchronization comprises following steps in the digital communication system of the present invention:
A: at transmitting terminal, the signal of communication after piece of digital modulation inserts training symbol and is sent, and this training symbol is made of impulse function sequence at interval in frequency domain;
B: at receiving terminal, from the signal that receives, extract training symbol, the training symbol that receives is transformed to frequency domain by fast fourier transform;
C: after the described training symbol in the described frequency domain be multiply by the conjugate of symbol of training symbol, be divided into the multistage of equal length, give corresponding weighting factor to every section, described multistage is superposed to one section;
D: the data in described a section are done Chirp-Z conversion and interpolation arithmetic, obtain the maximum amplitude position;
E: by the maximum amplitude position according to equation fe = fs ( Ω Λ - K / 2 ) / N Estimate frequency shift (FS), wherein, fe is frequency shift (FS), and fs is a sample frequency, and K is the number of data points in described section, and N is the length of training symbol correspondence, Position for maximum amplitude;
F: the frequency shift (FS) that utilizes the e step to obtain, the frequency of oscillation of control high-frequency generator makes the frequency of oscillation of high-frequency generator follow described frequency shift (FS) variation, reaches carrier frequency synchronization.
Transmitter in the digital communication system of the present invention comprises signal of communication is carried out the digital modulator of digital modulation and the wireless front end that the signal of communication after the modulation is sent, and it is characterized in that described transmitter also comprises:
Produce the training symbol generation device of the training symbol of the middle shock insulation sequence of function formation of frequency domain; With
Be connected the signal of communication after one section modulation between described digital modulator and the described wireless front end and insert the multiple devices of described training symbol.
Receiver in the digital communication system of the present invention, comprise the low-converter that carries out down-conversion to received signal, signal after the frequency conversion is carried out regularly synchronous timing synchronizer, produce the high-frequency generator that the higher-order of oscillation is used for described low-converter frequency conversion, it is characterized in that, also comprise:
From the signal that include training symbol related, extract the training symbol extraction element of training symbol with received signal;
Described training symbol is transformed to the fast fourier transformation apparatus of frequency domain;
With the described training symbol in the frequency domain be divided into equal length multistage, every section is given corresponding weighting factor, described multistage is superimposed as one section weighted superposition device;
To the described one section maximum amplitude location computing device that carries out Chirp-Z conversion and interpolation, acquisition maximum amplitude position after the weighted superposition;
Utilize the maximum amplitude position according to equation fe = fs ( Ω Λ - K / 2 ) / N Estimate the frequency offset estimation device of frequency shift (FS), this frequency offset estimation device output frequency skew, the frequency of oscillation of control high-frequency generator makes the frequency of oscillation of high-frequency generator follow this frequency shift (FS) variation, reaches carrier frequency synchronization, in the formula, fe is frequency shift (FS), and fs is a sample frequency, and K is the number of data points in described section, N is the length of training symbol
Figure A0311510900064
Position for maximum amplitude.
As above the inventive method of Gou Chenging and communicator have that expense is little, the precision advantages of higher.In addition, can also be advantageously used in channel estimating, regularly synchronous, computation complexity is also relatively low.
Brief Description Of Drawings
Fig. 1 illustrates the part-structure schematic diagram of the transmitter and receiver of one embodiment of the invention.
Embodiment
Describe preferred embodiment of the present invention in detail below in conjunction with accompanying drawing.
Referring to Fig. 1, dotted line the first half illustrates the part-structure figure of communicator transmitter in the digital communication system of one embodiment of the invention among Fig. 1, and improvement structure division of the present invention and its part that is associated with prior art only are shown here.Other part of transmitter belongs to prior art, thereby omits its diagram and explanation.This transmitter comprises signal of communication is carried out the digital modulator 1 of digital modulation and to the wireless front end 4 that sends of signal of communication after the modulation, they belong to prior art.The invention is characterized in, also comprise the training symbol generation device 3 that produces the training symbol that the shock insulation sequence of function constitutes in the middle of the frequency domain and be connected digital modulator 1 with wireless front end 4 between, every the multiple devices 2 of one section signal of communication insertion training symbol after digital modulator 1 modulation.
This digital communication system can be an orthogonal FDM communication system, and digital modulation is the OFDM modulation, and described " every one section signal of communication after digital modulator 1 modulation " is one or several OFDM symbols.
In one embodiment, the shock insulation sequence of function is by impulse function in every section in the middle of the frequency domain of above-mentioned training symbol, and the M section is formed altogether, 1≤M≤N, and N is for sending the sub-carrier number that signal of communication is used.
The present invention can adopt the training symbol that following formula is expressed in one embodiment:
In frequency domain:
p [ k ] = A ( k ) Σ r = 0 M - 1 δ [ k - rK - K / 2 ] , 0 k N - 1 , K = N / M
The amplitude of corresponding each impulse of A (k) wherein.
The characteristics that satisfy the training symbol of this expression formula are that it is made up of K positive and negative alternate impulse function in frequency domain.Here the training symbol expression formula of listing is for exploitativeness of the present invention is described, is not unique structure, and the essential characteristic of training symbol is to be made of at interval impulse function sequence in the frequency domain.
Referring to the latter half of dotted line among Fig. 1, show the part-structure schematic diagram of receiver in the opposite end communicator of one embodiment of the invention.This opposite end communicator intercoms mutually with the communicator of dotted line the first half.The prior art part that this latter half only illustrates improvement part of the present invention and is associated with improvement part, all the other prior art parts are not shown and omit its explanation.
Receiver in the digital communication system of one embodiment of the invention, comprise the low-converter 6 that carries out down-conversion to received signal, signal after the frequency conversion is carried out regularly synchronous timing synchronizer 5, produce the high-frequency generator 14 that the higher-order of oscillation is used for described low-converter 6 frequency conversions.The invention is characterized in also and comprise: the training symbol extraction element 7 that extracts training symbol the received signal after timing synchronizer 5 is regularly synchronous, though training symbol extraction element 7 is to extract training symbol from the output signal of timing synchronizer 5 in the present embodiment, also can from receiver, includes in the signal of output Anywhere of training symbol and be extracted; The training symbol of training symbol extraction element 7 outputs is transformed to the fast fourier transformation apparatus 8 of frequency domain; Training symbol in the frequency domain of fast fourier transformation apparatus 8 output be multiply by the multistage that is divided into equal length after the conjugate of symbol of training symbol, every section is given corresponding weighting factor, multistage is superimposed as one section weighted superposition device 9; To one section after weighted superposition maximum amplitude location computing device 10 that carries out Chirp-Z conversion and interpolation, acquisition maximum amplitude position; Utilize the maximum amplitude position according to equation fe = fs ( Ω Λ - K / 2 ) / N Estimate the frequency offset estimation device 12 of frequency shift (FS), this frequency offset estimation device 12 output frequencies skew, the frequency of oscillation of control high-frequency generator 14 makes the frequency of oscillation of high-frequency generator 14 follow this frequency shift (FS) variation, reaches carrier frequency synchronization, in the formula, fe is frequency shift (FS), and fs is a sample frequency, and K is the number of data points in described section, N is the length of training symbol
Figure A0311510900082
Position for maximum amplitude.
For the ease of understanding, calculate below to one section process of carrying out Chirp-Z conversion, interpolation, acquisition maximum amplitude position after the stack.
If the K point data after the stack is y i, 0≤i≤K-1
1, finds the rough position Ω of the maximum amplitude in the frequency domain 0, Ω 0 = arg max i | y i | , 0 ≤ i ≤ K - 1 ;
2, by K point IFFT conversion with sequences y=(y 0, y 1..., y K-1)
Transform to time domain, D=(d 0, d 1... d K-1)=IFFT (y 0, y 1..., y K-1)
3, with Ω 0-1 to Ω 0The spectrum division in+1 interval is the 2M section, utilizes the positional increment information of the maximum amplitude of Chirp-Z algorithm search in should the zone.
3.1 select L=2 m＞P+2M, W = e j 2 π N · M , Produce sequences h L(n)
Figure A0311510900085
3.2H(k)＝FFT[h L(n)]，0≤k≤L-1
Figure A0311510900086
3.4Y(k)＝FFT[y(n)]，0≤k≤L-1
3.5V(n)＝IFFT[Y(k)·H(k)]，0≤n≤L-1
3.6 X ( k ) = V ( k ) · W k 2 / 2 , 0 ≤ k ≤ 2 M - 1
3.7 find the positional increment information of maximum amplitude in this interval Ω 1 = arg max k | X ( K ) | , 0 ≤ k ≤ 2 M - 1
4, obtain the exact position increment of maximum amplitude in this interval by quadratic interpolation
Ω ^ 1 = Ω 1 + [ 3 · | X ( Ω 1 - 1 ) | - 4 · | X ( Ω 1 ) | + | X ( Ω 1 + 1 ) | 2 · | X ( Ω 1 - 1 ) | - 4 · | X ( Ω 1 ) | + 2 · | X ( Ω 1 + 1 ) | - 1 ]
Thereby obtain out the exact position of maximum amplitude on entire spectrum Ω Λ = Ω Λ 1 + Ω 0 .
In the above-described embodiments, digital communication system can adopt orthogonal FDM communication system.
In weighted superposition device 9, training symbol can be divided into the M section, every section has the K point, satisfies equation K=N/M, and wherein, the training symbol length N equals sub-carrier number, and M is the positive integer less than N.
Between high-frequency generator 14 and frequency offset estimation device 12, can be connected to the loop filter 13 that the frequency shift (FS) of this frequency offset estimation device 12 outputs is carried out loop filtering.
In weighted superposition device 9, weighted factor according to be subjected to the little section weighted factor of channel effect big, be subjected to the big weighted factor of channel effect little, make to be subjected to the little section of channel effect that Frequency Estimation is made big contribution.
In weighted superposition device 9, the amplitude of peak value in the average energy in the desirable correspondent section of the weighted factor of each section, also desirable correspondent section.
The inventive method described above and transmitter and receiver are not only applicable to orthogonal FDM communication system, are applicable to any digital communication system yet.
In fast fourier transformation apparatus 8, carrying out fast fourier transform is a kind of any means known.
Below embodiment has been described in detail the present invention in conjunction with the accompanying drawings, and those skilled in the art can make the many variations example to the present invention according to the above description.Thereby some details among the embodiment should not constitute limitation of the invention, and the scope that the present invention will define with appended claims is as protection scope of the present invention.

Claims (21)

1, the method for carrier frequency synchronization in a kind of digital communication system is characterized in that, comprises following steps:
A: at transmitting terminal, the signal of communication after piece of digital modulation inserts training symbol and is sent, and this training symbol is made of impulse function sequence at interval in frequency domain;
B: at receiving terminal, from the signal that include training symbol related, extract training symbol, the training symbol that receives is transformed to frequency domain by fast fourier transform with received signal;
C: after the described training symbol in the described frequency domain be multiply by the conjugate of symbol of training symbol, be divided into the multistage of equal length, give corresponding weighting factor to every section, described multistage is superposed to one section;
D: the data in described a section are done Chirp-Z conversion and interpolation arithmetic, obtain the maximum amplitude position;
E: by the maximum amplitude position according to equation fe = fs ( Ω Λ - K / 2 ) / N Estimate frequency shift (FS), wherein, fe is frequency shift (FS), and fs is a sample frequency, and K is the number of data points in described section, and N is the length of training symbol correspondence, Be the maximum amplitude position;
F: the frequency shift (FS) that utilizes the e step to obtain, the frequency of oscillation of control high-frequency generator makes the frequency of oscillation of high-frequency generator follow described frequency shift (FS) variation, reaches carrier frequency synchronization.
2., the method for claim 1, it is characterized in that, described digital communication system is an orthogonal FDM communication system, and the described digital modulation among the step a is the OFDM modulation, and the signal of communication after the described piece of digital modulation is one or several OFDM symbols.
3, the method for claim 1 is characterized in that, the interval impulse function sequence of training symbol described in the step a in frequency domain is by impulse function in every section, and the M section is formed altogether.
As the described method of claim 1,2 or 3, it is characterized in that 4, training symbol is divided into the M section described in the described step c, every section has the K point, satisfies equation K=N/M, and wherein, described training symbol length N equals sub-carrier number, and M is the positive integer less than N.
5, method as claimed in claim 1 or 2 is characterized in that, described training symbol is expressed as follows: in frequency domain:
p [ k ] = A ( k ) Σ r = 0 M - 1 δ [ k - rK - K / 2 ] , 0 kN - 1 , K = N / M
The amplitude of corresponding each impulse of A (k) wherein.
6, method as claimed in claim 1 or 2 is characterized in that, the weighted factor among the step c according to be subjected to the little section weighted factor of channel effect big, be subjected to the big weighted factor of channel effect little, make to be subjected to the little section of channel effect that Frequency Estimation is made big contribution.
7, method as claimed in claim 6 is characterized in that, described section weighted factor is got the average energy in this section.
8, method as claimed in claim 6 is characterized in that, described section weighted factor is got the amplitude of peak value in this section.
9, method as claimed in claim 1 or 2 is characterized in that, also comprises the step of described frequency shift (FS) being carried out loop filtering before step f.
10, the transmitter in a kind of digital communication system comprises signal of communication is carried out the digital modulator of digital modulation and the wireless front end that the signal of communication after the modulation is sent, and it is characterized in that described transmitter also comprises:
Produce the training symbol generation device of the training symbol of the middle shock insulation sequence of function formation of frequency domain; With
Be connected the signal of communication after one section modulation between described digital modulator and the described wireless front end and insert the multiple devices of described training symbol.
11, transmitter as claimed in claim 10, it is characterized in that, described digital communication system is an orthogonal FDM communication system, and described digital modulation is the OFDM modulation, and the signal of communication after the described piece of digital modulation is one or several OFDM symbols.
12, transmitter as claimed in claim 10 is characterized in that, the interval impulse function sequence of described training symbol is by impulse function in every section, and the M section is formed altogether, and 1≤M≤N, N are sub-carrier number.
13, as claim 10 or 11 described transmitters, it is characterized in that described training symbol is expressed as follows: in frequency domain:
p [ k ] = A ( k ) Σ r = 0 M - 1 δ [ k - rK - K / 2 ] , 0 kN - 1 , K = N / M
The amplitude of corresponding each impulse of A (k) wherein.
14, the receiver in a kind of digital communication system, comprise the low-converter that carries out down-conversion to received signal, signal after the frequency conversion is carried out regularly synchronous timing synchronizer, produce the high-frequency generator that the higher-order of oscillation is used for described low-converter frequency conversion, it is characterized in that, also comprise:
From the signal that include training symbol related, extract the training symbol extraction element of training symbol with received signal;
Described training symbol is transformed to the fast fourier transformation apparatus of frequency domain;
Described training symbol in the frequency domain be multiply by the multistage that is divided into equal length after the conjugate of symbol of training symbol, every section is given corresponding weighting factor, described multistage is superimposed as one section weighted superposition device;
To the described one section maximum amplitude location computing device that carries out Chirp-Z conversion and interpolation, acquisition maximum amplitude position after the weighted superposition;
Utilize the maximum amplitude position according to equation fe = fs ( Ω Λ - K / 2 ) / N Estimate the frequency offset estimation device of frequency shift (FS), this frequency offset estimation device output frequency skew, the frequency of oscillation of control high-frequency generator makes the frequency of oscillation of high-frequency generator follow this frequency shift (FS) variation, reaches carrier frequency synchronization, in the formula, fe is frequency shift (FS), and fs is a sample frequency, and K is the number of data points in described section, N is the length of training symbol Position for maximum amplitude.
15, receiver as claimed in claim 14 is characterized in that, described training symbol extraction element links to each other with the output of timing synchronizer, extracts training symbol from timing synchronizer output signal.
16, receiver as claimed in claim 14 is characterized in that, described digital communication system is an orthogonal FDM communication system.
17, as claim 14 or 16 described receivers, it is characterized in that described training symbol is divided into the M section, every section has the K point, satisfies equation K=N/M, and wherein, described training symbol length N equals sub-carrier number, and M is the positive integer less than N.
18, as claim 14 or 16 described receivers, it is characterized in that, between described high-frequency generator and described frequency offset estimation device, be connected to the loop filter that the frequency shift (FS) of this frequency offset estimation device output is carried out loop filtering.
19, as claim 14 or 16 described receivers, it is characterized in that, described weighted factor according to be subjected to the little section weighted factor of channel effect big, be subjected to the big weighted factor of channel effect little, make to be subjected to the little section of channel effect that Frequency Estimation is made big contribution.
20, receiver as claimed in claim 19 is characterized in that, described section weighted factor is got the average energy in this section.
21, receiver as claimed in claim 20 is characterized in that, described section weighted factor is got the amplitude of peak value in this section.
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Cited By (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN1767424B (en) * 2004-10-29 2010-05-12 株式会社瑞萨科技 Broadcast station synchronization method and mobile terminal
CN1773977B (en) * 2004-11-08 2011-04-20 中兴通讯股份有限公司 MIMO-OFDM carrier frequency synchronizing method based on pilot frequency design
CN101552761B (en) * 2009-05-25 2012-10-03 张剑 Method for modulating/demodulating reference Chirp ultra- wideband system based on SAW code domain
CN102724155A (en) * 2012-05-17 2012-10-10 哈尔滨工程大学 High frequency domain energy concentration synchronization method based on fractional Fourier transform
CN101473618B (en) * 2006-06-20 2012-12-05 Nxp股份有限公司 Method and equipment for estimating carrier frequency offset
CN105629219A (en) * 2015-12-29 2016-06-01 大连楼兰科技股份有限公司 Ranging accuracy and computation burden equalizing method
CN106789797A (en) * 2016-11-29 2017-05-31 重庆邮电大学 A kind of symbol timing synchronization method of wireless burst communication psk signal

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KR100238047B1 (en) * 1997-02-25 2000-01-15 윤종용 Carrier frequency synchronization method and apparatus of quadrature frequecy division multiplexing transfer system
US6608862B1 (en) * 1999-08-20 2003-08-19 Ericsson, Inc. Method and apparatus for computing prefilter coefficients
GB2361607A (en) * 2000-04-17 2001-10-24 Mitsubishi Electric Inf Tech Compensating for local oscillator and sampling frequency offsets in an OFDM receiver
JP3776716B2 (en) * 2000-11-17 2006-05-17 株式会社東芝 Orthogonal frequency division multiplex transmission signal receiver

Cited By (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN1767424B (en) * 2004-10-29 2010-05-12 株式会社瑞萨科技 Broadcast station synchronization method and mobile terminal
CN1773977B (en) * 2004-11-08 2011-04-20 中兴通讯股份有限公司 MIMO-OFDM carrier frequency synchronizing method based on pilot frequency design
CN101473618B (en) * 2006-06-20 2012-12-05 Nxp股份有限公司 Method and equipment for estimating carrier frequency offset
CN101552761B (en) * 2009-05-25 2012-10-03 张剑 Method for modulating/demodulating reference Chirp ultra- wideband system based on SAW code domain
CN102724155A (en) * 2012-05-17 2012-10-10 哈尔滨工程大学 High frequency domain energy concentration synchronization method based on fractional Fourier transform
CN102724155B (en) * 2012-05-17 2014-09-17 哈尔滨工程大学 High frequency domain energy concentration synchronization method based on fractional Fourier transform
CN105629219A (en) * 2015-12-29 2016-06-01 大连楼兰科技股份有限公司 Ranging accuracy and computation burden equalizing method
CN106789797A (en) * 2016-11-29 2017-05-31 重庆邮电大学 A kind of symbol timing synchronization method of wireless burst communication psk signal
CN106789797B (en) * 2016-11-29 2019-12-31 重庆邮电大学 Symbol synchronization method for wireless burst communication PSK signal

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