CN117595649A - Multiport input non-isolated direct current converter and control method thereof - Google Patents
Multiport input non-isolated direct current converter and control method thereof Download PDFInfo
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- 238000004146 energy storage Methods 0.000 claims abstract description 25
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/06—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider
- H02M3/07—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider using capacitors charged and discharged alternately by semiconductor devices with control electrode, e.g. charge pumps
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
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Abstract
The application relates to a multiport input non-isolated direct current converter and a control method thereof, wherein the multiport input non-isolated direct current converter comprises a boosting subunit and a rectifying energy storage unit, the boosting subunit consists of two boosting circuits with coupling inductors, and the rectifying energy storage unit is used for rectifying the voltage of the coupling inductors and supplying power to a load; the invention uses the second coils of the two coupling inductors in the boosting subunit to be in reverse series connection, and uses 180-degree staggered driving of the first switching tube and the second switching tube to enable the two coupling inductors to work in the transformer coupling and inductance energy storage/release modes, thereby realizing the forward and reverse excitation mixed boosting rectification mode. Compared with the traditional method, the invention effectively utilizes leakage inductance energy, reduces voltage stress of the diode and the switch tube in the circuit, and realizes high gain and high efficiency of boosting by the first switch tube and the second switch tube which work in a current interruption mode without peripheral absorption.
Description
Technical Field
The application relates to the technical field of power electronics and the field of battery equipment, in particular to a multiport input non-isolated direct current converter and a control method thereof.
Background
With more and more low-voltage and wide-range input power supply products being widely used, such as for providing bus voltages for inverter conversion, for example, 12V-48 VDC input vehicle-mounted inverter, 20V-60 VDC input single-board photovoltaic inverter or micro-inverter, 20V-60 VDC input portable energy storage inverter of battery pack, and 2.5V-40V input battery pack string production aging equipment, etc., the voltage boost ratio is up to 10-20 times higher than the voltage boost ratio of the inverter bus voltage of 360V-400 VDC. The traditional non-isolated Boost circuit scheme can realize such high gain by calculating the switch duty ratio according to theory to be more than 0.90 and even more than 0.95, and the problem that the load capacity of the Boost circuit is reduced and the loss is increased after the duty ratio is overlarge is solved, so that the traditional Boost circuit can not meet the scene requirement.
Patent document with publication number CN105515392B discloses a dc-dc Boost converter circuit, as shown in fig. 1, after the first Boost power inductor L1 stores energy, the coupling voltage of each turn of coupling voltage is reduced when the inductor releases energy through the coupling between the second Boost power inductor L2 and the first Boost power inductor L1, so as to achieve a low duty ratio and high Boost ratio. Although the high gain problem is solved in this way, there are other disadvantages, such as the first Boost power inductor L1 and the second Boost power inductor L2 of the magnetic device are also an energy storage type inductor, compared with the transformer with low utilization rate, the switching tube can generate leakage inductance due to incomplete coupling of the two inductors and further has high pressure stress, so that other auxiliary absorption circuits are needed; in addition, as in the photovoltaic field, multiple paths of photovoltaic inputs and tracking MMPT are needed, so that multiple paths of voltage boosting circuits are needed; the circuit configuration is very complex if a circuit as shown in fig. 1 is used in addition to the absorption circuit.
Disclosure of Invention
The invention aims to provide a multiport input non-isolated direct current converter and a control method thereof, which can solve the technical problems that the prior art cannot meet the requirement of high-gain direct current conversion, the multipath input structure is complex or the stress of a switching tube is high, and the utilization rate of a magnetic device is low.
The first technical scheme adopted by the invention is as follows: the multi-port input non-isolated direct current converter comprises at least one boosting subunit and a rectifying energy storage unit, wherein the boosting subunit comprises two boosting circuits with coupling inductors, the first boosting circuits and the second boosting circuits are identical in structure and comprise a direct current power supply, an input filter capacitor, a switching tube, coupling inductors and a rectifying diode, the coupling inductors are provided with two coils, two endpoints of the first coil are respectively marked as an endpoint 1 and an endpoint 2, two endpoints of the second coil are respectively marked as an endpoint 3 and an endpoint 4, one ends of a positive electrode of the direct current power supply and one end of the input filter capacitor are connected with the endpoint 1of the coupling inductors, the other ends of the negative electrode of the direct current power supply and the input filter capacitor are connected with a source electrode of the switching tube, a drain electrode of the switching tube and an anode of the rectifying diode are connected with the endpoint 2 of the coupling inductors, the two negative electrodes of the direct current power supply are connected and serve as negative output ends of the boosting subunit, the two cathodes of the rectifying diode are connected and serve as first output ends of the boosting subunit, the endpoint 3 of the first boosting subunit is respectively marked as an endpoint 3 and an endpoint 4, one end of the first coupling inductor in the first boosting circuit is connected with the second inductor 4, and the other end of the second coupling inductor is connected with the second endpoint 4 as a second endpoint of the second coupling end of the boosting unit is connected with the second output end of the second boosting unit; the negative output end and the first output end of each boosting subunit are respectively connected, and the second output ends and the third output ends of two adjacent boosting subunits are sequentially connected;
the rectifying and energy-storing unit comprises a first rectifying diode, a second rectifying diode, a third capacitor, a fourth capacitor, a fifth capacitor and a sixth capacitor, wherein the first rectifying diode and the second rectifying diode are connected in series, the cathode of the first rectifying diode is used as the positive output end of the rectifying and energy-storing unit, the anode of the second rectifying diode is connected with the first output end of the last boosting subunit, and the cathode of the second rectifying diode is connected with the second output end of the last boosting subunit; the third capacitor, the fourth capacitor and the fifth capacitor are sequentially connected in series, one end of the fifth capacitor, which is not connected with the fourth capacitor, is connected with the cathode of the first rectifying diode, one end of the third capacitor, which is connected with the fourth capacitor, is connected with the first output end of the last boosting subunit, and the other end of the third capacitor, which is connected with the negative output end of the last boosting subunit, is used as the negative output end of the rectifying energy storage unit; the third output end of the first boosting subunit is connected with the other end of the fifth capacitor; and two ends of the sixth capacitor are respectively connected with the positive output end and the negative output end of the rectifying and energy-storing unit.
Further, the rectifying diode in the boost subunit and the first rectifying diode and the second rectifying diode in the rectifying energy storage unit may be replaced by synchronous rectifying switch tubes with antiparallel diodes.
Further, the coupling inductor is an energy-storable inductor with an air gap, the two coils are coupled to each other, and the number of turns of the second coil is larger than the number of turns of the first coil.
Further, the boosting subunit further comprises an inductor, one end of the inductor is connected with the endpoint 4 of the first coupling inductor, and the other end of the inductor is used as a third output end of the boosting subunit; the inductance is leakage inductance of two coils in the two coupling inductances, or the external inductance is adopted, or the combination of the leakage inductance and the external inductance is adopted.
Further, the direct current power supplies of the two boost circuits in the boost subunit are equal voltage direct current power supplies or unequal voltage direct current power supplies, and the voltage of the two direct current power supplies is less than or equal to one half of the output voltage Vo between the positive output end and the negative output end of the rectifying and energy storing unit; the two booster circuits may share one dc power supply.
Further, the switching tube in the boost circuit is a high-frequency switching tube provided with an anti-parallel diode, or can be equivalently a high-frequency switching tube with the same function; the anti-parallel diode is an integrated diode, a parasitic diode or an external diode; the third capacitor, the fourth capacitor and the fifth capacitor are electrolytic capacitors, high-frequency nonpolar capacitors or high-frequency polar capacitors; when the third capacitor, the fourth capacitor and the fifth capacitor are high-frequency capacitors with polarity, the positive electrode of the fifth capacitor is connected with the cathode of the first rectifying diode, the positive electrode of the fourth capacitor is connected with the negative electrode of the fifth capacitor, the negative electrode of the fourth capacitor is connected with the positive electrode of the third capacitor, the positive electrode of the third capacitor is also connected with the first output end of the last boosting subunit, and the negative electrode is connected with the negative output end of the last boosting subunit.
Further, the first output end of the boosting subunit can be used as an intermediate output voltage endpoint, and the first output end of the boosting subunit and the negative output end of the rectifying energy storage unit are connected together to be supplied with power.
The invention adopts another technical scheme that: a control method for a multi-port input non-isolated DC converter is used for controlling the multi-port input non-isolated DC converter according to the technical scheme, and comprises the following steps: applying staggered driving of 180 degrees of phase stagger or one half of switching period to a first switching tube of a first boost circuit and a second switching tube of a second boost circuit in each boost subunit; when the first switching tube is turned on, the first coupling inductor works in a transformer coupling mode and an inductance energy storage mode, and the second coil of the first coupling inductor is coupled with voltage through a transformation ratio and performs series output work with the second coil of the second coupling inductor through inductance energy release freewheeling; when the second switching tube is turned on, the second coupling inductor works in a transformer coupling mode and an inductance energy storage mode, and the second coil of the second coupling inductor is coupled with voltage through a transformation ratio and performs series output work with the second coil of the first coupling inductor through inductance energy release freewheeling.
Further, the duty ratio applied to the first switching tube and the second switching tube is 0.5 or more, so that the first switching tube, the second switching tube and the third capacitor obtain lower voltage stress than when the duty ratio is less than 0.5.
Further, when a synchronous rectification switching tube having an antiparallel diode is used in the booster circuit, a driving signal may be applied to the synchronous rectification switching tube for rectification to perform synchronous rectification.
The invention has the beneficial effects that: the invention uses the second coils of the two coupling inductors in the boosting subunit to be reversely connected in series, and uses 180-degree staggered driving of the first switching tube and the second switching tube to enable the two coupling inductors to work in transformer coupling and inductor energy storage/energy release modes, thereby realizing a forward and reverse excitation mixed boosting rectification mode, effectively utilizing leakage inductance energy, reducing voltage stress of a diode and a switching tube in a circuit, enabling the first switching tube and the second switching tube to work in a current interruption mode without peripheral absorption, and realizing high-gain boosting and high efficiency of multipath direct current input.
Drawings
In order to more clearly illustrate the technical solutions of the embodiments of the present invention, the drawings that are needed in the embodiments will be briefly described below, and it is obvious that the drawings in the following description are only some embodiments of the present application, and that other drawings may be obtained according to these drawings without inventive effort for a person skilled in the art.
FIG. 1 is a schematic diagram of a conventional DC boost converter circuit;
FIG. 2 is a circuit diagram of embodiment 1;
FIG. 3 is a schematic view showing the working state of example 1;
FIG. 4 is a schematic view showing another working state of embodiment 1;
FIG. 5 is a circuit diagram of embodiment 2;
FIG. 6 is a circuit diagram of embodiment 3;
fig. 7 is a circuit diagram of embodiment 4.
Detailed Description
In order that the above-recited objects, features and advantages of the present invention will be more clearly understood, a more particular description of the invention will be rendered by reference to the appended drawings and appended detailed description. In the following description, numerous specific details are set forth in order to provide a thorough understanding of the present invention, however, the present invention may be practiced in other ways than those described herein, and therefore the present invention is not limited to the specific embodiments disclosed below.
Unless defined otherwise, technical or scientific terms used herein should be given the ordinary meaning as understood by one of ordinary skill in the art to which this application pertains. The terms "first," "second," and the like in the description and in the claims, are not used for any order, quantity, or importance, but are used for distinguishing between different elements. Likewise, the terms "a" or "an" and the like do not denote a limitation of quantity, but rather denote the presence of at least one. The terms "connected" or "connected," and the like, are not limited to physical or mechanical connections, but may include electrical connections, whether direct or indirect. "upper", "lower", "left", "right", etc. are used merely to indicate a relative positional relationship, which changes accordingly when the absolute position of the object to be described changes.
Example 1
As shown in fig. 2, the multi-port input non-isolated dc converter includes a boost subunit and a rectifying energy storage unit, where the boost subunit includes two boost circuits with coupling inductors, the first boost circuit and the second boost circuit have the same structure and each include a dc power supply, an input filter capacitor, a switching tube, a coupling inductor and a rectifying diode, the coupling inductor has two coils, two end points of the first coil N1 are respectively marked as an end point 1 and an end point 2, and two end points of the second coil N2 are respectively marked as an end point 3 and an end point 4. First coupling inductance T R1 Terminal 1 and terminal 4 of (1) are homonymous terminals, a second coupling inductance T R2 Endpoint 1 and endpoint 3 of (a) are homonymous endpoints. The positive electrode of the direct current power supply and one end of the input filter capacitor are connected with the end point 1of the coupling inductor, the negative electrode of the direct current power supply and the other end of the input filter capacitor are connected with the source electrode of the switching tube, and the drain electrode of the switching tube and the anode of the rectifier diode are connected with the end point 2 of the coupling inductor; namely, in the first booster circuit, the positive electrode of the first direct current power supply DC1 and one end of the first input filter capacitor C1 are connected with the first coupling inductance T R1 The negative electrode of the first direct current power supply DC1 and the other end of the first input filter capacitor C1 are connected with the source electrode of the first switch tube Q1, the drain electrode of the first switch tube Q1 and the anode of the fourth rectifier diode D4 are connected with the first coupling inductance T R1 Is connected at endpoint 2; in the second boost circuit, the positive electrode of the second DC power supply DC2 and one end of the second input filter capacitor C2 are connected with the second coupling inductance T R2 The negative electrode of the second direct current power supply DC2 and the other end of the second input filter capacitor C2 are connected with the source electrode of the second switch tube Q2, the drain electrode of the second switch tube Q2 and the anode of the third rectifier diode D3 are connected with the second coupling inductance T R2 Is connected to terminal 2 of (c).
The cathodes of the two direct current power supplies, namely the first direct current power supply DC1 and the second direct current power supply DC2 are connected and serve as the negative output end BUS 1-of the boosting subunit, the cathodes of the two rectifying diodes, namely the third rectifying diode D3 and the fourth rectifying diode D4 are connected and serve as the first output end REC 1of the boosting subunit, and the first coupling inductance T in the first boosting circuit R1 Terminal 3 of (2) and the second coupling inductance T in the second boost circuit R2 Terminal 4 of the second coupling inductor is connected to terminal 3 of the first coupling inductor T as the second output terminal REC2 of the boost subunit R1 Is used as the third output REC3 of the boost subunit.
The rectifying and energy-storing unit comprises a first rectifying diode D1, a second rectifying diode D2, a third capacitor C3, a fourth capacitor C4, a fifth capacitor C5 and a sixth capacitor C6, wherein the first rectifying diode D1 and the second rectifying diode D2 are connected in series, the cathode of the first rectifying diode D1 is used as a positive output end BUS+ of the rectifying and energy-storing unit, the anode of the second rectifying diode D2 is connected with a first output end REC 1of the boosting subunit, and the cathode of the second rectifying diode D2 is connected with a second output end REC2 of the boosting subunit; the third capacitor C3, the fourth capacitor C4 and the fifth capacitor C5 are sequentially connected in series, one end of the fifth capacitor C5, which is not connected with the fourth capacitor C4, is connected with the cathode of the first rectifying diode D1, one end of the third capacitor C3, which is connected with the fourth capacitor C4, is connected with the first output end REC 1of the boosting subunit, and the other end of the third capacitor C3, which is connected with the negative output end BUS 1-of the boosting subunit, is used as the negative output end BUS-of the rectifying energy storage unit; the third output end REC3 of the boosting subunit is connected with the other end of the fifth capacitor C5; and two ends of the sixth capacitor C6 are respectively connected with a positive output end BUS+ and a negative output end BUS of the rectifying and energy-storing unit.
In embodiment 1, a first coupling inductance T R1 And a second coupling inductance T R2 For the storable inductance with an air gap, the first coil N1 and the second coil N2 are coupled to each other, and the number of turns of the second coil N2 is larger than that of the first coil N1. The first DC power supply DC1 and the second DC power supply DC2 are equal voltage DC power supply or non-equal voltage DC power supply, and the first DC power supply DC1 and the second DC power supplyThe voltage of DC2 is less than or equal to one half of the output voltage Vo between the positive output end BUS+ and the negative output end BUS-of the rectifying and energy storing unit; the two booster circuits may share one dc power supply. The first switching tube Q1 and the second switching tube Q2 are high-frequency switching tubes provided with anti-parallel diodes or can be equivalently high-frequency switching tubes with the same function; the anti-parallel diode is an integrated diode, a parasitic diode or an external diode; the third capacitor C3, the fourth capacitor C4 and the fifth capacitor C5 are electrolytic capacitors, high-frequency nonpolar capacitors or high-frequency polar capacitors; when the third capacitor C3, the fourth capacitor C4 and the fifth capacitor C5 are high-frequency capacitors with polarity, the positive electrode of the fifth capacitor C5 is connected with the cathode of the first rectifying diode D1, the positive electrode of the fourth capacitor C4 is connected with the negative electrode of the fifth capacitor C5, the negative electrode of the fourth capacitor C4 is connected with the positive electrode of the third capacitor C3, the positive electrode of the third capacitor C3 is connected with the first output terminal REC 1of the boosting subunit, and the negative electrode is connected with the negative output terminal BUS 1-of the most boosting subunit. The first output REC 1of the boost subunit may also be used as an intermediate output voltage terminal, and is connected to a load together with the negative output BUS of the rectifying and energy-storing unit for supplying power.
In order to analyze the working state of embodiment 1, in embodiment 1, the first DC power source DC1 and the second DC power source DC2 have voltage inputs, and the voltages are equal in magnitude and V1, and the turn ratio of the first coil N1 to the second coil N2 is 1: n, N is more than or equal to 1, the inductance of the first coil N1 is L1, and the inductance of the second coil N2 is N 2 * L1; for ease of analysis, the voltage drop across the diode and the on-resistance of the switching tube are ignored.
The control method of the embodiment 1 is as follows: applying staggered driving of 180 degrees or one half of a switching period of a phase stagger to a first switching tube Q1 of the first boost circuit and a second switching tube Q2 of the second boost circuit; when the first switching tube Q1 is turned on, the first coupling inductor T R1 Working in a transformer coupling mode and an inductance energy storage mode, a first coupling inductance T R1 Is coupled to the voltage by a transformation ratio and is coupled to a second inductance T R2 The energy release freewheels of the second coil N2 of the transformer are subjected to series output work; the working state of example 1 is now as shown in FIG. 3, firstCoupling inductance T R1 Operating in hybrid mode, the inductance of the first coil N1 is excited to store energy and the first coupling inductance T is used for simultaneously R1 The second coil N2 of the transformer is coupled to operate in a transformer mode, the first coupling inductance T R1 By coupling with the first coil N1, a voltage of about N x V1 is generated, the electromotive force direction being positive at the terminal 4 and negative at the terminal 3; at the same time, the second switching tube Q2 is turned off due to 180 DEG phase error, and the second coupling inductance T R2 The inductive energy storage during the turn-on period of the second switching tube Q2 is already released, the second coupling inductance T R2 The voltage of the first coil N1 is Vc3-V1, vc3 is the voltage at two ends of the third capacitor C3, the electromotive force direction is positive at the end point 2, and the end point 1 is negative; charging the third capacitor C3 via the third rectifying diode D3 or rectifying and supplying power via the second rectifying diode D2, and coupling with the first coupling inductor T R1 Second coupling inductance T R2 Is connected in series with the voltage of the second coil N2; second coupling inductance T R2 By coupling with the first coil N1, a voltage of about N x (Vc 3-V1) is generated, the electromotive force direction being positive at the terminal 4 and negative at the terminal 3; therefore, at this time, the second coupling inductance T R2 The second coil N2 of (1) serves as a freewheeling inductor and is coupled with the first coupling inductor T R1 Forms a forward conversion-like operation with the second coil N2, and the current passes through the second rectifying diode D2 and the second coupling inductance T R2 A second coil N2 of the (C) and a first coupling inductance T R1 The second coil N2 and the fourth capacitor C4 form a charging loop, vc4=n (vc3-V1) +n v1=n×vc3, and Vc4 is the voltage across the fourth capacitor C4.
When the second switching tube Q2 is turned on, the second coupling inductor T R2 Working in a transformer coupling mode and an inductance energy storage mode, and a second coupling inductance T R2 Is coupled to the voltage by a transformation ratio and is coupled to the first coupling inductance T R1 The energy release freewheels of the second coil N2 of the transformer are subjected to series output work; the working state of example 1 is shown in FIG. 4, the second coupling inductance T R2 Operating in hybrid mode, exciting the second coupling inductance T R2 The inductance of the first coil N1of the transformer is stored with energy and is also passed through the second coupling inductance T R2 Is connected with the second coil N2 ofThe coupling works in a transformer mode, and a second coupling inductance T R2 By coupling with the first coil N1, a voltage of about N x V1 is generated, the electromotive force direction being positive at the terminal 3 and negative at the terminal 4; at the same time, the first switching tube Q1 is closed because of 180 DEG phase error, the first coupling inductance T R1 The inductive energy storage during the turn-on period of the first switching tube Q1 is released, the first coupling inductance T R1 The voltage of the first coil N1 is Vc3-V1, the electromotive force direction is positive at the end point 2, and the end point 1 is negative; the third capacitor C3 is charged by the fourth rectifying diode D4, the first coupling inductance T R1 The second coil N2 is coupled with the first coil N1 to generate voltage of about N (Vc 3-V1), the electromotive force direction is positive at the end point 3, and the end point 4 is negative; therefore, at this time, the first coupling inductance T R1 The second coil N2 of (1) serves as a freewheeling inductor and is coupled with the second coupling inductor T R2 The second coil N2 of the transformer is operated like forward conversion, and the current passes through the first coupling inductance T R1 Second coil N2, second coupling inductance T R2 The second winding N2, the first rectifying diode D1 and the fifth capacitor C5 form a charging loop, where vc5=n (vc3-V1) +nv1=n×vc3, and Vc5 is the voltage across the fifth capacitor C5, so vo=vc3+vc4+vc5= (2n+1) ×vc3.
Thus, the first coupling inductance T is no matter the first switch tube Q1 is on or the second switch tube Q2 is on R1 Second coupling inductance T R2 The voltage of the second coil N2 of the transformer is connected in series, and typical voltage doubling rectification is formed by the first rectifying diode D1, the second rectifying diode D2, the fourth capacitor C4 and the fifth capacitor C5; while the current is clamped by the coupled inductor which is discharging the inductive energy. The first rectifying diode D1 and the second rectifying diode D2 are not due to the first coupling inductance T R1 Second coupling inductance T R2 The second coil N2 of the capacitor (C) has leakage inductance to generate larger voltage stress, but is naturally clamped by the fourth capacitor C4 and the fifth capacitor C5. At the same time, during the period when the first switching tube Q1 is closed or the second switching tube Q2 is closed, the first coupling inductance T R1 Second coupling inductance T R2 The inductance potential voltage of the first coil N1of the transformer is rectified by the fourth rectifier diode D4 and the third rectifier diode D3Compared with the high-gain boost converter circuit in fig. 1, the capacitor C3 is clamped, and no additional absorption circuit is needed, and no larger voltage stress is generated.
Assuming that the current in the coupling inductance coil is in a critical state when the first switching tube Q1 and the second switching tube Q2 are turned on next time, recording the on duty ratio of the first switching tube Q1 as Dq1, the on duty ratio of the second switching tube Q2 as Dq2, the on duty ratio of the switching tube corresponding to the boost circuit where the direct current source with higher voltage value is located as D, and the off duty ratio as 1-D; the first switch tube Q1 is applied to the first coupling inductance T when being conducted R1 Voltage vn1on=v1 of the first coil N1of the first switching tube Q1, the first coupling inductance T when the first switching tube Q1 is turned off R1 According to the balance theorem, VL1on d=vl 1off (1-D), v1 d= (Vc 3-V1) (1-D)), v1=vc3 (1-D) is derived, and the output voltage vo= (2n+1) ((Vc 3), and the voltage V1 of the first DC power supply DC1 is equal to the voltage V2 of the second DC power supply DC2, so the calculation formula of the boost gain G isD=dq1=dq2 at this time;
when the first DC power supply DC1 and the second DC power supply DC2 have voltage inputs, but the voltage V1 of the first DC power supply DC1 is not equal to the voltage V2 of the second DC power supply DC2, if V1 is greater than V2Where Dq1 < Dq2, d=dq1; if V2 is greater than or equal to V1, thenAt this time, dq2 is equal to or less than Dq1, d=dq2;
when only one of the first DC power source DC1 or the second DC power source DC2 has a voltage input,d=dq1 when only the first direct current power DC1 has a voltage input; when only the second direct current power supply DC2 has a voltage input, d=dq2。
Because D is smaller than 1 and N is larger than or equal to 1, the boost gain G is far larger than that of the traditional boost circuitIs also much larger than the boost gain of figure 1 +.>Namely G>G2>G1. In embodiment 1, taking n=1.5, v1=30v, d=0.70, switching frequency fs=150k, capacitance values of the third capacitor C3, the fourth capacitor C4 and the fifth capacitor C5 are all 4.7uf, inductance value of the first coil N1 is 7.5uH, inductance value of the second coil N2 is 16.9uH, and load is 100 ohms. The output voltage Vo calculated according to the calculation formula of the boost gain G is 400V, the output voltage calculated according to the calculation formula of the boost gain G2 of fig. 1 is 205V, the output voltage calculated according to the calculation formula of the boost gain G1 of the conventional boost circuit is 100V, and the output voltage Vo actually measured using the above parameters is 379V, which is far more than the theoretical calculation value obtained according to the calculation formulas of the boost gain G1 of the conventional boost circuit and the boost gain G2 of fig. 1, the reason why the actually measured output voltage differs from the theoretical value calculated according to the calculation formula of the boost gain G is that the actual circuit is non-ideal, there are cases where line impedance, diode voltage drop, switching-on impedance of the switching tube, and driving duty ratio (rise rate, fall rate) are lost, the inductance of the first coil N1 does not realize critical continuity, etc., so that in actual use, it is necessary to adjust the duty ratio correction error to reach the required voltage by closed loop control.
From the above analysis, it is clear that the embodiment 1 exhibits a higher boost gain than the prior art, and when the two input voltages are not identical, the drive duty ratio of the input voltage is higher than the drive duty ratio of the input voltage is lower, and the respective duty ratios can be adjusted by referring to the calculation formula of the boost gain G. In order to obtain lower voltage stress of the first switching tube Q1, the second switching tube Q2 and the third capacitor C3, the duty ratio applied to the first switching tube Q1 and the second switching tube Q2 in embodiment 1 is 0.5 or more to reduce the first coupling inductance T R1 And a second coupling inductance T R2 Is the first of (1)The coil N1 transfers the energy of the coupling inductor to the fourth capacitor C4 and the fifth capacitor C5 as much as possible due to the voltage rise caused by the charging of the third capacitor C3 in the closing interval of the first switching tube Q1 and the second switching tube Q2; so that a lower voltage stress than an applied duty cycle of less than 0.5 can be obtained with the same output voltage.
Example 2
Due to the first coupling inductance T R1 Second coupling inductance T R2 Leakage inductance is necessarily present, and thus the boost subunit described in embodiment 1 further includes inductance Lr, thereby constituting embodiment 2. The circuit structure of embodiment 2 is shown in fig. 5, wherein one end of the inductor Lr is coupled with the first coupling inductor T R1 The other end is connected with the end point 4 of the voltage boosting subunit, and the other end is used as a third output end REC3 of the voltage boosting subunit; the inductance Lr is a first coupling inductance T R1 And a second coupling inductance T R2 The leakage inductance of the first coil N1 and the second coil N2 is either the externally applied inductance or the combination of the leakage inductance and the externally applied inductance. At this time, the inductor Lr can be used as a freewheeling inductor at the DC output side in the forward mode and coupled with the first coupling inductor T R1 Second coupling inductance T R2 The operation principle of embodiment 2 is identical to that of embodiment 1 and will not be described here, as the second coil N2 of embodiment 2 acts as a flywheel inductor to release energy together.
Example 3
On the basis of embodiment 1, the boosting sub-unit may be provided with at least two, thereby constituting embodiment 3. As shown in fig. 6, the circuit configuration of embodiment 3 is such that in embodiment 3, the number of booster subcells is n, and n is an integer of 2 or more. The structure of each boosting subunit is the same as that of embodiment 1, and the first output end of the ith boosting subunit is REC1-i, the second output end is REC2-i, the third output end is REC3-i, and the negative output end is BUS i-, i=1, 2, …, n. The negative output end of each boosting subunit is connected together and is connected with one end of the third capacitor C3, which is not connected with the fourth capacitor C4, and the negative output end is used as a negative output end BUS-of the rectifying and energy storing unit. The first output end of each boosting subunit is connected together and is connected with the anode of the second rectifying diode D2 and one end of the third capacitor C3 connected with the fourth capacitor C4. The second output end REC2-i of the ith boosting subunit is connected with the third output end REC3-i of the (i+1) th boosting subunit, the third output end REC3-1 of the first boosting subunit and the fifth capacitor C5 are connected with one end connected with the fourth capacitor C4, and the second output end REC2-i of the nth boosting subunit is connected with the cathode of the second rectifying diode D2, so that a combined non-isolated direct current converter with more multi-port inputs is formed. The connection mode of the second coils N2 of the two coupling inductors in each booster subunit is a sequential connection mode, or only one of the two coupling inductors, and the two coupling inductors may be connected in a disordered order when the same function is satisfied.
Example 4
The third rectifying diode D3 and the fourth rectifying diode D4 in the boost subunit and the first rectifying diode D1 and the second rectifying diode D2 in the rectifying and energy storing unit in embodiment 1 can be replaced by synchronous rectifying switching transistors with antiparallel diodes, forming embodiment 4. The circuit structure of embodiment 4 is as shown in FIG. 7, wherein the source of the fourth synchronous rectification switch QD4 is coupled with the first coupling inductor T R1 The source of the third synchronous rectification switch QD3 is connected with the second coupling inductance T R2 The drain of the fourth synchronous rectifier switch QD4 is connected to the drain of the third synchronous rectifier switch QD3 and serves as the first output REC 1of the boost subunit. The source electrode of the first synchronous rectification switch tube QD1 is connected with the drain electrode of the second synchronous rectification switch tube QD2, the drain electrode of the first synchronous rectification switch tube QD1 is used as a positive output end BUS+ of the rectification energy storage unit, the source electrode of the second synchronous rectification switch tube QD2 is connected with a first output end REC 1of the boosting subunit, and the drain electrode is connected with a second output end REC2 of the boosting subunit. The working principle of embodiment 4 is the same as that of embodiment 1, and description thereof will not be repeated here, and in the working engineering of embodiment 4, the driving signal may be applied to the synchronous rectification switch tube for rectification to perform synchronous rectification.
The above description is only of the preferred embodiments of the present invention and is not intended to limit the present invention, but various modifications and variations can be made to the present invention by those skilled in the art. Any modification, equivalent replacement, improvement, etc. made within the spirit and principle of the present invention should be included in the protection scope of the present invention.
Claims (10)
1. The multi-port input non-isolated direct current converter is characterized by comprising at least one boosting subunit and a rectifying energy storage unit, wherein the boosting subunit comprises two boosting circuits with coupling inductors, the first boosting circuits and the second boosting circuits are identical in structure and comprise a direct current power supply, an input filter capacitor, a switching tube, a coupling inductor and a rectifying diode, the coupling inductors are provided with two coils, two endpoints of the first coil are respectively marked as an endpoint 1 and an endpoint 2, two endpoints of the second coil are respectively marked as an endpoint 3 and an endpoint 4, one ends of a positive electrode of the direct current power supply and one end of the input filter capacitor are connected with the endpoint 1of the coupling inductor, the other ends of the negative electrode of the direct current power supply and the input filter capacitor are connected with a source electrode of the switching tube, a drain electrode of the switching tube and an anode of the rectifying diode are connected with the endpoint 2 of the coupling inductor, the negative electrodes of the two direct current power supplies are connected and serve as negative output ends of the boosting units, the cathodes of the two rectifying diodes are connected and serve as first output ends of the boosting subunits, the endpoints of the first boosting units, the endpoints of the first boosting circuits are respectively marked as endpoints 3 and 4, one end of the first coupling inductor is connected with the endpoint 4 of the second coupling inductor, and the second coupling ends of the boosting circuits are respectively; the negative output end and the first output end of each boosting subunit are respectively connected, and the second output ends and the third output ends of two adjacent boosting subunits are sequentially connected;
the rectifying and energy-storing unit comprises a first rectifying diode, a second rectifying diode, a third capacitor, a fourth capacitor, a fifth capacitor and a sixth capacitor, wherein the first rectifying diode and the second rectifying diode are connected in series, the cathode of the first rectifying diode is used as the positive output end of the rectifying and energy-storing unit, the anode of the second rectifying diode is connected with the first output end of the last boosting subunit, and the cathode of the second rectifying diode is connected with the second output end of the last boosting subunit; the third capacitor, the fourth capacitor and the fifth capacitor are sequentially connected in series, one end of the fifth capacitor, which is not connected with the fourth capacitor, is connected with the cathode of the first rectifying diode, one end of the third capacitor, which is connected with the fourth capacitor, is connected with the first output end of the last boosting subunit, and the other end of the third capacitor, which is connected with the negative output end of the last boosting subunit, is used as the negative output end of the rectifying energy storage unit; the third output end of the first boosting subunit is connected with the other end of the fifth capacitor; and two ends of the sixth capacitor are respectively connected with the positive output end and the negative output end of the rectifying and energy-storing unit.
2. The multi-port input non-isolated dc converter of claim 1 wherein the rectifying diode in the boost subunit and the first rectifying diode and the second rectifying diode in the rectifying and energy storage unit are each replaceable with a synchronous rectifying switch having anti-parallel diodes.
3. A multi-port input non-isolated dc converter as claimed in claim 1 or 2 wherein the coupling inductance is an storable inductance with an air gap, the two coils are coupled to each other and the number of turns of the second coil is greater than the number of turns of the first coil.
4. A multi-port input non-isolated dc converter as claimed in claim 3 wherein the boost subunit further comprises an inductor having one end connected to the terminal 4 of the first coupling inductor and the other end serving as a third output of the boost subunit; the inductance is leakage inductance of two coils in the two coupling inductances, or the external inductance is adopted, or the combination of the leakage inductance and the external inductance is adopted.
5. The multi-port input non-isolated dc converter of claim 4, wherein the dc power sources of the two boost circuits in the boost subunit are equal voltage dc power sources or unequal voltage dc power sources, and the voltages of the two dc power sources are less than or equal to one half of the output voltage Vo between the positive output terminal and the negative output terminal of the rectifying and energy-storing unit; the two booster circuits may share one dc power supply.
6. The multi-port input non-isolated DC converter of claim 5 wherein the switching tube in the boost circuit is a high frequency switching tube with anti-parallel diode or a high frequency switching tube equivalent to the same function; the anti-parallel diode is an integrated diode, a parasitic diode or an external diode; the third capacitor, the fourth capacitor and the fifth capacitor are electrolytic capacitors, high-frequency nonpolar capacitors or high-frequency polar capacitors; when the third capacitor, the fourth capacitor and the fifth capacitor are high-frequency capacitors with polarity, the positive electrode of the fifth capacitor is connected with the cathode of the first rectifying diode, the positive electrode of the fourth capacitor is connected with the negative electrode of the fifth capacitor, the negative electrode of the fourth capacitor is connected with the positive electrode of the third capacitor, the positive electrode of the third capacitor is also connected with the first output end of the last boosting subunit, and the negative electrode is connected with the negative output end of the last boosting subunit.
7. The multi-port input non-isolated dc converter of claim 6 wherein the first output of the boost subunit is further configured to serve as an intermediate output voltage terminal for connection to a load for supplying power along with the negative output of the rectifying and energy storage unit.
8. A control method of a multi-port input non-isolated dc converter for controlling the multi-port input non-isolated dc converter according to claim 1 or 2, characterized in that staggered driving of 180 ° or one half of a switching period of a phase stagger is applied to a first switching tube of a first booster circuit and a second switching tube of a second booster circuit in each booster subunit; when the first switching tube is turned on, the first coupling inductor works in a transformer coupling mode and an inductance energy storage mode, and the second coil of the first coupling inductor is coupled with voltage through a transformation ratio and performs series output work with the second coil of the second coupling inductor through inductance energy release freewheeling; when the second switching tube is turned on, the second coupling inductor works in a transformer coupling mode and an inductance energy storage mode, and the second coil of the second coupling inductor is coupled with voltage through a transformation ratio and performs series output work with the second coil of the first coupling inductor through inductance energy release freewheeling.
9. The method according to claim 8, wherein the duty ratio applied to the first switching tube and the second switching tube is 0.5 or more, so that the first switching tube, the second switching tube and the third capacitor obtain a lower voltage stress than when the duty ratio is less than 0.5.
10. The method according to claim 8 or 9, wherein when a synchronous rectification switching tube having an anti-parallel diode is used in the boost circuit, the driving signal is applied to the synchronous rectification switching tube for rectification to perform synchronous rectification.
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