CN117420519A - Broadband radio frequency emission channel amplitude and phase fluctuation correction system based on photon declivity reception - Google Patents
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
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Abstract
A broadband radio frequency emission channel amplitude-phase fluctuation correction system based on photon declivity reception belongs to the technical field of microwave photon radars and solves the problem of how to correct the amplitude-phase fluctuation of the broadband radio frequency emission channel; the input end of the broadband radio frequency emission channel is connected with the output end of the digital demodulation parameter extraction unit, the output end of the broadband radio frequency emission channel is connected with the input end of the broadband photon declivity receiving link, and the output end of the broadband photon declivity receiving link is connected with the input end of the digital demodulation parameter extraction unit; the method comprises the steps of generating a radio frequency broadband LFM signal by a broadband radio frequency transmitting channel, digitally collecting the radio frequency broadband LFM signal by a broadband photon declivity receiving link by converting the radio frequency broadband LFM signal into a point frequency signal with low intermediate frequency, demodulating transmitting channel amplitude and phase fluctuation information carried in the outgoing frequency broadband LFM signal by a digital demodulation parameter extracting unit, generating channel amplitude and phase correction parameters, and realizing the amplitude and phase fluctuation correction of the broadband radio frequency transmitting channel in a digital predistortion mode.
Description
Technical Field
The invention belongs to the technical field of microwave photon radars, and relates to a broadband radio frequency emission channel amplitude-phase fluctuation correction system based on photon declivity reception.
Background
The range resolution of the imaging radar is:
where c is the speed of light and B is the bandwidth of the imaging radar pulse.
In order to realize imaging with higher precision, the instantaneous working bandwidth of an imaging radar system is wider and wider, and the working bandwidth of the imaging radar can reach several GHz or even tens GHz (10 9 Hertz).
However, not only the bandwidth of the imaging radar system is affected, but also the nonlinear fluctuation of the amplitude and phase of the radio frequency channel of the radar system can cause the degradation of the imaging quality. As shown in fig. 6 (a) and 6 (b), one-dimensional distance pulse pressure imaging simulation is performed using LFM (linear frequency modulation) signals, fig. 6 (a) is a pulse pressure result of an ideal LFM signal, and fig. 6 (b) is a distorted LFM signal pulse pressure result affected by nonlinear fluctuation of channel amplitude and phase. The nonlinear fluctuation of the channel amplitude and the phase causes the amplitude phase distortion of the LFM signal, and the problems of main lobe widening, side lobe rising, stray echo and the like of a one-dimensional range profile after pulse pressure occur.
To achieve higher imaging effects, correction of in-band amplitude-phase fluctuations of the radio frequency channel is required. Under the imaging radar system of analog declining reception, ultra-wideband signals can be generated in a frequency multiplication mode, but the prior digital technology is difficult to directly carry out digital acquisition and amplitude-phase fluctuation correction on radio frequency signals with bandwidths above GHz.
The sampling rate of the high-end oscilloscope can reach 100Gsps (10 9 Sampling points per second) above, the analog bandwidth can reach above 50GHz, but the direct satisfaction of the broadband radio frequency signal in imaging application is still difficultDigital acquisition requirements (e.g., millimeter wave automotive radar, terahertz imaging applications). In addition, in-band amplitude and phase fluctuation correction using meters is costly and difficult to use for frequent correction when imaging radar is used in engineering applications. Therefore, the amplitude and phase fluctuation correction method of the broadband radio frequency emission channel becomes a difficulty in improving the imaging quality of the radar.
In the prior art, the amplitude-phase correction of the radio frequency channel is mainly performed through the digital correction of channel amplitude-phase fluctuation in a broadband digital acquisition mode. Taking channel amplitude and phase fluctuation correction based on a least square method as an example, the method mainly comprises the following implementation processes: 1) Injecting an ideal LFM signal into a digital transmitting channel to obtain a distorted LFM signal with channel amplitude and phase fluctuation; 2) Digitally acquiring the distorted LFM signal by using a broadband digital acquisition board to obtain a digital LFM signal; performing frequency domain division on the frequency spectrum of the ideal LFM signal and the digitized distorted LFM signal to obtain the frequency response of a transmitting channel; 3) Constructing a frequency factor matrix, and using a frequency domain least square method to fit to obtain an FIR filter coefficient for channel amplitude-phase equalization; 4) And performing predistortion treatment on the transmitted LFM signal by using an amplitude-phase equalization FIR filter to obtain an amplitude-phase corrected LFM signal output.
The method for correcting the in-band amplitude and phase fluctuation by the broadband digital acquisition and digital predistortion technology has higher universality because the radio frequency receiving and transmitting system is used for generating signals and acquiring signals based on the digital technology, but in an ultra-broadband imaging radar system, the digital acquisition technology is difficult to realize direct digital acquisition of radio frequency signals with the bandwidth of several GHz. In addition, similar correction techniques include frequency modulation nonlinearity correction methods that implement a chirped light source by means of coherent detection and active feedback, such as the literature "nonlinear correction review of frequency modulated continuous wave lidar measurement techniques" (Li Chaolin et al, photoengineering, vol 49, no.7, 2022), but whose light source frequency modulation nonlinearity is primarily achieved by detecting the frequency nonlinearity of the light signal from heterodyning, and by directly modulating the light source to achieve instantaneous frequency adjustment of the output light signal.
Disclosure of Invention
The invention aims to solve the technical problem of correcting amplitude and phase fluctuation of a broadband radio frequency transmission channel.
The invention solves the technical problems through the following technical scheme:
a broadband radio frequency emission channel amplitude and phase fluctuation correction system based on photon declivity reception, comprising: the broadband photon declivity receiving device comprises a broadband radio frequency transmitting channel (1), a broadband photon declivity receiving link (2) and a digital demodulation parameter extracting unit (3); the input end of the broadband radio frequency emission channel (1) is connected with the output end of the digital demodulation parameter extraction unit (3), the output end of the broadband radio frequency emission channel (1) is connected with the input end of the broadband photon declivity receiving link (2), and the output end of the broadband photon declivity receiving link (2) is connected with the input end of the digital demodulation parameter extraction unit (3); a broadband radio frequency emission channel (1) is adopted to generate a radio frequency broadband LFM signal, a broadband photon declivity receiving link (2) is adopted to convert the radio frequency broadband LFM signal into a point frequency signal with low intermediate frequency for digital acquisition, a digital demodulation parameter extraction unit (3) is adopted to demodulate emission channel amplitude and phase fluctuation information carried in the emission channel broadband LFM signal, channel amplitude and phase correction parameters are generated, and broadband radio frequency emission channel amplitude and phase fluctuation correction is realized in a digital predistortion mode.
Further, the broadband radio frequency transmitting channel comprises a digital-to-analog converter (10), a first filter (11), a mixer (12), a second filter (13), a first amplifier (14), a frequency multiplier (15), a third filter (16) and a second amplifier (17) which are connected in sequence; the input end of the digital-to-analog converter (10) is used as the input end of the broadband radio frequency emission channel (1) to be connected with the output end of the digital demodulation parameter extraction unit (3), and the output end of the second amplifier (17) is used as the output end of the broadband radio frequency emission channel (1) to be connected with the input end of the broadband photon declivity receiving link (2).
Further, the broadband photon declivity receiving link (2) comprises: the device comprises a laser (20), an electro-optical modulator (21), an optical filter (22), a first optical power divider (23), a delay optical fiber (24), a frequency shifting unit (25), a second optical power divider (26) and a detector (27); the laser (20), the electro-optical modulator (21), the optical filter (22) and the first optical power divider (23) are sequentially connected, and one input end of the electro-optical modulator (21) is used as an input end of the broadband photon declivity receiving link (2) and is connected with the output end of the second amplifier (17); the output end of the first optical power divider (23) is connected with the input end of the delay optical fiber (24) and the input end of the frequency shift unit (25), the output end of the delay optical fiber (24) is connected with the input end of the second optical power divider (26), and the output end of the frequency shift unit (25) is connected with the input end of the second optical power divider (26); the output end of the second optical power divider (26) is connected with the input end of the detector (27), and the output end of the detector (27) is used as the output end of the broadband photon declivity receiving link (2) and is connected with the input end of the digital demodulation parameter extraction unit (3).
Further, the digital demodulation parameter extraction unit (3) comprises an analog-to-digital converter (30), a digital demodulator (31) and an amplitude-phase fluctuation parameter extractor (32) which are connected in sequence; the input end of the analog-digital converter (30) is used as the input end of the digital demodulation parameter extraction unit (3) to be connected with the output end of the detector (27), and the output end of the amplitude-phase fluctuation parameter extractor (32) is used as the output end of the digital demodulation parameter extraction unit (3) to be connected with the input end of the digital-analog converter (10).
Further, the workflow of the system is as follows: the digital-to-analog converter (10) generates a baseband LFM signal, the baseband LFM signal is subjected to frequency conversion to an intermediate frequency through the mixer (12) after passing through the first filter (11), the intermediate frequency signal is subjected to filtering through the second filter (13), then is amplified through the first amplifier (14), and is subjected to frequency multiplication to a radio frequency working frequency band through the frequency multiplier (15), at the moment, the bandwidth of the LFM signal is also multiplied, and finally, the broadband LFM signal is subjected to filtering amplification through the third filter (16) and the second amplifier (17) and then is output to the electro-optic modulator (21); the optical carrier wave output by the laser (20) is injected into the electro-optical modulator (21), and the radio frequency broadband LFM signal output by the broadband radio frequency transmission channel (1) is modulated into an optical carrier LFM signal by the electro-optical modulator (21); controlling bias voltage input, setting an electro-optical modulator (21) to work at a zero bias point, wherein an optical signal output by the electro-optical modulator (21) is a double-sideband carrier suppression signal, filtering one sideband by the double-sideband carrier suppression signal output by the electro-optical modulator (21) through an optical filter (22), dividing the rest single-sideband carrier suppression signal into two paths by a first optical power divider (23), introducing an optical carrier LFM signal on the upper path into a transmission delay difference with a lower path through an optical fiber delay line (24), and realizing frequency shifting of the input optical signal by a frequency shifting unit (25); the optical signals of the upper path and the lower path are coherently combined through a second optical power divider (26), and the output optical signals are injected into a detector (27) for photoelectric conversion; the analog-to-digital converter (30) collects the electric signal after photoelectric conversion, after signal demodulation is carried out by the digital demodulator (31), the LFM signal containing the channel amplitude and phase fluctuation parameters can be obtained, then the orthogonal down-conversion processing is carried out in the digital domain by the amplitude and phase fluctuation parameter extractor (32), the amplitude and phase fluctuation parameters carried by the distorted LFM signal are extracted, thus the digital predistortion channel correction parameters are generated, and the digital predistortion channel correction parameters are sent into the broadband radio frequency transmission channel for transmission predistortion.
Further, the method for extracting the amplitude and phase fluctuation parameters carried by the distorted LFM signal is as follows:
let the local oscillator frequency of quadrature down-conversion be f if The digitally demodulated signal is:
the digital zero intermediate frequency signal is obtained after the ideal linear frequency modulation signal passes through a photon declivity receiving channel correction system;
let the amplitude-phase characteristics of the ideal system be:
the amplitude-phase characteristic distortion of an actual system is decomposed into the sum of infinite simple harmonic distortion, and the amplitude-phase characteristic of the system containing the distortion is expressed as:
its amplitude-frequency characteristic surrounds a constant value a 0 With cosine wobble, the phase-frequency characteristic surrounding 2 pi b 0 f, performing sinusoidal oscillation; a, a i And c i Respectively representing the amplitude and the change frequency of amplitude-frequency characteristic fluctuation, b i And d i The amplitude and the change frequency of the fluctuation of the phase frequency characteristic are respectively represented;
when the LFM signal passes through the distorted system, if the amplitude-phase distortion is a gradual function of frequency, the output signal corresponds to the product of the frequency domain distortion and the LFM signal, namely:
v out (t)＝H′(γt)v in (t)
when the input chirp signal contains systematic amplitude phase distortion:
v rf (t)＝V rf ·A′(γt)·sin(ω rf t+πγt 2 +ψ′(γt))
wherein the amplitude fluctuation and phase fluctuation parameters are expressed as follows:
A′(γt)＝|H′(γt)|
ψ′(γt)＝Arg[H′(γt)]
the distorted LFM signal is injected into a photon declivity receiving channel correction system, and the complex intermediate frequency signal after digital demodulation is:
when the delay difference tau is small, the small signal approximation is taken from the first-order Bessel term in the signal amplitude, and then the amplitude term of the complex IQ signal is as follows:
the above formula includes the amplitude-frequency response A' (f) of the system;
the phase terms of the complex IQ signal are:
Pha IQ ＝2πγτt+ω 0 τ+2πf rf0 τ+πγτ 2 +ψ′(γt+γτ)-ψ′(γt)
wherein 2πγτt+ω 0 τ+2πf rf0 τ+πγτ 2 As linear terms, the nonlinear terms remaining after removal by linear fitting are:
Pha IQ_nonlinear ＝ψ′(γt+γτ)-ψ′(γt)
the above equation gives the instantaneous phase change amount caused by the phase frequency fluctuation, i.e. compared with the instantaneous frequency drift of the ideal chirp signal, the accumulated integration is performed on the rest nonlinear phase terms to obtain the nonlinear phase error ψ '(γt) of the chirp, i.e. the phase frequency response ψ' (f) of the system.
Further, the frequency shift unit (25) includes: an acousto-optic frequency shifter (251) and a microwave source (252); the output end of the first optical power divider (23) is connected with the first input end of the acousto-optic frequency shifter (251), and the output end of the delay optical fiber (24) is connected with the input end of the second optical power divider (26); the second input end of the acousto-optic frequency shifter (251) is connected with the microwave source (252), and the output end of the acousto-optic frequency shifter (251) is connected with the input end of the second optical power divider (26).
Further, the frequency shift unit (25) includes: a microwave source (252), a double parallel modulator (253), a phase shifter (254), a third power divider (255); the output end of the first optical power divider (23) is connected with the first input end of the double-parallel modulator (253), the output end of the microwave source (252) is connected with the input end of the third power divider (255), the output end of the third power divider (255) is connected with the input end of the phase shifter (254) and the second input end of the double-parallel modulator (253), the output end of the phase shifter (254) is connected with the third input end of the double-parallel modulator (253), and the output end of the double-parallel modulator (253) is connected with the input end of the second optical power divider (26).
Further, the detector (27) is a single photodetector or a balanced photodetector.
Further, the fiber delay line (24) is replaced by an adjustable fiber delay line.
The invention has the advantages that:
the invention adopts the broadband radio frequency emission channel to generate radio frequency broadband LFM signals, adopts the broadband photon declivity receiving link to convert the radio frequency broadband LFM signals into point frequency signals with low intermediate frequency for digital acquisition, and reduces the ADC sampling rate requirement of digital amplitude phase correction; demodulating the amplitude and phase fluctuation information of the transmitting channel carried in the outgoing frequency broadband LFM signal by adopting a digital demodulation parameter extraction unit, generating channel amplitude and phase correction parameters, and realizing the amplitude and phase fluctuation correction of the broadband radio frequency transmitting channel in a digital predistortion mode; according to the invention, the broadband LFM signal is converted into the low intermediate frequency signal for digital acquisition in a photon declining receiving mode, so that the requirement on performance index of the digital acquisition ADC is low; the method comprises the steps of dividing an optical carrier LFM signal into two paths, introducing a small transmission delay difference and then carrying out coherent beat frequency, and digitally demodulating channel amplitude and phase fluctuation information carried on the LFM signal from the beat frequency signal, thereby realizing amplitude and phase fluctuation correction of a broadband transmitting channel.
Drawings
FIG. 1 is a block diagram of a system for correcting amplitude and phase fluctuation of a broadband radio frequency emission channel of a photon declivity receiving link based on frequency shift of an acousto-optic frequency shifter according to an embodiment of the present invention;
FIG. 2 is a block diagram of a system for correcting amplitude and phase fluctuation of a broadband radio frequency emission channel of a photon declivity receiving link based on frequency shift of an acousto-optic frequency shifter according to a second embodiment of the present invention;
FIG. 3 is a block diagram of a system for correcting amplitude and phase fluctuations of a broadband radio frequency emission channel of a photon declivity receiving link based on frequency shift of a dual-parallel modulator according to a third embodiment of the present invention;
FIG. 4 is a block diagram of a system for correcting amplitude and phase fluctuations of a broadband radio frequency emission channel of a photon declivity receiving link based on frequency shift of a dual-parallel modulator according to a fourth embodiment of the present invention;
FIG. 5 (a) shows amplitude and phase nonlinear heave parameters set by the simulation test of the present invention;
FIG. 5 (b) is amplitude and phase error information demodulated by the simulation test of the present invention;
FIG. 6 (a) is a one-dimensional distance pulse pressure imaging diagram of an ideal LFM signal;
fig. 6 (b) is a one-dimensional distance pulse pressure imaging diagram of a distorted LFM signal.
Detailed Description
For the purpose of making the objects, technical solutions and advantages of the embodiments of the present invention more apparent, the technical solutions in the embodiments of the present invention will be clearly and completely described in the following in conjunction with the embodiments of the present invention, and it is apparent that the described embodiments are some embodiments of the present invention, but not all embodiments. All other embodiments, which can be made by those skilled in the art based on the embodiments of the invention without making any inventive effort, are intended to be within the scope of the invention.
The technical scheme of the invention is further described below with reference to the attached drawings and specific embodiments:
example 1
As shown in fig. 1, a block diagram of a system for correcting amplitude and phase fluctuation of a broadband radio frequency emission channel of a photon declivity receiving link based on frequency shift of an acousto-optic frequency shifter according to a first embodiment of the present invention includes: the broadband photon declivity receiving device comprises a broadband radio frequency transmitting channel (1), a broadband photon declivity receiving link (2) and a digital demodulation parameter extracting unit (3); the input end of the broadband radio frequency emission channel (1) is connected with the output end of the digital demodulation parameter extraction unit (3), the output end of the broadband radio frequency emission channel (1) is connected with the input end of the broadband photon declivity receiving link (2), and the output end of the broadband photon declivity receiving link (2) is connected with the input end of the digital demodulation parameter extraction unit (3).
The broadband radio frequency emission channel (1) is used for converting a baseband LFM signal into a radio frequency broadband LFM signal; the broadband radio frequency transmitting channel comprises a digital-to-analog converter (10), a first filter (11), a mixer (12), a second filter (13), a first amplifier (14), a frequency multiplier (15), a third filter (16) and a second amplifier (17) which are connected in sequence; the input end of the digital-to-analog converter (10) is used as the input end of the broadband radio frequency emission channel (1) to be connected with the output end of the digital demodulation parameter extraction unit (3), and the output end of the second amplifier (17) is used as the output end of the broadband radio frequency emission channel (1) to be connected with the input end of the broadband photon declivity receiving link (2).
The broadband photon declivity receiving link (2) comprises: the device comprises a laser (20), an electro-optical modulator (21), an optical filter (22), a first optical power divider (23), a delay optical fiber (24), a frequency shifting unit (25), a second optical power divider (26) and a detector (27), wherein the detector (27) adopts a single photoelectric detector; the frequency shift unit (25) includes: an acousto-optic frequency shifter (251) and a microwave source (252); the laser (20), the electro-optical modulator (21), the optical filter (22) and the first optical power divider (23) are sequentially connected, and one input end of the electro-optical modulator (21) is used as an input end of the broadband photon declivity receiving link (2) and is connected with the output end of the second amplifier (17); the output end of the first optical power divider (23) is connected with the input end of the delay optical fiber (24) and the first input end of the acousto-optic frequency shifter (251), and the output end of the delay optical fiber (24) is connected with the input end of the second optical power divider (26); the second input end of the acousto-optic frequency shifter (251) is connected with the microwave source (252), and the output end of the acousto-optic frequency shifter (251) is connected with the input end of the second optical power divider (26); the output end of the second optical power divider (26) is connected with the input end of the detector (27), and the output end of the detector (27) is used as the output end of the broadband photon declivity receiving link (2) and is connected with the input end of the digital demodulation parameter extraction unit (3).
The fiber delay line (24) may be replaced with an adjustable fiber delay line.
The digital demodulation parameter extraction unit (3) comprises an analog-digital converter (30), a digital demodulator (31) and an amplitude-phase fluctuation parameter extractor (32) which are connected in sequence; the input end of the analog-digital converter (30) is used as the input end of the digital demodulation parameter extraction unit (3) to be connected with the output end of the detector (27), and the output end of the amplitude-phase fluctuation parameter extractor (32) is used as the output end of the digital demodulation parameter extraction unit (3) to be connected with the input end of the digital-analog converter (10).
The working flow of the broadband radio frequency emission channel amplitude-phase fluctuation correction system of the embodiment is as follows:
the digital-to-analog converter (10) generates a baseband LFM signal, the baseband LFM signal is subjected to frequency conversion to an intermediate frequency through the mixer (12) after passing through the first filter (11), the intermediate frequency signal is subjected to filtering through the second filter (13), then is amplified through the first amplifier (14), and is subjected to frequency multiplication to a radio frequency working frequency band through the frequency multiplier (15), at the moment, the bandwidth of the LFM signal is also multiplied, and finally, the broadband LFM signal is subjected to filtering amplification through the third filter (16) and the second amplifier (17) and then is output to the electro-optic modulator (21); the optical carrier wave output by the laser (20) is injected into the electro-optical modulator (21), and the radio frequency broadband LFM signal output by the broadband radio frequency transmission channel (1) is modulated into an optical carrier LFM signal by the electro-optical modulator (21); controlling bias voltage input, setting an electro-optical modulator (21) to work at a zero bias point, wherein an optical signal output by the electro-optical modulator (21) is a double-sideband carrier suppression signal, filtering one sideband by the double-sideband carrier suppression signal output by the electro-optical modulator (21) through an optical filter (22), dividing the rest single-sideband carrier suppression signal into two paths by a first optical power divider (23), introducing an optical carrier LFM signal on the upper path into a transmission delay difference with a lower path through an optical fiber delay line (24), and realizing frequency shifting of the input optical signal by an acousto-optic frequency shifter (251), wherein the frequency shifting frequency is the frequency of a microwave signal loaded by a microwave source (252); the optical signals of the upper path and the lower path are coherently combined through a second optical power divider (26), and the output optical signals are injected into a detector (27) for photoelectric conversion; the analog-to-digital converter (30) collects the electric signal after photoelectric conversion, after signal demodulation is carried out by the digital demodulator (31), the LFM signal containing the channel amplitude and phase fluctuation parameters can be obtained, then the orthogonal down-conversion processing is carried out in the digital domain by the amplitude and phase fluctuation parameter extractor (32), the amplitude and phase fluctuation parameters carried by the distorted LFM signal are extracted, thus the digital predistortion channel correction parameters are generated, and the digital predistortion channel correction parameters are sent into the broadband radio frequency transmission channel for transmission predistortion.
The signal demodulation process is as follows:
the chirp signal is modulated onto the optical carrier by an electro-optic modulator (21), the electro-optic modulator (21) operating at a zero bias point. Taking the single drive electro-optic modulator (21) as an example, the output optical signal can be expressed as:
wherein E is 0 For light field amplitude, omega 0 Is the angular frequency of the optical carrier, V π For the half-wave voltage of the modulator,v rf (t) is a radio frequency modulated signal, V bias Biasing a modulator;
the radio frequency modulated signal can be expressed as:
v rf (t)＝V rf ·sin(2πf rf0 t+πγt 2 )
wherein V is rf For the amplitude of the linear frequency-modulated signal, f rf0 For the initial frequency of the chirp signal, gamma is the chirp rate, instantaneous frequency f of the chirp signal rf ＝f rf0 +γt。
At zero bias point, the electro-optic modulator (21) has a bias voltage of V bias ＝V π The optical carrier component in the output optical signal is suppressed, the electro-optical modulator (21) outputs the optical signal to filter out the positive first-order modulation sideband through the optical filter (22), and the output optical signal is simplified into:
wherein J is 1 Is a first order Bessel function.
The optical signal modulated by the single sideband is divided into two paths by a first optical power divider (23), and the optical field signal after the optical signal is delayed by a delay fiber (24) in the upper path is expressed as:
the audio frequency of the sound and light of the down path is f if The microwave-shifted optical field signal of (2) is represented as:
after being combined by the second optical power divider (26), the light field entering the detector (27) is as follows:
the detector (27) converts the light field into an electrical signal output:
wherein Z is the radio frequency output impedance of the detector (27), and eta is the photoelectric conversion responsivity of the detector (27).
From the above, the signal after photon declivity and photoelectric conversion is equal to (f if - γτ), in this embodiment, the delay τ of the two paths of optical signals is very small, so that the frequency of the point frequency signal is close to that of the frequency-shifted microwave signal source, and is a low-frequency signal, and the point frequency signal can be digitally acquired through a mature commercial analog-digital converter.
The electric signal output by the detector (27) is collected by an analog-to-digital converter (30), and then is subjected to quadrature down-conversion processing in the digital domain to extract amplitude and phase information. The local oscillation frequency of quadrature down-conversion is f if The digitally demodulated signal is:
the digital zero intermediate frequency signal is obtained after the ideal linear frequency modulation signal passes through the photon declivity receiving channel correction system.
Next consider the problem of amplitude phase nonlinear fluctuations in the wideband signal generation channel, assuming that the amplitude phase characteristics of an ideal system are:
the amplitude-phase characteristic distortion of an actual system can be decomposed into the sum of infinite simple harmonic distortion, and the amplitude-phase characteristic of the system containing the distortion can be expressed as:
its amplitude-frequency characteristic surrounds a constant value a 0 With cosine wobble, the phase-frequency characteristic surrounding 2 pi b 0 f, performing sinusoidal oscillation; a, a i And c i Respectively representing the amplitude and the change frequency of amplitude-frequency characteristic fluctuation, b i And d i The amplitude and the change frequency of the phase-frequency characteristic fluctuation are respectively represented.
When the LFM signal passes through the distorted system, if the amplitude-phase distortion is a gradual function of frequency, the output signal corresponds to the product of the frequency domain distortion and the LFM signal, namely:
v out (t)＝H′(γt)v in (t)
when the input chirp signal contains systematic amplitude phase distortion:
v rf (t)＝V rf ·A′(γt)·sin(ω rf t+πγt 2 +ψ′(γt))
wherein the amplitude fluctuation and phase fluctuation parameters are expressed as follows:
A′(γt)＝|H′(γt)|
ψ′(γt)＝Arg[H′(γt)]
the distorted LFM signal is injected into a photon declivity receiving channel correction system, and the complex intermediate frequency signal after digital demodulation is:
when the delay difference tau is small, the small signal approximation is taken from the first-order Bessel term in the signal amplitude, and then the amplitude term of the complex IQ signal is as follows:
the above equation includes the amplitude-frequency response a' (f) of the system.
The phase terms of the complex IQ signal are:
Pha IQ ＝2πγτt+ω 0 τ+2πf rf0 τ+πγτ 2 +ψ′(γt+γτ)-ψ′(γt)
wherein the method comprises the steps of，2πγτt+ω 0 τ+2πf rf0 τ+πγτ 2 As linear terms, the nonlinear terms remaining after removal by linear fitting are:
Pha IQ_nonlinear ＝ψ′(γt+γτ)-ψ′(γt)
the instantaneous phase change amount caused by the phase frequency fluctuation is reflected, namely, the instantaneous frequency drift compared with an ideal linear frequency modulation signal. The remaining nonlinear phase terms are integrated cumulatively to obtain the nonlinear phase error ψ '(γt) of the chirp, i.e. the phase frequency response ψ' (f) of the system.
In summary, the amplitude and phase fluctuation parameters of the transmitting channel carried by the distorted LFM signal can be extracted through photon deskew and digital demodulation, so as to generate digital predistortion channel correction parameters, and the digital predistortion channel correction parameters are sent to the transmitting channel for transmitting predistortion.
Example two
As shown in fig. 2, the frame diagram of the wideband radio frequency emission channel amplitude-phase fluctuation correction system of the photon declivity receiving link based on frequency shift of the acousto-optic frequency shifter according to the second embodiment of the present invention is different from the wideband radio frequency emission channel amplitude-phase fluctuation correction system of the first embodiment in that the detector (27) of the present embodiment adopts a balanced photoelectric detector, and the signal-to-noise ratio of the receiving can be improved by adopting the balanced photoelectric detector.
Example III
As shown in fig. 3, which is a block diagram of a wideband radio frequency emission channel amplitude-phase fluctuation correction system according to a third embodiment of the present invention, unlike the wideband radio frequency emission channel amplitude-phase fluctuation correction system according to the first embodiment, a dual-parallel modulator is used to replace an acousto-optic frequency shifter to perform optical frequency shift, so as to implement intermediate frequency signal deskewing; the frequency shift unit (25) of the present embodiment includes: a microwave source (252), a double parallel modulator (253), a phase shifter (254), a third power divider (255); the output end of the first optical power divider (23) is connected with the input end of the delay optical fiber (24) and the first input end of the double-parallel modulator (253), the output end of the microwave source (252) is connected with the input end of the third power divider (255), the output end of the third power divider (255) is connected with the input end of the phase shifter (254) and the second input end of the double-parallel modulator (253), the output end of the phase shifter (254) is connected with the third input end of the double-parallel modulator (253), and the output end of the double-parallel modulator (253) is connected with the input end of the second optical power divider (26).
The working flow of the broadband radio frequency emission channel amplitude-phase fluctuation correction system of the embodiment is as follows:
the digital-to-analog converter (10) generates a baseband LFM signal, the baseband LFM signal is subjected to frequency conversion to an intermediate frequency through the mixer (12) after passing through the first filter (11), the intermediate frequency signal is subjected to filtering through the second filter (13), then is amplified through the first amplifier (14), and is subjected to frequency multiplication to a radio frequency working frequency band through the frequency multiplier (15), at the moment, the bandwidth of the LFM signal is also multiplied, and finally, the broadband LFM signal is subjected to filtering amplification through the third filter (16) and the second amplifier (17) and then is output to the electro-optic modulator (21); the optical carrier wave output by the laser (20) is injected into the electro-optical modulator (21), and the radio frequency broadband LFM signal output by the broadband radio frequency transmission channel (1) is modulated into an optical carrier LFM signal by the electro-optical modulator (21); controlling bias voltage input, setting an electro-optical modulator (21) to work at a zero bias point, wherein an optical signal output by the electro-optical modulator (21) is a double-sideband carrier suppression signal, filtering one sideband by the double-sideband carrier suppression signal output by the electro-optical modulator (21) through an optical filter (22), dividing the rest single-sideband carrier suppression signal into two paths by a first optical power divider (23), introducing a transmission delay difference between an upper optical carrier LFM signal and a lower optical path through an optical fiber delay line (24), loading two paths of microwave signals with the same amplitude and 90-degree phase difference by the lower optical carrier LFM signal through a double-parallel modulator (253), setting the bias voltage of the double-parallel modulator (253) to be in a single-sideband modulation working state, and setting the optical signal output by the double-parallel modulator (253) to be a frequency shift signal of an input optical signal and the frequency shift of the loaded microwave signal; the microwave signals output by the microwave source (252) generate two paths of microwave signals with the same amplitude and 90-degree phase difference through the third power divider (255) and the phase shifter (254), the two paths of microwave signals are respectively loaded onto two sub-modulators of the double-parallel modulator (253), the optical signals on the upper path and the lower path are coherently combined through one 2X 2 equal-proportion optical power divider, and the output optical signals are injected into the detector (27) for photoelectric conversion; the analog-to-digital converter (30) collects the electric signal after photoelectric conversion, after signal demodulation is carried out by the digital demodulator (31), the LFM signal containing the channel amplitude and phase fluctuation parameters can be obtained, then the orthogonal down-conversion processing is carried out in the digital domain by the amplitude and phase fluctuation parameter extractor (32), the amplitude and phase fluctuation parameters carried by the distorted LFM signal are extracted, thus the digital predistortion channel correction parameters are generated, and the digital predistortion channel correction parameters are sent into the broadband radio frequency transmission channel for transmission predistortion.
Example IV
As shown in fig. 4, a block diagram of a wideband rf transmission channel amplitude-phase fluctuation correction system according to a fourth embodiment of the present invention is different from the wideband rf transmission channel amplitude-phase fluctuation correction system according to the third embodiment in that the detector (27) of the present embodiment adopts a balanced photodetector, and the signal-to-noise ratio of the reception can be improved by adopting the balanced photodetector.
Simulation test
By adopting the technical scheme of the invention, the extraction simulation of the amplitude-phase fluctuation correction parameters of the broadband radio frequency transmission channel is carried out, wherein (a) of fig. 5 is set amplitude and phase nonlinear fluctuation parameters, and (b) of fig. 5 is demodulated amplitude and phase error information; as can be seen from simulation results, the amplitude and phase nonlinear fluctuation parameters obtained by the technical scheme of the invention are basically consistent with the original setting, and certain errors exist at the edge of the working frequency band due to the frequency response problem of the pulse signal edge.
The above embodiments are only for illustrating the technical solution of the present invention, and are not limiting; although the invention has been described in detail with reference to the foregoing embodiments, it will be understood by those of ordinary skill in the art that: the technical scheme described in the foregoing embodiments can be modified or some technical features thereof can be replaced by equivalents; such modifications and substitutions do not depart from the spirit and scope of the technical solutions of the embodiments of the present invention.
Claims (10)
1. Broadband radio frequency emission channel amplitude and phase fluctuation correction system based on photon declivity reception, which is characterized by comprising: the broadband photon declivity receiving device comprises a broadband radio frequency transmitting channel (1), a broadband photon declivity receiving link (2) and a digital demodulation parameter extracting unit (3); the input end of the broadband radio frequency emission channel (1) is connected with the output end of the digital demodulation parameter extraction unit (3), the output end of the broadband radio frequency emission channel (1) is connected with the input end of the broadband photon declivity receiving link (2), and the output end of the broadband photon declivity receiving link (2) is connected with the input end of the digital demodulation parameter extraction unit (3); a broadband radio frequency emission channel (1) is adopted to generate a radio frequency broadband LFM signal, a broadband photon declivity receiving link (2) is adopted to convert the radio frequency broadband LFM signal into a point frequency signal with low intermediate frequency for digital acquisition, a digital demodulation parameter extraction unit (3) is adopted to demodulate emission channel amplitude and phase fluctuation information carried in the emission channel broadband LFM signal, channel amplitude and phase correction parameters are generated, and broadband radio frequency emission channel amplitude and phase fluctuation correction is realized in a digital predistortion mode.
2. The broadband radio frequency emission channel amplitude-phase fluctuation correction system based on photon declivity reception according to claim 1, wherein the broadband radio frequency emission channel comprises a digital-to-analog converter (10), a first filter (11), a mixer (12), a second filter (13), a first amplifier (14), a frequency multiplier (15), a third filter (16) and a second amplifier (17) which are connected in sequence; the input end of the digital-to-analog converter (10) is used as the input end of the broadband radio frequency emission channel (1) to be connected with the output end of the digital demodulation parameter extraction unit (3), and the output end of the second amplifier (17) is used as the output end of the broadband radio frequency emission channel (1) to be connected with the input end of the broadband photon declivity receiving link (2).
3. Broadband radio frequency emission channel amplitude and phase fluctuation correction system based on photon declivity reception according to claim 2, characterized in that said broadband photon declivity reception link (2) comprises: the device comprises a laser (20), an electro-optical modulator (21), an optical filter (22), a first optical power divider (23), a delay optical fiber (24), a frequency shifting unit (25), a second optical power divider (26) and a detector (27); the laser (20), the electro-optical modulator (21), the optical filter (22) and the first optical power divider (23) are sequentially connected, and one input end of the electro-optical modulator (21) is used as an input end of the broadband photon declivity receiving link (2) and is connected with the output end of the second amplifier (17); the output end of the first optical power divider (23) is connected with the input end of the delay optical fiber (24) and the input end of the frequency shift unit (25), the output end of the delay optical fiber (24) is connected with the input end of the second optical power divider (26), and the output end of the frequency shift unit (25) is connected with the input end of the second optical power divider (26); the output end of the second optical power divider (26) is connected with the input end of the detector (27), and the output end of the detector (27) is used as the output end of the broadband photon declivity receiving link (2) and is connected with the input end of the digital demodulation parameter extraction unit (3).
4. A broadband radio frequency emission channel amplitude and phase fluctuation correction system based on photon declivity reception according to claim 3, wherein the digital demodulation parameter extraction unit (3) comprises an analog-digital converter (30), a digital demodulator (31) and an amplitude and phase fluctuation parameter extractor (32) which are connected in sequence; the input end of the analog-digital converter (30) is used as the input end of the digital demodulation parameter extraction unit (3) to be connected with the output end of the detector (27), and the output end of the amplitude-phase fluctuation parameter extractor (32) is used as the output end of the digital demodulation parameter extraction unit (3) to be connected with the input end of the digital-analog converter (10).
5. The broadband radio frequency emission channel amplitude and phase fluctuation correction system based on photon deskew reception according to claim 4, wherein the workflow of the system is as follows: the digital-to-analog converter (10) generates a baseband LFM signal, the baseband LFM signal is subjected to frequency conversion to an intermediate frequency through the mixer (12) after passing through the first filter (11), the intermediate frequency signal is subjected to filtering through the second filter (13), then is amplified through the first amplifier (14), and is subjected to frequency multiplication to a radio frequency working frequency band through the frequency multiplier (15), at the moment, the bandwidth of the LFM signal is also multiplied, and finally, the broadband LFM signal is subjected to filtering amplification through the third filter (16) and the second amplifier (17) and then is output to the electro-optic modulator (21); the optical carrier wave output by the laser (20) is injected into the electro-optical modulator (21), and the radio frequency broadband LFM signal output by the broadband radio frequency transmission channel (1) is modulated into an optical carrier LFM signal by the electro-optical modulator (21); controlling bias voltage input, setting an electro-optical modulator (21) to work at a zero bias point, wherein an optical signal output by the electro-optical modulator (21) is a double-sideband carrier suppression signal, filtering one sideband by the double-sideband carrier suppression signal output by the electro-optical modulator (21) through an optical filter (22), dividing the rest single-sideband carrier suppression signal into two paths by a first optical power divider (23), introducing an optical carrier LFM signal on the upper path into a transmission delay difference with a lower path through an optical fiber delay line (24), and realizing frequency shifting of the input optical signal by a frequency shifting unit (25); the optical signals of the upper path and the lower path are coherently combined through a second optical power divider (26), and the output optical signals are injected into a detector (27) for photoelectric conversion; the analog-to-digital converter (30) collects the electric signal after photoelectric conversion, after signal demodulation is carried out by the digital demodulator (31), the LFM signal containing the channel amplitude and phase fluctuation parameters can be obtained, then the orthogonal down-conversion processing is carried out in the digital domain by the amplitude and phase fluctuation parameter extractor (32), the amplitude and phase fluctuation parameters carried by the distorted LFM signal are extracted, thus the digital predistortion channel correction parameters are generated, and the digital predistortion channel correction parameters are sent into the broadband radio frequency transmission channel for transmission predistortion.
6. The wideband radio frequency transmission channel amplitude and phase fluctuation correction system based on photon declivity reception of claim 5, wherein the method for extracting the amplitude and phase fluctuation parameters carried by the distorted LFM signal is as follows:
let the local oscillator frequency of quadrature down-conversion be f if The digitally demodulated signal is:
the digital zero intermediate frequency signal is obtained after the ideal linear frequency modulation signal passes through a photon declivity receiving channel correction system;
let the amplitude-phase characteristics of the ideal system be:
the amplitude-phase characteristic distortion of an actual system is decomposed into the sum of infinite simple harmonic distortion, and the amplitude-phase characteristic of the system containing the distortion is expressed as:
its amplitude-frequency characteristic surrounds a constant value a 0 With cosine wobble, the phase-frequency characteristic surrounding 2 pi b 0 f, performing sinusoidal oscillation; a, a i And c i Respectively representing the amplitude and the change frequency of amplitude-frequency characteristic fluctuation, b i And d i The amplitude and the change frequency of the fluctuation of the phase frequency characteristic are respectively represented;
when the LFM signal passes through the distorted system, if the amplitude-phase distortion is a gradual function of frequency, the output signal corresponds to the product of the frequency domain distortion and the LFM signal, namely:
v out (t)＝H′(γt)v in (t)
when the input chirp signal contains systematic amplitude phase distortion:
v rf (t)＝V rf ·A′(γt)·sin(ω rf t+πγt 2 +ψ′(γt))
wherein the amplitude fluctuation and phase fluctuation parameters are expressed as follows:
A′(γt)＝|H′(γt)|
the distorted LFM signal is injected into a photon declivity receiving channel correction system, and the complex intermediate frequency signal after digital demodulation is:
when the delay difference tau is small, the small signal approximation is taken from the first-order Bessel term in the signal amplitude, and then the amplitude term of the complex IQ signal is as follows:
the above formula includes the amplitude-frequency response A' (f) of the system;
the phase terms of the complex IQ signal are:
Pha IQ ＝2πγτt+ω 0 τ+2πf rf0 τ+πγτ 2 +ψ′(γt+γτ)-ψ′(γt)
wherein 2πγτt+ω 0 τ+2πf rf0 τ+πγτ 2 As linear terms, the nonlinear terms remaining after removal by linear fitting are:
Pha IQ_nonlinear ＝ψ′(γt+γτ)-ψ′(γt)
the above equation gives the instantaneous phase change amount caused by the phase frequency fluctuation, i.e. compared with the instantaneous frequency drift of the ideal chirp signal, the accumulated integration is performed on the rest nonlinear phase terms to obtain the nonlinear phase error ψ '(γt) of the chirp, i.e. the phase frequency response ψ' (f) of the system.
7. A broadband radio frequency emission channel amplitude and phase fluctuation correction system based on photon deskewing reception according to claim 3, wherein said frequency shift unit (25) comprises: an acousto-optic frequency shifter (251) and a microwave source (252); the output end of the first optical power divider (23) is connected with the first input end of the acousto-optic frequency shifter (251), and the output end of the delay optical fiber (24) is connected with the input end of the second optical power divider (26); the second input end of the acousto-optic frequency shifter (251) is connected with the microwave source (252), and the output end of the acousto-optic frequency shifter (251) is connected with the input end of the second optical power divider (26).
8. A broadband radio frequency emission channel amplitude and phase fluctuation correction system based on photon deskewing reception according to claim 3, wherein said frequency shift unit (25) comprises: a microwave source (252), a double parallel modulator (253), a phase shifter (254), a third power divider (255); the output end of the first optical power divider (23) is connected with the first input end of the double-parallel modulator (253), the output end of the microwave source (252) is connected with the input end of the third power divider (255), the output end of the third power divider (255) is connected with the input end of the phase shifter (254) and the second input end of the double-parallel modulator (253), the output end of the phase shifter (254) is connected with the third input end of the double-parallel modulator (253), and the output end of the double-parallel modulator (253) is connected with the input end of the second optical power divider (26).
9. A broadband radio frequency emission channel amplitude and phase fluctuation correction system based on photon deskewing reception according to claim 3, characterized in that said detector (27) is a single photodetector or a balanced photodetector.
10. A broadband radio frequency emission channel amplitude and phase fluctuation correction system based on photon declivity reception as claimed in claim 3, wherein said fiber optic delay line (24) is replaced by an adjustable fiber optic delay line.
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