CN116566224B - Control method for improving LLC dynamic response - Google Patents

Control method for improving LLC dynamic response Download PDF

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CN116566224B
CN116566224B CN202310834169.6A CN202310834169A CN116566224B CN 116566224 B CN116566224 B CN 116566224B CN 202310834169 A CN202310834169 A CN 202310834169A CN 116566224 B CN116566224 B CN 116566224B
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difference
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duty ratio
fluctuation amplitude
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CN116566224A (en
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许明军
王伟
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Shenzhen Tianbangda Technology Co ltd
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/4815—Resonant converters
    • H02M7/4818—Resonant converters with means for adaptation of resonance frequency, e.g. by modification of capacitance or inductance of resonance circuits
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/01—Resonant DC/DC converters
    • H02M3/015—Resonant DC/DC converters with means for adaptation of resonance frequency, e.g. by modification of capacitance or inductance of resonance circuit
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention relates to the technical field of direct current conversion, in particular to a control method for improving LLC dynamic response, which comprises the following steps: step S1, acquiring output voltage of an LLC circuit by using a DSP, and filtering high-frequency noise of the output voltage by using a low-pass filter; step S2, carrying out feedforward correction on the error amount of the output voltage, detecting the fluctuation amplitude of the output voltage in a unit period after the feedforward correction is finished, and regulating the detection period of the reference signal according to the fluctuation amplitude of the output voltage when the central control module judges that the voltage stability is lower than the allowable range; step S3, calculating the output of the voltage loop by adopting a PI regulator; step S4, calculating the output of the current inner loop by adopting the PI regulator which is the same as the step S3; the invention realizes the improvement of the accuracy and the control efficiency of dynamic response control.

Description

Control method for improving LLC dynamic response
Technical Field
The invention relates to the technical field of direct current conversion, in particular to a control method for improving LLC dynamic response.
Background
Most of the existing mature LLC circuits adopt an analog control mode, namely, a special IC chip is adopted to control the output voltage and the output current of the LLC, and because the LLC circuits are realized in an all-hardware mode, different control methods cannot be adopted under different load conditions, namely, a control algorithm cannot be adaptively modified, so that the working state of a power supply can be optimized. The method provided by the invention is realized digitally by adopting the DSP, can detect external input and output disturbance in real time, and adjusts the control algorithm at any time, so that the optimal running state is achieved.
Chinese patent publication No.: CN114583932B discloses a control circuit and a control method for an LLC resonant converter, which firstly acquire a resonant current signal of a resonant inductance Lr and a resonant voltage signal of two ends of a resonant capacitor Cr of a resonant circuit of the LLC resonant converter; and obtaining a switch driving signal according to the resonance current signal and the resonance voltage signal. The switching drive signal is used for realizing switching control of a power switch tube of a switching inverter circuit of the LLC resonant converter. It can be seen that the control circuit and the control method for the LLC resonant converter have the problems of insufficient control efficiency and control accuracy due to the need to perform load jump tests multiple times and inaccurate error determination for feedforward correction.
Disclosure of Invention
Therefore, the invention provides a control method for improving LLC dynamic response, which is used for solving the problems of insufficient control efficiency and control accuracy caused by the fact that multiple load jump tests are required to be carried out and error judgment is inaccurate in feedforward correction in the prior art.
In order to achieve the above object, the present invention provides a control method for improving LLC dynamic response, including: step S1, acquiring output voltage of an LLC circuit by using a DSP, and filtering high-frequency noise of the output voltage by using a low-pass filter; step S2, carrying out feedforward correction on the error amount of the output voltage, detecting the fluctuation amplitude of the output voltage in a unit period after the feedforward correction is finished, and adjusting the detection period of the reference signal according to the fluctuation amplitude of the output voltage when the voltage stability is judged to be lower than an allowable range by a central control module, or adjusting the capacitance to a corresponding capacitance value according to the duty ratio in the resonant cavity; step S3, calculating the output of the voltage loop by adopting a PI regulator; and S4, calculating the output of the current inner loop by adopting a PI regulator which is the same as that in the step S3, and regulating the inductance value to a corresponding inductance value according to the dynamic response time length when the central control module judges that the influence degree of the feedforward correction step on the dynamic response efficiency exceeds the allowable range.
Further, the system function of filtering the high-frequency noise in the step S1 is:
（1）；
wherein f t In order to be a cut-off frequency,s is a Laplacian operator, and a difference equation after discretization of the system function of the high-frequency noise filtering is as follows:
（2）；
wherein,calculating a period-filtered output voltage for the nth calculation period; />Calculating a period-filtered output voltage for the n-1 th; />Calculating the output voltage before periodic filtering for the nth calculation period; />Calculating the output voltage before periodic filtering for the n-1 th; />And +.>The filter coefficients corresponding to the respective output voltages.
Further, in the step S2, a feedforward correction equation corresponding to the feedforward correction process for the error amount of the output voltage is:
（3）；
and e (K) is the difference between the output voltage reference value of the kth computing period and the filtered output voltage, e (K-1) is the difference between the output voltage reference value of the kth-1 computing period and the filtered output voltage, K is a correction coefficient, and the value range of K is more than 0 and less than 1.
Further, the transfer functions of the controllers in the step S3 and the step S4 are respectively
And->The first difference equation after discretizing the transfer function of the controller in step S3 is:
（4）；
wherein,output of the periodic voltage ring for the kth computation period; />Calculating the output of the periodic voltage ring for the (k-1) th; />And->For the coefficients of the controller, +.>Greater than 0->Greater than 0; />And->The difference value between the output voltage reference value and the filtered output voltage in the kth calculation period and the difference value between the output voltage reference value and the filtered output voltage in the kth-1 calculation period are respectively;
the second differential equation after discretizing the transfer function of the controller in step S4 is:
（5）；
wherein,calculating the output of the periodic current loop for the kth; />Calculating the output of the periodic current loop for the k-1 th; />And->For the coefficients of the controller, +.>Greater than 0->Greater than 0; />And->The difference between the reference value of the input current and the actual input current in the kth calculation period and the difference between the reference value of the input current and the actual input current in the kth-1 calculation period are respectively.
Further, in the step S2, the central control module determines whether the voltage stability is within the allowable range according to the output voltage fluctuation range in the unit detection period, wherein,
the first type of judgment mode is that the central control module judges that the voltage stability degree is in an allowable range under the condition of presetting a first fluctuation amplitude;
the second type of judgment mode is that the central control module judges that the voltage stability is lower than the allowable range under the condition of presetting a second fluctuation amplitude, primarily judges that the energy stability degree in the circuit is lower than the allowable range, and secondarily judges whether the energy stability in the circuit is lower than the allowable range according to the duty ratio in the resonant cavity;
the third type of judgment mode is that the central control module judges that the error degree of the reference signal of the feedforward correction signal exceeds an allowable range under the condition of presetting a third fluctuation amplitude, and the detection period of the reference signal is adjusted to a corresponding period by calculating the difference value between the output voltage fluctuation amplitude and the preset second voltage fluctuation amplitude;
the preset first fluctuation amplitude condition is that the fluctuation amplitude of the conveying voltage is smaller than or equal to the difference value of the preset first fluctuation amplitude; the preset second fluctuation amplitude condition is that the fluctuation amplitude of the conveying voltage is larger than the preset first fluctuation amplitude and smaller than or equal to the preset second fluctuation amplitude; the preset third fluctuation amplitude condition is that the fluctuation amplitude of the conveying voltage is larger than the preset second fluctuation amplitude; the preset first voltage fluctuation amplitude is smaller than the preset second voltage fluctuation amplitude.
Further, the central control module determines three types of adjustment modes aiming at the reference signal detection period according to the difference value between the output voltage fluctuation amplitude and the preset second voltage fluctuation amplitude under the condition of the preset third fluctuation amplitude, wherein,
the first type of adjustment mode is that the central control module adjusts the reference signal detection period to a preset detection period under the condition of presetting a first fluctuation amplitude difference value;
the second type of adjustment mode is that the central control module adjusts the reference signal detection period to a first period by using a preset second period adjustment coefficient under the condition of presetting a second fluctuation amplitude difference value; the third type of adjustment mode is that the central control module adjusts the reference signal detection period to a second period by using a preset first period adjustment coefficient under the condition of presetting a third fluctuation amplitude difference value;
the preset first fluctuation amplitude difference condition is that the difference value between the output voltage fluctuation amplitude and the preset first voltage fluctuation amplitude is smaller than or equal to the preset first voltage fluctuation amplitude difference value; the preset second fluctuation amplitude difference condition is that the difference value between the output voltage fluctuation amplitude and the preset first voltage fluctuation amplitude is larger than the preset first voltage fluctuation amplitude difference value and smaller than or equal to the preset second fluctuation amplitude difference value; the preset third fluctuation amplitude difference condition is that the difference between the output voltage fluctuation amplitude and the preset first voltage fluctuation amplitude is larger than the preset second voltage fluctuation amplitude difference; the preset first voltage fluctuation amplitude difference value is smaller than the preset second voltage fluctuation amplitude difference value, and the preset first period adjustment coefficient is smaller than the preset second period adjustment coefficient.
Further, the central control module determines whether energy stability in the circuit is lower than two types of secondary judging modes within an allowable range according to the duty ratio in the resonant cavity under the condition of preset second fluctuation amplitude, wherein,
the first secondary judgment mode is that the energy stability in the secondary judgment circuit is lower than an allowable range under the condition of a preset first duty ratio by the central control module, and the capacitance of the circuit is adjusted to a corresponding value by calculating the difference value between the preset duty ratio and the duty ratio in the resonant cavity;
the second type of secondary judgment mode is that the energy stability in the secondary judgment circuit is within an allowable range under the condition of a preset second duty ratio by the central control module;
the first preset duty ratio condition is that the duty ratio in the resonant cavity is smaller than or equal to the preset duty ratio; the preset second duty ratio condition is that the duty ratio in the resonant cavity is larger than the preset duty ratio.
Further, the central control module determines three types of adjustment modes for the capacitor according to the difference value between the preset duty ratio and the duty ratio in the resonant cavity under the condition of the preset first duty ratio, wherein,
the first type of capacitance adjustment mode is that the central control module adjusts the capacitance to a preset capacitance under the condition of a preset first duty ratio difference value;
the second type of capacitance adjusting mode is that the central control module adjusts the capacitance to a first capacitance by using a preset first capacitance adjusting coefficient under the condition of a preset second duty ratio difference value;
the third type of capacitance adjusting mode is that the central control module adjusts the capacitance to a second capacitance by using a preset second capacitance adjusting coefficient under the condition of presetting a third duty ratio difference value;
the preset first duty ratio difference condition is that the difference between the preset duty ratio and the duty ratio in the resonant cavity is smaller than or equal to the preset first duty ratio difference; the preset second duty ratio difference condition is that the difference between the preset duty ratio and the duty ratio in the resonant cavity is larger than the preset first duty ratio difference and smaller than or equal to the preset second duty ratio difference; the preset third duty ratio difference condition is that the difference between the preset duty ratio and the duty ratio in the resonant cavity is larger than the preset second duty ratio difference; the preset first duty ratio difference value is smaller than the preset second duty ratio difference value, and the preset first capacitance adjustment coefficient is smaller than the preset second capacitance adjustment coefficient.
Further, the central control module determines two types of judging modes of whether the influence degree of the feedforward correction step on the dynamic response efficiency is within an allowable range according to the dynamic response time length, wherein,
the first type of influence judging mode is that the central control module judges that the influence degree of the feedforward correction step on the dynamic response efficiency is in an allowable range under the condition of presetting a first response time length;
the second type of influence judging mode is that the central control module judges that the influence degree of the feedforward correction step on the dynamic response efficiency exceeds an allowable range under the condition of the preset second response time length, and the inductance value is reduced to the corresponding inductance value by calculating the difference value between the dynamic response time length and the preset response time length;
the preset first response time length condition is that the dynamic response time length is smaller than or equal to the preset response time length; the condition of the preset second response time length is that the dynamic response time length is longer than the preset response time length.
Further, the central control module determines three types of adjustment modes for the inductance value according to the difference value between the dynamic response time length and the preset response time length under the condition of the preset second response time length, wherein,
the first type of inductance adjustment mode is that the central control module adjusts the inductance value to a preset inductance value under the condition of a preset first response time difference value;
the second type of inductance adjustment mode is that the central control module adjusts the inductance value to a first inductance value by using a preset second inductance value adjustment coefficient under the condition of presetting a second response time difference value;
the third type of inductance adjustment mode is that the central control module adjusts the inductance value to a second inductance value by using a preset first inductance value adjustment coefficient under the condition of presetting a third response time difference value;
the preset first response time length difference condition is that the difference between the dynamic response time length and the preset response time length is smaller than or equal to the preset first response time length difference; the difference value condition of the preset second response time length is that the difference value between the dynamic response time length and the preset response time length is larger than the difference value of the preset first response time length and smaller than or equal to the difference value of the preset second response time length; the difference value condition of the preset third response time length is that the difference value between the dynamic response time length and the preset response time length is larger than the difference value of the preset second response time length; the preset first response time length difference value is smaller than the preset second response time length difference value, and the preset first inductance value adjusting coefficient is smaller than the preset second inductance value adjusting coefficient. Compared with the prior art, the method has the beneficial effects that the method improves the precision and the stability of a circuit by performing feedforward correction on the error amount of output voltage through different processing steps of setting in each step, such as step S1 to step S4, and performs corresponding parameter adjustment on a voltage control process through a plurality of preset parameters, and reduces the influence on correction accuracy due to the inconsistency of waveform properties of two parameter signals in the feedforward correction process through adjustment on a reference signal detection period and capacitance; by adjusting the inductance value to the corresponding inductance value according to the dynamic response time length, the influence on the response efficiency caused by inaccurate adjustment of the inductance value is reduced, and the accuracy of dynamic response control and the improvement of control efficiency are realized. Further, according to the method, through the preset first voltage fluctuation amplitude difference value, the preset second voltage fluctuation amplitude difference value, the preset first period adjustment coefficient and the preset second period adjustment coefficient, three types of adjustment modes for the reference signal detection period are determined according to the difference value between the output voltage fluctuation amplitude and the preset first voltage fluctuation amplitude, the influence on control accuracy caused by inaccuracy in adjustment of the detection period is reduced, and the accuracy and the control efficiency of dynamic response control are further improved. Furthermore, according to the method, through the preset first duty ratio difference value, the preset second duty ratio difference value, the preset first capacitance adjustment coefficient and the preset second capacitance adjustment coefficient, three types of adjustment modes for the capacitance are determined according to the difference value between the preset duty ratio and the duty ratio in the resonant cavity, the influence of the duty ratio reflected in the resonant cavity on the energy stability in the circuit is reduced, and the accuracy of dynamic response control and the improvement of control efficiency are further realized.
Drawings
FIG. 1 is a flowchart illustrating a control method for improving LLC dynamic response according to an embodiment of the present invention;
fig. 2 is a specific flowchart of step S2 of a control method for improving LLC dynamic response in accordance with an embodiment of the invention.
Detailed Description
In order that the objects and advantages of the invention will become more apparent, the invention will be further described with reference to the following examples; it should be understood that the specific embodiments described herein are for purposes of illustration only and are not intended to limit the scope of the invention. Preferred embodiments of the present invention are described below with reference to the accompanying drawings. It should be understood by those skilled in the art that these embodiments are merely for explaining the technical principles of the present invention, and are not intended to limit the scope of the present invention.
Please refer to fig. 1 and fig. 2, which are a general flowchart of a control method for improving LLC dynamic response and a specific flowchart of step S2 according to an embodiment of the invention; the invention discloses a control method for improving LLC dynamic response, which comprises the following steps:
step S1, acquiring output voltage of an LLC circuit by using a DSP, and filtering high-frequency noise of the output voltage by using a low-pass filter;
step S2, carrying out feedforward correction on the error amount of the output voltage, detecting the fluctuation amplitude of the output voltage in a unit period after the feedforward correction is finished, and adjusting the detection period of the reference signal according to the fluctuation amplitude of the output voltage when the voltage stability is judged to be lower than an allowable range by a central control module, or adjusting the capacitance to a corresponding capacitance value according to the duty ratio in the resonant cavity;
step S3, calculating the output of the voltage loop by adopting a PI regulator;
and S4, calculating the output of the current inner loop by adopting a PI regulator which is the same as that in the step S3, and regulating the inductance value to a corresponding inductance value according to the dynamic response time length when the central control module judges that the influence degree of the feedforward correction step on the dynamic response efficiency exceeds the allowable range.
Specifically, the step S2 includes:
step S21, feedforward correction is carried out on the error quantity of the output voltage, and the fluctuation amplitude of the output voltage in the unit period is detected after the correction is finished;
in step S22, the central control module adjusts the detection period of the reference signal according to the fluctuation amplitude of the output voltage when the voltage stability is determined to be lower than the allowable range, or adjusts the capacitance to a corresponding capacitance value according to the duty ratio in the resonant cavity.
The method of the invention improves the precision and stability of the circuit by performing feedforward correction on the error amount of the output voltage through the set steps S1 to S4 and through the different processing steps in each step, for example, the corresponding parameter adjustment is performed on the voltage control process through a plurality of preset parameters, and the influence on the correction accuracy caused by the inconsistency of the waveform properties of two parameter signals in the feedforward correction process is reduced through the adjustment of the reference signal detection period and the capacitance; by adjusting the inductance value to the corresponding inductance value according to the dynamic response time length, the influence on the response efficiency caused by inaccurate adjustment of the inductance value is reduced, and the accuracy of dynamic response control and the improvement of control efficiency are realized.
With continued reference to fig. 1, the system function of the high-frequency noise filtering in step S1 is as follows:
（1）；
wherein f t In order to be a cut-off frequency,s is a Laplacian operator, and a difference equation after discretization of the system function of the high-frequency noise filtering is as follows:
(2) The method comprises the steps of carrying out a first treatment on the surface of the Wherein,calculating a period-filtered output voltage for the nth calculation period; />Calculating a period-filtered output voltage for the n-1 th; />Calculating the output voltage before periodic filtering for the nth calculation period; />Calculating the output voltage before periodic filtering for the n-1 th; />And +.>The filter coefficients corresponding to the respective output voltages.
With continued reference to fig. 1, in the step S2, a feedforward correction equation corresponding to the feedforward correction process for the error amount of the output voltage is:
（3）；
and e (K) is the difference between the output voltage reference value of the kth computing period and the filtered output voltage, e (K-1) is the difference between the output voltage reference value of the kth-1 computing period and the filtered output voltage, K is a correction coefficient, and the value range of K is more than 0 and less than 1.
With continued reference to fig. 1, the transfer functions of the controllers in the step S3 and the step S4 are respectivelyAnd->The first difference equation after discretizing the transfer function of the controller in step S3 is:
（4）；
wherein,output of the periodic voltage ring for the kth computation period; />Calculating the output of the periodic voltage ring for the (k-1) th; />And->For the coefficients of the controller, +.>Greater than 0->Greater than 0; />And->The difference value between the output voltage reference value and the filtered output voltage in the kth calculation period and the difference value between the output voltage reference value and the filtered output voltage in the kth-1 calculation period are respectively;
the second differential equation after discretizing the transfer function of the controller in step S4 is:
（5）；
wherein,calculating the output of the periodic current loop for the kth; />Calculating the output of the periodic current loop for the k-1 th; />And->For the coefficients of the controller, +.>Greater than 0->Greater than 0; />And->The difference between the reference value of the input current and the actual input current in the kth calculation period and the difference between the reference value of the input current and the actual input current in the kth-1 calculation period are respectively.
With continued reference to fig. 1 and 2, in step S2, the central control module determines whether the voltage stability is within the allowable range according to the output voltage fluctuation range in the unit detection period, wherein,
the first type of judgment mode is that the central control module judges that the voltage stability degree is in an allowable range under the condition of presetting a first fluctuation amplitude;
the second type of judgment mode is that the central control module judges that the voltage stability is lower than the allowable range under the condition of presetting a second fluctuation amplitude, primarily judges that the energy stability degree in the circuit is lower than the allowable range, and secondarily judges whether the energy stability in the circuit is lower than the allowable range according to the duty ratio in the resonant cavity;
the third type of judgment mode is that the central control module judges that the error degree of the reference signal of the feedforward correction signal exceeds an allowable range under the condition of presetting a third fluctuation amplitude, and the detection period of the reference signal is adjusted to a corresponding period by calculating the difference value between the output voltage fluctuation amplitude and the preset second voltage fluctuation amplitude;
the preset first fluctuation amplitude condition is that the fluctuation amplitude of the conveying voltage is smaller than or equal to the difference value of the preset first fluctuation amplitude; the preset second fluctuation amplitude condition is that the fluctuation amplitude of the conveying voltage is larger than the preset first fluctuation amplitude and smaller than or equal to the preset second fluctuation amplitude; the preset third fluctuation amplitude condition is that the fluctuation amplitude of the conveying voltage is larger than the preset second fluctuation amplitude; the preset first voltage fluctuation amplitude is smaller than the preset second voltage fluctuation amplitude. Specifically, the output voltage fluctuation amplitude is denoted as F, the preset first voltage fluctuation amplitude is denoted as F1, the preset second voltage fluctuation amplitude is denoted as F2, wherein F1 < F2, the difference between the output voltage fluctuation amplitude and the preset first voltage fluctuation amplitude is denoted as Δf, and Δf=f-F2 is set.
With continued reference to fig. 1, the central control module determines three types of adjustment modes for the reference signal detection period according to the difference between the output voltage fluctuation range and the preset second voltage fluctuation range under the preset third fluctuation range condition, wherein,
the first type of adjustment mode is that the central control module adjusts the reference signal detection period to a preset detection period under the condition of presetting a first fluctuation amplitude difference value;
the second type of adjustment mode is that the central control module adjusts the reference signal detection period to a first period by using a preset second period adjustment coefficient under the condition of presetting a second fluctuation amplitude difference value;
the third type of adjustment mode is that the central control module adjusts the reference signal detection period to a second period by using a preset first period adjustment coefficient under the condition of presetting a third fluctuation amplitude difference value;
the preset first fluctuation amplitude difference condition is that the difference value between the output voltage fluctuation amplitude and the preset first voltage fluctuation amplitude is smaller than or equal to the preset first voltage fluctuation amplitude difference value; the preset second fluctuation amplitude difference condition is that the difference value between the output voltage fluctuation amplitude and the preset first voltage fluctuation amplitude is larger than the preset first voltage fluctuation amplitude difference value and smaller than or equal to the preset second fluctuation amplitude difference value; the preset third fluctuation amplitude difference condition is that the difference between the output voltage fluctuation amplitude and the preset first voltage fluctuation amplitude is larger than the preset second voltage fluctuation amplitude difference; the preset first voltage fluctuation amplitude difference value is smaller than the preset second voltage fluctuation amplitude difference value, and the preset first period adjustment coefficient is smaller than the preset second period adjustment coefficient.
Specifically, the preset first voltage fluctuation amplitude difference is denoted as Δf1, the preset second voltage fluctuation amplitude difference is denoted as Δf2, the preset first period adjustment coefficient is denoted as α1, the preset second period adjustment coefficient is denoted as α2, the preset detection period is denoted as T0, Δf1 < [ Δf2 ], 0 < α1 < α2 < 1, the adjusted parameter signal detection period is denoted as T ', T' =t0× (1+αi)/2, wherein αi is the preset i-th period adjustment coefficient, and i=1, 2.
Further, according to the method, through the preset first voltage fluctuation amplitude difference value, the preset second voltage fluctuation amplitude difference value, the preset first period adjustment coefficient and the preset second period adjustment coefficient, three types of adjustment modes for the reference signal detection period are determined according to the difference value between the output voltage fluctuation amplitude and the preset first voltage fluctuation amplitude, the influence on control accuracy caused by inaccuracy in adjustment of the detection period is reduced, and the accuracy and the control efficiency of dynamic response control are further improved.
With continued reference to fig. 1, the central control module determines, according to a duty ratio in the resonant cavity, whether energy stability in the circuit is lower than two types of secondary determination modes within an allowable range under a preset second fluctuation range condition, where the first type of secondary determination mode is that the energy stability in the secondary determination circuit is lower than the allowable range under a preset first duty ratio condition, and adjusts the capacitance of the circuit to a corresponding value by calculating a difference value between the preset duty ratio and the duty ratio in the resonant cavity;
the second type of secondary judgment mode is that the energy stability in the secondary judgment circuit is within an allowable range under the condition of a preset second duty ratio by the central control module;
the first preset duty ratio condition is that the duty ratio in the resonant cavity is smaller than or equal to the preset duty ratio; the preset second duty ratio condition is that the duty ratio in the resonant cavity is larger than the preset duty ratio.
Specifically, the duty ratio in the resonant cavity is denoted as Q, the duty ratio Q0 is preset, the difference between the preset duty ratio and the duty ratio in the resonant cavity is denoted as Δq, and Δq=q0-Q is set.
With continued reference to fig. 2, the central control module determines three types of adjustment modes for the capacitor according to a difference between a preset duty ratio and a duty ratio in the resonant cavity under a preset first duty ratio condition, wherein,
the first type of capacitance adjustment mode is that the central control module adjusts the capacitance to a preset capacitance under the condition of a preset first duty ratio difference value;
the second type of capacitance adjusting mode is that the central control module adjusts the capacitance to a first capacitance by using a preset first capacitance adjusting coefficient under the condition of a preset second duty ratio difference value;
the third type of capacitance adjusting mode is that the central control module adjusts the capacitance to a second capacitance by using a preset second capacitance adjusting coefficient under the condition of presetting a third duty ratio difference value;
the preset first duty ratio difference condition is that the difference between the preset duty ratio and the duty ratio in the resonant cavity is smaller than or equal to the preset first duty ratio difference; the preset second duty ratio difference condition is that the difference between the preset duty ratio and the duty ratio in the resonant cavity is larger than the preset first duty ratio difference and smaller than or equal to the preset second duty ratio difference; the preset third duty ratio difference condition is that the difference between the preset duty ratio and the duty ratio in the resonant cavity is larger than the preset second duty ratio difference; the preset first duty ratio difference value is smaller than the preset second duty ratio difference value, and the preset first capacitance adjustment coefficient is smaller than the preset second capacitance adjustment coefficient.
Specifically, the preset capacitance is denoted as C0, the preset first duty cycle difference is denoted as Δq1, the preset second duty cycle difference is denoted as Δq2, the preset first capacitance adjustment coefficient is denoted as β1, the preset second capacitance adjustment coefficient is denoted as β2, wherein Δq1 < Δq2,1 < β1 < β2, the adjusted capacitance is denoted as C ', C' =c0×βj is set, wherein βj is the preset j-th capacitance adjustment coefficient, and j=1, 2.
Furthermore, according to the method, through the preset first duty ratio difference value, the preset second duty ratio difference value, the preset first capacitance adjustment coefficient and the preset second capacitance adjustment coefficient, three types of adjustment modes for the capacitance are determined according to the difference value between the preset duty ratio and the duty ratio in the resonant cavity, the influence of the duty ratio reflected in the resonant cavity on the energy stability in the circuit is reduced, and the accuracy of dynamic response control and the improvement of control efficiency are further realized.
With continued reference to fig. 1, the central control module determines, according to the dynamic response time, two types of determination manners whether the degree of influence of the feedforward correction step on the dynamic response efficiency is within an allowable range, where,
the first type of influence judging mode is that the central control module judges that the influence degree of the feedforward correction step on the dynamic response efficiency is in an allowable range under the condition of presetting a first response time length;
the second type of influence judging mode is that the central control module judges that the influence degree of the feedforward correction step on the dynamic response efficiency exceeds an allowable range under the condition of the preset second response time length, and the inductance value is reduced to the corresponding inductance value by calculating the difference value between the dynamic response time length and the preset response time length;
the preset first response time length condition is that the dynamic response time length is smaller than or equal to the preset response time length; the condition of the preset second response time length is that the dynamic response time length is longer than the preset response time length. Specifically, the dynamic response time length is denoted as T, the preset response time length is denoted as T0, the difference between the dynamic response time length and the preset response time length is denoted as Δt, and Δt=t-T0 is set.
With continued reference to fig. 1, the central control module determines three types of adjustment modes for the inductance value according to the difference between the dynamic response time length and the preset response time length under the condition of the preset second response time length, wherein,
the first type of inductance adjustment mode is that the central control module adjusts the inductance value to a preset inductance value under the condition of a preset first response time difference value;
the second type of inductance adjustment mode is that the central control module adjusts the inductance value to a first inductance value by using a preset second inductance value adjustment coefficient under the condition of presetting a second response time difference value;
the third type of inductance adjustment mode is that the central control module adjusts the inductance value to a second inductance value by using a preset first inductance value adjustment coefficient under the condition of presetting a third response time difference value;
the preset first response time length difference condition is that the difference between the dynamic response time length and the preset response time length is smaller than or equal to the preset first response time length difference; the difference value condition of the preset second response time length is that the difference value between the dynamic response time length and the preset response time length is larger than the difference value of the preset first response time length and smaller than or equal to the difference value of the preset second response time length; the difference value condition of the preset third response time length is that the difference value between the dynamic response time length and the preset response time length is larger than the difference value of the preset second response time length; the preset first response time length difference value is smaller than the preset second response time length difference value, and the preset first inductance value adjusting coefficient is smaller than the preset second inductance value adjusting coefficient.
Specifically, the preset inductance value is denoted as L0, the preset first response time length difference is denoted as Δt1, the preset second response time length difference is denoted as Δt2, the preset first inductance value adjustment coefficient is denoted as γ1, the preset second inductance value adjustment coefficient is denoted as γ2, wherein Δt1 < [ Δt2 ], 0 < γ1 < γ2 < 1, the adjusted inductance value is denoted as L ', L' =l0× (1+2γg)/3 is set, γg is the g-th inductance value adjustment coefficient, and g=1, 2 is set.
Example 1
The central control module in this embodiment 1 determines three types of adjustment modes for the capacitor according to the difference between the preset duty ratio and the duty ratio in the resonant cavity under the preset first duty ratio condition, wherein the preset capacitor is denoted as C0, the preset first duty ratio difference is denoted as Δq1, the preset second duty ratio difference is denoted as Δq2, the preset first capacitance adjustment coefficient is denoted as β1, the preset second capacitance adjustment coefficient is denoted as β2, and wherein Δq1=0.15, Δq2=0.24, β1=1.1, β2=1.3, c0=20pf,
in this embodiment 1, Δq=0.18 is obtained, the central control module determines that Δq1 < Δq2is less than or equal to Δq2, and adjusts the capacitance to a first capacitance C 'by using a preset first capacitance adjustment coefficient β1, so as to calculate C' =20μf×1.1=22μf.
According to the embodiment, the preset first duty ratio difference value, the preset second duty ratio difference value, the preset first capacitance adjustment coefficient and the preset second capacitance adjustment coefficient are set, and the capacitance is adjusted to the corresponding value according to the difference value between the preset duty ratio and the duty ratio in the resonant cavity, so that the influence of the duty ratio reflected in the resonant cavity on the energy stability in the circuit is reduced, and the accuracy of dynamic response control and the improvement of control efficiency are realized.
Thus far, the technical solution of the present invention has been described in connection with the preferred embodiments shown in the drawings, but it is easily understood by those skilled in the art that the scope of protection of the present invention is not limited to these specific embodiments. Equivalent modifications and substitutions for related technical features may be made by those skilled in the art without departing from the principles of the present invention, and such modifications and substitutions will be within the scope of the present invention. The foregoing description is only of the preferred embodiments of the invention and is not intended to limit the invention; various modifications and variations of the present invention will be apparent to those skilled in the art. Any modification, equivalent replacement, improvement, etc. made within the spirit and principle of the present invention should be included in the protection scope of the present invention.

Claims (10)

1. A control method for enhancing LLC dynamic response, comprising:
step S1, acquiring output voltage of an LLC circuit by using a DSP, and filtering high-frequency noise of the output voltage by using a low-pass filter;
step S2, carrying out feedforward correction on the error amount of the output voltage, detecting the fluctuation amplitude of the output voltage in a unit period after the feedforward correction is finished, and adjusting the detection period of the reference signal according to the fluctuation amplitude of the output voltage when the voltage stability is judged to be lower than an allowable range by a central control module, or adjusting the capacitance to a corresponding capacitance value according to the duty ratio in the resonant cavity;
step S3, calculating the output of the voltage loop by adopting a PI regulator;
and S4, calculating the output of the current inner loop by adopting a PI regulator which is the same as that in the step S3, and regulating the inductance value to a corresponding inductance value according to the dynamic response time length when the central control module judges that the influence degree of the feedforward correction step on the dynamic response efficiency exceeds the allowable range.
2. The control method for improving LLC dynamic response according to claim 1, wherein the system function of high frequency noise filtering in step S1 is:
wherein f t For the cutoff frequency, pi=pi, s is the laplace operator, and the difference equation after discretizing the system function of the high-frequency noise filtering is:
V filter (n)＝A 1 *V filter (n-1)+B 0 *V(n)+B 1 *V(n-1) (2)；
wherein V is filter (n) the output voltage after the period filtering for the nth calculation; v (V) filter (n-1) is the output voltage after the n-1 th calculation cycle filtering; v (n) is the output voltage before the nth calculation period filtering; v (n-1) is the period before filtering of the n-1 th calculationOutputting a voltage; a is that 1 、B 0 B, B 1 The filter coefficients corresponding to the respective output voltages.
3. The control method for improving LLC dynamic response according to claim 2, wherein in step S2, a feedforward correction equation corresponding to a feedforward correction process for the error amount of the output voltage is:
e v (k-1)＝e v (k-1)–K*e v (k) (3)；
wherein e v (k) Calculating a difference between the periodic output voltage reference value and the filtered output voltage for the kth period, e v And (K-1) is the difference between the output voltage reference value and the filtered output voltage in the K-1 calculation period, K is a correction coefficient, and the value range of K is more than 0 and less than 1.
4. A control method for improving LLC dynamic response according to claim 3, wherein the transfer functions of the controllers in step S3 and step S4 are respectivelyAnd->The first difference equation after discretizing the transfer function of the controller in the step S3 is:
V loopctrl (k)＝V loopctrl (k-1)+K pv *(e v (k)-e v (k-1))+K iv *e v (k) (4)；
wherein,output of the periodic voltage ring for the kth computation period; />Calculating the output of the periodic voltage ring for the (k-1) th; k (K) pv And K iv To controlCoefficient of the making machine, K pv Greater than 0 and K iv Greater than 0; e, e v (k) And e v (k-1) outputting a difference between the voltage reference value and the filtered output voltage for the kth calculation period and a difference between the voltage reference value and the filtered output voltage for the kth calculation period, respectively;
the second differential equation after discretizing the transfer function of the controller in step S4 is:
I loopctrl (k)＝I loopctrl (k-1)+K pi *(e i (k)-e i (k-1))+K ii *e v (k) (5)；
wherein,calculating the output of the periodic current loop for the kth; />Calculating the output of the periodic current loop for the k-1 th; k (K) pi And K ii K being coefficients of the controller pi Greater than 0, and K ii Greater than 0; e, e i (k) And e i (k-1) is the difference between the reference value of the input current and the actual input current in the kth calculation period and the kth calculation period, respectively.
5. The control method for improving LLC dynamic response according to claim 4, wherein in said step S2, said central control module determines whether the voltage stability is within an allowable range according to the output voltage fluctuation range in a unit detection period, wherein,
the first type of judgment mode is that the central control module judges that the voltage stability degree is in an allowable range under the condition of presetting a first fluctuation amplitude;
the second type of judgment mode is that the central control module judges that the voltage stability is lower than the allowable range under the condition of presetting a second fluctuation amplitude, primarily judges that the energy stability degree in the circuit is lower than the allowable range, and secondarily judges whether the energy stability in the circuit is lower than the allowable range according to the duty ratio in the resonant cavity;
the third type of judgment mode is that the central control module judges that the error degree of the reference signal of the feedforward correction signal exceeds an allowable range under the condition of presetting a third fluctuation amplitude, and the detection period of the reference signal is adjusted to a corresponding period by calculating the difference value between the output voltage fluctuation amplitude and the preset second voltage fluctuation amplitude;
the preset first fluctuation amplitude condition is that the fluctuation amplitude of the conveying voltage is smaller than or equal to the difference value of the preset first fluctuation amplitude; the preset second fluctuation amplitude condition is that the fluctuation amplitude of the conveying voltage is larger than the preset first fluctuation amplitude and smaller than or equal to the preset second fluctuation amplitude; the preset third fluctuation amplitude condition is that the fluctuation amplitude of the conveying voltage is larger than the preset second fluctuation amplitude; the preset first voltage fluctuation amplitude is smaller than the preset second voltage fluctuation amplitude.
6. The control method for improving LLC dynamic response according to claim 5, wherein the central control module determines three types of adjustment modes for the reference signal detection period according to a difference between the output voltage fluctuation range and the preset second voltage fluctuation range under the preset third fluctuation range condition, wherein,
the first type of adjustment mode is that the central control module adjusts the reference signal detection period to a preset detection period under the condition of presetting a first fluctuation amplitude difference value;
the second type of adjustment mode is that the central control module adjusts the reference signal detection period to a first period by using a preset second period adjustment coefficient under the condition of presetting a second fluctuation amplitude difference value;
the third type of adjustment mode is that the central control module adjusts the reference signal detection period to a second period by using a preset first period adjustment coefficient under the condition of presetting a third fluctuation amplitude difference value;
the preset first fluctuation amplitude difference condition is that the difference value between the output voltage fluctuation amplitude and the preset first voltage fluctuation amplitude is smaller than or equal to the preset first voltage fluctuation amplitude difference value; the preset second fluctuation amplitude difference condition is that the difference value between the output voltage fluctuation amplitude and the preset first voltage fluctuation amplitude is larger than the preset first voltage fluctuation amplitude difference value and smaller than or equal to the preset second fluctuation amplitude difference value; the preset third fluctuation amplitude difference condition is that the difference between the output voltage fluctuation amplitude and the preset first voltage fluctuation amplitude is larger than the preset second voltage fluctuation amplitude difference; the preset first voltage fluctuation amplitude difference value is smaller than the preset second voltage fluctuation amplitude difference value, and the preset first period adjustment coefficient is smaller than the preset second period adjustment coefficient.
7. The control method for improving LLC dynamic response according to claim 6, wherein the central control module determines whether energy stability in the circuit is lower than two types of secondary decision modes within an allowable range according to a duty ratio in the resonant cavity under a preset second fluctuation range condition, wherein,
the first secondary judgment mode is that the energy stability in the secondary judgment circuit is lower than an allowable range under the condition of a preset first duty ratio by the central control module, and the capacitance of the circuit is adjusted to a corresponding value by calculating the difference value between the preset duty ratio and the duty ratio in the resonant cavity;
the second type of secondary judgment mode is that the energy stability in the secondary judgment circuit is within an allowable range under the condition of a preset second duty ratio by the central control module;
the first preset duty ratio condition is that the duty ratio in the resonant cavity is smaller than or equal to the preset duty ratio; the preset second duty ratio condition is that the duty ratio in the resonant cavity is larger than the preset duty ratio.
8. The control method for improving LLC dynamic response according to claim 7, wherein the central control module determines three types of adjustment modes for the capacitance according to a difference between a preset duty cycle and a duty cycle in the resonant cavity under a preset first duty cycle condition, wherein,
the first type of capacitance adjustment mode is that the central control module adjusts the capacitance to a preset capacitance under the condition of a preset first duty ratio difference value;
the second type of capacitance adjusting mode is that the central control module adjusts the capacitance to a first capacitance by using a preset first capacitance adjusting coefficient under the condition of a preset second duty ratio difference value;
the third type of capacitance adjusting mode is that the central control module adjusts the capacitance to a second capacitance by using a preset second capacitance adjusting coefficient under the condition of presetting a third duty ratio difference value;
the preset first duty ratio difference condition is that the difference between the preset duty ratio and the duty ratio in the resonant cavity is smaller than or equal to the preset first duty ratio difference; the preset second duty ratio difference condition is that the difference between the preset duty ratio and the duty ratio in the resonant cavity is larger than the preset first duty ratio difference and smaller than or equal to the preset second duty ratio difference; the preset third duty ratio difference condition is that the difference between the preset duty ratio and the duty ratio in the resonant cavity is larger than the preset second duty ratio difference; the preset first duty ratio difference value is smaller than the preset second duty ratio difference value, and the preset first capacitance adjustment coefficient is smaller than the preset second capacitance adjustment coefficient.
9. The control method for improving LLC dynamic response according to claim 8, wherein the central control module determines two types of decision modes of whether the degree of influence of the feedforward correction step on the dynamic response efficiency is within an allowable range according to the dynamic response time length, wherein,
the first type of influence judging mode is that the central control module judges that the influence degree of the feedforward correction step on the dynamic response efficiency is in an allowable range under the condition of presetting a first response time length;
the second type of influence judging mode is that the central control module judges that the influence degree of the feedforward correction step on the dynamic response efficiency exceeds an allowable range under the condition of the preset second response time length, and the inductance value is reduced to the corresponding inductance value by calculating the difference value between the dynamic response time length and the preset response time length;
the preset first response time length condition is that the dynamic response time length is smaller than or equal to the preset response time length; the condition of the preset second response time length is that the dynamic response time length is longer than the preset response time length.
10. The control method for improving LLC dynamic response according to claim 9, wherein the central control module determines three types of adjustment modes for the inductance value according to the difference between the dynamic response time length and the preset response time length under the condition of the preset second response time length, wherein,
the first type of inductance adjustment mode is that the central control module adjusts the inductance value to a preset inductance value under the condition of a preset first response time difference value;
the second type of inductance adjustment mode is that the central control module adjusts the inductance value to a first inductance value by using a preset second inductance value adjustment coefficient under the condition of presetting a second response time difference value;
the third type of inductance adjustment mode is that the central control module adjusts the inductance value to a second inductance value by using a preset first inductance value adjustment coefficient under the condition of presetting a third response time difference value;
the preset first response time length difference condition is that the difference between the dynamic response time length and the preset response time length is smaller than or equal to the preset first response time length difference; the difference value condition of the preset second response time length is that the difference value between the dynamic response time length and the preset response time length is larger than the difference value of the preset first response time length and smaller than or equal to the difference value of the preset second response time length; the difference value condition of the preset third response time length is that the difference value between the dynamic response time length and the preset response time length is larger than the difference value of the preset second response time length; the preset first response time length difference value is smaller than the preset second response time length difference value, and the preset first inductance value adjusting coefficient is smaller than the preset second inductance value adjusting coefficient.
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