CN116054595B - Flyback converter control method and flyback converter - Google Patents
Flyback converter control method and flyback converter Download PDFInfo
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- CN116054595B CN116054595B CN202310340726.9A CN202310340726A CN116054595B CN 116054595 B CN116054595 B CN 116054595B CN 202310340726 A CN202310340726 A CN 202310340726A CN 116054595 B CN116054595 B CN 116054595B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from dc input or output
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Dc-Dc Converters (AREA)
Abstract
The application relates to a flyback converter control method and a flyback converter, and relates to the field of switching power supply control methods. The control circuit comprises a peak current control module, a comparator, a pulse width recording module, a pulse width detection module, a turn-off time calculation module, a turn-off time control module and a driving module. In the process of controlling the working frequency and the working state of the flyback converter, the comparator is used for determining the pulse width of the feedback signal, and a control signal for controlling the turn-off time and the working mode is generated based on the real-time pulse width, so that the working frequency and the working mode of the flyback converter can correspond to the current working state in real time, the switching efficiency of the working frequency and the working state of the flyback converter is further improved, and the working stability of the flyback converter is improved.
Description
Technical Field
The present disclosure relates to the field of switching power supply control methods, and in particular, to a flyback converter control method and a flyback converter.
Background
Flyback converters are widely used in various consumer electronic products and are the main topology of medium and small power supplies. The scheme of high efficiency, low noise is extremely important to reduce system cost, improves user experience. Fig. 1 is a schematic diagram of a typical flyback converter circuit. Wherein the input is AC alternating voltage, and C1 is a filter capacitor after rectifying the input voltage. Q1 is the primary side main switching tube. The transformer T1 has a primary winding Np, a secondary winding Ns, and an auxiliary winding Na. D1 is an output rectifier. The controller provides the pick-up supply VCC from the auxiliary winding through a rectifier tube D2. The controller output signal DRV drives the on and off of Q1. When Q1 is on, the transformer stores energy from the input. When Q1 is off, the transformer releases energy to the output. The control circuit can acquire the voltage information of the transformer operation by detecting the signal of the auxiliary winding Na to the ZCD. The control circuit obtains the operating current information of Q1 by detecting the Rcs voltage to CS. FB is a feedback loop output to control the output voltage or current. To simplify control, reduce the stress of the main power switching tube and the output rectifying tube, the medium and small power flyback circuit usually works in a discontinuous conduction mode (Discontinuous Conduction Mode, DCM), as shown in FIG. 2, wherein DRV Is the driving signal of the switching tube, ip Is the current of the primary side of the transformer, is the current of the secondary side of the transformer, and Vdrain Is the signal of the drain electrode of the switching tube. In DCM, the turn-on (t 1, t 2) of the drive signal DRV occurs after the secondary current ends to zero. Fig. 2 shows a typical quasi-resonant operating waveform, i.e., the on signal is waiting until the Vdrain signal is on to the lowest point. And figure 3 shows DCM with a longer dead time after secondary current return to zero.
Corresponding to the DCM mode is a current continuous mode, i.e. continuous conduction mode (Continuous Conduction Mode, CCM), as shown in fig. 4. In CCM mode, the turn-on (t 1, t 2) of the drive signal DRV occurs before the secondary side current ends to zero. The voltage stress of the switching tube and the rectifying tube in the CCM mode is higher, but the CCM mode improves the switching frequency, and can improve the output power under the same switching working current condition. In many flyback converter applications with low cost DCM operation, if a smaller input capacitor is used to reduce the cost and the output power requirement is high, when the input voltage is low, the peak current is limited by the maximum value of the controller, so that the output is out of balance and a power frequency ripple exceeding the index requirement is generated. In order to be able to reduce the output ripple, CCM control schemes are introduced, which reduce the ripple by increasing the output power by CCM. In contrast, in the case of a low input voltage, the voltage stresses of the switching tube and the rectifying tube are relatively low even in CCM mode, so that this is a comparatively advantageous control method.
In CCM mode, the time Toff of the shutdown needs to be determined. There are 2 general approaches as follows.
Practice 1: a fixed preset off time Toff is used. As shown in fig. 4, toff is the off-portion time of the switching tube. The controller determines a fixed off time Toff. When the controller finds that the loop feedback signal FB has reached a limit and cannot achieve the output regulation function, changing the switching process forces the switching tube to turn on the next drive signal according to the predetermined toff time.
And 2: a variable off-time Toff is employed. As shown in fig. 5. During each cycle, the controller records the off time Toff of the current cycle. When the controller finds that the loop feedback signal FB has approached the limit, this Toff time is taken as the off time controlled in CCM mode. The threshold value (fb_a) of FB for this comparison may be determined according to the control target, and a deeper CCM may take on a lower fb_a value. As shown in fig. 5, after FB reaches fb_a, the off time toff3 is recorded. After entering CCM, the switching tube turns on the next drive signal according to the recorded predetermined toff3 time.
Both current practices 1 and 2 can achieve the purpose of reducing ripple, but there are certain limitations in practical applications.
In the method 1, since the Toff time is fixed, the resistance of the sampling resistor Rcs increases when the flyback converter temperature increases. The same switching currents Ip, CS have a rising sample value. This results in reduced primary current, reduced output power, and reduced CCM dynamics of reducing output ripple for the same peak current control level. In practical applications, the output ripple increases after the temperature increases.
Approach 2 can detect Toff time in real time. When the temperature increases, if the DCM control mode adopts the quasi-resonant mode, the relative Toff time decreases, so that the CCM depth is automatically increased, but when the value of the detection point fb_a is increased, the value of the detection point fb_a does not operate in the condition of the first trough of quasi-resonance (as shown in fig. 3), or does not operate in the condition of quasi-resonance, the corresponding Toff time changes, and an error or an excessive value is recorded. In this control method, FB is required to correspond to a corresponding operating frequency, for example, the frequency is increased by 2 times, the frequency is relatively high, and the system efficiency is rather reduced. Therefore, there is a limit to the control of the flyback converter, reducing the application range of such control methods. That is, the control method in the related art has difficulty in efficiently selecting and switching the appropriate operation mode in response to the actual operation state of the flyback converter.
Disclosure of Invention
The application relates to a control method of a flyback converter and the flyback converter, which can efficiently select and switch a proper working mode according to the actual working state of the flyback converter. The technical scheme is as follows:
in one aspect, a control method of a flyback converter is provided, and the method is applied to a control circuit of the flyback converter, wherein the control circuit comprises a peak current control module, a comparator, a pulse width recording module, a pulse width detection module, a turn-off time calculation module, a turn-off time control module and a driving module;
the peak current control module is connected with the positive electrode input end of the comparator, and the output end of the comparator is connected with the pulse width recording module;
the pulse width recording module is connected with the pulse width detection module and the turn-off time calculation module;
the turn-off time calculation module is connected with the turn-off time control module;
the turn-off time control module is connected with the driving module;
the driving module is used for generating and outputting a driving signal;
the pulse width detection module is used for receiving a zero crossing detection (Zero Crossing Detector, ZCD) signal;
the peak current control module is used for receiving the feedback loop output signal;
the method comprises the following steps:
receiving a feedback signal;
the feedback signal passes through a peak current control module to generate a peak current control quantity;
inputting the peak current control quantity into the positive electrode input end of the comparator, and outputting to obtain a comparison pulse signal;
acquiring ZCD pulse signals;
performing width detection on the ZCD pulse signal by a pulse width detection module to obtain a pulse signal width;
inputting the pulse signal width into a pulse width recording module for width recording;
inputting the pulse signal width into a turn-off time calculation module, and generating turn-off time data, wherein the turn-off time data is used for indicating turn-off time in each working period under a continuous conduction mode CCM;
the turn-off time data is input into the turn-off time control module and the driving module, a driving signal corresponding to the turn-off time data is output, and the driving signal is used for controlling the working state and the working frequency of the flyback converter.
In an alternative embodiment, the peak current control quantity is input to the positive electrode input end of the comparator, and the output obtains a comparison pulse signal, which comprises:
and inputting the peak current control quantity into the positive end of the comparator, inputting the peak current control quantity threshold value into the negative end of the comparator, and outputting to obtain a comparison pulse signal.
In an alternative embodiment, the pulse signal width is input to a turn-off time calculation module to generate turn-off time data, comprising:
acquiring CCM depth control quantity data;
inputting CCM depth control quantity data and pulse signal width into a turn-off time calculation module;
the turn-off time data is generated by a turn-off time calculation module based on a turn-off time calculation rule.
In an alternative embodiment, the off-time calculation rule comprises a subtraction rule;
generating, by the turn-off time calculation module, turn-off time data based on a turn-off time calculation rule, comprising:
determining a depth control constant corresponding to the CCM depth control quantity data through a turn-off time calculation module;
based on the subtraction rule, the difference in depth control constant and pulse signal width is determined as off-time data.
In an alternative embodiment, the off-time calculation rule comprises a multiplication rule,
generating, by the turn-off time calculation module, turn-off time data based on a turn-off time calculation rule, comprising:
determining a depth data percentage constant corresponding to the CCM depth control quantity data through a turn-off time calculation module;
based on the multiplication rule, the product of the depth data percentage constant and the pulse signal width is determined as off-time data.
In another aspect, a flyback converter is provided, including a control circuit of the flyback converter as described above.
The beneficial effects that this application provided technical scheme brought include at least:
(1) In the process of controlling the working frequency and the working state of the flyback converter, the comparator is used for determining the pulse width of the feedback signal, and a control signal for controlling the turn-off time and the working mode is generated based on the real-time pulse width, so that the working frequency and the working mode of the flyback converter can correspond to the current working state in real time.
(2) The switching efficiency of the working frequency and the working state of the flyback converter is improved, and the working stability of the flyback converter is improved.
(3) The output ripple when the input filter capacitance is small is significantly reduced.
(4) The implementation mode is simple, slope compensation is not needed, and the chip design is simplified.
Drawings
In order to more clearly illustrate the technical solutions of the embodiments of the present application, the drawings that are needed in the description of the embodiments will be briefly introduced below, and it is obvious that the drawings in the following description are only some embodiments of the present application, and that other drawings may be obtained according to these drawings without inventive effort for a person skilled in the art.
Fig. 1 shows a schematic structure of a flyback converter in the related art.
Fig. 2 shows a schematic diagram of the operation waveforms of a flyback converter in the related art.
Fig. 3 shows a schematic diagram of DCM operation waveforms in the related art.
Fig. 4 shows a schematic diagram of CCM operation waveforms in the related art.
Fig. 5 shows a schematic diagram of the operation waveform of the DCM to CCM transition in the related art.
Fig. 6 shows a schematic structural diagram of a control circuit of a flyback converter according to an exemplary embodiment of the present application.
Fig. 7 is a schematic flow chart of a control method of a flyback converter according to an exemplary embodiment of the present application.
Fig. 8 shows a schematic diagram of an operational waveform of a flyback converter according to an exemplary embodiment of the present application.
Fig. 9 shows a flowchart of another method for controlling a flyback converter according to an exemplary embodiment of the present application.
Detailed Description
For the purpose of making the objects, technical solutions and advantages of the present application more apparent, the embodiments of the present application will be described in further detail below with reference to the accompanying drawings.
Fig. 6 shows a schematic structural diagram of a control circuit of a flyback converter according to an exemplary embodiment of the present application. Referring to fig. 6, the control circuit includes a peak current control module 610, a comparator 620, a pulse width recording module 630, a pulse width detecting module 640, a turn-off time calculating module 650, a turn-off time control module 660, and a driving module 670; the peak current control module 610 is connected to the positive input of the comparator 620, and the output of the comparator 620 is connected to the pulse width recording module 630; the pulse width recording module 630 is connected with the pulse width detecting module 640 and the off-time calculating module 650; the turn-off time calculation module 650 is connected with the turn-off time control module 660; the turn-off time control module 660 is connected with the driving module 670; the driving module 670 is used for generating and outputting a driving signal; the pulse width detection module 640 is configured to receive the ZCD signal; the peak current control module 610 is configured to receive the feedback loop output signal.
The specific implementation forms of the modules in the control circuit and the application are not limited, and only the module functions and connection relations of the modules are described.
Fig. 6 shows a circuit configuration of the flyback converter, which is obtained by replacing the configuration of the flyback converter in the related art shown in fig. 1 with a control circuit.
Referring to fig. 6, fig. 7 is a schematic flow chart of a control method of a flyback converter according to an exemplary embodiment of the present application, where the method includes:
This is the process of the feedback process entering the control circuit of the flyback converter as shown in fig. 6. This signal is the loop feedback signal FB shown in fig. 6.
After receiving the feedback signal, the feedback signal is transformed by the peak current control module to generate the peak current control amount ipk_reg.
In step 703, the peak current control amount is input to the positive input terminal of the comparator, and a comparison pulse signal is output.
In the embodiment of the application, the comparator is used for comparing the peak current control quantity with the parameter input by the cathode to generate a comparison pulse signal. As shown in fig. 6, the comparison pulse signal is p1.
In the embodiment of the present application, corresponding to the case shown in fig. 6, the control circuit shown in the present application has two data input terminals, and in the other data input terminal, the control circuit will acquire the ZCD pulse signal from the other modules of the flyback converter.
In the embodiment of the application, the pulse width of the ZCD pulse signal can be determined by the pulse width detection module.
In the embodiment of the present application, the pulse signal width is recorded based on the generation period of the comparison pulse signal in one width recording period. That is, when one comparison pulse signal p1 is received, one recording is performed for the pulse signal width to unify the timings, and thus a matched operation waveform is generated.
In the embodiment of the present application, the off-time data is used to indicate the off-time in each working cycle in the continuous conduction mode CCM.
After determining the turn-off time, the control circuit generates a corresponding driving signal DRV and outputs the driving signal.
In correspondence to the above process, please refer to fig. 8, which shows the correspondence between the driving signal and the primary current Ip of the transformer, the secondary current Is of the transformer, and the signal Vdrain of the drain of the switching tube.
According to the technical scheme, in different control strategies, although the peak current and the working frequency are changed, an identity shown in the following formula 1 exists:
in the formula, lm is the excitation inductance of the transformer, ipk is the primary peak current, n is the primary-secondary turn ratio of the transformer, vout is the output voltage, and Tr is the magnetic recovery time of the transformer. In a stable operating circuit Lm, n, and Vout are all determined, so Ipk has a fixed relationship with Tr and does not change with the frequency control method. Regardless of the variation of the control curve, there can always be a consistent Tz value as long as the width of the ZCD is recorded at the ipk_a point. Therefore, when the method is adopted, the uncertainty caused by different frequency control methods and caused by recording Toff time in the method 2 related to the prior art is avoided by recording the width of the ZCD according to the Ipk_a.
Meanwhile, when the temperature changes, the resistance of the sampling resistor Rcs increases. Although the current on the primary side is reduced under the same control amount of Ipk reg, the power of the CCM for providing output power is weakened. However, under the working condition of the method, when the actual switching current is reduced, the magnetic recovery time Tr of the transformer is also reduced, that is, the detected tz3 is reduced by the formula. Therefore, the amount calculated by the off-time becomes automatically small, thereby automatically deepening the CCM and improving the output power.
In the embodiment of the application, the driving signal is used for controlling the working mode and the working frequency of the flyback converter.
In summary, in the method provided by the embodiment of the present application, during the process of controlling the working frequency and the working state of the flyback converter, the comparator is used to determine the pulse width of the feedback signal, and generate the control signal for controlling the turn-off time and the working mode based on the real-time pulse width, so that the working frequency and the working mode of the flyback converter can correspond to the current working state in real time, thereby improving the switching efficiency of the working frequency and the working state of the flyback converter, and improving the working stability of the flyback converter.
Fig. 9 is a schematic flow chart of another method for controlling a flyback converter according to an exemplary embodiment of the present application, and the method is applied to a control circuit of the flyback converter shown in fig. 6, for example, and includes:
This process corresponds to the process shown in step 701, and will not be described in detail here.
This process corresponds to the process shown in step 702, and will not be described in detail here.
In step 903, the peak current control amount is input to the positive terminal of the comparator, and the peak current control amount threshold is input to the negative terminal of the comparator, and a comparison pulse signal is output.
In the embodiment of the present application, the input quantity of the negative input end of the comparator is a peak current control quantity threshold value, so as to generate the comparison pulse signal.
In step 905, the ZCD pulse signal is detected in width by a pulse width detection module, so as to obtain the pulse signal width.
In step 907, CCM depth control amount data is acquired.
In this embodiment of the present application, the CCM depth control amount data is a preset value corresponding to a control circuit of the flyback converter, and the CCM depth control amount data may be implemented as a control constant in a numerical form, or may be implemented as a data combination.
This process is the data entry process.
In step 909, turn-off time data is generated based on the turn-off time calculation rule by the turn-off time calculation module.
In the embodiment of the present application, the off-time calculation rule includes a subtraction rule and a multiplication rule. The corresponding subtraction rule is shown in the following equation 2:
the corresponding multiplication rule is as shown in the following equation 3:
in the above equations 2 and 3, toff is the off time, tz is the pulse signal width, tc is the depth control constant determined by the CCM depth control amount data, and m is the depth data percentage constant corresponding to the CCM depth control amount data.
That is, the depth control constant corresponding to the CCM depth control amount data is determined by the off-time calculation module in correspondence with the subtraction rule, and the difference between the depth control constant and the pulse signal width is determined as the off-time data based on the subtraction rule. And determining a depth data percentage constant corresponding to the CCM depth control quantity data through a turn-off time calculation module according to the multiplication rule, and determining the product of the depth data percentage constant and the pulse signal width as turn-off time data based on the multiplication rule.
The process corresponds to step 708.
The beneficial effects corresponding to the embodiment of the application at least comprise:
(1) In the process of controlling the working frequency and the working state of the flyback converter, the comparator is used for determining the pulse width of the feedback signal, and a control signal for controlling the turn-off time and the working mode is generated based on the real-time pulse width, so that the working frequency and the working mode of the flyback converter can correspond to the current working state in real time.
(2) The switching efficiency of the working frequency and the working state of the flyback converter is improved, and the working stability of the flyback converter is improved.
(3) The output ripple when the input filter capacitance is small is significantly reduced.
(4) The implementation mode is simple, slope compensation is not needed, and the chip design is simplified.
The foregoing description of the preferred embodiments is merely exemplary in nature and is not intended to limit the invention, but is intended to cover various modifications, substitutions, improvements, and alternatives falling within the spirit and principles of the invention.
Claims (3)
1. A control method of flyback converter is characterized in that the method is applied to the self-adaptive intermittent and continuous current mode control circuit of flyback converter,
the control circuit comprises a peak current control module, a comparator, a pulse width recording module, a pulse width detection module, a turn-off time calculation module, a turn-off time control module and a driving module;
the peak current control module is connected with the positive electrode input end of the comparator, and the output end of the comparator is connected with the pulse width recording module;
the pulse width recording module is connected with the pulse width detection module and the turn-off time calculation module;
the turn-off time calculation module is connected with the turn-off time control module;
the turn-off time control module is connected with the driving module;
the driving module is used for generating and outputting a driving signal;
the pulse width detection module is used for receiving the zero crossing detection ZCD signal;
the peak current control module is used for receiving a feedback loop output signal;
the method comprises the following steps:
receiving a feedback signal;
the feedback signal passes through the peak current control module to generate a peak current control quantity;
inputting the peak current control quantity into the positive electrode input end of the comparator, and outputting to obtain a comparison pulse signal;
acquiring ZCD pulse signals;
performing width detection on the ZCD pulse signal through the pulse width detection module to obtain a pulse signal width;
inputting the pulse signal width into a pulse width recording module for width recording;
acquiring CCM depth control quantity data which is a preset value corresponding to a control circuit of a flyback converter;
inputting the CCM depth control amount data and the pulse signal width into the turn-off time calculation module;
determining, by the off-time calculation module, a depth control constant corresponding to the CCM depth control amount data, and determining, based on a subtraction rule, that a difference between the depth control constant and the pulse signal width is the off-time data; or, determining, by the off-time calculation module, a depth data percentage constant corresponding to the CCM depth control amount data, and determining, based on a multiplication rule, a product of the depth data percentage constant and the pulse signal width as the off-time data;
and inputting the turn-off time data into the turn-off time control module and the driving module, and outputting a driving signal corresponding to the turn-off time data, wherein the driving signal is used for controlling the working mode and the working frequency of the flyback converter.
2. The method of claim 1, wherein said inputting said peak current control amount to a positive input of said comparator and outputting a resulting comparison pulse signal comprises:
and inputting the peak current control quantity into the positive end of the comparator, inputting the peak current control quantity threshold value into the negative end of the comparator, and outputting to obtain the comparison pulse signal.
3. A flyback converter, characterized in that the flyback converter comprises a control circuit of the flyback converter for performing the control method of the flyback converter of claim 1.
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| CN104486891A (en) * | 2014-12-30 | 2015-04-01 | 杭州士兰微电子股份有限公司 | Led drive circuit and constant current driver |
| CN204291527U (en) * | 2014-12-30 | 2015-04-22 | 杭州士兰微电子股份有限公司 | LED drive circuit and constant-current driver |
| CN104953829A (en) * | 2015-05-21 | 2015-09-30 | 西南交通大学 | Quasi frequency peak current control method applied to BUCK circuit |
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| US7642733B2 (en) * | 2008-05-19 | 2010-01-05 | Leadtrend Technology Corp. | Driving circuit for light emitting device with compensation mechanism and driving method thereof |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN104486891A (en) * | 2014-12-30 | 2015-04-01 | 杭州士兰微电子股份有限公司 | Led drive circuit and constant current driver |
| CN204291527U (en) * | 2014-12-30 | 2015-04-22 | 杭州士兰微电子股份有限公司 | LED drive circuit and constant-current driver |
| CN104953829A (en) * | 2015-05-21 | 2015-09-30 | 西南交通大学 | Quasi frequency peak current control method applied to BUCK circuit |
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