CN115632536A - Double closed-loop control method and device of single-phase inverter and storage medium - Google Patents
Double closed-loop control method and device of single-phase inverter and storage medium Download PDFInfo
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Abstract
The application provides a double closed-loop control method, a device and a storage medium of a single-phase inverter, wherein the double closed-loop control method comprises the following steps: acquiring inversion output voltage and inversion output current of a single-phase inverter, and determining first orthogonal voltage and second orthogonal voltage based on the inversion output voltage; determining a D-axis direct current input voltage and a Q-axis direct current input voltage based on the first quadrature voltage and the second quadrature voltage; carrying out park inverse processing on the D-axis direct-current input voltage and the Q-axis direct-current input voltage to determine a current inner ring reference value; and PR processing is carried out on the current inner ring reference value and the inversion output current, a sine signal of the single-phase inverter is output, and double closed-loop control of the single-phase inverter is completed by utilizing the sine signal. The problem of hysteresis of the alternating current output voltage is solved by adopting the inner loop current PR control method, and the fast voltage response capability, the phase deviation reduction and the output current non-static tracking are realized.
Description
Technical Field
The present disclosure relates to the field of inverter control technologies, and in particular, to a method and an apparatus for dual closed-loop control of a single-phase inverter, and a storage medium.
Background
Inverters are widely used in various industries, and are relatively common devices. The inverter adopts various control modes, and open-loop control and closed-loop control are common. The open-loop control method directly outputs the inverter as a voltage source, but has many disadvantages, and when the output load becomes large, the output voltage drops accordingly. The voltage closed-loop control method can still maintain the voltage stability when the load of the output end becomes large, but the method has the defect that the output phase is inconsistent with the given phase.
At this stage, the instantaneous voltage and current values are usually used as PI feedback control, or imaginary voltage and current α and β coordinates are used. Because the feedback control quantity is alternating current voltage and alternating current, the alternating current output voltage has the disadvantages of hysteresis and difficulty in adjusting control parameters to be optimal, and the adoption of an imaginary coordinate system has the disadvantages of high requirement on the operation speed of the micro control unit and 90-degree hysteresis of voltage and current control. Therefore, how to avoid the ac voltage hysteresis in the single-phase inverter dual closed-loop control process becomes a non-trivial technical problem.
Disclosure of Invention
In view of this, an object of the present invention is to provide a method, an apparatus, and a storage medium for controlling a double closed loop of a single-phase inverter, which can not only instantaneously control an output voltage waveform by using a PI controller in a DQ coordinate but also implement non-dead-center tracking of an output current by using current inner loop PR control, thereby avoiding a problem of hysteresis of an ac output voltage, and implementing fast voltage response capability and phase deviation reduction.
The embodiment of the application provides a double closed-loop control method of a single-phase inverter, which comprises the following steps:
acquiring inversion output voltage and inversion output current of a single-phase inverter, and determining first orthogonal voltage and second orthogonal voltage based on the inversion output voltage;
determining a D-axis direct current input voltage and a Q-axis direct current input voltage based on the first quadrature voltage and the second quadrature voltage;
carrying out park inverse processing on the D-axis direct-current input voltage and the Q-axis direct-current input voltage to determine a current inner ring reference value;
and PR processing is carried out on the current inner ring reference value and the inversion output current, a sine signal of the single-phase inverter is output, and double closed-loop control of the single-phase inverter is completed by utilizing the sine signal.
In one possible embodiment, the determining the D-axis dc input voltage and the Q-axis dc input voltage based on the first quadrature voltage and the second quadrature voltage includes:
performing DQ conversion on the first orthogonal voltage to determine a D-axis voltage feedback value; performing DQ conversion on the second orthogonal voltage to determine a Q-axis voltage feedback value;
performing PI processing on the D-axis voltage feedback value to determine a D-axis direct current input voltage; and performing PI processing on the Q-axis voltage feedback value to determine Q-axis direct-current input voltage.
In a possible implementation manner, the first orthogonal voltage is subjected to DQ conversion, and a D-axis voltage feedback value is determined; and performing DQ transformation on the second orthogonal voltage to determine a Q-axis voltage feedback value, including:
acquiring a preset sine wave angle, and determining a cosine value of the sine wave angle and a sine value of the sine wave angle;
determining a first matrix formed by cosine values of the sine wave angles and sine values of the sine wave angles;
and determining the D-axis voltage feedback value and the Q-axis voltage feedback value according to the product of the first matrix and a first vector formed by the first orthogonal voltage and the second orthogonal voltage.
Determining the D-axis DC input voltage by:
acquiring a preset D-axis voltage reference value;
determining a first voltage difference value based on the D-axis voltage reference value and the D-axis voltage feedback value;
and performing PI processing on the first voltage difference value to determine the D-axis direct-current input voltage.
In one possible embodiment, the Q-axis dc input voltage is determined by:
acquiring a preset Q-axis voltage reference value;
determining a second voltage difference value based on the Q-axis voltage reference value and the Q-axis voltage feedback value;
and performing PI processing on the second voltage difference value to determine the direct current input voltage of the Q axis.
In one possible implementation, the performing park inverse processing on the D-axis dc input voltage and the Q-axis dc input voltage to determine a current inner loop reference value includes:
determining a second matrix formed by sine values of preset sine wave angles and cosine values of the preset sine wave angles;
and determining the current inner loop reference value according to the second matrix and the product of a second vector formed by the D-axis direct-current input voltage and the Q-axis direct-current input voltage.
The embodiment of the present application further provides a dual closed-loop control device of a single-phase inverter, where the dual closed-loop control device includes:
the determining module is used for acquiring the inversion output voltage and the inversion output current of the single-phase inverter and determining a first orthogonal voltage and a second orthogonal voltage based on the inversion output voltage;
a transformation module for determining a D-axis dc input voltage and a Q-axis dc input voltage based on the first and second quadrature voltages;
the current inner ring reference value determining module is used for performing park inverse processing on the D-axis direct-current input voltage and the Q-axis direct-current input voltage to determine a current inner ring reference value;
and the sinusoidal signal determination module is used for carrying out PR processing on the current inner ring reference value and the inversion output current, outputting a sinusoidal signal of the single-phase inverter and completing double closed-loop control on the single-phase inverter by using the sinusoidal signal.
In a possible implementation manner, when the transformation module is configured to determine the D-axis dc input voltage and the Q-axis dc input voltage based on the first quadrature voltage and the second quadrature voltage, the transformation module is specifically configured to:
performing DQ conversion on the first orthogonal voltage to determine a D-axis voltage feedback value; performing DQ conversion on the second orthogonal voltage to determine a Q-axis voltage feedback value;
performing PI processing on the D-axis voltage feedback value to determine a D-axis direct-current input voltage; and performing PI processing on the Q-axis voltage feedback value to determine Q-axis direct-current input voltage.
An embodiment of the present application further provides an electronic device, including: a processor, a memory and a bus, the memory storing machine readable instructions executable by the processor, the processor and the memory communicating via the bus when the electronic device is running, the machine readable instructions when executed by the processor performing the steps of the method for dual closed-loop control of a single-phase inverter as described above.
Embodiments of the present application also provide a computer-readable storage medium, on which a computer program is stored, where the computer program is executed by a processor to perform the steps of the double closed-loop control method for a single-phase inverter as described above.
The embodiment of the application provides a double closed-loop control method and device for a single-phase inverter and a storage medium, wherein the double closed-loop control method comprises the following steps: acquiring inversion output voltage and inversion output current of a single-phase inverter, and determining first orthogonal voltage and second orthogonal voltage based on the inversion output voltage; determining a D-axis direct current input voltage and a Q-axis direct current input voltage based on the first quadrature voltage and the second quadrature voltage; carrying out park inverse processing on the D-axis direct-current input voltage and the Q-axis direct-current input voltage to determine a current inner ring reference value; and PR processing is carried out on the current inner ring reference value and the inversion output current, a sine signal of the single-phase inverter is output, and double closed-loop control of the single-phase inverter is completed by utilizing the sine signal. By adopting the method of controlling the inner loop current PR, the output voltage waveform can be instantly controlled by using a PI controller under a DQ coordinate, and the output current can be tracked without static error by controlling the current inner loop PR, so that the problem of lag of the alternating current output voltage is avoided, and the fast voltage response capability and the phase deviation reduction are realized.
In order to make the aforementioned objects, features and advantages of the present application more comprehensible, preferred embodiments accompanied with figures are described in detail below.
Drawings
To more clearly illustrate the technical solutions of the embodiments of the present application, the drawings needed in the embodiments will be briefly described below, it should be understood that the following drawings only illustrate some embodiments of the present application and therefore should not be considered as limiting the scope, and those skilled in the art can also obtain other related drawings based on the drawings without inventive efforts.
Fig. 1 is a flowchart of a double closed-loop control method of a single-phase inverter according to an embodiment of the present disclosure;
fig. 2 is a schematic diagram of a double closed-loop control method of a single-phase inverter according to an embodiment of the present disclosure;
fig. 3 is a schematic diagram of a sinusoidal signal waveform of a dual closed-loop control method of a single-phase inverter according to an embodiment of the present disclosure;
fig. 4 is a schematic structural diagram of a dual closed-loop control device of a single-phase inverter according to an embodiment of the present disclosure;
fig. 5 is a schematic structural diagram of an electronic device according to an embodiment of the present application.
Detailed Description
In order to make the purpose, technical solutions and advantages of the embodiments of the present application clearer, the technical solutions in the embodiments of the present application will be clearly and completely described below with reference to the drawings in the embodiments of the present application, and it should be understood that the drawings in the present application are for illustrative and descriptive purposes only and are not intended to limit the scope of the present application. Additionally, it should be understood that the schematic drawings are not necessarily drawn to scale. The flowcharts used in this application illustrate operations implemented according to some embodiments of the present application. It should be understood that the operations of the flow diagrams may be performed out of order, and that steps without logical context may be reversed in order or performed concurrently. In addition, one skilled in the art, under the guidance of the present disclosure, may add one or more other operations to the flowchart, or may remove one or more operations from the flowchart.
In addition, the described embodiments are only a part of the embodiments of the present application, and not all of the embodiments. The components of the embodiments of the present application, as generally described and illustrated in the figures herein, could be arranged and designed in a wide variety of different configurations. Thus, the following detailed description of the embodiments of the present application, presented in the accompanying drawings, is not intended to limit the scope of the claimed application, but is merely representative of selected embodiments of the application. All other embodiments, which can be derived by a person skilled in the art from the embodiments of the present application without making any creative effort, shall fall within the protection scope of the present application.
To enable one skilled in the art to use the present disclosure, the following embodiments are given in conjunction with a specific application scenario "double closed loop control of a single-phase inverter", and it will be apparent to one skilled in the art that the general principles defined herein may be applied to other embodiments and application scenarios without departing from the spirit and scope of the present disclosure.
The following method, apparatus, electronic device or computer-readable storage medium in the embodiments of the present application may be applied to any scenario where dual closed-loop control of a single-phase inverter is required, and the embodiments of the present application do not limit specific application scenarios.
First, an application scenario to which the present application is applicable will be described. The method and the device can be applied to the technical field of inverter control.
It has been found that, at the present stage, the instantaneous voltage and current values are usually used as PI feedback control, or imaginary α and β coordinates of voltage and current are used. Because the feedback control quantity is alternating current voltage and alternating current, the alternating current output voltage has the disadvantages of hysteresis and difficulty in adjusting control parameters to be optimal, and the adoption of an imaginary coordinate system has the disadvantages of high requirement on the operation speed of the micro-control unit and 90-degree hysteresis of voltage and current control. Therefore, how to avoid the ac voltage hysteresis in the single-phase inverter dual closed-loop control process becomes a non-trivial technical problem.
Based on this, the embodiment of the application provides a double closed-loop control method for a single-phase inverter, and by adopting a method of inner loop current PR control, not only can the output voltage waveform be instantly controlled by using a PI controller under a DQ coordinate, but also no static error tracking of the output current can be realized through the current inner loop PR control, so that the problem of hysteresis of alternating-current output voltage is avoided, and the fast voltage response capability and the reduction of phase deviation are realized.
Referring to fig. 1, fig. 1 is a flowchart illustrating a double closed-loop control method of a single-phase inverter according to an embodiment of the present disclosure. As shown in fig. 1, a dual closed-loop control method provided in an embodiment of the present application includes:
s101: the method comprises the steps of obtaining inversion output voltage and inversion output current of the single-phase inverter, and determining first orthogonal voltage and second orthogonal voltage based on the inversion output voltage.
In the step, the inversion output voltage and the inversion output current of the single-phase inverter are obtained, the inversion output voltage is subjected to virtual coordinate axis algorithm calculation, and a first orthogonal voltage and a second orthogonal voltage are determined.
Here, the virtualized axis algorithm differentiates the acquired inverter output voltage Vac
And obtaining a first orthogonal voltage V alpha and a second orthogonal voltage V beta of the virtual coordinate axis after calculation.
The circuit for converting direct current into alternating current is referred to as an inverter circuit, and the inverter circuit is also referred to as an inverter for short. The inverter circuit can be divided into a single-phase inverter, a three-phase inverter and a multi-phase inverter according to the difference of the number of phases of the output alternating voltage.
S102: determining a D-axis DC input voltage and a Q-axis DC input voltage based on the first and second quadrature voltages.
In this step, a D-axis dc input voltage and a Q-axis dc input voltage are determined according to the first quadrature voltage and the second quadrature voltage.
In one possible embodiment, the determining the D-axis dc input voltage and the Q-axis dc input voltage based on the first quadrature voltage and the second quadrature voltage includes:
a: performing DQ conversion on the first orthogonal voltage to determine a D-axis voltage feedback value; and performing DQ conversion on the second orthogonal voltage to determine a Q-axis voltage feedback value.
Here, the DQ conversion is performed on the first quadrature voltage to determine a D-axis voltage feedback value, and the DQ conversion is performed on the second quadrature voltage to determine a Q-axis voltage feedback value.
The DQ conversion is used to provide a standard sinusoidal reference value for the current inner loop and to provide a quiet control of the ac voltage signal by PI control.
In a possible implementation manner, the first orthogonal voltage is subjected to DQ conversion, and a D-axis voltage feedback value is determined; and performing DQ conversion on the second orthogonal voltage to determine a Q-axis voltage feedback value, including:
a: the method comprises the steps of obtaining a preset sine wave angle, and determining a cosine value of the sine wave angle and a sine value of the sine wave angle.
Here, the cosine value of the preset sine wave angle and the sine value of the sine wave angle are determined.
Wherein the preset sine wave angle is 0-2 pi.
b: a first matrix of cosine values of the sine wave angles and sine values of the sine wave angles is determined.
The method comprises the steps of determining a first matrix by utilizing a cosine value of a sine wave angle and a sine value of the sine wave angle.
Wherein, the expression form of the first matrix is as follows:
wherein, theta is a sine wave angle and ranges from 0 pi to 2 pi.
c: and determining the D-axis voltage feedback value and the Q-axis voltage feedback value according to the product of the first matrix and a first vector formed by the first orthogonal voltage and the second orthogonal voltage.
Here, the D-axis voltage feedback value and the Q-axis voltage feedback value are determined based on a product between a first matrix composed of cosine values of sine wave angles and sine values of the sine wave angles and a first vector composed of a first quadrature voltage and a second quadrature voltage.
Wherein, the first vector that first quadrature voltage and second quadrature voltage constitute is:
wherein the first orthogonal voltage is V α The second orthogonal voltage is V β 。
The determination formula of the D-axis voltage feedback value and the Q-axis voltage feedback value is as follows:
wherein the first orthogonal voltage is V α The second orthogonal voltage is V β Theta is a sine wave angle, V D Is a D-axis voltage feedback value, V Q And the Q-axis voltage feedback value is obtained.
B: performing PI processing on the D-axis voltage feedback value to determine a D-axis direct current input voltage; and performing PI processing on the Q-axis voltage feedback value to determine Q-axis direct-current input voltage.
Here, the D-axis voltage feedback value is input to a PI controller to perform PI processing, and the D-axis dc input voltage is determined. And inputting the Q-axis voltage feedback value into a PI controller for PI processing to determine the Q-axis direct-current input voltage.
In a specific embodiment, a preset sine wave angle is obtained, and a cosine value of the sine wave angle and a sine value of the sine wave angle are determined; determining a first matrix formed by cosine values of sine wave angles and sine values of the sine wave angles; and determining a D-axis voltage feedback value and a Q-axis voltage feedback value according to the product of the first matrix and a first vector formed by the first orthogonal voltage and the second orthogonal voltage. Acquiring a preset D-axis voltage reference value; and determining a first voltage difference value based on the D-axis voltage reference value and the D-axis voltage feedback value, inputting the first voltage difference value into a PI controller for PI processing, and determining the D-axis direct current input voltage. And obtaining a preset Q-axis voltage reference value, determining a second voltage difference value based on the Q-axis voltage reference value and the Q-axis voltage feedback value, inputting the second voltage difference value into a PI (proportional integral) controller to carry out PI (proportional integral) processing on the second voltage difference value, and determining the Q-axis direct-current input voltage. After the alternating voltage signal is converted into the direct current signal, the static-error-free control of the inversion output voltage can be realized through the PI controller, and meanwhile, a high-progress reference signal can be provided for the control of the current inner ring.
In one possible embodiment, the D-axis dc input voltage is determined by:
(1): and acquiring a preset D-axis voltage reference value.
Here, a preset D-axis voltage reference value is acquired.
(2): and determining a first voltage difference value based on the D-axis voltage reference value and the D-axis voltage feedback value.
Here, a first voltage difference value is determined according to a difference value between the D-axis voltage reference value and the D-axis voltage feedback value.
If the D-axis voltage reference value is smaller than the D-axis voltage feedback value, determining a first voltage difference value according to the absolute value of the difference value between the D-axis voltage reference value and the D-axis voltage feedback value.
(3): and performing PI processing on the first voltage difference value to determine the D-axis direct-current input voltage.
And inputting the first voltage difference value into a D-axis PI controller, and performing PI processing on the first voltage difference value to determine a D-axis direct-current input voltage.
In one possible embodiment, the Q-axis dc input voltage is determined by:
i: and acquiring a preset Q-axis voltage reference value.
Here, a preset Q-axis voltage reference value is acquired.
II: and determining a second voltage difference value based on the Q-axis voltage reference value and the Q-axis voltage feedback value.
Here, a second voltage difference value is determined based on a difference between the Q-axis voltage reference value and the Q-axis voltage feedback value.
And if the Q-axis voltage reference value is smaller than the Q-axis voltage feedback value, determining a second voltage difference value according to the absolute value of the difference value between the Q-axis voltage reference value and the Q-axis voltage feedback value.
III: and performing PI processing on the second voltage difference value to determine the direct current input voltage of the Q axis.
And inputting the second voltage difference value into a Q-axis PI controller, and performing PI processing on the second voltage difference value to determine the Q-axis direct-current input voltage.
In a specific embodiment, a preset D-axis voltage reference value and a preset Q-axis voltage reference value are obtained, a first voltage difference value is determined according to a difference value between the D-axis voltage reference value and a D-axis voltage feedback value, and a second voltage difference value is determined according to a difference value between the Q-axis voltage reference value and a Q-axis voltage feedback value. And inputting the first voltage difference value into a D-axis PI controller to determine D-axis direct-current input voltage, and inputting the second voltage difference value into a Q-axis PI controller to determine Q-axis direct-current input voltage.
S103: and carrying out park inverse processing on the D-axis direct-current input voltage and the Q-axis direct-current input voltage to determine a current inner ring reference value.
In this step, park inverse processing is performed on the D-axis dc input voltage and the Q-axis dc input voltage, and a current inner loop reference value is determined.
Here, the D-axis dc input voltage and the Q-axis dc input voltage are input to a park inverter to perform park inversion processing, and a current inner loop reference value is determined.
Here, the park transform equates the projection of ia, ib, ic currents on the α, β axes to the d, q axes, and equates the currents on the stator to both the direct and quadrature axes. For steady state, after such an equivalence, iq, id is exactly a constant. This is done so that when the differential equation of the rotor loop electromagnetic relationship is established, the coefficient matrix becomes a constant matrix, rather than a coefficient matrix that varies with the amount of time and space, which greatly simplifies the differential equation for analyzing the electromagnetic relationship of the generator and the motor.
In one possible embodiment, the determining the current inner loop reference value by performing park inverse processing on the D-axis dc input voltage and the Q-axis dc input voltage includes:
i: a second matrix is determined which is composed of preset sine values of sine wave angles and cosine values of sine wave angles.
Here, a second matrix is determined which is composed of sine values of sine wave angles and cosine values of sine wave angles set in advance.
Wherein the sine wave angle is 0-2 pi.
Wherein the expression form of the second matrix is:
wherein, theta is a sine wave angle and ranges from 0 pi to 2 pi.
ii: and determining the current inner loop reference value according to the second matrix and the product of a second vector formed by the D-axis direct-current input voltage and the Q-axis direct-current input voltage.
Here, the current inner loop reference value is determined based on the second matrix and a product between the D-axis direct-current input voltage and a second vector constituted by the Q-axis direct-current input voltage.
Wherein, the second vector that D axle direct current input voltage and Q axle direct current input voltage constitute is:
wherein, V d Is D-axis DC input voltage, V q Is the Q-axis dc input voltage.
Thus, the current inner loop reference value is determined by the following equation:
wherein, V α1 、V β1 Are all current inner ring reference values, and V is adopted in the scheme α1 As the current inner loop reference value.
S104: and PR processing is carried out on the current inner ring reference value and the inversion output current, a sine signal of the single-phase inverter is output, and double closed-loop control of the single-phase inverter is completed by utilizing the sine signal.
In the step, PR processing is carried out on the current inner ring reference value and the inversion output current, a sine signal of the single-phase inverter is output, and double closed-loop control over the single-phase inverter is completed by utilizing the sine signal.
And inputting the current inner ring reference value and the inversion output current into a PR controller for PR processing to obtain a sinusoidal signal of the single-phase inverter.
The PR controller has infinite gain within a specified fundamental frequency, and can realize the non-static tracking of alternating current.
In an embodiment, please refer to fig. 2, wherein fig. 2 is a schematic diagram of a dual closed-loop control method of a single-phase inverter according to an embodiment of the present disclosure. As shown in fig. 2, the α and β axis arithmetic units, the park converter, the park inverter, the D axis PI controller, and the Q axis PI controller are virtualized. The virtualized alpha-axis arithmetic unit and the virtualized beta-axis arithmetic unit are respectively connected with the D-axis PI controller and the Q-axis PI controller through DQ converters, and the outputs of the D-axis PI controller and the Q-axis PI controller are connected with the PR controller through park inverse converters. The virtualization coordinate axis algorithm obtains a first orthogonal voltage V alpha and a second orthogonal voltage V beta of a virtual coordinate axis by calculating the differential dv/dt of the acquired inversion output voltage Vac, and the Park transformation converts the first orthogonal voltage V alpha and the second orthogonal voltage V beta into a D-axis voltage feedback value and a Q-axis voltage feedback value respectively. And the D-axis voltage reference value and the D-axis voltage feedback value calculation difference value are subjected to PI operation and then serve as D-axis direct-current input voltage of Park inverse transformation, and the Q-axis voltage reference value and the Q-axis voltage feedback value calculation difference value are subjected to PI operation and then serve as Q-axis direct-current input voltage of Park inverse transformation. Determining a second matrix formed by sine values of preset sine wave angles and cosine values of the preset sine wave angles; and determining the current inner loop reference value according to the second matrix and the product of a second vector formed by the D-axis direct-current input voltage and the Q-axis direct-current input voltage. And the current inner ring reference value Iref and the inversion output current Iac are subjected to PR operation to obtain a sinusoidal signal, and the sinusoidal signal is used for controlling other devices such as an MOS (metal oxide semiconductor) tube and the like in the single-phase inverter to be started so as to complete double closed-loop control on the single-phase inverter. Through the quiet control of the inversion alternating current signals, the output harmonic component of the inverter can be greatly reduced, and the real-time dynamic regulation function of the output voltage can be realized. The inner loop AC signal can be controlled without a dead-end tracking by PR control. By means of the quiet control of the inverted alternating current signals, the output harmonic component of the inverter can be greatly reduced, and the real-time dynamic adjusting function of the output voltage can be greatly achieved.
Further, please refer to fig. 3, wherein fig. 3 is a schematic diagram of a sinusoidal signal waveform of a dual closed-loop control method of a single-phase inverter according to an embodiment of the present application. As shown in fig. 3, the current reference overcurrent limit reference signal generated by PI control and by DQ control, which is a standard sinusoidal signal, contains no harmonic components, and is very advantageous for the quiet tracking of the current inner loop PR. If the ac voltage signal passes through the PI controller directly and does not pass through the current reference overcurrent limit reference signal generated by the DQ control, it contains a large amount of harmonic components, which is not favorable for the non-static tracking of the current inner loop PR.
The non-static tracking is controlled according to a non-static principle, namely that a controlled object runs in a steady state or in a non-static mode or tracks a certain target signal. In engineering practice, a control system is usually affected by external disturbance, wherein step disturbance is one of the most common forms, such as sudden change of voltage and flow, and disturbance degrades the static characteristic, dynamic characteristic and steady-state performance of the system; furthermore, uncertainties in system parameters can also affect the performance of the control system. Therefore, a high performance quiet control system solution must compromise target tracking characteristics, interference suppression characteristics, and robustness.
The embodiment of the application provides a double closed-loop control method for a single-phase inverter, which comprises the following steps: acquiring inversion output voltage and inversion output current of a single-phase inverter, and determining first orthogonal voltage and second orthogonal voltage based on the inversion output voltage; determining a D-axis direct current input voltage and a Q-axis direct current input voltage based on the first quadrature voltage and the second quadrature voltage; carrying out park inverse processing on the D-axis direct-current input voltage and the Q-axis direct-current input voltage to determine a current inner ring reference value; PR processing is carried out on the current inner ring reference value and the inversion output current, a sine signal of the single-phase inverter is output, and double closed-loop control over the single-phase inverter is completed through the sine signal. By adopting the method of controlling the inner loop current PR, the output voltage waveform can be instantly controlled by using the PI controller under the DQ coordinate, and the output current can be controlled by the current inner loop PR without static error, so that the problem of lag of the alternating current output voltage is avoided, the rapid voltage response capability is realized, and the phase deviation and harmonic output are avoided.
Referring to fig. 4, fig. 4 is a schematic structural diagram of a dual closed-loop control device of a single-phase inverter according to an embodiment of the present disclosure. As shown in fig. 4, the double closed-loop control apparatus 400 of the single-phase inverter includes:
the determining module 410 is configured to obtain an inversion output voltage and an inversion output current of the single-phase inverter, and determine a first quadrature voltage and a second quadrature voltage based on the inversion output voltage;
a transformation module 420 configured to determine a D-axis dc input voltage and a Q-axis dc input voltage based on the first quadrature voltage and the second quadrature voltage;
a current inner loop reference value determining module 430, configured to perform park inverse processing on the D-axis dc input voltage and the Q-axis dc input voltage to determine a current inner loop reference value;
the sinusoidal signal determining module 440 is configured to perform PR processing on the current inner loop reference value and the inversion output current, output a sinusoidal signal of the single-phase inverter, and complete double closed-loop control on the single-phase inverter by using the sinusoidal signal.
Further, when the transformation module 420 is configured to determine the D-axis dc input voltage and the Q-axis dc input voltage based on the first orthogonal voltage and the second orthogonal voltage, the transformation module 420 is specifically configured to:
performing DQ conversion on the first orthogonal voltage to determine a D-axis voltage feedback value; performing DQ conversion on the second orthogonal voltage to determine a Q-axis voltage feedback value;
performing PI processing on the D-axis voltage feedback value to determine a D-axis direct-current input voltage; and performing PI processing on the Q-axis voltage feedback value to determine Q-axis direct-current input voltage.
Further, the transformation module 420 is configured to perform DQ transformation on the first orthogonal voltage to determine a D-axis voltage feedback value; and when DQ conversion is performed on the second quadrature voltage and a Q-axis voltage feedback value is determined, the conversion module 420 is specifically configured to:
acquiring a preset sine wave angle, and determining a cosine value of the sine wave angle and a sine value of the sine wave angle;
determining a first matrix formed by cosine values of the sine wave angles and sine values of the sine wave angles;
and determining the D-axis voltage feedback value and the Q-axis voltage feedback value according to the product of the first matrix and a first vector formed by the first orthogonal voltage and the second orthogonal voltage.
Further, the conversion module 420 determines the D-axis dc input voltage by:
acquiring a preset D-axis voltage reference value;
determining a first voltage difference value based on the D-axis voltage reference value and the D-axis voltage feedback value;
and performing PI processing on the first voltage difference value to determine the D-axis direct-current input voltage.
Further, the conversion module 420 determines the Q-axis dc input voltage by:
acquiring a preset Q-axis voltage reference value;
determining a second voltage difference value based on the Q-axis voltage reference value and the Q-axis voltage feedback value;
and performing PI processing on the second voltage difference value to determine the direct current input voltage of the Q axis.
Further, when the current inner loop reference value determining module 430 is configured to perform park inverse processing on the D-axis dc input voltage and the Q-axis dc input voltage to determine the current inner loop reference value, the current inner loop reference value determining module 430 is specifically configured to:
determining a second matrix formed by sine values of preset sine wave angles and cosine values of the preset sine wave angles;
and determining the current inner loop reference value according to the second matrix and the product of a second vector formed by the D-axis direct-current input voltage and the Q-axis direct-current input voltage.
The embodiment of the application provides a double closed-loop control device of a single-phase inverter, the double closed-loop control device includes: the determining module is used for acquiring the inversion output voltage and the inversion output current of the single-phase inverter and determining a first orthogonal voltage and a second orthogonal voltage based on the inversion output voltage; a transformation module for determining a D-axis dc input voltage and a Q-axis dc input voltage based on the first and second quadrature voltages; the current inner ring reference value determining module is used for carrying out park inverse processing on the D-axis direct-current input voltage and the Q-axis direct-current input voltage to determine a current inner ring reference value; and the sinusoidal signal determination module is used for carrying out PR processing on the current inner ring reference value and the inversion output current, outputting a sinusoidal signal of the single-phase inverter and finishing double closed-loop control on the single-phase inverter by using the sinusoidal signal. By adopting the method of controlling the inner loop current PR, the output voltage waveform can be instantly controlled by using the PI controller under the DQ coordinate, the output current can be controlled by the current inner loop PR, the problem of lag of the alternating current output voltage is avoided, the rapid voltage response capability is realized, and the phase deviation and the output harmonic wave are reduced.
Referring to fig. 5, fig. 5 is a schematic structural diagram of an electronic device according to an embodiment of the present disclosure. As shown in fig. 5, the electronic device 500 includes a processor 510, a memory 520, and a bus 530.
The memory 520 stores machine-readable instructions executable by the processor 510, when the electronic device 500 runs, the processor 510 communicates with the memory 520 through the bus 530, and when the machine-readable instructions are executed by the processor 510, the steps of the double closed-loop control method for a single-phase inverter in the embodiment of the method shown in fig. 1 may be executed.
An embodiment of the present application further provides a computer-readable storage medium, where a computer program is stored on the computer-readable storage medium, and when the computer program is executed by a processor, the steps of the double closed-loop control method for a single-phase inverter in the embodiment of the method shown in fig. 1 may be executed.
It can be clearly understood by those skilled in the art that, for convenience and simplicity of description, the specific working processes of the above-described systems, apparatuses and units may refer to the corresponding processes in the foregoing method embodiments, and are not described herein again.
In the several embodiments provided in the present application, it should be understood that the disclosed system, apparatus and method may be implemented in other ways. The above-described apparatus embodiments are merely illustrative, and for example, the division of the units into only one type of logical function may be implemented in other ways, and for example, multiple units or components may be combined or integrated into another system, or some features may be omitted, or not implemented. In addition, the shown or discussed mutual coupling or direct coupling or communication connection may be an indirect coupling or communication connection of devices or units through some communication interfaces, and may be in an electrical, mechanical or other form.
The units described as separate parts may or may not be physically separate, and parts displayed as units may or may not be physical units, may be located in one place, or may be distributed on a plurality of network units. Some or all of the units can be selected according to actual needs to achieve the purpose of the solution of the embodiment.
In addition, functional units in the embodiments of the present application may be integrated into one processing unit, or each unit may exist alone physically, or two or more units are integrated into one unit.
The functions, if implemented in software functional units and sold or used as a stand-alone product, may be stored in a non-transitory computer-readable storage medium executable by a processor. Based on such understanding, the technical solution of the present application or portions thereof that substantially contribute to the prior art may be embodied in the form of a software product stored in a storage medium and including instructions for causing a computer device (which may be a personal computer, a server, or a network device) to execute all or part of the steps of the method according to the embodiments of the present application. And the aforementioned storage medium includes: various media capable of storing program codes, such as a usb disk, a removable hard disk, a Read-only memory (ROM), a Random Access Memory (RAM), a magnetic disk, or an optical disk.
Finally, it should be noted that: the above-mentioned embodiments are only specific embodiments of the present application, and are used for illustrating the technical solutions of the present application, but not limiting the same, and the scope of the present application is not limited thereto, and although the present application is described in detail with reference to the foregoing embodiments, those skilled in the art should understand that: those skilled in the art can still make modifications or changes to the embodiments described in the foregoing embodiments, or make equivalent substitutions for some features, within the technical scope of the present disclosure; such modifications, changes or substitutions do not depart from the spirit and scope of the embodiments of the present application and are intended to be covered by the appended claims. Therefore, the protection scope of the present application shall be subject to the protection scope of the claims.
Claims (10)
1. A double closed-loop control method of a single-phase inverter, the double closed-loop control method comprising:
acquiring inversion output voltage and inversion output current of a single-phase inverter, and determining first orthogonal voltage and second orthogonal voltage based on the inversion output voltage;
determining a D-axis direct current input voltage and a Q-axis direct current input voltage based on the first quadrature voltage and the second quadrature voltage;
carrying out park inverse processing on the D-axis direct-current input voltage and the Q-axis direct-current input voltage to determine a current inner ring reference value;
and PR processing is carried out on the current inner ring reference value and the inversion output current, a sine signal of the single-phase inverter is output, and double closed-loop control of the single-phase inverter is completed by utilizing the sine signal.
2. The dual closed-loop control method of claim 1, wherein determining a D-axis dc input voltage and a Q-axis dc input voltage based on the first and second quadrature voltages comprises:
performing DQ conversion on the first orthogonal voltage to determine a D-axis voltage feedback value; performing DQ conversion on the second orthogonal voltage to determine a Q-axis voltage feedback value;
performing PI processing on the D-axis voltage feedback value to determine a D-axis direct-current input voltage; and performing PI processing on the Q-axis voltage feedback value to determine Q-axis direct-current input voltage.
3. The dual closed-loop control method according to claim 2, wherein the DQ transformation is performed on the first quadrature voltage to determine a D-axis voltage feedback value; and performing DQ transformation on the second orthogonal voltage to determine a Q-axis voltage feedback value, including:
acquiring a preset sine wave angle, and determining a cosine value of the sine wave angle and a sine value of the sine wave angle;
determining a first matrix formed by cosine values of the sine wave angles and sine values of the sine wave angles;
and determining the D-axis voltage feedback value and the Q-axis voltage feedback value according to the product of the first matrix and a first vector formed by the first orthogonal voltage and the second orthogonal voltage.
4. The dual closed-loop control method of claim 2, wherein the D-axis dc input voltage is determined by:
acquiring a preset D-axis voltage reference value;
determining a first voltage difference value based on the D-axis voltage reference value and the D-axis voltage feedback value;
and performing PI processing on the first voltage difference value to determine the D-axis direct-current input voltage.
5. The dual closed-loop control method of claim 2, wherein the Q-axis dc input voltage is determined by:
acquiring a preset Q-axis voltage reference value;
determining a second voltage difference value based on the Q-axis voltage reference value and the Q-axis voltage feedback value;
and performing PI processing on the second voltage difference value to determine the direct current input voltage of the Q axis.
6. The method of claim 1, wherein the determining the current inner loop reference value by performing park inverse processing on the D-axis dc input voltage and the Q-axis dc input voltage comprises:
determining a second matrix formed by preset sine values of sine wave angles and cosine values of the sine wave angles;
and determining the current inner loop reference value according to the second matrix and the product of a second vector formed by the D-axis direct-current input voltage and the Q-axis direct-current input voltage.
7. A dual closed-loop control apparatus for a single-phase inverter, the dual closed-loop control apparatus comprising:
the determining module is used for acquiring the inversion output voltage and the inversion output current of the single-phase inverter and determining a first orthogonal voltage and a second orthogonal voltage based on the inversion output voltage;
a transformation module for determining a D-axis dc input voltage and a Q-axis dc input voltage based on the first and second quadrature voltages;
the current inner ring reference value determining module is used for performing park inverse processing on the D-axis direct-current input voltage and the Q-axis direct-current input voltage to determine a current inner ring reference value;
and the sinusoidal signal determination module is used for carrying out PR processing on the current inner ring reference value and the inversion output current, outputting a sinusoidal signal of the single-phase inverter and finishing double closed-loop control on the single-phase inverter by using the sinusoidal signal.
8. The dual closed-loop control device of claim 7, wherein the transformation module, when configured to determine the D-axis dc input voltage and the Q-axis dc input voltage based on the first quadrature voltage and the second quadrature voltage, is specifically configured to:
performing DQ conversion on the first orthogonal voltage to determine a D-axis voltage feedback value; performing DQ conversion on the second orthogonal voltage to determine a Q-axis voltage feedback value;
performing PI processing on the D-axis voltage feedback value to determine a D-axis direct current input voltage; and performing PI processing on the Q-axis voltage feedback value to determine Q-axis direct-current input voltage.
9. An electronic device, comprising: a processor, a memory and a bus, the memory storing machine-readable instructions executable by the processor, the processor and the memory communicating over the bus when an electronic device is operating, the machine-readable instructions when executed by the processor performing the steps of the method of dual closed-loop control of a single-phase inverter as claimed in any one of claims 1 to 6.
10. A computer-readable storage medium, characterized in that the computer-readable storage medium has stored thereon a computer program which, when being executed by a processor, performs the steps of the method for double closed-loop control of a single-phase inverter according to any one of claims 1 to 6.
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| CN202211105416.0A CN115632536A (en) | 2022-09-09 | 2022-09-09 | Double closed-loop control method and device of single-phase inverter and storage medium |
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| Application Number | Priority Date | Filing Date | Title |
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| CN202211105416.0A CN115632536A (en) | 2022-09-09 | 2022-09-09 | Double closed-loop control method and device of single-phase inverter and storage medium |
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