CN115580961B - Multi-path wireless power transmission LED drive circuit based on constant current source compensation network - Google Patents

Multi-path wireless power transmission LED drive circuit based on constant current source compensation network Download PDF

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CN115580961B
CN115580961B CN202211572333.2A CN202211572333A CN115580961B CN 115580961 B CN115580961 B CN 115580961B CN 202211572333 A CN202211572333 A CN 202211572333A CN 115580961 B CN115580961 B CN 115580961B
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constant current
unit
output
current
led
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CN115580961A (en
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何青青
陆旭峰
杨鸿宇
周克亮
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Wuhan University of Technology WUT
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Wuhan University of Technology WUT
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    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
    • H02J50/12—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling of the resonant type
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/01—Resonant DC/DC converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33573—Full-bridge at primary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/06—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode
    • H02M7/068—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode mounted on a transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/32—Pulse-control circuits
    • H05B45/325—Pulse-width modulation [PWM]
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/345—Current stabilisation; Maintaining constant current

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Inverter Devices (AREA)

Abstract

The invention relates to the technical field of LED wireless driving, in particular to a multi-path wireless power transmission LED driving circuit based on a constant current source compensation network. The receiving end comprises multiple paths of constant current output units, each path of constant current output unit is connected through a non-contact transformer, and the input end of the first constant current output unit is connected through a non-contact transformer T m The constant current output unit comprises an AC/DC rectification unit and an LED load string, the output end of the power supply is connected with the input end of the DC/AC inversion unit, the output end of the DC/AC inversion unit is connected with the input end of the passive resonance constant current unit, and the output end of the passive resonance constant current unit is connected with the contactless transformer T m Primary side connected, contactless transformer T m The secondary side of the LED is connected with an AC/DC rectifying unit of the first constant current output unit, and the output end of the AC/DC rectifying unit is connected with the LED load string. The circuit has the advantages of simple structure, high efficiency and low cost.

Description

Multi-path wireless power transmission LED drive circuit based on constant current source compensation network
Technical Field
The invention relates to the technical field of LED wireless driving, in particular to a multi-path wireless power transmission LED driving circuit based on a constant current source compensation network.
Background
Compared with the conventional lighting method, the Light Emitting Diode (LED) lighting has the outstanding advantages of high efficiency, energy saving, no pollution, long service life, etc., and is regarded as a "fourth generation lighting source", and has become a research focus in the lighting field in recent years, and has gradually been widely applied in the lighting fields such as street lighting, tunnel lighting, landscape lighting, etc. According to the voltage and current variation characteristics of the LED device, there are two driving methods: firstly, a constant voltage source and a plurality of paths of constant current sources are adopted for driving, one path of constant voltage source simultaneously provides power for the plurality of paths of constant current sources, and each path of constant current source drives one group of lamp sets. And secondly, the direct constant current source is adopted for driving, so that the control method is simple and the cost is lower.
As a new electric energy transmission technology, the wireless electric energy transmission technology has the advantages of safety, reliability, flexibility and convenience, and is widely applied to the fields of electronic equipment, electric automobiles, human body medical implantation equipment and the like. The wireless power transmission technology is widely applied to occasions of constant-current or constant-voltage power supply of electric equipment, and a reasonable compensation network is added in a wireless power transmission system, so that reactive circulation can be eliminated to improve power factors, and constant-current or constant-voltage output irrelevant to loads can be realized. Therefore, it is one of the hot spots of the research of the wireless power transmission technology to design a reasonable compensation network to realize constant current or constant voltage output. The invention focuses on realizing multi-channel wireless drive output by adopting a constant current source type compensation network under a simpler control method through a wireless power transmission technology.
In order to realize multi-channel constant current output, a constant current output resonance compensation network and a topological structure are researched by related documents. The scholars have proposed the topology that a single inverter is connected with a plurality of IPT systems in parallel at the same time, in the thesis of compensation topology research of constant output of an induction type wireless power transmission system, a series of loads are connected behind a transformer, a plurality of transformers are adopted to realize multi-path constant current output, wherein each transformer secondary side needs a resonance compensation network, so the circuit structure is complex and the cost is high. In order to simplify the structure and save the cost, in research on an electrolytic capacitor-free LED driving circuit based on an LCL constant current resonant network in the journal of Power supply science, an LED driving power supply consisting of a front-stage Boost-PFC converter and a rear-stage half-bridge LCL resonant converter is provided, and constant alternating current is generated by using the LCL resonant circuit on the primary side of a transformer. The topology can greatly simplify the circuit, but cannot realize the multi-path constant current output of the LED.
Disclosure of Invention
Aiming at the defects of the prior art, the invention provides a multipath wireless electric energy transmission LED drive circuit based on a constant current source compensation network, which has the advantages of simple circuit structure, high efficiency and low cost.
The invention provides a multi-path wireless power transmission LED drive circuit based on a constant current source compensation network, which comprises an emitting end and a receiving end, wherein the receiving end comprises a plurality of paths of constant current output units, each path of constant current output unit is connected through a non-contact transformer, the input end of the first constant current output unit is also connected through a non-contact transformer T m The constant current output unit comprises an AC/DC rectifying unit and an LED load string, the output end of a power supply is connected with the input end of the DC/AC inverting unit, the output end of the DC/AC inverting unit is connected with the input end of the passive resonance constant current unit, and the output end of the passive resonance constant current unit is connected with the contactless transformer T m Is connected on the primary side, the contactless transformer T m The secondary side of the constant current output unit is connected with an AC/DC rectifying unit of the first constant current output unit, the output end of the AC/DC rectifying unit is connected with the LED load string, and each path of constant current output unit comprises a plurality of AC/DC rectifying units which are connected in series and a plurality of LED load strings which are in one-to-one correspondence with each AC/DC rectifying unit.
Preferably, the DC/AC inverter unit is a full-bridge inverter network, and the full-bridge inverter network includes a switching tube S 1 -S 4 Switching tube S 1 、S 3 Respectively connected with the switchesPipe S 2 、S 4 Of the substrate.
Preferably, the passive resonance constant current unit is an LCL-T network, and the passive resonance constant current unit includes an inductorL am InductorL bm And a capacitorC m Said inductorL bm One end of the non-contact transformer T m The same-name end of the primary side and the other end are connected with a capacitor simultaneouslyC m And an inductorL am One terminal of (1), a capacitorC m The other end of the transformer is connected with a non-dotted terminal of the primary side of the transformer, an inductorL am And the other end of the DC/AC inverter unit is connected with the output end of the DC/AC inverter unit.
Preferably, the AC/DC rectifying unit includes a diode D ij ~D （i+3）j And a capacitorC oji Said diode D ij Anode of (2), diode D （i+1）j And a contactless transformer T j Is connected to the secondary side of diode D ij And D （i+2）j Is connected to the cathode of the capacitorC oji Is connected to one end of a capacitorC oji Is connected with the positive end of the LED load string, and a diode D （i+1）j 、D （i+3）j Anode and capacitor ofC oji Is connected to the other end of the capacitorC oji The other end of the LED load string is connected with the negative end of the LED load string;
the constant current output units of the receiving end are s-m +1 paths, the number of the AC/DC rectification units arranged in each constant current output unit is n, i is any natural number from 1 to n, and j is any natural number from m to s.
Preferably, the control circuit further comprises an open-loop control circuit, the open-loop control circuit comprises a first pulse width modulator, a phase-shift modulation unit and a first driver, a PWM control signal output end of the first pulse width modulator is connected with an input end of the phase-shift modulation unit, an output end of the phase-shift modulation unit is connected with an input end of the first driver, and an output end of the first driver is connected with a control signal input end of the DC/AC inversion unit.
Preferably, the LED load string control circuit further comprises a closed-loop control circuit, the closed-loop control circuit comprises an adder, a compensator, a second pulse width modulator and a second driver, a sampling current output end and a reference current input end of the LED load string are connected with an input end of the adder, an output end of the adder is connected with an input end of the compensator, an output end of the compensator is connected with an input end of the second pulse width modulator, a PWM control signal output end of the second pulse width modulator is connected with an input end of the second driver, and an output end of the second driver is connected with a control signal input end of the DC/AC inversion unit.
Preferably, the passive resonance constant current unit has an internal inductorL am Inductance value of greater than inductanceL bm The sensitivity value of (1).
Preferably, when the first pulse width modulator outputs the specified duty ratio K, the phase shift angle is adjusted within a range of 0 to 180 ° by the phase shift modulation unit, so that the output current of the LED load string is kept within the specified precision.
Preferably, the control method of the closed-loop control circuit includes:
the summator calculates the sampling current of the LED load stringILED and reference currentICurrent error of refIerr，ILED-Iref=Ierr；
When in useIerr>At 0, the output value of the compensatorXIncreasing, and adjusting the duty ratio of the PWM control signal to increase by the second pulse width modulator;
when in useIerr<At 0, the output value of the compensatorXAnd decreasing, the second pulse width modulator adjusts the duty cycle of the PWM control signal to decrease.
The invention has the beneficial effects that:
1. the multi-path isolated output of the circuit only uses the resonance network on the primary side of the transformer, the use of the secondary side resonance network is reduced, only one rectifying unit is needed to be added for each path of output, the modularized multi-path constant current output is easy to realize, the efficiency is higher, and the cost is low. Meanwhile, the circuit realizes multi-path LED constant current output by connecting transmission line transformers in a multi-stage series mode. And a plurality of rectifying units are connected in series, so that most application places can use open-loop control, and the overall control scheme is simple and easy to realize.
2. According to the scheme, an open-loop control circuit is arranged and comprises a first pulse width modulator, a phase-shifting modulation unit and a first driver, the duty ratio of a PWM control signal output by the first pulse width modulator is directly given, and a phase-shifting angle is adjusted within the range of 0-180 degrees by combining the phase-shifting modulation unit, so that the output current of an LED load string can be kept within any specified precision, and constant current output is realized.
3. The scheme is provided with a closed-loop control circuit, wherein the closed-loop control circuit comprises an adder, a compensator, a second pulse width modulator and a second driver. The summator calculates the sampling current of the LED load stringILED and reference currentICurrent error of refIerr whenIerr>When 0, the output value of the compensatorXIncreasing, and adjusting the duty ratio of the PWM control signal to increase by the second pulse width modulator; when in useIerr<At 0, the output value of the compensatorXAnd decreasing, the second pulse width modulator adjusts the duty cycle of the PWM control signal to decrease. Thereby makingILED=IAnd ref, realizing constant current output in a severe environment.
4. The scheme designs the internal inductor of the passive resonance constant-current unitL am Inductance value of greater than inductanceL bm The inductive value of can make the switching tube homoenergetic in the DC/AC contravariant unit realize soft switching to reduce switching loss, raise the efficiency.
Drawings
Fig. 1 is a schematic diagram of an architecture of a multi-path wireless power transmission LED driving circuit based on a constant current source compensation network according to the present invention;
fig. 2 is a schematic diagram of a wireless LED driving system in a multi-path wireless power transmission LED driving circuit based on a constant current source compensation network according to the present invention;
FIG. 3 is a schematic diagram of a full-bridge inverter network constituting a DC/AC inverter unit;
FIG. 4 is a schematic diagram of an LCL-T resonant network forming a passive resonant constant current network in an AC/DC passive resonant constant current unit;
FIG. 5 is a schematic diagram of a bridge rectifier circuit constituting a rectifier module in an AC/DC passive resonant constant current unit;
FIG. 6 is a schematic circuit diagram of a multi-channel wireless power transmission LED driving circuit based on a constant current source compensation network according to a preferred embodiment of the present invention;
FIG. 7 is a schematic diagram of a switching tube driver and main operating waveforms of the circuit shown in FIG. 6;
FIG. 8 shows the switch tube S of the circuit of FIG. 6 when it is open-loop 1 And S 2 A simulation oscillogram of voltage and current at two ends at a rated working point;
FIGS. 9 to 12 are simulation waveforms of the main and slave output currents under different output loads when the circuit shown in FIG. 6 operates in an open loop;
FIGS. 13 to 15 are simulation waveforms of output current varying with output load for different input voltages when the circuit shown in FIG. 6 is operated in an open loop;
FIGS. 16 to 17 are simulated waveforms of output voltage and current when the circuit shown in FIG. 6 operates under open loop and the load is suddenly changed;
FIGS. 18 to 20 are simulation waveforms of output voltage and current under different phase shift angles when the circuit shown in FIG. 6 operates in an open loop;
FIGS. 21 to 23 are simulation waveforms of the output voltage and current after the output voltage and current are stabilized when the circuit shown in FIG. 6 is operated in a closed loop and the input voltage changes greatly;
FIGS. 24 to 25 are simulation waveforms of output voltage and output current when the circuit shown in FIG. 6 is operated in a closed loop and the input voltage is suddenly changed;
FIG. 26 is a schematic diagram of waveforms between resonant current, switching tube current and switching tube voltage;
fig. 27 and 28 are vector diagrams based on the relationship between the parameters of the resonant network.
Detailed Description
In order to make the technical problems, technical solutions and advantageous effects to be solved by the present application clearer, the present application is further described in detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the present application and are not intended to limit the present application.
In the following description, for purposes of explanation and not limitation, specific details are set forth, such as particular system structures, techniques, etc. in order to provide a thorough understanding of the embodiments of the present application. It will be apparent, however, to one skilled in the art that the present application may be practiced in other embodiments that depart from these specific details. In other instances, detailed descriptions of well-known systems, devices, circuits, and methods are omitted so as not to obscure the description of the present application with unnecessary detail.
It will be understood that the terms "comprises" and/or "comprising," when used in this specification and the appended claims, specify the presence of stated features, integers, steps, operations, elements, and/or components, but do not preclude the presence or addition of one or more other features, integers, steps, operations, elements, components, and/or groups thereof.
It should also be understood that the term "and/or" as used in this specification and the appended claims refers to any and all possible combinations of one or more of the associated listed items and includes such combinations.
As used in this specification and the appended claims, the term "if" may be interpreted contextually as "when", "upon" or "in response to" determining "or" in response to detecting ". Similarly, the phrase "if it is determined" or "if a [ described condition or event ] is detected" may be interpreted contextually to mean "upon determining" or "in response to determining" or "upon detecting [ described condition or event ]" or "in response to detecting [ described condition or event ]".
Furthermore, in the description of the present application and the appended claims, the terms "first," "second," "third," and the like are used for distinguishing between descriptions and not necessarily for describing or implying relative importance.
Reference throughout this specification to "one embodiment" or "some embodiments," or the like, means that a particular feature, structure, or characteristic described in connection with the embodiment is included in one or more embodiments of the present application. Thus, appearances of the phrases "in one embodiment," "in some embodiments," "in other embodiments," or the like, in various places throughout this specification are not necessarily all referring to the same embodiment, but rather "one or more but not all embodiments" unless specifically stated otherwise. The terms "comprising," "including," "having," and variations thereof mean "including, but not limited to," unless otherwise specifically stated. "plurality" means "two or more".
Example one
Fig. 1 shows a schematic architecture diagram of a multi-wireless power transmission LED driving circuit based on a constant current source compensation network according to a preferred embodiment of the present application (fig. 1 shows a first embodiment of the present application), and for convenience of description, only the parts related to the present application are shown, and the detailed description is as follows:
the invention provides a multi-path wireless power transmission LED drive circuit based on a constant current source compensation network, which comprises an emitting end and a receiving end, wherein the receiving end comprises a plurality of paths of constant current output units, each path of constant current output unit is connected through a non-contact transformer, the input end of the first constant current output unit is also connected through a non-contact transformer T m The transmitting end is connected with the transmitting end, the transmitting end comprises a DC/AC inversion unit and a passive resonance constant current unit, the constant current output unit comprises an AC/DC rectification unit and an LED load string, the output end of a power supply is connected with the input end of the DC/AC inversion unit, the output end of the DC/AC inversion unit is connected with the input end of the passive resonance constant current unit, and the output end of the passive resonance constant current unit is connected with a contactless transformer T m Is connected to the primary side of the contactless transformer T m The secondary side of the constant current output unit is connected with an AC/DC rectifying unit of the first constant current output unit, the output end of the AC/DC rectifying unit is connected with the LED load string, and each path of constant current output unit comprises a plurality of AC/DC rectifying units which are connected in series and a plurality of LED load strings which are in one-to-one correspondence with each AC/DC rectifying unit. Based on the thought method of the invention, different multi-path constant current LED driving power supplies can be obtained through reasonable combination of topological structures in all the conversion units.
As shown in fig. 2, the DC power supply of the present invention generates a high frequency driving source through the DC/AC inverter unit and the passive resonant network, and the electric energy is transmitted to the receiving network through the transmitting end of the transmission network and supplied to the LED load, thereby realizing multi-path LED constant current output.
The DC/AC inverter unit can adopt full-bridge and half-bridge inverter network structures, such as a full-bridge inverter network shown in FIG. 3, wherein the input of the full-bridge inverter network is connected with DC voltageU dc The full-bridge inverter network comprises a switch tube S 1 -S 4 Switching tube S 1 、S 3 Respectively connected with a switch tube S 2 、S 4 Drain electrode of (2), switching tube S 1 -S 4 An N-channel MOSFET is used.
The passive resonance constant current network in the AC/DC passive resonance constant current unit can be formed into four topological structures of LCL-T, CLC-pi, CLC-T or LCL-pi resonance network. As shown in fig. 4, the passive resonant constant current unit in the AC/DC passive resonant constant current unit adopts an LCL-T network, and the passive resonant constant current unit includes an inductorL am InductorL bm And a capacitorC m Said inductorL bm One end of the non-contact transformer T m The same name end of the primary side and the other end are connected with a capacitor simultaneouslyC m And an inductorL am One terminal of (1), a capacitorC m The other end of the transformer is connected with a non-dotted terminal of the primary side of the transformer, an inductorL am And the other end of the DC/AC inverter unit is connected with the output end of the DC/AC inverter unit.
The three topological structures which can form the rectifying module in the AC/DC rectifying unit can be half-wave rectification, bridge rectification and voltage-doubling rectifying circuits. FIG. 5 shows a bridge rectifier circuit including a diode D ij ~D （i+3）j And a capacitorC oji Said diode D ij Anode of (2), diode D （i+1）j Cathode and contactless transformer T j Is connected to the secondary side of a diode D ij And D （i+2）j Is connected to the cathode of the capacitorC oji Is connected to one end of a capacitorC oji Is connected with the positive end of the LED load string, and a diode D （i+1）j 、D （i+3）j Anode and capacitor ofC oji Is connected to the other end of the capacitorC oji The other end of the LED load string is connected with the negative end of the LED load string;
the constant current output units of the receiving end are s-m +1 paths, the number of the AC/DC rectification units arranged in each constant current output unit is n, i is any natural number from 1 to n, and j is any natural number from m to s.
Fig. 6 shows a preferred circuit topology diagram of the circuit of the present invention, in which each component adopts the full-bridge inverter network, the LCL-T network and the bridge rectifier structure shown in fig. 3 to 5, and further includes an open-loop control circuit and a closed-loop control circuit.
The open-loop control circuit comprises a first pulse width modulator, a phase-shifting modulation unit and a first driver, wherein a PWM control signal output end of the first pulse width modulator is connected with an input end of the phase-shifting modulation unit, an output end of the phase-shifting modulation unit is connected with an input end of the first driver, and an output end of the first driver is connected with a control signal input end of a DC/AC inversion unit.
The closed-loop control circuit comprises an adder, a compensator, a second pulse width modulator and a second driver, wherein a sampling current output end and a reference current input end of the LED load string are connected with an input end of the adder, an output end of the adder is connected with an input end of the compensator, an output end of the compensator is connected with an input end of the second pulse width modulator, a PWM control signal output end of the second pulse width modulator is connected with an input end of the second driver, and an output end of the second driver is connected with a control signal input end of the DC/AC inversion unit.
Input and output isolation is achieved between the LCL-T resonant network and the bridge rectifier network through the contactless transformer T, wireless transmission of electric energy is completed, meanwhile, through reasonable parameter design, proper resonant frequency is selected, current of the switching tube can lag behind voltage, and therefore in switching state change, the voltage drops to zero before switching on, and the current drops to zero before switching off, and therefore soft switching is achieved. Fig. 6 has two wireless receiving terminals in common, and for convenience of analysis, parameters of components of the two receiving terminals may be set to be the same. The control adopts open-loop control or closed-loop control, duty ratio K is directly given in the open-loop control, the switch tube is driven through a driver, the closed-loop control obtains an error signal by sampling a certain path of output current and making a difference with reference current through an adder, the current error is sent to a compensator, and finally the switch tube is driven through a pulse width modulator and the driver.
As shown in fig. 7, where Q is 1 -Q 4 Are respectively a switch tube S 1 -S 4 In a switching periodT SW Inner S 1 Has a turn-on time ofDT SW . From the drive waveform, S 1 And S 2 、S 3 And S 4 Respectively conducting complementarily. S 3 Relative to S 1 Is shifted 180 DEG and in one switching periodT SW Inner, S 1 And S 3 、S 2 And S 4 Are equal, i.e. phase shift control is used. However, it should be noted that this control method is not exclusive and can make the output end voltage of the inverter unitu ac Any control method for the alternating square wave can be adopted.
In one embodiment, the passive resonant constant current unit internal inductorL am Inductance value of (2) is greater than inductanceL bm The sensitivity value of (1). The specific analysis process is as follows:
by reasonable parameter design of the passive resonance constant-current network, soft switching of the switching tubes in the DC/AC inversion unit can be realized, so that switching loss is reduced, and efficiency is improved.
Taking LCL-pi resonant network as an example, only considering fundamental component, and not considering higher harmonic wave, the current at the input end of the resonant networkI Lam And the current of the output terminalI Lbm To be derived from the following formula:
Figure DEST_PATH_IMAGE001
；
Figure DEST_PATH_IMAGE002
；
whereinI Lam Is the current on the input side and is,I Lbm in order to output the side current,L am for the inductance of the input side, the inductance,L bm as an output-side inductance, a capacitance,U am for the voltage on the input side, the voltage,U bm for the purpose of outputting the side voltage,ω SW is the switching angular frequency.
In order to reduce the loss of the switching tube and improve the efficiency of the power supply, two soft switching methods, namely Zero Voltage Switching (ZVS) and Zero Current Switching (ZCS), are available. Zero Voltage Switching (ZVS), i.e., the voltage of the switching tube drops to zero before turning on and remains zero when turning off. Zero Current Switching (ZCS) reduces the current to zero before switching off even though the current of the switching tube remains zero when it is on. As shown in fig. 26, to implement Zero Voltage Switching (ZVS), the voltage of the switching tube should lead the current, that is, before the switching tube is turned on, the current flows through the body diode (S to D) of the switching MOS tube, the voltage between the switching MOS tubes D-S is clamped to be close to 0V (diode drop), and at this time, the switching MOS tube is turned on, so that zero voltage conduction can be implemented; before the switch-off, the capacitor voltage between D and S is 0V and can not change suddenly, so the switch-off is similar to zero voltage switch-off.
According to the relation between the parameters of the resonant network, considerL am Is greater thanL bm AndL am is less thanL bm The following vector diagrams are shown in FIGS. 27 and 28, and it can be seen from these diagrams that only when the vector diagram is shownL am Is greater thanL bm Only when the condition of the voltage advance current of the switch tube is satisfied, thereby realizing zero-voltage switching, and when the parameters are selected, the condition that the voltage advance current of the switch tube is ensuredL am Is greater thanL bm The design requirements can be met.
In one embodiment, when the first pulse width modulator outputs a specified duty ratio K, the phase shift angle is adjusted within a range of 0 to 180 ° by the phase shift modulation unit, so that the output current of the LED load string is kept within a specified precision.
The DC voltage is controlled by phase shift modulation via the output voltage of the inverter. High order resonant circuits as bandpass filters, mainly by inversionFundamental component of converter output voltage, and therefore, for simplicity of analysis, only the fundamental component is considered here, the inverter output voltageU am ：
Figure DEST_PATH_IMAGE003
；
WhereinU dc In order to input a direct-current voltage,αis a phase shift angle.
Taking LCL-pi resonant network as an example, only considering fundamental component, and not considering high-order harmonic, current at output side of resonant networkI Lbm Can be derived from the following equation:
Figure DEST_PATH_IMAGE004
；
whereinU am Is the input side voltage i.e. the inverter output voltage,L am is the input side inductance.
Substituting can obtain:
Figure DEST_PATH_IMAGE005
；
the following formula shows that the phase shift angle is in the range of 0 to 180 DEG, and the current at the output sideI Lbm With followingαThe phase shift angle can be reasonably selected according to the requirement of the method when the ring is opened, so that the proper constant current output can be obtained. The modulation method is only used for reference, and other modulation means can be reasonably selected to achieve the required constant current output.
In one embodiment, the control method of the closed-loop control circuit comprises the following steps:
the summator calculates the sampling current of the LED load stringILED and reference currentICurrent error of refIerr，ILED-Iref=Ierr；
When in useIerr>When 0, the output value of the compensatorXIncreasing, and adjusting the duty ratio of the PWM control signal to increase by the second pulse width modulator;
when in useIerr<At 0, the output value of the compensatorXAnd decreasing, the second pulse width modulator adjusts the duty cycle of the PWM control signal to decrease.
Example two
In this embodiment, the open-loop control process of the present embodiment is described with reference to various simulation diagrams of the circuit shown in fig. 6 under open-loop control.
The input and output and the parameter setting of each component of this embodiment are as follows:
rated input voltageU dc =80V, rated output current 0.56A, rated output voltage 45V, switching frequency 100kHZ, transformer turn ratioN=n 1 ：n 2 =2.3, inductanceL am =270 μ H, inductanceL bm =75 muH, capacitanceC m Capacitance of =9.38nFC om =150µF。
Fig. 8 shows the switching tube voltage and current waveforms at the nominal operating point when the circuit of fig. 6 is operating in open loop.
When the output load changes, the output current can be kept basically unchanged at the rated value of 0.56A. As shown in FIG. 9, the output voltage of the main circuit and the slave circuit is about 44.5V, and the current of the slave circuit is outputI os1 About 0.556A; as shown in FIG. 10, the main output voltageU om1 About 44.7V, the output voltage from the circuitU os1 About 22.4V, and the current is output from the circuitI os1 About 0.556A; as shown in FIG. 11, the main circuit outputs a voltageU om1 About 11.24V, and the voltage is output from the circuitU os1 About 44.97V, current output from the circuitI os1 About 0.562A; as shown in FIG. 12, the main circuit outputs voltageU om1 About 11.5V, the output voltage from the circuitU os1 About 17.2V, current output from the circuitI os1 About 0.573A. From the above, although the output voltage variation of the main circuit and the slave circuit can affect the output current of the slave circuit, the accuracy of the current of the slave circuit can be kept within 5% (0.556A-0.573A), and the output has high current accuracy.
U o1 AndU o2 respectively represent the output voltages of any two paths of LED strings,I o1 andI o2 respectively, representing the output current of the corresponding branch. FIG. 13 is a waveform diagram of an input voltage of 78V, in which the output voltage is shownU o1 The output current is about 0.54A and the output voltage is about 43.1VU o2 An output current of about 0.54A corresponding to about 32.4V; FIG. 14 is a waveform diagram of an input voltage of 80V, in which an output voltage is shownU o1 About 44.3V corresponds to an output current of about 0.55A and an output voltageU o2 An output current of about 0.55A at about 33.2V; FIG. 15 is a waveform diagram of 82V input voltage, in which the output voltage is shownU o1 About 45.36V corresponds to an output current of about 0.567A and an output voltageU o2 An output current of about 0.567A corresponds to about 34V. From the above, it can be seen that in the open-loop operation mode, when the input and output voltages are varied within a certain range, the output current accuracy can be kept within 5% (0.54A-0.567A), and the output has high current accuracy.
U o1 AndI o1 the output voltage and current of the LED branch circuit in which the load sudden change is positioned are represented,U o2 andI o2 representing the output voltage and current of any other LED branch. FIG. 16 is a diagram of the output voltage and current waveforms when the load suddenly decreases, and the branch voltage when the load suddenly changesU o1 Gradually decreases from 45V to 24V, and the current isI o1 Gradually stabilizing to an initial value of 0.55A after sudden rising, and keeping the voltage and current stabilization time at 0.02s; output voltageU o2 Gradually decreases from 44.6V to 44.15V, and outputs currentI o2 Gradually decreasing from 0.557A to 0.552A, and the stabilization time is 0.03s; FIG. 17 is a diagram of the output voltage and current waveforms when the load suddenly increases, and the branch voltage of the load suddenly changesU o1 Gradually increases from 22.4V to 44.5V, and the current isI o1 Gradually stabilizing to an initial value of 0.56A after the sudden drop, wherein the voltage and current stabilization time is 0.02s; output voltageU o2 Gradually increases from 44.1V to 44.5V, and outputs currentI o2 Gradually decreasing from 0.551A to 0.556A, and the stabilization time is 0.05s; from the foregoing, it can be seen that in the open loop mode of operation, whenThe output current precision can be kept within 5% (0.55A-0.556A) when the load suddenly changes, the output has high current precision, and the recovery speed is higher.
U o1 AndU o2 respectively represent the output voltages of any two LED strings,I o1 andI o2 respectively, the output current of the corresponding branch. FIG. 18 is a graph showing the output voltage and current waveforms at a given phase shift angle of 60U o1 The output current is about 0.274A and the output voltage is about 21.94VU o2 An output current of about 0.274A at about 21.94V; FIG. 19 is a graph showing the waveforms of the output voltage and current at a given phase shift angle of 120 DEG, in which the output voltageU o1 About 38.24V corresponds to an output current of about 0.478A and an output voltageU o2 An output current of about 0.478A at about 38.24V; FIG. 20 is a graph showing the waveform of the output voltage and current at a given phase shift angle of 180 DEG, in which the output voltageU o1 The output current is about 0.557A and the output voltage is about 44.59VU o2 An output current of about 0.557A corresponding to about 44.59V; it can be seen from the above that, by changing the phase shift angle, the output current will increase with the increase of the phase shift angle, and the accuracy of the output current can be kept within 5%, and the output has high current accuracy.
EXAMPLE III
In this embodiment, the closing control process in this embodiment is described with reference to various simulation diagrams of the circuit shown in fig. 6 under closed-loop control.
When there is a large variation in the input voltage, the output voltage current is stabilized at a given reference current of 0.55A.U o1 AndU o2 respectively represent the output voltages of any two paths of LED strings,I o1 andI o2 respectively, representing the output current of the corresponding branch. FIG. 21 is a waveform diagram of an input voltage of 64V, in which an output voltage is shownU o1 About 44V corresponds to an output current of about 0.55A and an output voltageU o2 An output current of about 0.55A at about 44V; FIG. 22 shows that when the input voltage is 80VIn which the output voltage isU o1 About 44V corresponds to an output current of about 0.55A and an output voltageU o2 An output current of about 0.55A at about 44V; FIG. 23 is a waveform diagram of 120V input voltage, in which the output voltage is shownU o1 About 44V corresponds to an output current of about 0.55A and an output voltageU o2 An output current of about 0.55A corresponds to about 44V. From the above, it can be seen that in the closed-loop operation mode, the output current accuracy can be kept within 0.02% (0.54993A-0.55008A) when the input and output voltages are varied within a wide range, and the output has high current accuracy.
U o1 AndI o1 、U o2 andI o2 and the output voltage and the current of any two LED branches are represented. FIG. 24 is a waveform diagram of the output voltage and current when the input voltage suddenly increases from 80V to 120V, and the branch voltageU o1 Gradually increasing from 44V to 47V, then decreasing to 44V to keep stable, and the currentI o1 Rising to 0.59A, then gradually stabilizing to an initial value of 0.55A, and the voltage and current stabilization time is 0.02s; output voltageU o2 Gradually increased from 44V to 47V, and output currentI o2 Rising to 0.59A, then gradually stabilizing to an initial value of 0.55A, and the stabilizing time is 0.02s; FIG. 25 is a diagram showing the waveform of the output voltage and current when the input voltage suddenly decreases from 80V to 64V, and the branch voltageU o1 Gradually decreases from 44V to 42V, then increases to 44V and keeps stable, and the currentI o1 The voltage is reduced to 0.525A and then gradually stabilizes to the initial value of 0.55A, and the voltage and current stabilization time is 0.03s; output voltageU o2 Gradually decreases from 44V to 42V, then increases to 44V and keeps stable, and the currentI o2 The voltage is reduced to 0.525A and then gradually stabilizes to the initial value of 0.55A, and the voltage and current stabilization time is 0.03s; (ii) a From the above, it can be seen that in the closed-loop operation mode, the output voltage and current have a fast recovery speed and a strong anti-interference performance.
The above-mentioned embodiments are only used for illustrating the technical solutions of the present application, and not for limiting the same; although the present application has been described in detail with reference to the foregoing embodiments, it should be understood by those of ordinary skill in the art that: the technical solutions described in the foregoing embodiments may still be modified, or some technical features may be equivalently replaced; such modifications and substitutions do not substantially depart from the spirit and scope of the embodiments of the present application and are intended to be included within the scope of the present application.

Claims (9)

1. The utility model provides a multichannel wireless power transmission LED drive circuit based on constant current source compensation network which characterized in that: the receiving end comprises a plurality of paths of constant current output units, each path of constant current output unit is connected through a non-contact transformer, and the input end of the first constant current output unit is also connected through a non-contact transformer T m The transmitting end is connected with the transmitting end, the transmitting end comprises a DC/AC inversion unit and a passive resonance constant current unit, the constant current output unit comprises an AC/DC rectification unit and an LED load string, the output end of a power supply is connected with the input end of the DC/AC inversion unit, the output end of the DC/AC inversion unit is connected with the input end of the passive resonance constant current unit, and the output end of the passive resonance constant current unit is connected with a contactless transformer T m Is connected to the primary side of the contactless transformer T m The secondary side of the constant current output unit is connected with an AC/DC rectifying unit of the first constant current output unit, the output end of the AC/DC rectifying unit is connected with the LED load string, and each path of constant current output unit comprises a plurality of AC/DC rectifying units which are connected in series and a plurality of LED load strings which are in one-to-one correspondence with each AC/DC rectifying unit.
2. The multi-path wireless power transmission LED driving circuit based on the constant current source compensation network as claimed in claim 1, wherein: the DC/AC inversion unit is a full-bridge inversion network, and the full-bridge inversion network comprises a switch tube S 1 -S 4 Switching tube S 1 、S 3 Respectively connected with a switch tube S 2 、S 4 Of the substrate.
3. The multi-path wireless power transmission LED driving circuit based on the constant current source compensation network of claim 1, wherein: the passive resonance constant current unit is an LCL-T type network and comprises an inductorL am An inductorL bm And a capacitorC m Said inductorL bm One end of the non-contact transformer T m The same-name end of the primary side and the other end are connected with a capacitor simultaneouslyC m And an inductorL am One terminal of (1), a capacitorC m The other end of the transformer is connected with a non-homonymous end of the primary side of the transformer, namely an inductorL am And the other end of the DC/AC inverter unit is connected with the output end of the DC/AC inverter unit.
4. The multi-path wireless power transmission LED driving circuit based on the constant current source compensation network as claimed in claim 1, wherein: the AC/DC rectifying unit includes a diode D ij ~D （i+3）j And a capacitorC oji Said diode D ij Anode of (2), diode D （i+1）j Cathode and contactless transformer T j Is connected to the secondary side of diode D ij And D （i+2）j Is connected to the cathode of the capacitorC oji Is connected to one end of a capacitorC oji Is connected with the positive end of the LED load string, and a diode D （i+1）j 、D （i+3）j Anode and capacitor ofC oji Is connected to the other end of the capacitorC oji The other end of the LED load string is connected with the negative end of the LED load string;
the constant current output units of the receiving end are s-m +1 paths, the number of the AC/DC rectification units arranged in each constant current output unit is n, i is any natural number from 1 to n, and j is any natural number from m to s.
5. The multi-path wireless power transmission LED driving circuit based on the constant current source compensation network as claimed in claim 1, wherein: the PWM control circuit comprises a first PWM, a phase-shift modulation unit and a first driver, wherein the PWM control signal output end of the first PWM is connected with the input end of the phase-shift modulation unit, the output end of the phase-shift modulation unit is connected with the input end of the first driver, and the output end of the first driver is connected with the control signal input end of the DC/AC inversion unit.
6. The multi-path wireless power transmission LED driving circuit based on the constant current source compensation network as claimed in claim 1, wherein: the LED load string control circuit comprises an adder, a compensator, a second pulse width modulator and a second driver, wherein a sampling current output end and a reference current input end of the LED load string are connected with an input end of the adder, an output end of the adder is connected with an input end of the compensator, an output end of the compensator is connected with an input end of the second pulse width modulator, a PWM control signal output end of the second pulse width modulator is connected with an input end of the second driver, and an output end of the second driver is connected with a control signal input end of a DC/AC inversion unit.
7. The multi-path wireless power transmission LED driving circuit based on the constant current source compensation network according to claim 3, wherein: the passive resonance constant current unit internal inductorL am Inductance value of greater than inductanceL bm The sensitivity value of (1).
8. The multi-path wireless power transmission LED driving circuit based on the constant current source compensation network according to claim 5, wherein: when the first pulse width modulator outputs the specified duty ratio K, the phase shift angle is adjusted within the range of 0 to 180 degrees through the phase shift modulation unit, so that the output current of the LED load string is kept within the specified precision.
9. The multi-path wireless power transmission LED driving circuit based on the constant current source compensation network as claimed in claim 6, wherein the control method of the closed-loop control circuit comprises:
the summator calculates the sampling current of the LED load stringILED and reference currentICurrent error of refIerr，ILED-Iref=Ierr；
When in useIerr>When 0, the output value of the compensatorXIncreasing, and adjusting the duty ratio of the PWM control signal to increase by the second pulse width modulator;
when in useIerr<At 0, the output value of the compensatorXAnd decreasing, the second pulse width modulator adjusts the duty cycle of the PWM control signal to decrease.
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