CN115580517A - Method, device, equipment and medium for compensating phase noise of millimeter wave system - Google Patents

Method, device, equipment and medium for compensating phase noise of millimeter wave system Download PDF

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CN115580517A
CN115580517A CN202211066929.5A CN202211066929A CN115580517A CN 115580517 A CN115580517 A CN 115580517A CN 202211066929 A CN202211066929 A CN 202211066929A CN 115580517 A CN115580517 A CN 115580517A
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pilot
compensation factor
phase noise
symbol
compensation
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CN115580517B (en
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陈达
滕帅
陈城
罗锴
彭薇
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Huazhong University of Science and Technology
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2649—Demodulators
    • H04L27/26534—Pulse-shaped multi-carrier, i.e. not using rectangular window
    • H04L27/2654—Filtering per subcarrier, e.g. filterbank multicarrier [FBMC]
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2689—Link with other circuits, i.e. special connections between synchronisation arrangements and other circuits for achieving synchronisation
    • H04L27/2691—Link with other circuits, i.e. special connections between synchronisation arrangements and other circuits for achieving synchronisation involving interference determination or cancellation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2697—Multicarrier modulation systems in combination with other modulation techniques
    • H04L27/2698—Multicarrier modulation systems in combination with other modulation techniques double density OFDM/OQAM system, e.g. OFDM/OQAM-IOTA system

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Abstract

The invention discloses a method, a device, equipment and a medium for compensating phase noise of a millimeter wave system, and belongs to the technical field of wireless communication. The method comprises the following steps: based on an FBMC-OQAM system, a continuous insertion type pilot frequency structure is designed to reduce interference of adjacent symbols to pilot frequency symbols; calculating a compensation factor for the pilot symbols on each subcarrier; measuring the interference of each subcarrier pilot frequency and distributing weight to the compensation factor of each subcarrier pilot frequency according to the interference; and synthesizing the compensation factors of all the sub-carrier pilot frequencies to obtain a final phase noise compensation result. Therefore, the invention can effectively reduce the influence of phase noise on a millimeter wave system.

Description

Method, device, equipment and medium for compensating phase noise of millimeter wave system
Technical Field
The present invention belongs to the field of wireless communication technologies, and in particular, to a method, an apparatus, a device, and a medium for compensating phase noise of a millimeter wave system.
Background
Millimeter wave communication technology is one of the keys of 6G communication. Millimeter wave communication can realize lower time delay and higher flux, so that a plurality of application scenes with larger scale, more calculated amount and higher cooperativity can be supported, and the millimeter wave communication is a technical point which is very worthy of attention. In addition, FBMC-OQAM is a very promising waveform modulation scheme. The FBMC-OQAM system utilizes a prototype filter with certain frequency focusing capability, and has lower sidelobe and out-of-band leakage and higher spectrum utilization rate. Under the objective condition of limited frequency spectrum resources, the FBMC-OQAM communication system can set a larger subcarrier interval, and is very suitable for the requirements of high bandwidth and high speed in millimeter wave communication. Due to the advantages, the millimeter wave FBMC-OQAM shows great potential in future communications.
Although the FBMC-OQAM communication system can set a larger subcarrier spacing to reduce the influence of the phase noise because it does not need a guard band, the deterioration of the communication system by the phase noise is still significant in the millimeter wave band. It is therefore necessary to investigate the problem of phase noise compensation in a mmwave FBMC-OQAM communication system.
The conventional pilot-based phase noise compensation method mainly has two main problems: (1) The pilot frequency structure inserted between frequency domains is used, so that the flexibility of inserting the pilot frequency sub-carrier is limited. (2) The influence of interference inherent to the FBMC-OQAM system on the phase noise compensation estimation is not considered.
Disclosure of Invention
Aiming at the defects or improvement requirements of the prior art, the invention provides a method, a device, equipment and a medium for compensating phase noise of a millimeter wave system, so as to reduce the influence of the phase noise on the millimeter wave system, thereby solving the problems of the prior art.
In order to achieve the above object, in a first aspect, the present invention provides a method for compensating phase noise of a millimeter wave system, including the steps of:
s1, inserting pilot symbols on a plurality of subcarriers of a sending end;
s2, calculating the symbol index m of each subcarrier 0 A compensation factor of the pilot symbol of (a), wherein each subcarrier is at a symbol index m 0 The result of taking the real part after the demodulation symbol is multiplied by the compensation factor is equal to the corresponding pilot frequency symbol;
s3, averaging all the compensation factors, calculating the absolute value of the difference value between each compensation factor and the average value, and taking the average value as a final compensation factor if the sum of the absolute values of all the difference values is smaller than a preset threshold value; otherwise, distributing weight to each compensation factor according to the absolute value of each difference value, and obtaining a final compensation factor through weighted average;
s4, utilizing the final compensation factor to carry out symbol index m 0 And compensating the demodulation symbols on all the subcarriers to obtain a final phase noise compensation result.
Further, in S1, a frequency domain continuous interpolation pilot structure is adopted, and the pilot structure satisfies: for any pilot symbol, the left pilot symbol and the right pilot symbol are equal, and the upper pilot symbol and the lower pilot symbol are opposite.
Further, in S2, the symbol index m of each subcarrier is calculated by the following equation set 0 Compensation factor of pilot symbol at:
Figure BDA0003828039090000021
wherein the content of the first and second substances,
Figure BDA0003828039090000022
and
Figure BDA0003828039090000023
respectively represent
Figure BDA0003828039090000024
Subcarrier at symbol index m 0 The demodulated symbols and the pilot symbols at (a),
Figure BDA0003828039090000031
representing pilot symbols
Figure BDA0003828039090000032
The compensation factor of (a) is determined,
Figure BDA0003828039090000033
and I { } denotes taking the real part and the imaginary part, respectively.
Further, in S3, assigning a weight to each compensation factor according to the magnitude of the absolute value of each difference value includes:
and normalizing the absolute value of each difference value, and taking the normalized value as the weight of each compensation factor.
In a second aspect, the present invention provides a device for compensating phase noise of a millimeter wave system, comprising:
the inserting module is used for inserting pilot symbols in a plurality of subcarriers of a sending end;
a first calculation module for calculating the symbol index m of each subcarrier 0 A compensation factor of the pilot symbol of (a), wherein each subcarrier is at a symbol index m 0 After the demodulation symbol is multiplied by the compensation factor, the result of taking the real part is equal to the corresponding pilot frequency symbol;
the second calculation module is used for averaging all the compensation factors, calculating the absolute value of the difference value between each compensation factor and the average value, and taking the average value as the final compensation factor if the sum of the absolute values of all the difference values is smaller than a preset threshold value; otherwise, distributing weight for each compensation factor according to the absolute value of each difference value, and obtaining a final compensation factor through weighted average;
a compensation module for indexing the symbol m by the final compensation factor 0 And compensating the demodulation symbols on all the subcarriers to obtain a final phase noise compensation result.
Further, the inserting module is further configured to adopt a frequency domain continuous inserting type pilot frequency structure, and the pilot frequency structure satisfies: for any pilot symbol, the left pilot symbol and the right pilot symbol are equal, and the upper pilot symbol and the lower pilot symbol are opposite.
Further, the first calculating module is further configured to calculate the symbol index m of each subcarrier by the following equation set 0 Compensation factor of pilot symbol at:
Figure BDA0003828039090000034
wherein the content of the first and second substances,
Figure BDA0003828039090000041
and
Figure BDA0003828039090000042
respectively represent
Figure BDA0003828039090000043
Subcarrier at symbol index m 0 The demodulated symbols and the pilot symbols at (a),
Figure BDA0003828039090000044
representing pilot symbols
Figure BDA0003828039090000045
The compensation factor of (a) is determined,
Figure BDA0003828039090000046
and I { } denotes taking the real part and the imaginary part, respectively.
Further, the second calculating module is further configured to perform a normalization operation on the absolute value of each difference, and then use the normalized value as the weight of each compensation factor.
In a third aspect, the present invention provides an electronic device, comprising:
a processor;
a memory storing a computer-executable program that, when executed by the processor, causes the processor to execute the method of compensating for millimeter wave system phase noise according to the first aspect.
In a fourth aspect, the present invention provides a computer-readable storage medium, on which a computer program is stored, which when executed by a processor, implements the method for compensating for phase noise of a millimeter wave system according to the first aspect.
Generally, by the above technical solution conceived by the present invention, the following beneficial effects can be obtained:
(1) According to the characteristics that the interference from surrounding symbols on the pilot frequency on different sub-carriers at the same moment is different and the phase noise is the same, the interference from other symbols on the pilot frequency symbol is extracted from the compensation factor; and distributing a weight value for each subcarrier based on the interference of each subcarrier, and synthesizing compensation factors on all subcarrier pilots according to the weight values to obtain a final phase noise compensation result. Therefore, the invention can effectively reduce the influence of phase noise on a millimeter wave system.
(2) The invention designs a frequency domain continuous insertion type pilot frequency structure to reduce the interference from adjacent symbols in a millimeter wave system, thereby enabling the phase noise estimation compensation to be more accurate.
Drawings
Fig. 1 is a schematic flow chart of a method for compensating phase noise of a millimeter wave system according to an embodiment of the present invention;
fig. 2 is a schematic diagram illustrating an exemplary frequency domain continuous insertion pilot structure according to an embodiment of the present invention;
fig. 3 is a bit error rate comparison graph of the original Method-I algorithm without considering ICI and ISI interference inherent in the FBMC-OQAM system and the PPNC-S (Pilot-based PNC-Single) algorithm with considering ICI and ISI inherent in the FBMC-OQAM system according to the present invention under the frequency domain interleaved Pilot structure according to the present invention; wherein, the I-All1 pilot frequency structure is full 1,I-Rand pilot frequency structure is random;
FIG. 4 is a graph comparing different pilot structures provided by the embodiment of the present invention with the performance of the PPNC-S algorithm proposed by the present invention; wherein, C-All1, C-Rand and C-UDsame are respectively a frequency domain continuous insertion type All1 pilot frequency, a random pilot frequency and an upper and lower identical pilot frequency structure; C-UDoppo is a frequency domain continuous interpolation type pilot frequency structure with the upper and lower opposite directions; I-All1 and I-Rand are inter-frequency domain interpolation type All1 pilot frequency and random pilot frequency structures;
fig. 5 is a block diagram of a phase noise compensation apparatus of a millimeter wave system according to an embodiment of the present invention;
fig. 6 is a block diagram of an electronic device provided by an embodiment of the invention.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention is described in further detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the invention and are not intended to limit the invention. In addition, the technical features involved in the embodiments of the present invention described below may be combined with each other as long as they do not conflict with each other.
In the present application, the terms "first," "second," and the like (if any) in the description and the drawings are used for distinguishing between similar elements and not necessarily for describing a particular sequential or chronological order.
Fig. 1 is a flowchart of a method for compensating phase noise of a millimeter wave system according to an embodiment of the present invention. Referring to fig. 1, a detailed description will be given of a method for compensating phase noise of a millimeter wave system in this embodiment with reference to fig. 2 to 4, where the method includes operations S1 to S4.
In operation S1, pilot symbols are inserted into a number of subcarriers at a transmitting end.
In this embodiment, to reduce interference from adjacent symbols in FBMC-OQAM and make phase noise estimation compensation more accurate, a frequency domain continuous-insertion pilot structure is designed, which aims to realize interference cancellation by designing adjacent pilot symbols.
Time frequency point (k) after phase noise compensation 0 ,m 0 ) The demodulated symbols of (a) can be expressed as:
Figure BDA0003828039090000061
wherein omega Δk,Δm ({ (p, q) > ", | p | < Δ k, | q | < Δ m, and p ≠ k 0 ,q≠m 0 And the neighborhood range of the time-frequency point is used as the term.
In the above equation, the second part is interference caused by adjacent symbols, and the final real operation of the demodulation step can remove imaginary interference, but real interference still exists:
Figure BDA0003828039090000062
to design the pilot frequency
Figure BDA0003828039090000063
Taking a PHYDYAS filter with α =4 as an example, looking at the interference factor table, we can find that the interference exists mainly in a first-order range of the current symbol, so the real part interference of the adjacent symbols, up, down, left and right, is considered to be cancelled to 0.
Firstly, the interference of adjacent symbols in the left-right first-level range is analyzed, corresponding to the condition that deltak =0, deltam = +/-1, p = k 0 ，q＝m 0 ±1。
Figure BDA0003828039090000071
Therefore when
Figure BDA0003828039090000072
In this case, the interference caused by the adjacent symbols of the left and right stages can be cancelled to 0.
And analyzing the interference of adjacent symbols in the upper and lower levels, wherein the corresponding delta k = +/-1, the delta m =0, p = k 0 ±1，q＝m 0 。
Figure BDA0003828039090000073
At this time, a fuzzy function A is introduced g [(m 0 -m)τ,(k-k 0 )ν]To see the distribution of the virtual and real values.
Figure BDA0003828039090000074
Where τ = K/2 represents time accuracy, time resolution, and v =1/K represents frequency accuracy, frequency resolution. Shortening the summation period of interest to within one prototype filter length yields:
Figure BDA0003828039090000081
phase noise margin at the same time in the above equation
Figure BDA0003828039090000082
In the same way, the first and second,
Figure BDA0003828039090000083
are identical to each other,
Figure BDA0003828039090000084
and
Figure BDA0003828039090000085
are conjugate with each other, and the summation terms are consistent in range. Then
Figure BDA0003828039090000086
Each of the multiplied sum factors is in fact all of
Figure BDA0003828039090000087
The summation factors of each multiplied term are conjugate, so that the real part interference needs to be cancelled
Figure BDA0003828039090000088
Therefore, in order to cancel the interference caused by the adjacent symbols, the designed pilot symbols should satisfy the following rule: left and right one-level adjacent symbol adoption
Figure BDA0003828039090000089
Selection of adjacent symbols at upper and lower stages
Figure BDA00038280390900000810
Therefore, the finally designed frequency domain continuous interpolation pilot structure is shown in fig. 2, which is a pilot structure with an upper and a lower opposite directions, and can effectively eliminate interference from surrounding symbols on pilot symbols, so as to increase the accuracy of the following phase noise compensation algorithm.
Operation S2, calculating a symbol index m of each subcarrier 0 Compensation factor of pilot symbols, where each subcarrier is at symbol index m 0 The result of taking the real part after multiplying the demodulated symbol by the compensation factor is equal to the corresponding pilot symbol.
Specifically, pilot symbols are inserted into a plurality of subcarriers at the transmitting end, for the transmitted pilot of each subcarrier, demodulation and equalization are performed at the receiving end to obtain a corresponding received pilot, and then an interference compensation formula is substituted to obtain a compensation factor of the subcarrier pilot.
The transmission signal obtained after FBMC-OQAM system modulation of the real input sequence can be represented as:
Figure BDA0003828039090000091
wherein denotes a convolution operation;
Figure BDA0003828039090000092
representing a set of natural numbers; k represents the number of subcarriers; g [ n ]]Representing the prototype filter, filter length L g = α K +1, α is an overlap factor;
Figure BDA0003828039090000093
is the phase rotation factor, d k,m Is a transmitted pilot symbol.
The signal passes through a millimeter wave channel, and the influence of phase noise of a sender and a receiver is considered, and the received baseband time domain signal is as follows:
Figure BDA0003828039090000094
wherein, h [ n ]]Representing the time domain response of the millimeter wave channel,
Figure BDA0003828039090000095
representing the phase noise at the nth discrete sampling point of the sender,
Figure BDA0003828039090000096
representing the phase noise at the nth discrete sampling point on the receiving side.
Since the bandwidth of the phase noise is much smaller than the bandwidth of the signal, it can be considered
Figure BDA0003828039090000097
Then the equation for the received signal at this time can be simplified as:
Figure BDA0003828039090000098
in general, τ max Is much smaller than L g (L g K +1, i.e. τ max K, tau K) is
Figure BDA0003828039090000099
Thus, the received signal r [ n ]]Can be further simplified into:
Figure BDA0003828039090000101
at time-frequency point (k) 0 ,m 0 ) The demodulated symbols at (a) can be expressed as:
Figure BDA0003828039090000102
obtaining a demodulated signal
Figure BDA0003828039090000103
Later, to facilitate the next calculation, the subcarrier index k is indexed 0 Is shown as
Figure BDA0003828039090000104
Substituting the interference into an interference compensation formulaIs composed of
Figure BDA0003828039090000105
Wherein, the first and the second end of the pipe are connected with each other,
Figure BDA0003828039090000106
is at the sub-carrier
Figure BDA0003828039090000107
Upper m 0 The pilot symbols transmitted at the time of day,
Figure BDA0003828039090000108
is a compensation factor. Compensation factor
Figure BDA0003828039090000109
The compensation of the phase noise is of primary interest and is therefore a rotation angle with a modulus value of 1, i.e. constrained
Figure BDA00038280390900001010
A system of equations is obtained:
Figure BDA00038280390900001011
solving the system of equations to obtain an estimate of the compensation factor
Figure BDA00038280390900001012
Figure BDA0003828039090000111
Wherein
Figure BDA0003828039090000112
The two solution groups correspond to two different situations, and the solution group with the smaller rotation angle should be selected because the angle value of the phase noise is smaller.
Although the compensation factor here is not only for phase noiseCompensating for all interference including ISI and ICI, and reducing the influence of other interference
Figure BDA0003828039090000113
The approximation is seen as a compensation of the phase noise.
In addition, other than by interference compensation formulas
Figure BDA0003828039090000114
Solving the compensation factor, the compensation factor can also be solved by the following formula:
Figure BDA0003828039090000115
formula for calculating compensation factor used in this patent
Figure BDA0003828039090000116
For its simplicity. Let us order:
Figure BDA0003828039090000117
wherein:
Figure BDA0003828039090000121
Figure BDA0003828039090000122
then, the objective function pair is taken
Figure BDA0003828039090000123
And set it to 0, one can get:
Figure BDA0003828039090000124
then
Figure BDA0003828039090000125
Operation S3, averaging the compensation factors, calculating the absolute value of the difference between each compensation factor and the average value, and taking the average value as a final compensation factor if the sum of the absolute values of the difference values is smaller than a preset threshold value; otherwise, distributing weight to each compensation factor according to the absolute value of each difference value, and obtaining the final compensation factor through weighted average.
In an alternative embodiment, step S3 specifically includes:
the amount of interference experienced by the pilot symbols includes two parts: phase noise interference and other interference such as ISI and ICI. We need to scale the magnitude of the interference in addition to the phase noise. The idea here is that the smaller the interference other than phase noise is on the pilot symbols, the closer the compensation factor obtained by the interference compensation algorithm is to the phase noise compensation.
With an index
Figure BDA0003828039090000126
Of
Figure BDA0003828039090000127
Is a set of
Figure BDA0003828039090000128
By calculating
Figure BDA0003828039090000129
The difference between each other can be measured
Figure BDA00038280390900001210
The magnitude of the interference experienced, other than phase noise. The algorithm is as follows:
s31, calculating the expectation of P subcarrier phase noise compensation:
Figure BDA00038280390900001211
in S32, since the phase noise interference received by each subcarrier pilot at the same time is the same, but other interference such as ISI and ICI is different, the calculation is performed
Figure BDA0003828039090000131
And
Figure BDA0003828039090000132
the difference can measure the magnitude of other disturbances than phase noise, i.e.
Figure BDA0003828039090000133
S33, firstly, the
Figure BDA0003828039090000134
And summing the medium elements to obtain the total interference size:
Figure BDA0003828039090000135
then a threshold value mu is set φ ：
If it is
Figure BDA0003828039090000136
The influence of other interference can be ignored, and the result obtained in step S31
Figure BDA0003828039090000137
It can be expressed as the final result of the phase noise compensation
Figure BDA0003828039090000138
If it is
Figure BDA0003828039090000139
The effect of other interference cannot be ignored, depending on the magnitude of the other interference
Figure BDA00038280390900001310
Assign weights, i.e.
Figure BDA00038280390900001311
Wherein
Figure BDA00038280390900001312
Represents the normalization operation:
Figure BDA00038280390900001313
operation S4, indexing the symbol m by using the final compensation factor 0 And compensating the demodulation symbols on all the subcarriers to obtain a final phase noise compensation result.
In particular, the phase noise compensation result is finally utilized
Figure BDA00038280390900001314
For symbol index m 0 Demodulated symbols on all sub-carriers of
Figure BDA00038280390900001315
And (3) performing phase noise compensation:
Figure BDA00038280390900001316
the following describes the beneficial effects of the present invention with reference to specific simulation tests. The phase noise model used in the simulation is a single zero-pole power spectral density model and uses the data in the IEEE 802.11ad standard, the carrier center frequency f c =60GHz, sampling rate f of phase noise s The total carrier band width is constant, the influence of phase noise on the system is concerned, therefore, the receiving end is assumed to obtain ideal channel information, the channel influence is perfectly balanced, a prototype filter adopted by the FBMC-OQAM system is a PHYDYAS filter, the superposition factor is alpha =4, in a pilot frequency structure inserted between frequency domains, the insertion density of the pilot frequency sub-carriers is that one pilot frequency sub-carrier is inserted in each 16 sub-carriers, the number of the pilot frequency sub-carriers of the pilot frequency structure inserted between frequency domains is equal to that of the pilot frequency sub-carriers of the pilot frequency structure inserted between frequency domainsThe number of waves is the same and is K/16.
As shown in fig. 3, wherein the Method-I algorithm is an original algorithm without considering ICI and ISI interference inherent in the FBMC-OQAM system, the PPNC-S algorithm is the algorithm proposed in the present invention. Shown in the figure is the BER performance comparison of the Method-I algorithm with the PPNC-S algorithm at 1694am, k = 64. It can be found that when the number of pilot subcarriers is small in the PPNC-S algorithm, the BER of the pilot structure is much smaller than that of the Method-I algorithm no matter the pilot structure is I-All1 or I-Rand, which shows that the PPNC-S algorithm can realize a relatively good phase noise compensation result with only a few pilot subcarriers, and has a stronger information capture capability on phase noise.
As shown in fig. 4, it can be seen that the performance of the algorithm proposed by the present invention is improved by designing the pilot structure in an up-down opposite manner. The BER performance of the algorithm provided by the invention under different pilot frequency structures is shown when 1694am and K = 128. As can be seen from the figure, the designed pilot frequency structure C-UDoppo with the upper and lower parts opposite has the most excellent performance, the BER value is as low as below 10 < -6 >, and is far lower than the BER of other pilot frequency structures, and the C-UDoppo pilot frequency structure has a strong promotion effect on the performance of the algorithm provided by the invention. On the other hand, it can be found that the frequency domain interleaved pilot structures I-AllI and I-Rand have the worst effect and are not suitable for the algorithm provided by the invention, and the remaining pilot structures C-AllI, C-Rand and C-UDsame have almost the same effect. Wherein PPNC-S refers to the algorithm provided by the invention.
Fig. 5 is a block diagram of a phase noise compensation apparatus for millimeter wave systems according to an embodiment of the present invention. Referring to fig. 5, the apparatus 500 for compensating phase noise of a millimeter wave system includes an insertion module 510, a first calculation module 520, a second calculation module 530, and a compensation module 540.
The inserting module 510 performs, for example, operation S1 for inserting pilot symbols on a number of subcarriers at the transmitting end.
The first calculation module 520 performs, for example, operation S2 for calculating a symbol index m of each subcarrier 0 Compensation factor of pilot symbols, where each subcarrier is at symbol index m 0 The result of taking the real part after multiplying the demodulated symbol by the compensation factor and correspondingThe pilot symbols are equal.
The second calculating module 530, for example, performs operation S3, and is configured to average the compensation factors, calculate an absolute value of a difference between each compensation factor and the average, and if a sum of absolute values of the differences is smaller than a preset threshold, take the average as a final compensation factor; otherwise, distributing weight to each compensation factor according to the absolute value of each difference value, and obtaining the final compensation factor through weighted average.
The compensation module 540 performs, for example, operation S4 for indexing the symbol m with the final compensation factor 0 And compensating the demodulation symbols on all the subcarriers to obtain a final phase noise compensation result.
The millimeter wave system phase noise compensation apparatus 500 is used to perform the millimeter wave system phase noise compensation method in the embodiments shown in fig. 1-4. For details that are not described in the present embodiment, please refer to the method for compensating the phase noise of the millimeter wave system in the embodiments shown in fig. 1 to fig. 4, which is not described herein again.
An electronic device 600 includes a processor 610 and a readable storage medium 620, as shown in fig. 6. The electronic device 600 may perform the method of compensating for phase noise of the millimeter wave system described above in fig. 1-4.
In particular, the processor 610 may comprise, for example, a general purpose microprocessor, an instruction set processor and/or related chip set and/or a special purpose microprocessor (e.g., an Application Specific Integrated Circuit (ASIC)), or the like. The processor 610 may also include on-board memory for caching purposes. The processor 610 may be a single processing unit or a plurality of processing units for performing the different actions of the method flows according to embodiments of the present disclosure described with reference to fig. 1-4.
Readable storage medium 620 may be, for example, any medium that can contain, store, communicate, propagate, or transport the instructions. For example, a readable storage medium may include, but is not limited to, an electronic, magnetic, optical, electromagnetic, infrared, or semiconductor system, apparatus, device, or propagation medium. Specific examples of the readable storage medium include: magnetic storage devices, such as magnetic tape or Hard Disk Drives (HDDs); optical storage devices, such as compact disks (CD-ROMs); a memory, such as a Random Access Memory (RAM) or a flash memory; and/or wired/wireless communication links.
The readable storage medium 620 may include a computer program 621, which computer program 621 may include code/computer-executable instructions that, when executed by the processor 610, cause the processor 610 to perform a method flow, such as described above in connection with fig. 1-4, and any variations thereof.
The computer program 621 may be configured with, for example, computer program code comprising computer program modules. For example, in an example embodiment, code in computer program 621 may include one or more program modules, including 621A, 621B, … …, for example. It should be noted that the division and number of modules are not fixed, and those skilled in the art may use suitable program modules or program module combinations according to actual situations, which when executed by the processor 610, enable the processor 610 to perform the method flows described above in conjunction with fig. 1-4, for example, and any variations thereof.
Embodiments of the present invention further provide a computer-readable storage medium, on which a computer program is stored, where the computer program, when executed by a processor, implements a method for compensating phase noise of a millimeter wave system in the embodiments shown in fig. 1 to 4.
It will be understood by those skilled in the art that the foregoing is only a preferred embodiment of the present invention, and is not intended to limit the invention, and that any modification, equivalent replacement, or improvement made within the spirit and principle of the present invention should be included in the scope of the present invention.

Claims (10)

1. A method for compensating phase noise of a millimeter wave system is characterized by comprising the following steps:
s1, inserting pilot symbols into a plurality of subcarriers of a sending end;
s2, calculating the symbol index m of each subcarrier 0 Compensation factor of pilot symbols, where each subcarrier is at symbol index m 0 OfAfter the demodulation symbols are multiplied by the compensation factors, the result of the real part is taken to be equal to the corresponding pilot symbols;
s3, averaging all the compensation factors, calculating the absolute value of the difference value between each compensation factor and the average value, and taking the average value as a final compensation factor if the sum of the absolute values of all the difference values is smaller than a preset threshold value; otherwise, distributing weight to each compensation factor according to the absolute value of each difference value, and obtaining a final compensation factor through weighted average;
s4, using the final compensation factor to index the symbol m 0 And compensating the demodulation symbols on all the subcarriers to obtain a final phase noise compensation result.
2. The method for compensating phase noise of millimeter wave system according to claim 1, wherein in S1, a frequency domain continuous interpolation pilot structure is adopted, and the pilot structure satisfies: for any pilot symbol, the left pilot symbol and the right pilot symbol are equal, and the upper pilot symbol and the lower pilot symbol are opposite.
3. The method for compensating phase noise of millimeter wave system according to claim 1 or 2, wherein in S2, the symbol index m of each subcarrier is calculated by the following equation set 0 Compensation factor of pilot symbol at:
Figure FDA0003828039080000011
wherein the content of the first and second substances,
Figure FDA0003828039080000012
and
Figure FDA0003828039080000013
respectively represent
Figure FDA0003828039080000014
Subcarrier at symbol index m 0 The demodulated symbols and the pilot symbols at (a),
Figure FDA0003828039080000015
representing pilot symbols
Figure FDA0003828039080000016
The compensation factor of (a) is determined,
Figure FDA0003828039080000017
and I { } denotes taking the real part and the imaginary part, respectively.
4. The method for compensating phase noise of a millimeter wave system according to claim 1 or 2, wherein in the step S3, assigning a weight to each compensation factor according to the magnitude of the absolute value of each difference value comprises:
and normalizing the absolute value of each difference value, and taking the normalized value as the weight of each compensation factor.
5. A device for compensating phase noise of a millimeter wave system, comprising:
the inserting module is used for inserting pilot symbols in a plurality of subcarriers of a sending end;
a first calculation module for calculating the symbol index m of each subcarrier 0 A compensation factor of the pilot symbol of (a), wherein each subcarrier is at a symbol index m 0 The result of taking the real part after the demodulation symbol is multiplied by the compensation factor is equal to the corresponding pilot frequency symbol;
the second calculation module is used for averaging all the compensation factors, calculating the absolute value of the difference value between each compensation factor and the average value, and taking the average value as the final compensation factor if the sum of the absolute values of all the difference values is smaller than a preset threshold value; otherwise, distributing weight to each compensation factor according to the absolute value of each difference value, and obtaining a final compensation factor through weighted average;
compensation module forIndexing the symbol m by the final compensation factor 0 And compensating the demodulation symbols on all the subcarriers to obtain a final phase noise compensation result.
6. The apparatus for compensating phase noise of millimeter wave system according to claim 5, wherein the inserting module is further configured to employ a frequency domain continuous inserting pilot structure, and the pilot structure satisfies: for any pilot symbol, the left pilot symbol and the right pilot symbol are equal, and the upper pilot symbol and the lower pilot symbol are opposite.
7. The apparatus as claimed in claim 5 or 6, wherein the first calculating module is further configured to calculate the symbol index m of each sub-carrier by using the following equation set 0 Compensation factor of pilot symbol at:
Figure FDA0003828039080000031
wherein the content of the first and second substances,
Figure FDA0003828039080000032
and
Figure FDA0003828039080000033
respectively represent
Figure FDA0003828039080000034
Subcarrier at symbol index m 0 The demodulated symbols and the pilot symbols at (a),
Figure FDA0003828039080000035
representing pilot symbols
Figure FDA0003828039080000036
The compensation factor of (a) is determined,
Figure FDA0003828039080000037
and I { } denotes taking the real part and the imaginary part, respectively.
8. The apparatus for compensating phase noise of a millimeter wave system according to claim 5 or 6, wherein the second calculating module is further configured to perform a normalization operation on the absolute value of each difference, and use the normalized value as the weight of each compensation factor.
9. An electronic device, comprising:
a processor;
a memory storing a computer-executable program that, when executed by the processor, causes the processor to perform the method of compensating for millimeter wave system phase noise of any of claims 1-4.
10. A computer-readable storage medium on which a computer program is stored, the program, when being executed by a processor, implementing the method for compensating for phase noise of a millimeter wave system according to any one of claims 1 to 4.
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