CN115528405A - Strip line broadband two-dimensional sum-difference network and multifunctional sum-difference network - Google Patents
Strip line broadband two-dimensional sum-difference network and multifunctional sum-difference network Download PDFInfo
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- CN115528405A CN115528405A CN202211210821.9A CN202211210821A CN115528405A CN 115528405 A CN115528405 A CN 115528405A CN 202211210821 A CN202211210821 A CN 202211210821A CN 115528405 A CN115528405 A CN 115528405A
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- H01—ELECTRIC ELEMENTS
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Abstract
The invention discloses a strip line broadband two-dimensional sum-difference network and a multifunctional sum-difference network, wherein the two-dimensional sum-difference network comprises an upper dielectric plate, an upper semi-solidified sheet, a middle dielectric plate, a lower semi-solidified sheet and a lower dielectric plate which are sequentially stacked from top to bottom, and the two-dimensional sum-difference network also comprises a metalized through hole penetrating through the whole two-dimensional sum-difference network, and is characterized in that: the upper surface of the upper dielectric plate is covered by an upper anti-interference layer, the lower surface of the lower dielectric plate is covered by a lower anti-interference layer, and the metallized through hole penetrates through the upper anti-interference layer and the lower anti-interference layer; the upper surface and the lower surface of the middle dielectric plate are respectively provided with a conduction band, the overlapped part of the conduction band and the edge of the middle dielectric plate forms a port, the conduction bands are partially overlapped, the overlapped region forms four constant bias couplers, and the four constant bias couplers are cascaded to form a strip line wide-band two-dimensional sum-difference network. The invention provides a strip line broadband two-dimensional sum-difference network and a multifunctional sum-difference network which have high integration degree and broadband and are easy to be integrally designed with an antenna and a radio frequency circuit.
Description
Technical Field
The invention belongs to the technical field of millimeter waves, and particularly relates to a strip line broadband two-dimensional sum-difference network and a multifunctional sum-difference network.
Background
As a key part of a millimeter wave monopulse radar system, the performance of a sum-difference network directly influences important indexes such as the tracking precision and the tracking distance of a radar. The two-dimensional sum-difference network, also called a two-dimensional comparator and a two-dimensional sum-difference device, can synthesize four paths of signals corresponding to four quadrants of a space at the same time, and simultaneously output sum, azimuth difference and pitch difference signals. Currently, common sum and difference networks include: waveguide sum and difference networks, microstrip line sum and difference networks and stripline sum and difference networks.
The waveguide sum and difference network is mostly used for a single-pulse radar system with a brick structure, which has low integration level, low packaging efficiency and low requirement on space size, and the sum and difference network is usually large in size and not beneficial to realizing the miniaturization and light weight of the radar system. The microstrip line sum and difference network has the advantages of small volume and light weight, can be used for a tile type structure single pulse radar system with higher integration level, and usually the sum and difference network needs to design a single microstrip line shielding cavity to realize electromagnetic shielding, which brings certain limitation to system integration.
The solid-state single-pulse phased array antenna is in the development trend of multi-mode composition, ultra wide band and high integration, which not only puts higher requirements on the planarization, miniaturization and broadband characteristics of a sum-difference network, but also makes the simple two-dimensional sum-difference network difficult to meet the requirements of multifunctional work of the phased array antenna, for example, when the sum and difference beams of the phased array antenna are realized, the phased array antenna is required to realize the sum and difference beams of a sub-array in order to realize multi-beam or improve the anti-interference capability, and therefore, the multifunctional sum-difference network is necessary to be researched and developed to meet the application requirements.
Disclosure of Invention
The invention aims to overcome the defects of the prior art and provide a stripline broadband two-dimensional sum-difference network and a multifunctional sum-difference network which have high integration degree and broadband and are easy to be integrally designed with an antenna and a radio frequency circuit.
The purpose of the invention is realized by the following technical scheme:
a two-dimensional sum-difference network of a strip line broadband comprises an upper dielectric slab, an upper semi-cured sheet, a middle dielectric slab, a lower semi-cured sheet and a lower dielectric slab which are sequentially stacked from top to bottom, and the two-dimensional sum-difference network further comprises a metalized through hole penetrating through the whole two-dimensional sum-difference network;
the upper surface of the upper dielectric plate is covered by an upper anti-interference layer, the lower surface of the lower dielectric plate is covered by a lower anti-interference layer, and the metallized through hole penetrates through the upper anti-interference layer and the lower anti-interference layer;
the upper surface and the lower surface of the middle dielectric plate are respectively provided with a conduction band, the overlapped part of the conduction band and the edge of the middle dielectric plate forms a port, the conduction bands are partially overlapped, the overlapped area forms four constant bias couplers, and the four constant bias couplers are cascaded to form a two-dimensional sum-difference network of a strip line width band.
Further, the upper anti-interference layer and the lower anti-interference layer comprise copper sheets.
Furthermore, the upper conduction band and the lower conduction band of the middle medium plate are respectively mirror-symmetrical, and the upper conduction band and the lower conduction band are mirror-symmetrical.
Further, the bias coupler comprises a first coupling branch, a coupling cross branch and a second coupling branch, the first coupling branch and the second coupling branch form a two-stage coupling line, and the bias coupler adopts two-stage coupling line cascade.
Further, the bias coupler achieves quadrature coupling by adjusting the lengths and widths of the first coupling stub, the coupling cross stub, and the second coupling stub.
Furthermore, the metallized through holes are uniformly distributed at a certain distance around the upper conduction band and the lower conduction band and serve as shielding holes of a strip line two-dimensional sum-difference network.
Furthermore, the distance between the metalized through holes is between lambda/10 and lambda/8.
On the other hand, the invention also provides a multifunctional sum-difference network, which comprises a first dielectric plate, a first semi-cured sheet, a second dielectric plate, a second semi-cured sheet, a third dielectric plate, a third semi-cured sheet, a fourth dielectric plate, a fourth semi-cured sheet and a fifth dielectric plate, wherein a plurality of strip line broadband two-dimensional sum-difference networks and a plurality of radio frequency switches according to any one of claims 1 to 7 are arranged in the multifunctional sum-difference network, and the radio frequency switches are used for realizing the switching of a transceiving radio frequency signal subarray and the separation of a public end receiving transmitting frequency signal.
Furthermore, a floor layer covers the upper surface of the first dielectric plate, the radio frequency switch is adhered or welded on the floor layer, and a plurality of ports are arranged on the upper surface of the first dielectric plate, which is not covered by the floor layer;
a conduction band is arranged on the upper surface of the second dielectric plate;
a floor layer and a plurality of medium gaps are arranged on the upper surface of the third medium plate;
the upper surface and the lower surface of the fourth dielectric plate are provided with conduction bands;
the lower surface of the fifth medium plate is provided with a floor layer, and a plurality of ports are arranged at the positions, where the floor layer is not arranged, of the lower surface of the fifth medium plate.
Furthermore, the first prepreg, the second prepreg, the third prepreg and the fourth prepreg are respectively positioned among the first dielectric plate, the second dielectric plate, the third dielectric plate, the fourth dielectric plate and the fifth dielectric plate and are used for fixing the dielectric plates together through high-temperature pressing.
The invention has the beneficial effects that:
(1) The invention adopts a strip line two-dimensional sum-difference network, has compact structure and high integration level, is easy to be integrally designed with an antenna and a radio frequency circuit, can effectively control the section height, weight and volume of the whole circuit and is convenient to realize miniaturized design.
(2) The invention adopts the strip line two-dimensional sum-difference network and adopts the multilayer PCB processing technology, does not need additional assembly procedures and is more beneficial to batch production.
(3) The invention adopts the strip line two-dimensional sum-difference network, designs the metallized through holes around the metal conduction band to serve as the shielding holes, has good electromagnetic shielding property, can effectively inhibit interlayer crosstalk, and does not need to design a separate shielding cavity to realize electromagnetic shielding.
(4) The invention utilizes four constant bias couplers formed by mutually overlapping metal conduction bands on two layers of the middle dielectric plate to form a strip line two-dimensional sum-difference network, the bias couplers have no gradual change, the overlapping coupling area is wider, the size is more compact, and the influence of the bias tolerance of the metal conduction band of the middle dielectric plate is less.
(5) The multifunctional sum-difference network provided by the invention realizes the same transmitting and receiving functions as the full array in each subarray through a plurality of built-in broadband two-dimensional sum-difference networks and a plurality of radio frequency switches. Because the mode can realize simultaneous multi-subarray scanning and pilot frequency work, the radar beam scanning capability and the anti-interference capability can be effectively improved.
Drawings
Figure 1 is a schematic diagram of a stripline two-dimensional sum and difference network of the present invention.
Figure 2 is a top view of a stripline two-dimensional sum and difference network of the present invention.
Figure 3 is a right side view of the stripline two-dimensional sum and difference network of the present invention.
Figure 4 is a schematic of a stripline two-dimensional sum and difference network interlevel dielectric layer of the present invention.
Figure 5 is a schematic top layer view of a stripline two-dimensional sum and difference network interlevel dielectric layer of the present invention.
Figure 6 is a schematic view of the lower layer of the stripline two-dimensional sum and difference network interlevel dielectric layer of the present invention.
Fig. 7 is a simulation result of the stripline two-dimensional sum and difference network common terminal S11 of the present invention.
Fig. 8 is a simulation result of a stripline two-dimensional sum and difference network drop port S11 of the present invention.
Fig. 9 is the results of a stripline two-dimensional sum and difference network inter-common port S21 simulation of the present invention.
Fig. 10 is a simulation result of S21 between adjacent sub-ports of the stripline two-dimensional sum and difference network of the present invention.
FIG. 11 is a stripline two-dimensional sum and difference network port-to-sum port S21 simulation result of the present invention.
Figure 12 is a stripline two-dimensional sum and difference network drop port to azimuth port S21 simulation result of the present invention.
Fig. 13 is a stripline two dimensional sum and difference network drop port to pitch port S21 simulation result of the present invention.
FIG. 14 is a simulation result of a stripline two-dimensional sum and difference network of the present invention for azimuthal normalization of phase differences.
FIG. 15 is a stripline two-dimensional sum and difference network pitch-to-normalized phase difference simulation result of the present invention.
Figure 16 is a schematic diagram of a multifunctional sum and difference network of the present invention.
Figure 17 is a schematic diagram of a multifunction sum and difference network stack of the present invention.
Figure 18 is a schematic top surface view of a first dielectric slab of the multifunctional sum and difference network of the present invention.
Fig. 19 is a partial schematic view of the metal conduction band on the top surface of the multifunctional sum and difference network first dielectric slab of the present invention.
Figure 20 is a partial schematic view of a metal disk on the top surface of a first dielectric slab of the multifunctional sum and difference network of the present invention.
Fig. 21 is a partial schematic view of a surface circulator on a first dielectric board of the multifunction sum and difference network of the present invention.
Figure 22 is a schematic top surface view of a second dielectric slab of the multifunctional sum and difference network of the present invention.
Figure 23 is a schematic top surface view of a third dielectric slab of the multifunctional sum and difference network of the present invention.
Fig. 24 is a partial schematic view of the upper surface of a third dielectric slab of the multifunctional sum and difference network of the present invention.
Figure 25 is a top view of a fourth dielectric slab of the multifunctional sum and difference network of the present invention.
Fig. 26 is a schematic view of the lower surface of a fourth dielectric slab of the multifunctional sum and difference network of the present invention.
Fig. 27 is a schematic view of the lower surface of the fifth dielectric plate of the multifunctional sum and difference network of the present invention.
Fig. 28 is a wiring schematic diagram of the multifunction sum and difference network of embodiment 2 of the present invention.
Fig. 29 is a wiring schematic diagram of the multifunction sum and difference network of embodiment 3 of the present invention.
Fig. 30 is a wiring schematic diagram of the multifunction sum and difference network of embodiment 4 of the present invention.
1-upper anti-interference layer, 2-upper dielectric plate, 3-upper half-cured sheet, 4-middle dielectric plate, 5-lower prepreg, 6-lower dielectric plate, 7-lower anti-interference layer, 8-upper metal conduction band, 9-lower metal conduction band, 10-first dielectric plate, 11-second dielectric plate, 12-third dielectric plate, 13-fourth dielectric plate, 14-fifth dielectric plate, 15-first prepreg, 16-second prepreg, 17-third prepreg, 18-fourth prepreg, 19-stripline broadband two-dimensional sum-difference network, 41-metalized through hole, 42-upper port, 43-lower port, 44-offset coupler, 421-first coupling branch section, 422-coupling cross branch section, 423-second coupling branch section, 104-first dielectric plate layer, 111-second dielectric plate metal, 122-third dielectric plate, 131-fourth dielectric plate upper metal conduction band, 132-fourth coupling branch section, 133-first dielectric plate metal conduction band-coplanar dielectric plate, 1011-coplanar dielectric plate, 31-coplanar dielectric plate metal transmission line, 1011-coplanar waveguide-coplanar dielectric plate, and transmission line disc.
Detailed Description
The embodiments of the present invention are described below with reference to specific embodiments, and other advantages and effects of the present invention will be easily understood by those skilled in the art from the disclosure of the present specification. The invention is capable of other and different embodiments and of being practiced or of being carried out in various ways, and its several details are capable of modification in various respects, all without departing from the spirit and scope of the present invention. It is to be noted that the features in the following embodiments and examples may be combined with each other without conflict.
All other embodiments, which can be obtained by a person skilled in the art without making any creative effort based on the embodiments in the present invention, belong to the protection scope of the present invention.
The waveguide sum and difference network is mostly used for a single-pulse radar system with a brick structure, which has low integration level, low packaging efficiency and low requirement on space size, and the sum and difference network is usually large in size and not beneficial to realizing the miniaturization and light weight of the radar system. The microstrip line sum and difference network has the advantages of small volume and light weight, can be used for a tile type structure single pulse radar system with higher integration level, and usually the sum and difference network needs to design a single microstrip line shielding cavity to realize electromagnetic shielding, which brings certain limitation to system integration.
The solid-state single-pulse phased array antenna is in the development trend of multi-mode composition, ultra wide band and high integration, which not only puts higher requirements on the planarization, miniaturization and broadband characteristics of a sum-difference network, but also makes the simple two-dimensional sum-difference network difficult to meet the requirements of multifunctional work of the phased array antenna, for example, when the sum and difference beams of the phased array antenna are realized, the phased array antenna is required to realize the sum and difference beams of a sub-array in order to realize multi-beam or improve the anti-interference capability, and therefore, the multifunctional sum-difference network is necessary to be researched and developed to meet the application requirements.
In order to solve the above technical problems, the following embodiments of a stripline broadband two-dimensional sum-and-difference network and a multifunctional sum-and-difference network of the present invention are proposed.
Example 1
Referring to fig. 1 to 6, fig. 1 is a schematic diagram of a stripline two-dimensional sum and difference network of the present embodiment, fig. 2 is a top view of the stripline two-dimensional sum and difference network of the present embodiment, fig. 3 is a right view of the stripline two-dimensional sum and difference network of the present embodiment, fig. 4 is a schematic diagram of a middle dielectric layer of the stripline two-dimensional sum and difference network of the present embodiment, fig. 5 is a schematic diagram of an upper layer of the middle dielectric layer of the stripline two-dimensional sum and difference network of the present embodiment, and fig. 6 is a schematic diagram of a lower layer of the middle dielectric layer of the stripline two-dimensional sum and difference network of the present embodiment.
The stripline two-dimensional sum and difference network provided in this embodiment specifically includes the following parts, which are an upper dielectric plate 2, an upper semi-cured sheet 3, a middle dielectric plate, a lower semi-cured sheet 5, and a lower dielectric plate 6, respectively, and the two-dimensional sum and difference network further includes a metalized through hole penetrating through the whole two-dimensional sum and difference network.
The upper surface of the upper dielectric plate 2 is covered by the upper anti-interference layer 1, the lower surface of the lower dielectric plate 6 is covered by the lower anti-interference layer 7, and the metallized through holes penetrate through the upper anti-interference layer 1 and the lower anti-interference layer 7.
The upper surface and the lower surface of the middle dielectric plate are both provided with metal conduction bands, the overlapped parts of the metal conduction bands and the edges of the middle dielectric plate form ports, the metal conduction bands are partially overlapped, the overlapped areas form four constant bias couplers, and the four constant bias couplers are cascaded to form a two-dimensional sum-difference network of a strip line width band.
In this embodiment, the upper interference rejection layer 1 and the lower interference rejection layer 7 are made of copper sheets. In the PCB processing technique adopted in this embodiment, the dielectric board used for processing has a copper layer.
As an implementation manner, in this embodiment, the upper conduction band and the lower conduction band of the middle dielectric slab are mirror-symmetric, and the upper conduction band and the lower conduction band are mirror-symmetric. The upper layer conduction band and the lower layer conduction band are formed by bending a single metal conducting wire, the main structure is distributed in a U shape, a part which is overlapped with the edge of the middle medium plate exists, and the part respectively forms an upper layer port 42 and a lower layer port 43. The upper port 42 and the lower port 43 are specifically divided into a sum port, an azimuth difference port, a pitch difference port, a load port, and respective branch ports. The branch ports respectively correspond to four quadrants of the monopulse radar or the monopulse antenna. The ports of the stripline broadband two-dimensional sum-difference network can be interconnected with external radio frequency ports through horizontal probes or coaxial transition, vertical transition, gap coupling and the like.
As an implementation manner, in this embodiment, the offset coupler 44 includes a first coupling branch 421, a coupling cross branch 422, and a second coupling branch 423, the first coupling branch 421 and the second coupling branch 423 form a two-stage coupling line, and the offset coupler 44 adopts a two-stage coupling line cascade connection. Compared with a sum-difference network formed by a gradual change coupler, the constant bias coupler 44 is free of gradual change, has a wider overlapped coupling area and a more compact size, and is less influenced by the offset tolerance of the upper metal conduction band 8 and the lower metal conduction band 9 of the middle dielectric plate.
As an implementation manner, the offset coupler 44 in this embodiment achieves the orthogonal coupling by adjusting the lengths and widths of the first coupling branch 421, the coupling cross branch 422, and the second coupling branch 423. In order to make the power ratio of the offset coupler 44 be 1 and the difference between adjacent output ends be constant at 90deg, the lengths and widths of the first coupling branch 421, the coupling cross branch 422 and the second coupling branch 423 need to be adjusted appropriately to achieve the effect of quadrature coupling.
As an implementation, in this embodiment, the metalized through holes 41 are uniformly distributed at a certain distance around the upper conduction band and the lower conduction band, and serve as shielding holes of the two-dimensional sum-difference network of the strip lines. The metalized through holes 41 play a role in electromagnetic shielding, effectively improve interlayer isolation of the sum-difference network, and better ensure indexes such as zero depth of the monopulse radar or the antenna.
As an implementation mode, the interval of the metallized through holes 41 is between lambda/10 and lambda/8 in the embodiment. Where λ is the corresponding wavelength for which the highest operating frequency is in the selected dielectric material. The limitation of the distance between the through holes is to limit leakage of electromagnetic waves in the transmission process, the smaller the distance is, the smaller the leakage is, but the smaller the distance is, more metallized through holes are inevitably needed, which increases the difficulty of processing and further increases the cost.
It should be noted that the upper dielectric plate 2 and the lower dielectric plate 6 mainly serve to support the intermediate dielectric plate in this embodiment.
Referring to fig. 7, as shown in fig. 7, which is a simulation result of the stripline two-dimensional sum and difference network common terminal S11 of the present embodiment, it can be seen that, in the range of 11.8GHz to 16.3GHz, four common ports S11 < -25dB, and the relative bandwidth is greater than 33.4%.
Referring to fig. 8, as shown in fig. 8, the simulation result of the stripline two-dimensional sum-difference network split port of the present embodiment includes a curve of the stripline two-dimensional sum-difference network split port along with the frequency variation, it can be seen that in the range of 11.8GHz to 16.3GHz, four common ports S11 < -26dB, and the relative bandwidth is greater than 33.4%.
Referring to fig. 9, as shown in fig. 9, which is a simulation result of S21 between common ports of the stripline two-dimensional sum and difference network in this embodiment, it can be seen that, in the range of 11.8GHz to 16.3GHz, S21 between the azimuth and elevation ports is less than-27 dB, S21 between the azimuth and sum ports is less than-23 dB, and S21 between the elevation and sum ports is less than-50 dB, which indicates that the two-dimensional sum and difference network has good common port isolation and can ensure that the monopulse radar or the antenna has good difference beam zero depth.
Referring to fig. 10, as a result of the simulation of S21 between adjacent sub-ports of the stripline two-dimensional sum-difference network in this embodiment shown in fig. 10, it can be seen that S21 between sub-ports 1 and 3 and between sub-ports 2 and 4 is less than-27 dB in the range of 11.8GHz to 16.3GHz, which shows that the isolation between the sub-ports of the two-dimensional sum-difference network is excellent, and the influence of radio frequency signals between the sub-ports can be effectively reduced.
Referring to fig. 11, as shown in fig. 11, which is a simulation result of the port to port S21 of the stripline two-dimensional sum and difference network of this embodiment, it can be seen that, in the range of 11.8GHz to 16.3GHz, each port to port S21 is in the range of-6.4 dB to-5.9 dB, and the maximum difference is ± 0.25dB. When the monopulse radar or the antenna is in a transmitting state, complete constant-amplitude in-phase output can be basically realized after phase matching is carried out on a tail end channel, and the strip line two-dimensional sum-difference network can obtain higher sum beam gain.
Referring to fig. 12, as shown in the simulation result of the sub-port to azimuth port S21 of the stripline two-dimensional sum and difference network of this embodiment shown in fig. 12, it can be seen that, in the range of 11.8GHz to 16.3GHz, the maximum difference is ± 0.25dB, where the sub-port to sum port S21 is in the range of-6.4 dB to-5.9 dB.
Referring to fig. 13, as shown in fig. 13, which is a simulation result of the sub-port to the pitch port S21 of the stripline two-dimensional sum and difference network of the embodiment, it can be seen that, in the range of 11.8GHz to 16.3GHz, each sub-port to sum port S21 is in the range of-6.4 dB to-5.9 dB, and the maximum difference is ± 0.25dB.
Referring to fig. 14, as shown in fig. 14, it is a simulation result of the azimuth normalized phase difference of the stripline two-dimensional sum and difference network in the present embodiment, after the phase pairs corresponding to the ports of the stripline two-dimensional sum and difference network from the ports to the azimuth ports are normalized, the phase differences between normalized port 1 and normalized port 3, and between normalized port 2 and normalized port 4 are observed, and the azimuth phase difference is 179.1 deg. to 180.3 deg. in the range of 11.8GHz to 16.3 GHz.
Referring to fig. 15, as shown in fig. 15, it is a result of the pitch-direction normalized phase difference simulation of the stripline two-dimensional sum-difference network of the present embodiment, which includes the phase differences between the normalized port 1 and the normalized port 2, and between the normalized port 4 and the normalized port 3 after the phase pairs from the sub-ports to the pitch-ports of the stripline two-dimensional sum-difference network are normalized to the corresponding sum-ports, it can be seen that, in the range of 11.8GHz to 16.3GHz, the azimuth-direction phase difference is between-180.3 deg and-179.08 deg.
As can be seen from fig. 12 and 14, the ports 1 and 3, and the ports 2 and 4 can almost realize the constant-amplitude reverse transmission characteristic of the constant-amplitude in-phase signals input from the branch ports, which can effectively ensure that the monopulse radar or the antenna forms a receiving azimuth difference beam.
As can be seen from fig. 13 and fig. 15, the port 1 and the port 2, and the port 4 and the port 3 can almost realize the constant amplitude reverse transmission characteristic of the constant amplitude in-phase signal input from the branch port, which can effectively ensure that the monopulse radar or the antenna forms a receiving difference-elevation beam.
The two-dimensional sum-difference network for the strip line broadband provided by the embodiment is formed by laminating three dielectric plates and two prepregs, wherein an upper copper sheet and a lower copper sheet serve as an upper metal floor and a lower metal floor of the strip line, an upper metal conduction band and a lower metal conduction band inside the strip line are respectively positioned on two sides of the middle dielectric plate, and the upper metal conduction band and the lower metal conduction band are partially overlapped together from a top view to form a constant bias coupler, and the size of a first coupling branch, a coupling cross branch and a second coupling branch B423 of the bias coupler is properly adjusted to achieve the effect of orthogonal coupling. After the four bias couplers are cascaded by utilizing the strip lines, a complete strip line broadband two-dimensional sum-difference network is formed, the ultra-wideband characteristic is achieved, and the relative bandwidth is larger than 33.4%. In addition, the metallized through holes are uniformly distributed on the peripheries of the upper metal conduction band and the lower metal conduction band of the strip line broadband two-dimensional sum-difference network, serve as shielding holes of the strip line two-dimensional sum-difference network, play a role in electromagnetic shielding, effectively improve the line-to-line isolation of the sum-difference network, and better ensure indexes such as zero depth of the pulse radar or the antenna. The stripline broadband two-dimensional sum-difference network provided by the embodiment has the advantages of compact structure, high integration level, easiness in integrated design with the antenna and the radio frequency circuit, capability of effectively controlling the profile height, weight and volume of the whole circuit, convenience in realizing miniaturized design, capability of directly processing by adopting a multilayer PCB (printed Circuit Board) processing process, no need of additional assembly procedures and more benefit for batch production.
Example 2
The present embodiment provides a multifunctional sum and difference network, and referring to fig. 16 to 27, as shown in fig. 16, a multifunctional sum and difference network schematic diagram of the present embodiment is provided. Fig. 17 is a schematic diagram of a multi-functional sum and difference network stack of the present embodiment. Fig. 18 is a schematic top view of the first dielectric plate of the multifunctional sum and difference network of the present embodiment. Fig. 19 is a partial schematic view of the metal conduction band on the upper surface of the first dielectric plate of the multifunctional sum-difference network in the embodiment. Fig. 20 is a partial schematic view of the metal disc on the upper surface of the first dielectric plate of the multifunctional sum and difference network of the present embodiment. Fig. 21 is a partial schematic view of the multifunctional sum and difference network first dielectric slab upper surface circulator of the present embodiment. Fig. 22 is a schematic top surface view of the second dielectric plate of the multifunctional sum and difference network of this embodiment. Fig. 23 is a schematic top view of the third dielectric plate of the multifunctional sum and difference network of the present embodiment. Fig. 24 is a partial schematic view of the upper surface of the third dielectric plate of the multifunctional sum and difference network of the present embodiment. Fig. 25 is a schematic top view of the fourth dielectric plate of the multifunctional sum and difference network of the present embodiment. Fig. 26 is a schematic view of the lower surface of the fourth dielectric plate of the multifunctional sum and difference network of the present embodiment. Fig. 27 is a schematic view of the lower surface of the fifth dielectric plate of the multifunctional sum and difference network of the present embodiment.
The multifunctional sum-difference network comprises a first dielectric plate 10, a first prepreg 15, a second dielectric plate 11, a second prepreg 16, a third dielectric plate 12, a third prepreg 17, a fourth dielectric plate 13, a fourth prepreg 18 and a fifth dielectric plate 14.
The first dielectric plate floor layer 104 is disposed on the upper surface of the first dielectric plate 10, the first dielectric plate floor layer 104 covers a large part of the upper surface of the first dielectric plate 10, and is mainly used as a metal floor of a multifunctional sum-difference network, twelve single-pole double-throw rf switches 1012, a circulator 1032 and a grounded coplanar waveguide transmission line 1031 are welded or bonded on the metal floor, so as to implement sub-array switching of the rf signals for transceiving and separation of the rf signals for transceiving at the common terminal. In this embodiment, the first dielectric slab floor layer and the subsequent floor layer are made of copper sheets.
The non-copper position on the upper surface of the first dielectric plate 10 is provided with a plurality of first dielectric plate metal conduction bands 1011, and the first dielectric plate metal conduction bands 1011 transmit each subarray radio frequency signal to the multi-functional sum-difference network surface, and are switched by the radio frequency switch 1012 or separated by the circulator 1032 and then fed into each main port or branch port.
The non-copper position of the upper surface of the first dielectric slab 10 has a plurality of metal discs 1021, and the metal discs 1021 are respectively a transmitting (T), a receiving (R), a azimuth difference (FW), a pitch difference (FY) and a load (FZ) total port. The transmitted radio frequency signal can be fed into the multifunctional sum and difference network through the transmission main port, then transmitted to the branch output ports A1-A4 and B1-B4, then transmitted to the T component for amplification and phase shift, and radiated by the antenna to form a transmission sum beam. The electromagnetic wave received by the receiving antenna can be amplified and phase-shifted through the R component, transmitted to the ports A1-A4 and B1-B4 of each branch circuit, and then formed into a receiving sum wave beam, a azimuth difference wave beam and a pitching difference wave beam through the multifunctional sum and difference network. In addition, the load port is used to terminate a matched load. The center of the metal disk 1021 is provided with a plurality of metallized blind holes which are communicated with other dielectric plates and used for transmitting radio frequency signals.
The upper surface of the second dielectric plate 11 has a plurality of second dielectric plate metal conduction bands 111 for conducting the first dielectric plate 10 and the third dielectric plate 12, and its main functions are two: firstly, the radio frequency signal is transmitted to each radio frequency switch 1012, and secondly, the cross-over when the conduction band structures of other layers of metal interfere is realized.
The upper surface of the third dielectric plate 12 has a third dielectric plate floor layer 122 serving as a metal floor of a plurality of second dielectric plate metal conduction bands 111 on the upper surface of the second dielectric plate 11.
The upper surface of the third dielectric plate 12, in addition to serving as the third dielectric plate floor layer 122 of the metal floor, has a plurality of dielectric gaps 1211, which mainly serve to prevent short-circuit of radio frequency signals and realize effective transmission of radio frequency signals between metal conduction bands or metal discs on different layers of the multifunctional sum-difference network.
The upper surface of the fourth dielectric plate 13 is provided with a fourth dielectric plate upper metal conduction band 131, the lower surface is provided with a plurality of fourth dielectric plate lower metal conduction bands 132, the first function of the fourth dielectric plate upper metal conduction band is to transmit radio frequency signals, and the other key function of the fourth dielectric plate upper metal conduction band is to form eight constant bias couplers and form two strip line width two-dimensional sum-difference networks 19 in a cascade mode.
The bottom surface of the fifth dielectric plate 14 has a fifth dielectric plate floor layer 141 as a metal floor of the fourth dielectric plate upper metal conduction band 131 and the fourth dielectric plate lower metal conduction band 132. The non-copper sheet positions on the lower surface of the fifth dielectric plate 14 are provided with a plurality of metal discs A1-A4 and B1-B4, the metal discs are radio frequency branch ports, and the multifunctional sum and difference network can realize radio frequency signal transmission through the branch ports and the T/R component.
As an implementation manner, in this embodiment, the first, second, third, and fourth prepregs are respectively located in the first, second, third, fourth, and fifth dielectric slabs, and the dielectric slabs are fixed together by high-temperature pressing.
The multifunctional network metalized through hole 142 penetrates from the upper surface of the first dielectric plate 10 to the lower surface of the fifth dielectric plate 14, so as to realize electromagnetic shielding of metal conduction bands of each layer and reduce interlayer mutual interference.
The metallized radio frequency blind hole 133 is used for realizing radio frequency signal conduction of metal conduction bands or metal discs of different layers, and the metallized blind hole 133 can be realized by conventional PCB processing technologies such as depth control, back drilling and the like.
Referring to fig. 28, a schematic diagram of the multi-function sum and difference network wiring of the present embodiment is shown in fig. 28. The multifunctional sum and difference network can mainly realize two working modes, namely full array working and sub-array working respectively, under the control of a radio frequency switch 1012.
The first working mode is full-array working, and the working mode of the first working mode is the same as that of the traditional monopulse phased array radar. In the transmitting state, the radio frequency switches 1012 from the transmitting sum port T1 to all the branch ports A1 to A4 and B1 to B4 are in a conducting state, transmitting sum signals reach the branch ports A1 to A4 and B1 to B4 through the multifunctional sum-difference network, and are transmitted to the T-block for amplification and phase shifting, and then form transmitting sum beams through antenna radiation. In a receiving state, an electromagnetic wave signal received by the phased array antenna is converted into a radio frequency signal, the radio frequency signal is amplified and phase-shifted through the R component, transmitted to the branch ports A1-A4 and B1-B4, then transmitted to the receiving sum port R1, the azimuth port FW1 and the elevation port FY1 through the multifunctional sum-difference network, and finally transmitted to the receiving sum port R1, the azimuth port FW1 and the elevation port FY1, so that a receiving sum beam, an azimuth difference beam and an elevation difference beam are formed.
The second operating mode is sub-array operation, in this mode, the radio frequency switches 1012 of the branch ports A1-A4 and B1-B4 corresponding to each sub-array to the corresponding total ports T1, R1, FW1, FY1 and T2, FW2, FY2 (at this time, T1, R1, FW1, FY1 are used as the common port of the sub-array a, and T2, R2, FW2, FY2 are used as the common port of the sub-array B) are in a conducting state, the sub-arrays a and B can operate at different frequencies at the same time, and the function of operating two monopulse phased array radars at the same time is realized. The multifunctional sum-difference network realizes the same transmitting and receiving functions as the working mode I in the A or B sub-array through two built-in broadband two-dimensional sum-difference networks and twelve radio frequency switches. Because this mode can realize two subarrays scanning and pilot frequency work simultaneously, can effectively promote radar beam scanning ability and interference killing feature.
Example 3
Referring to fig. 29, a wiring schematic diagram of the multifunctional sum and difference network of the present embodiment is shown in fig. 29. The difference between the present embodiment and embodiment 2 is that the multifunctional sum and difference network is built in with three broadband two-dimensional sum and difference networks and eleven radio frequency switches. The multifunctional sum-difference network is additionally provided with a broadband two-dimensional sum-difference network, one radio frequency switch is omitted, and the same function as that of the embodiment 2 is realized. The specific working mode refers to embodiment 2, and is not described herein again.
Example 4
Referring to fig. 30, a schematic diagram of the multi-function sum and difference network wiring of the present embodiment is shown in fig. 30. The difference between this embodiment and embodiments 2 and 3 is that the multifunctional sum-difference network is provided with three broadband two-dimensional sum-difference networks and eight radio frequency switches, and meanwhile, the a sub-array does not share the total ports T1, R1, FW1 and FY1 with the full array, and the total ports of the a sub-array are changed to T3, R3, FW3 and FY3, so that the functions similar to those of embodiments 2 and 3 are realized. The specific working mode refers to embodiment 2, and is not described herein again.
The above description is only for the purpose of illustrating the preferred embodiments of the present invention and is not to be construed as limiting the invention, and any modifications, equivalents and improvements made within the spirit and principle of the present invention are intended to be included within the scope of the present invention.
Claims (10)
1. The utility model provides a two-dimentional sum and difference network of stripline broadband, two-dimentional sum and difference network includes from last to lower last dielectric slab, last semi-solid piece, middle dielectric slab, lower semi-solid piece and the lower dielectric slab that stacks gradually, two-dimentional sum and difference network still includes the metallized through-hole that runs through whole two-dimentional sum and difference network, its characterized in that:
the upper surface of the upper dielectric plate is covered by an upper anti-interference layer, the lower surface of the lower dielectric plate is covered by a lower anti-interference layer, and the metallized through hole penetrates through the upper anti-interference layer and the lower anti-interference layer;
the upper surface and the lower surface of the middle dielectric plate are respectively provided with a conduction band, the overlapped part of the conduction band and the edge of the middle dielectric plate forms a port, the conduction bands are partially overlapped, the overlapped area forms four constant bias couplers, and the four constant bias couplers are cascaded to form a two-dimensional sum-difference network of a strip line width band.
2. The stripline wideband two-dimensional sum-difference network of claim 1, wherein the upper and lower immunity layers comprise copper sheets.
3. The stripline wideband two-dimensional sum-and-difference network of claim 1, wherein the upper and lower conduction bands of the intermediate dielectric slab each have mirror symmetry, and the upper and lower conduction bands have mirror symmetry.
4. The stripline wideband two-dimensional sum and difference network of claim 1, wherein the bias coupler comprises a first coupling stub, a coupling cross stub, and a second coupling stub, wherein the first coupling stub and the second coupling stub form a two-stage coupled line, and wherein the bias coupler employs a two-stage coupled line cascade.
5. The stripline wideband two-dimensional sum and difference network of claim 4, wherein the bias coupler achieves quadrature coupling by adjusting the length and width of the first, coupling cross and second coupling stubs.
6. The stripline wideband two-dimensional sum and difference network of claim 3, wherein the metallized vias are uniformly distributed at a distance around the upper and lower conduction bands to serve as shielding vias for the stripline two-dimensional sum and difference network.
7. The stripline broadband two-dimensional sum and difference network of claim 6, wherein the metallized via spacing is between λ/10 and λ/8, λ being the corresponding wavelength for which the highest operating frequency is in the selected dielectric material.
8. A multifunctional sum-difference network is characterized by comprising a first dielectric plate, a first semi-cured sheet, a second dielectric plate, a second semi-cured sheet, a third dielectric plate, a third semi-cured sheet, a fourth dielectric plate, a fourth semi-cured sheet and a fifth dielectric plate, wherein a plurality of strip line broadband two-dimensional sum-difference networks and a plurality of radio frequency switches according to any one of claims 1 to 7 are arranged in the multifunctional sum-difference network, and the radio frequency switches are used for realizing the switching of a receiving and transmitting radio frequency signal subarray and the separation of a receiving and transmitting radio frequency signal at a public terminal.
9. The multifunctional sum and difference network of claim 8, wherein a floor layer is coated on the upper surface of the first dielectric plate, the radio frequency switch is adhered or welded on the floor layer, and a plurality of ports are arranged on the upper surface of the first dielectric plate, which is not coated with the floor layer;
a conduction band is arranged on the upper surface of the second dielectric plate;
a floor layer and a plurality of medium gaps are arranged on the upper surface of the third medium plate;
the upper surface and the lower surface of the fourth dielectric plate are provided with conduction bands;
the lower surface of the fifth medium plate is provided with a floor layer, and a plurality of ports are formed in the positions, where the floor layer is not arranged, of the lower surface of the fifth medium plate.
10. The multi-function sum and difference network of claim 8 wherein the first, second, third and fourth prepregs are positioned between the first, second, third, fourth and fifth dielectric slabs, respectively, and are bonded together by high temperature bonding.
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| CN118040276A (en) * | 2024-04-15 | 2024-05-14 | 成都华兴大地科技有限公司 | Ultra-wideband two-dimensional sum-difference network |
| CN118040276B (en) * | 2024-04-15 | 2024-06-07 | 成都华兴大地科技有限公司 | Ultra-wideband two-dimensional sum-difference network |
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