CN115276503B - Output ripple eliminating system of small-capacitance frequency converter with permanent magnet synchronous motor load and control method - Google Patents
Output ripple eliminating system of small-capacitance frequency converter with permanent magnet synchronous motor load and control method Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
- H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
- H02P25/022—Synchronous motors
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from dc input or output
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4233—Arrangements for improving power factor of AC input using a bridge converter comprising active switches
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
- H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
- H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
- H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
- H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
- H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M5/4585—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only having a rectifier with controlled elements
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
- H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
- H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
- H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
- H02P27/085—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation wherein the PWM mode is adapted on the running conditions of the motor, e.g. the switching frequency
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P2207/00—Indexing scheme relating to controlling arrangements characterised by the type of motor
- H02P2207/05—Synchronous machines, e.g. with permanent magnets or DC excitation
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Abstract
The invention discloses a small-capacity frequency converter output ripple eliminating system with a permanent magnet synchronous motor load and a control method thereof, wherein a high-capacity electrolytic capacitor originally used for balancing the pulsation power difference between instantaneous input power and output power is replaced by a two-port split type virtual capacitor, the two-port split type virtual capacitor is formed by splitting and connecting the small-capacity capacitor and a power converter in parallel, and the whole of the small-capacity frequency converter output ripple eliminating system is enabled to have the equivalent impedance characteristic of the high-capacity capacitor by utilizing a semiconductor switch in the power converter. The control method is to automatically calculate the real-time impedance control function value by sampling the input voltage, the input current and the bus voltage, and realize the capacitance multiplier in the current mode, so that the split virtual capacitance at two ends is equivalent to a large capacitance capable of balancing the instantaneous input power and the output power. The invention improves the power density and the service life of the system, ensures the good working performance of the motor, has simple and feasible realization method, has strong applicability and is easy to realize in a digital way.
Description
Technical Field
The invention relates to a power electronic control technology, in particular to a small-capacitance frequency converter output ripple eliminating system with a permanent magnet synchronous motor load and a control method.
Background
In recent years, with the rapid development of power electronics technology, permanent Magnet Synchronous Motors (PMSM) are widely applied to various fields such as household appliances, electric automobiles, numerical control machine tools and the like due to the advantages of high efficiency, easy control, high power density and the like. At present, the traditional permanent magnet synchronous motor variable frequency driving system mainly comprises a rectifier, a power factor correction circuit, an electrolytic capacitor, an inverter and a PMSM. Under the condition of single-phase alternating current power supply, the voltage of a direct current bus can greatly fluctuate due to the problem of difference of input and output power, and output ripple is usually eliminated by adopting a large-capacity energy storage capacitor. At present, the electrolytic capacitor is the only energy storage capacitor with enough energy density to adapt to high-power application, but the electrolytic capacitor has the advantages of large volume, high cost, short service life, high temperature and easy liquid leakage, and the service life of the whole machine is clamped to the service life of the electrolytic capacitor, so that the miniaturization and the reliability of the system are seriously affected.
In order to effectively reduce the system volume and improve the system reliability, a thin film capacitor/ceramic capacitor with long service life and small capacity is adopted to replace a large-capacity electrolytic capacitor. However, for thin film/ceramic capacitors, typically only tens of microfarads at maximum, the dc bus voltage inevitably exhibits large output ripple when the small capacitor absorbs the grid pulsating power. The voltage fluctuation of the double power grid frequency existing in the direct current bus voltage can directly influence the torque and the rotating speed of the permanent magnet synchronous motor, so that the running performance of the motor is reduced. Therefore, how to make the small-capacitance frequency converter with the electric load simultaneously consider high power density and motor output performance becomes a research hot spot, and has great research value.
Disclosure of Invention
The invention aims to provide a small-capacitance frequency converter output ripple eliminating system with a permanent magnet synchronous motor load and a control method.
The technical solution for realizing the purpose of the invention is as follows: the output ripple eliminating system of the small-capacity frequency converter with the load of the permanent magnet synchronous motor comprises a single-phase alternating current input, a single-phase uncontrolled diode rectifier, a PFC converter, a two-port split virtual capacitor, an inverter and the permanent magnet synchronous motor, wherein the input end of an uncontrolled rectifier circuit unit is connected with the single-phase alternating current input, the positive electrode of the output end of the uncontrolled rectifier circuit is connected with the positive electrode of the input end of the PFC converter, and the negative electrode of the output end of the uncontrolled rectifier circuit is connected with the negative electrode of the input end of the PFC converter; the positive electrode of the output end of the PFC converter is connected with the positive electrode of the split-type virtual capacitor input end of the two ends, and the negative electrode of the output end of the PFC converter is connected with the negative electrode of the split-type virtual capacitor input end of the two ends; the positive electrode of the two-port split virtual capacitor output end is connected with the positive electrode of the direct current bus, and the negative electrode of the two-port split virtual capacitor output end is connected with the negative electrode of the direct current bus; the positive electrode of the input end of the inverter is connected with the positive electrode of the direct current bus, the negative electrode of the input end of the inverter is connected with the negative electrode of the direct current bus, and the output end of the inverter is connected with the three-phase winding of the permanent magnet synchronous motor;
The two-port split virtual capacitor is formed by connecting a small-capacity thin film/ceramic capacitor and an H-bridge power converter which consists of an inductor, an energy storage capacitor and first to fourth power switch tubes in parallel, wherein the positive output end of the small-capacity thin film/ceramic capacitor is connected with one end of a cathode and one end of an inductor of a main power diode in the PFC converter, the other end of the inductor is connected with a source electrode of a first power switch tube and a drain electrode of a second power switch tube, the negative output end of the small-capacity thin film/ceramic capacitor is connected with a source electrode of a third power switch tube and a drain electrode of a fourth power switch tube, the drain electrode of the first power switch tube, the drain electrode of the third power switch tube and one end of the energy storage capacitor are connected, and the source electrode of the second power switch tube, the source electrode of the fourth power switch tube and the other end of the energy storage capacitor are connected.
Further, the single-phase uncontrolled diode rectifying circuit is composed of first to fourth rectifying diodes, wherein the first rectifying diode and the third rectifying diode are connected in series to form one bridge arm, and the second rectifying diode and the fourth rectifying diode form the other bridge arm.
Further, the PFC converter comprises a Boost inductor, a main power diode and a main power switch tube to form a Boost PFC circuit, wherein the positive output end of the direct current side of the single-phase uncontrolled diode rectifying circuit is connected with one end of the Boost inductor, the other end of the Boost inductor is simultaneously connected with the drain electrode of the main power switch tube and the anode of the main power diode, the source electrode of the main power switch tube is connected with the negative output end of the direct current side of the single-phase uncontrolled diode rectifying circuit and the negative output end of the small-capacity thin film/ceramic capacitor, and the cathode of the main power diode is connected with the positive output end of the small-capacity thin film/ceramic capacitor.
Further, the value of the energy storage capacitor is related to the voltage variation range of the energy storage capacitor C s, and is irrelevant to the type of the power converter, and the specific relation is as follows:
wherein V m、Im is the amplitude of the ac input voltage and current, ω=2pi f line,fline is the single-phase input frequency of the ac power grid, and V c_max and V c_min are the maximum and minimum values of the periodically varying instantaneous voltage of the storage capacitor C s, respectively.
Further, the three-phase inverter circuit is composed of first to sixth inverter switching tubes, wherein the drain electrode of the first inverter switching tube, the drain electrode of the third inverter switching tube and the drain electrode of the fifth inverter switching tube are connected with the positive output end of the small-capacity thin film/ceramic capacitor, the source electrode of the second inverter switching tube, the source electrode of the fourth inverter switching tube and the source electrode of the sixth inverter switching tube are connected with the negative output end of the small-capacity thin film/ceramic capacitor, the source electrode of the first inverter switching tube is simultaneously connected with the drain electrode of the second inverter switching tube and one end of the permanent magnet synchronous motor load, the source electrode of the third inverter switching tube is simultaneously connected with the drain electrode of the fourth inverter switching tube and one end of the permanent magnet synchronous motor load, and the source electrode of the fifth inverter switching tube is simultaneously connected with the drain electrode of the sixth inverter switching tube and one end of the permanent magnet synchronous motor load.
The small-capacitance frequency converter output ripple elimination control method with the permanent magnet synchronous motor load is based on the small-capacitance frequency converter output ripple elimination control system with the permanent magnet synchronous motor load, and realizes the small-capacitance frequency converter output ripple elimination control with the permanent magnet synchronous motor load, and comprises the following steps:
Step one: the overall circuit state of the two-port split virtual capacitor is detected, and the total energy storage capacitance value C all of the direct-current bus required by absorbing ripple is calculated according to the circuit state and the expected voltage ripple, wherein the specific expression is as follows:
Wherein, P in (T) is input instantaneous power, P o is output power, ω=2pi f line,fline is single-phase input frequency of the ac power grid, the integration interval [ T line/8,3Tline/8 ] is charging time of the total energy storage capacitor of the dc bus, C all is the total energy storage capacitor value of the dc bus, Δe is energy required to be stored by the total energy storage capacitor of the dc bus, V dc_max and V dc_min are respectively the maximum voltage value charged and the minimum voltage value discharged, V dc_ave is average voltage on the total energy storage capacitor of the dc bus, and Δv dc＝Vdc_max-Vdc_min is ripple voltage on the total energy storage capacitor of the dc bus;
comprehensively obtaining the total energy storage capacitance value of the direct current bus:
Wherein V m、Im is the amplitude of the alternating input voltage and current respectively;
step two: based on a current control current source method, the equivalent power impedance of the split virtual capacitor with two ports is obtained in an s domain, and the specific expression is as follows:
Wherein, C dc is the capacitance value of the small-capacity passive capacitor, N is the impedance control function value, and s is the frequency domain; the two-port split virtual capacitor can be equivalently C dc and an equivalent virtual capacitor n·c dc in parallel, namely:
Call＝(N+1)Cdc
step three: and (3) combining the first step and the second step to obtain a real-time impedance control function value N, wherein the specific expression is as follows:
step four: the voltage and current double closed-loop control strategy is adopted to control the equivalent capacitance value of the split virtual capacitor at two ports and the voltage at two ends of the energy storage capacitor C s, and specifically comprises the following steps:
Solving an error between the average voltage of the energy storage small capacitor and a given reference value of the average voltage of the energy storage small capacitor, adding the error with i * after passing through a voltage compensator, and generating a reference value of expected split current i 2, wherein i * is the product of a real-time impedance control function value N and a current i 1 flowing through the small-capacity passive capacitor; and solving an error between the actual value of the split current i 2 and the reference value of the split current i 2, and generating a PWM square wave modulation signal after the error passes through a current compensator to control a switching tube of an H bridge in the split virtual capacitor at two ports in real time, so that the aim of eliminating output ripple waves is fulfilled.
The computer equipment comprises a memory, a processor and a computer program which is stored in the memory and can run on the processor, wherein when the processor executes the computer program, the output ripple cancellation control method of the small-capacitance frequency converter with the permanent magnet synchronous motor load is based on the small-capacitance frequency converter with the permanent magnet synchronous motor load, and the output ripple cancellation control of the small-capacitance frequency converter with the permanent magnet synchronous motor load is realized.
A computer readable storage medium, on which a computer program is stored, which when executed by a processor, realizes the control of the output ripple cancellation of the small-capacity frequency converter with the load of the permanent magnet synchronous motor based on the control method of the output ripple cancellation of the small-capacity frequency converter with the load of the permanent magnet synchronous motor.
Compared with the prior art, the invention has the remarkable advantages that: 1) The method has the advantages of effectively inhibiting the fluctuation of bus voltage, meeting the characteristics of high power factor, high efficiency, long service life and excellent driving performance, and can effectively solve the problems of serious fluctuation of direct current bus voltage and poor motor running performance in the existing small-capacitance frequency converter scheme with the load of the permanent magnet synchronous motor. 2) The two-port split virtual capacitor and the control method thereof provided replace the original high-capacity electrolytic capacitor to absorb ripple power, effectively reduce the volume of the required energy storage element, avoid the use of the electrolytic capacitor, improve the power density of the system, simultaneously give consideration to good motor operation performance, improve the service life of the whole system and increase the stability of the system. 3) The two-port split virtual capacitor and the control method thereof are mutually independent from motor control, do not need to change the original load connection mode, have simple structure and low device cost, are simple and feasible to control, and are beneficial to digital design.
Drawings
FIG. 1 is a block diagram of the overall structure of the output ripple cancellation system of the small-capacitance frequency converter with permanent magnet synchronous motor load of the present invention;
FIG. 2 is a voltage, current and power waveform diagram of a power converter in a two-port split virtual capacitor of the present invention;
FIG. 3 is a voltage-current dual closed-loop control block diagram of a power converter in a two-port split virtual capacitor of the present invention;
FIG. 4 is a circuit diagram of output ripple cancellation of a small capacitance frequency converter with a permanent magnet synchronous motor load according to an embodiment of the present invention;
Fig. 5 is a graph comparing the front-back simulation effect of a small-capacitance frequency converter with a load of a permanent magnet synchronous motor using a split virtual capacitor with two ports according to an embodiment of the invention.
Detailed Description
The present application will be described in further detail with reference to the drawings and examples, in order to make the objects, technical solutions and advantages of the present application more apparent. It should be understood that the specific embodiments described herein are for purposes of illustration only and are not intended to limit the scope of the application.
Referring to fig. 1, an output ripple eliminating system of a small-capacitance frequency converter with a permanent magnet synchronous motor load is formed by sequentially connecting a single-phase alternating current input, a single-phase uncontrolled diode rectifying circuit 1, a PFC converter 2, a two-end split type virtual capacitor 3, an inverter 4 and a permanent magnet synchronous motor load 5 in series. The input end of the single-phase uncontrolled diode rectifying circuit 1 is connected with a single-phase alternating current input, the positive electrode of the output end of the single-phase uncontrolled diode rectifying circuit 1 is connected with the positive electrode of the input end of the PFC converter 2, and the negative electrode of the output end of the single-phase uncontrolled diode rectifying circuit 1 is connected with the negative electrode of the input end of the PFC converter 2; the positive electrode of the output end of the PFC converter 2 is connected with the positive electrode of the input end of the two-port split virtual capacitor 3, and the negative electrode of the output end of the PFC converter 2 is connected with the negative electrode of the input end of the two-port split virtual capacitor 3; the positive electrode of the output end of the two-port split virtual capacitor 3 is connected with the positive electrode of the direct current bus, and the negative electrode of the output end of the two-port split virtual capacitor 3 is connected with the negative electrode of the direct current bus; the positive pole of the input end of the inverter 4 is connected with the positive pole of the direct current bus, the negative pole of the input end of the inverter 4 is connected with the negative pole of the direct current bus, and the output end of the inverter 4 is connected with the three-phase winding 5 of the permanent magnet synchronous motor.
Referring to fig. 4, the single-phase uncontrolled diode rectifying circuit 1 is composed of rectifying diodes D 1-D4, wherein a first rectifying diode D 1 and a third rectifying diode D 3 are connected in series to form one bridge arm, and a second rectifying diode D 2 and a fourth rectifying diode D 4 form another bridge arm.
The PFC circuit 2 comprises a boost inductor L b, a main power diode D b and a main power switch tube S b to form a boost PFC circuit, and achieves a power factor correction function, wherein the positive output end of the direct-current side of the single-phase uncontrolled diode rectifying circuit 1 is connected with one end of the boost inductor L b, the other end of the boost inductor L b is simultaneously connected with the drain electrode of the main power switch tube S b and the anode of the main power diode D b, the source electrode of the main power switch tube S b is connected with the negative output end of the direct-current side of the single-phase uncontrolled diode rectifying circuit 1and the negative output end of the small-capacity film/ceramic capacitor C dc, and the cathode of the main power diode D b is connected with the positive output end of the small-capacity film/ceramic capacitor C dc.
The two-port split virtual capacitor 3 is realized by a power semiconductor switch and a passive element, and is formed by connecting a small-capacity film/ceramic capacitor C dc with an H-bridge power converter formed by an inductor L 2, an energy storage capacitor C s and a power switch tube S 1-S4 in parallel, wherein the positive output end of the small-capacity film/ceramic capacitor C dc is connected with the cathode of a main power diode D b and one end of the inductor L 2, the other end of the inductor L 2 is connected with the source electrode of a first power switch tube S 1 and the drain electrode of a second power switch tube S 2, the negative output end of the small-capacity film/ceramic capacitor C dc is connected with the source electrode of a third power switch tube S 3 and the drain electrode of a fourth power switch tube S 4, the drain electrode of the first power switch tube S 1, one end of the third power switch tube S 3 and one end of the energy storage capacitor C s are connected with the source electrode of the second power switch tube S 2 and the source electrode of the fourth power switch tube S 4 and the other end of the energy storage capacitor C s. The value of C s is related to the voltage variation range of the energy storage capacitor C s, and is irrelevant to the type of the power converter.
The three-phase inverter circuit 4 is composed of an inverter switching tube S i1-Si6, wherein the drain electrode of the first inverter switching tube S i1, the drain electrode of the third inverter switching tube S i3, the drain electrode of the fifth inverter switching tube S i5 are connected with the positive output end of the small-capacity thin film/ceramic capacitor C dc, the source electrode of the second inverter switching tube S i2, the source electrode of the fourth inverter switching tube S i4, the source electrode of the sixth inverter switching tube S i6 are connected with the negative output end of the small-capacity thin film/ceramic capacitor C dc, the source electrode of the first inverter switching tube S i1 is simultaneously connected with the drain electrode of the second inverter switching tube S i2 and one end of the permanent magnet synchronous motor load 5, the source electrode of the third inverter switching tube S i3 is simultaneously connected with the drain electrode of the fourth inverter switching tube S i4 and one end of the permanent magnet synchronous motor load 5, and the source electrode of the fifth inverter switching tube S i5 is simultaneously connected with the drain electrode of the sixth inverter switching tube S i6 and one end of the permanent magnet synchronous motor load 5.
The controller 6 of the two-port split virtual capacitor comprises a sampling circuit which samples the input voltage and the input current from the alternating current power grid and the voltages at two ends of the direct current bus; and a real-time impedance control function value N calculation unit, which realizes a capacitance multiplier in a current mode, so that the split virtual capacitance at two ports is equivalent to a large capacitance (1+N) C dc capable of balancing instantaneous input power and output power. The method comprises the following specific steps:
Step one: the sampling circuit in the two-port split virtual capacitor controller detects the current overall circuit state, and the total energy storage capacitance value C all of the direct current bus required by absorbing ripple is calculated according to the circuit state and the expected voltage ripple in a preset mode, and the specific expression is as follows:
Wherein, P in (T) is input instantaneous power, P o is output power, ω=2pi f line,fline is single-phase input frequency of the ac power grid, the integration interval [ T line/8,3Tline/8 ] is charging time of the total energy storage capacitor of the dc bus, C all is the total energy storage capacitor value of the dc bus, Δe is energy required to be stored by the total energy storage capacitor of the dc bus, V dc_max and V dc_min are respectively the maximum voltage value charged and the minimum voltage value discharged, V dc_ave is average voltage on the total energy storage capacitor of the dc bus, and Δv dc＝Vdc_max-Vdc_min is ripple voltage on the total energy storage capacitor of the dc bus;
from the above equation set, it is possible to obtain:
wherein V m、Im is the amplitude of the alternating input voltage and current respectively.
Step two: based on a current control current source method, the equivalent power impedance of the split virtual capacitor with two ports is obtained in an s domain, and the specific expression is as follows:
wherein, C dc is the capacitance value of the small-capacity passive capacitor, N is the impedance control function value, and s is the frequency domain;
It can be derived that the two-port split virtual capacitor can be equivalently connected in parallel with the equivalent virtual capacitor n·c dc, namely:
Call＝(N+1)Cdc
step three: and (3) combining the first step and the second step to obtain a real-time impedance control function value N, wherein the specific expression is as follows:
At this time, from the energy absorption point of view, the secondary ripple energy on the bus voltage is absorbed by the two-port split virtual capacitor in two parts, a small part is absorbed by the small-capacity passive capacitor, and the rest is absorbed by the energy storage capacitor in the power converter, and the specific expression is as follows:
Delta E is the energy required to be absorbed by the total energy storage capacitor of the direct current bus; Δe Cdc is the energy absorbed by the small-capacity passive capacitor C dc; Δe Cs is the energy absorbed by the storage capacitor C s in the power converter. The voltage, current and power waveforms of the power converter in the two-port split virtual capacitor in the specific embodiment are shown in fig. 2.
Step four: adopting a voltage-current double closed-loop control strategy to control the equivalent capacitance value of the split virtual capacitor at two ends and the voltage at two ends of the energy storage capacitor C s; and solving an error between the average voltage of the energy storage small capacitor and a given reference value of the average voltage of the energy storage small capacitor, adding the error with i * after the error passes through a voltage compensator, and generating a reference value of expected split current i 2, wherein i * is the product of a real-time impedance control function value N and a current i 1 flowing through a small-capacity passive capacitor C dc. The error between the actual value of the split current i 2 and the reference value of the split current i 2 is obtained, and after the error passes through a current compensator, a PWM square wave modulation signal is generated to control the switching tube S 1-S4 of the H bridge in the two-port split virtual capacitor in real time, so that the purpose of eliminating output ripple waves is achieved.
The electromagnetic torque formula:
Tc＝1.5p(ψfiq+(Ld-Lq)idiq)
It is known that the motor electromagnetic torque is determined by the q-axis current component, the voltage fluctuation of the dc bus voltage is reduced, and the frequency fluctuation in the q-axis current is reduced, so that the motor electromagnetic torque fluctuation is significantly reduced.
The equation of motion is:
Wherein i d、iq is the d and q axis stator current respectively; l d、Lq is d and q axis inductance respectively; phi f is a permanent magnet flux linkage; p is the pole pair number of the motor; t e is motor electromagnetic torque; t L is the load torque; r Ω is the motor damping coefficient; j is the rotational inertia of the motor rotor; omega r is the electromechanical angular velocity. From this equation, the motor rotation speed is determined by the electromagnetic torque of the motor, with the motor load torque unchanged. Therefore, the fluctuation of the motor rotation speed during the motor operation is also reduced.
In summary, the circuit control parts of the invention are mutually independent and simultaneously carried out, so that the invention has the advantages of high input power factor, long service life and excellent driving performance while effectively inhibiting the voltage fluctuation of the direct current bus, and can effectively solve the problems of serious voltage fluctuation and poor static and dynamic performance of the motor of the existing small-capacitance frequency converter charged load driving system.
Examples
In order to verify the effectiveness of the inventive protocol, the following simulation experiments were performed.
The specific implementation parameters of this embodiment are as follows: the single-phase alternating current input voltage is 220Vac/50Hz, the direct current bus voltage is 400V, the small capacity capacitor C dc uF on the direct current bus is 150uF, and the energy storage capacitor C s 265uF in the power converter is 22. The effect of using a small capacity electrolytic capacitor and a two-port split virtual capacitor under the same circuit conditions is shown in fig. 5.
It can be seen that through the control, the two-port split virtual capacitor has the same effect as the passive high-capacity electrolytic capacitor, plays the role of absorbing the same ripple power, and transfers the power which cannot be absorbed by the low-capacity capacitor C dc on the direct-current bus to the energy storage capacitor C s in the power converter through the active switch. Because the energy storage capacitor C s allows larger voltage fluctuation, the capacitance value can be obviously reduced, the power density of the whole machine is improved, the original PFC function is ensured, and the busbar voltage fluctuation is effectively restrained.
The technical features of the above embodiments may be arbitrarily combined, and all possible combinations of the technical features in the above embodiments are not described for brevity of description, however, as long as there is no contradiction between the combinations of the technical features, they should be considered as the scope of the description.
The above examples merely represent a few embodiments of the present application, which are described in more detail and are not to be construed as limiting the scope of the present application. It should be noted that it will be apparent to those skilled in the art that several variations and modifications can be made without departing from the spirit of the application, which are all within the scope of the application. Accordingly, the scope of the application should be assessed as that of the appended claims.
Claims (8)
1. The utility model provides a little electric capacity converter output ripple elimination system of synchronous motor load of area permanent magnetism which characterized in that: the power supply comprises a single-phase alternating current input, a single-phase uncontrolled diode rectifier, a PFC converter, a two-port split virtual capacitor, an inverter and a permanent magnet synchronous motor, wherein the input end of an uncontrolled rectifier circuit unit is connected with the single-phase alternating current input, the positive electrode of the output end of the uncontrolled rectifier circuit is connected with the positive electrode of the input end of the PFC converter, and the negative electrode of the output end of the uncontrolled rectifier circuit is connected with the negative electrode of the input end of the PFC converter; the positive electrode of the output end of the PFC converter is connected with the positive electrode of the split-type virtual capacitor input end of the two ends, and the negative electrode of the output end of the PFC converter is connected with the negative electrode of the split-type virtual capacitor input end of the two ends; the positive electrode of the two-port split virtual capacitor output end is connected with the positive electrode of the direct current bus, and the negative electrode of the two-port split virtual capacitor output end is connected with the negative electrode of the direct current bus; the positive electrode of the input end of the inverter is connected with the positive electrode of the direct current bus, the negative electrode of the input end of the inverter is connected with the negative electrode of the direct current bus, and the output end of the inverter is connected with the three-phase winding of the permanent magnet synchronous motor;
The two-port split virtual capacitor is formed by connecting a small-capacity thin film/ceramic capacitor (C dc) with an H-bridge power converter which is formed by an inductor (L 2), an energy storage capacitor (C s) and first to fourth power switching tubes (S 1-S4) in parallel, wherein the positive output end of the small-capacity thin film/ceramic capacitor (C dc) is connected with the cathode of a main power diode (D b) in the PFC converter and one end of the inductor (L 2), the other end of the inductor (L 2) is connected with the source electrode of the first power switching tube (S 1) and the drain electrode of the second power switching tube (S 2), the negative output end of the small-capacity thin film/ceramic capacitor (C dc) is connected with the source electrode of a third power switching tube (S 3) and the drain electrode of the fourth power switching tube (S 4), the drain electrode of the first power switching tube (S 1), the drain electrode of the third power switching tube (S 3) and one end of the energy storage capacitor (C s) are connected with the source electrode of the second power switching tube (S7) and the source electrode of the fourth power switching tube (S 4).
2. The small-capacitance frequency converter output ripple cancellation system with permanent magnet synchronous motor load according to claim 1, wherein: the single-phase uncontrolled diode rectifying circuit is composed of first to fourth rectifying diodes (D 1-D4), wherein the first rectifying diode (D 1) and the third rectifying diode (D 3) are connected in series to form one bridge arm, and the second rectifying diode (D 2) and the fourth rectifying diode (D 4) form the other bridge arm.
3. The small-capacitance frequency converter output ripple cancellation system with permanent magnet synchronous motor load according to claim 1, wherein: the PFC converter comprises a Boost inductor (L b), a main power diode (D b) and a main power switch tube (S b) to form a Boost PFC circuit, wherein the positive output end of the direct current side of the single-phase uncontrolled diode rectifying circuit is connected with one end of the Boost inductor (L b), the other end of the Boost inductor (L b) is simultaneously connected with the drain electrode of the main power switch tube (S b) and the anode of the main power diode (D b), the source electrode of the main power switch tube (S b) is connected with the negative output end of the direct current side of the single-phase uncontrolled diode rectifying circuit and the negative output end of the small-capacity thin film/ceramic capacitor (C dc), and the cathode of the main power diode (D b) is connected with the positive output end of the small-capacity thin film/ceramic capacitor (C dc).
4. The small-capacitance frequency converter output ripple cancellation system with permanent magnet synchronous motor load according to claim 1, wherein: the value of the energy storage capacitor (C s) is related to the voltage change range of the energy storage capacitor C s, and is irrelevant to the type of the power converter, and the specific relation is as follows:
wherein V m、Im is the amplitude of the ac input voltage and current, ω=2pi f line,fline is the single-phase input frequency of the ac power grid, and V c_max and V c_min are the maximum and minimum values of the periodically varying instantaneous voltage of the storage capacitor C s, respectively.
5. The small-capacitance frequency converter output ripple cancellation system with permanent magnet synchronous motor load according to claim 1, wherein: the three-phase inverter circuit is composed of first to sixth inverter switching tubes (S i1-Si6), wherein the drain electrode of the first inverter switching tube (S i1), the drain electrode of the third inverter switching tube (S i3), the drain electrode of the fifth inverter switching tube (S i5) are connected with the positive output end of a small-capacity thin film/ceramic capacitor (C dc), the source electrode of the second inverter switching tube (S i2), the source electrode of the fourth inverter switching tube (S i4), the source electrode of the sixth inverter switching tube (S i6) are connected with the negative output end of the small-capacity thin film/ceramic capacitor (C dc), the source electrode of the first inverter switching tube (S i1) is simultaneously connected with the drain electrode of the second inverter switching tube (S i2) and one end of a permanent magnet synchronous motor load, the source electrode of the third inverter switching tube (S i3) is simultaneously connected with the drain electrode of the fourth inverter switching tube (S i4) and one end of the permanent magnet synchronous motor load, and the source electrode of the fifth inverter switching tube (S i5) is simultaneously connected with the drain electrode of the sixth inverter switching tube (S i6) and one end of the permanent magnet synchronous motor load.
6. The method for eliminating and controlling the output ripple of the small-capacitance frequency converter with the load of the permanent magnet synchronous motor is characterized by comprising the following steps of: the small-capacitance frequency converter output ripple cancellation control system with the permanent magnet synchronous motor load based on any one of claims 1 to 5, which realizes the small-capacitance frequency converter output ripple cancellation control with the permanent magnet synchronous motor load, and comprises the following steps:
Step one: the overall circuit state of the two-port split virtual capacitor is detected, and the total energy storage capacitance value C all of the direct-current bus required by absorbing ripple is calculated according to the circuit state and the expected voltage ripple, wherein the specific expression is as follows:
Wherein, P in (T) is input instantaneous power, P o is output power, ω=2pi f line,fline is single-phase input frequency of the ac power grid, the integration interval [ T line/8,3Tline/8 ] is charging time of the total energy storage capacitor of the dc bus, C all is the total energy storage capacitor value of the dc bus, Δe is energy required to be stored by the total energy storage capacitor of the dc bus, V dc_max and V dc_min are respectively the maximum voltage value charged and the minimum voltage value discharged, V dc_ave is average voltage on the total energy storage capacitor of the dc bus, and Δv dc＝Vdc_max-Vdc_min is ripple voltage on the total energy storage capacitor of the dc bus;
comprehensively obtaining the total energy storage capacitance value of the direct current bus:
Wherein V m、Im is the amplitude of the alternating input voltage and current respectively;
step two: based on a current control current source method, the equivalent power impedance of the split virtual capacitor with two ports is obtained in an s domain, and the specific expression is as follows:
wherein, C dc is the capacitance value of the small-capacity passive capacitor, N is the impedance control function value, and s is the frequency domain;
The two-port split virtual capacitor can be equivalently C dc and an equivalent virtual capacitor n·c dc in parallel, namely:
Call＝(N+1)Cdc
step three: and (3) combining the first step and the second step to obtain a real-time impedance control function value N, wherein the specific expression is as follows:
step four: the voltage and current double closed-loop control strategy is adopted to control the equivalent capacitance value of the split virtual capacitor at two ports and the voltage at two ends of the energy storage capacitor C s, and specifically comprises the following steps:
Solving an error between the average voltage of the energy storage small capacitor and a given reference value of the average voltage of the energy storage small capacitor, adding the error with i * after passing through a voltage compensator, and generating a reference value of expected split current i 2, wherein i * is the product of a real-time impedance control function value N and a current i 1 flowing through a small-capacity passive capacitor (C dc); the error between the actual value of the split current i 2 and the reference value of the split current i 2 is obtained, and after the error passes through a current compensator, a PWM square wave modulation signal is generated to control the switching tube (S 1-S4) of the H bridge in the split virtual capacitor with two ports in real time, so that the purpose of eliminating output ripple waves is achieved.
7. A computer device comprising a memory, a processor and a computer program stored on the memory and operable on the processor, wherein when the processor executes the computer program, the small capacitance frequency converter output ripple cancellation control with the permanent magnet synchronous motor load is realized based on the small capacitance frequency converter output ripple cancellation control method with the permanent magnet synchronous motor load of claim 6.
8. A computer-readable storage medium having stored thereon a computer program which, when executed by a processor, implements the small-capacitance inverter output ripple cancellation control with permanent magnet synchronous motor load based on the small-capacitance inverter output ripple cancellation control method with permanent magnet synchronous motor load of claim 6.
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